JP4781116B2 - Wireless device - Google Patents

Description

  The present invention relates to a radio apparatus, and more particularly, to a radio apparatus using a plurality of subcarriers.

  An OFDM (Orthogonal Frequency Division Multiplexing) modulation scheme, which is one of the multicarrier schemes, is a communication scheme that enables high-speed data transmission and is strong in a multipath environment. This OFDM modulation scheme is applied to IEEE802.11a, g and HIPERLAN / 2, which are standardized standards for wireless LAN (Local Area Network). A burst signal in such a wireless LAN is generally transmitted via a transmission path environment that fluctuates with time, and is affected by frequency selective fading. Therefore, a receiver generally performs transmission path estimation dynamically. Execute.

In order for the receiving apparatus to perform transmission path estimation, two types of known signals are provided in the burst signal. One is a known signal provided for all carriers at the head of the burst signal, which is a so-called preamble or training signal. The other is a known signal provided for some of the carriers in the data section of the burst signal, which is called a so-called pilot signal (see Non-Patent Document 1, for example).
Sine Coleri, Mustafa Ergen, Anuj Puri, and Ahmad Bahai, "Channel Estimation Techniques Based on Pilot Arrangement in OFDM Systems", IbnEstemEs. 48, no. 3, pp. 223-229, Sept. 2002.

  One technique for effectively using frequency resources in wireless communication is an adaptive array antenna technique. The adaptive array antenna technology controls the directivity pattern of an antenna by controlling the amplitude and phase of a signal to be processed in each of a plurality of antennas. There is a MIMO (Multiple Input Multiple Output) system as a technique for increasing the data rate by using such adaptive array antenna technology. In the MIMO system, each of a transmission apparatus and a reception apparatus includes a plurality of antennas, and sets a plurality of packet signals to be transmitted in parallel (hereinafter, each of the plurality of packet signals is referred to as a “sequence” Unit, or each is referred to as a “packet signal”). That is, the data rate is improved by setting a sequence up to the maximum number of antennas for communication between the transmission device and the reception device.

  Furthermore, if an OFDM modulation system is combined with such a MIMO system, the data rate is further increased. Also in such a MIMO system, generally, a base station apparatus transmits a signal including control information for communication (hereinafter, “beacon”) to a terminal apparatus that desires communication with the base station apparatus. )). When receiving the beacon, the terminal device requests the base station device to start communication according to the contents of the beacon. The beacon in the MIMO system requires the following. The first requirement is that transmission is performed from a plurality of streams in order to reduce transmission power per antenna. The second requirement is that the antenna directivity when transmitting a beacon is close to omnidirectional so that the beacon is received by as many terminal devices as possible. The third requirement is that reception is possible even for a terminal device that performs smoothing processing between subcarriers when estimating a propagation path for the purpose of reducing noise.

  The present invention has been made in view of such circumstances, and an object of the present invention is to provide a wireless device that transmits beacons suitable for a plurality of sequences.

  In order to solve the above-described problem, a radio apparatus according to an aspect of the present invention includes a plurality of burst signals each using a plurality of subcarriers and each including a burst signal including control information for communication. Execution of a cyclic time shift within the period in the time domain when using multiple subcarriers is specified for each antenna by the amount of time shift corresponding to each antenna and multiple antennas. In accordance with the above, a generation unit that generates burst signals broadcast from each of the plurality of antennas is provided. The generation unit generates a burst signal while changing a time shift amount corresponding to each of the plurality of antennas.

  According to this aspect, since burst signals are generated with various time shift amounts, it is possible to adapt to various requirements.

  The generation unit may generate the burst signal while switching a predetermined time shift amount and a time shift amount longer than the predetermined time shift amount in units of burst signals. In this case, since the amount of time shift is switched in units of burst signals, the requirement for directivity and the requirement for correlation can be satisfied.

  The burst signal generated in the generation unit may include a portion where time shift is executed by a fixed time shift amount, and may include a portion where time shift is executed while switching the time shift amount after the portion. .

  When the generation unit generates a burst signal with a predetermined time shift amount, processing between subcarriers at the time of reception is performed on a portion of the burst signal where time shift is performed with a fixed time shift amount. Information indicating permission may be included.

An example of “processing between subcarriers” is smoothing of channel coefficients between subcarriers when deriving channel characteristics for each subcarrier. For example, when the propagation path coefficients derived from adjacent subcarriers are h-1, h0, h1, h2, and h3, an example of the smoothing process is
This is to reduce the influence of noise by setting h0 ′ = (h−1 + 2 × h0 + h1) / 4, h1 ′ = (h0 + 2 × h1 + h2) / 4, and the like.

  When the burst signal is generated with a time shift amount longer than a predetermined time shift amount, the generation unit includes a portion between which the time shift is performed with a fixed time shift amount between subcarriers at the time of reception. Information indicating prohibition of processing may be included.

  The generation unit may include information indicating whether the smoothing process is permitted or prohibited in the burst signal. In this case, it is possible to change the time shift amount and instruct permission or prohibition of the smoothing process.

  It should be noted that any combination of the above-described constituent elements and a conversion of the expression of the present invention between a method, an apparatus, a system, a recording medium, a computer program, etc. are also effective as an aspect of the present invention.

  According to the present invention, a beacon suitable for a plurality of sequences can be transmitted.

  Before describing the present invention in detail, an outline will be described. Embodiments of the present invention relate to a MIMO system composed of at least two wireless devices. One of the wireless devices corresponds to a base station device, and the other corresponds to a terminal device. The base station apparatus broadcasts a beacon, and at that time, performs a broadcast from a plurality of antennas in order to reduce transmission power in one antenna. When beacons are broadcast from a plurality of antennas, it is necessary to reduce interference between them, and one of the solutions is execution of CDD (Cyclic Delay Diversity). Here, CDD is a process in which a waveform in the time domain is shifted backward by a shift amount in a predetermined section, and the waveform pushed out from the end of the predetermined section is cyclically arranged at the head portion of the predetermined section. It is. Further, when a beacon is broadcast from a plurality of antennas, a different amount of shift is associated with each of the plurality of antennas.

  Under such circumstances, if the shift amount is small, the signals transmitted from the plurality of antennas are similar, so that a direction in which the signals are strengthened and a direction in which the signals are weakened occur. That is, the effect of beam forming occurs. As a result, the antenna has directivity and a direction in which the beacon does not reach occurs. Therefore, a request for a beacon that reception by as many terminal devices as possible is not satisfied. On the other hand, if the shift amount is large, the effect of beamforming is reduced, so that the antenna directivity is close to omnidirectional, and the request for beacons that reception by as many terminal devices as possible is required is satisfied. The However, since a large shift amount is equivalent to the presence of a delayed wave having a long delay time, the correlation between the subcarriers of the channel coefficient is small. As a result, if a terminal device that performs signal processing between subcarriers, for example, statistical processing or smoothing processing between subcarriers, receives a beacon with a small correlation between subcarriers of propagation path coefficients, Is likely to occur. In particular, a terminal device that cannot turn off the smoothing function cannot receive such a beacon. In general, the smoothing process is executed for the purpose of reducing noise in channel estimation.

  The base station apparatus according to the present embodiment performs the following processing in order to solve these problems. The base station apparatus defines a first shift amount with a small shift amount and a second shift amount with a large shift amount. Here, the first shift amount and the second shift amount are defined as a group in which shift amounts for a plurality of antennas are combined. Further, the first shift amount and the second shift amount may include a shift amount that becomes zero.

  FIG. 1 shows a spectrum of a multicarrier signal according to an embodiment of the present invention. In particular, FIG. 1 shows the spectrum of a signal in the OFDM modulation scheme. One of a plurality of carriers in the OFDM modulation system is generally called a subcarrier, but here, one subcarrier is designated by a “subcarrier number”. In the MIMO system, 56 subcarriers from subcarrier numbers “−28” to “28” are defined. The subcarrier number “0” is set to null in order to reduce the influence of the DC component in the baseband signal. On the other hand, in the conventional system, 52 subcarriers from subcarrier numbers “−26” to “26” are defined. An example of a conventional system is a wireless LAN compliant with the IEEE802.11a standard.

  Each subcarrier is modulated by a variably set modulation method. As a modulation method, any one of BPSK (Binary Phase Shift Keying), QSPK (Quadrature Phase Shift Keying), 16QAM (Quadrature Amplitude Modulation), and 64QAM is used.

  Also, convolutional coding is applied to these signals as an error correction method. The coding rate of convolutional coding is set to 1/2, 3/4, and the like. Furthermore, the number of data to be transmitted in parallel is set variably. The data is transmitted as a burst signal, and here, each of the burst signals to be transmitted in parallel is referred to as a “sequence”. As a result, the data rate is also variably set by variably setting the modulation scheme, coding rate, and number of sequences. The “data rate” may be determined by any combination of these, or may be determined by one of them.

  FIG. 2 shows a configuration of the communication system 100 according to the embodiment of the present invention. The communication system 100 includes a first wireless device 10a and a second wireless device 10b collectively referred to as a wireless device 10. The first radio apparatus 10a includes a first antenna 12a, a second antenna 12b, a third antenna 12c, and a fourth antenna 12d, which are collectively referred to as an antenna 12, and the second radio apparatus 10b is collectively referred to as an antenna 14. A first antenna 14a, a second antenna 14b, a third antenna 14c, and a fourth antenna 14d are included. Here, the first radio apparatus 10a corresponds to a base station apparatus, and the second radio apparatus 10b corresponds to a terminal apparatus.

  Before describing the configuration of the communication system 100, an outline of a MIMO system will be described. It is assumed that data is transmitted from the first radio apparatus 10a to the second radio apparatus 10b. The first radio apparatus 10a transmits a plurality of series of data from each of the first antenna 12a to the fourth antenna 12d. As a result, the data rate is increased. The second radio apparatus 10b receives a plurality of series of data by the first antenna 14a to the fourth antenna 14d. Furthermore, the second radio apparatus 10b separates the received data by adaptive array signal processing and independently demodulates a plurality of series of data.

  Here, since the number of antennas 12 is “4” and the number of antennas 14 is also “4”, the combination of transmission paths between the antennas 12 and 14 is “16”. A transmission path characteristic between the i-th antenna 12i and the j-th antenna 14j is denoted by hij. In the figure, the transmission path characteristic between the first antenna 12a and the first antenna 14a is h11, the transmission path characteristic between the first antenna 12a and the second antenna 14b is h12, the second antenna 12b and the first antenna. 14a, the transmission path characteristic between the second antenna 12b and the second antenna 14b is h22, and the transmission path characteristic between the fourth antenna 12d and the fourth antenna 14d is h44. Has been. Note that transmission lines other than these are omitted for clarity of illustration.

  3A to 3C show packet formats in the communication system 100. FIG. In particular, here, a packet format in a beacon will be described. A beacon is a signal transmitted from a base station device at a predetermined interval to a terminal device that wishes to communicate with the base station device. In addition, information related to the base station apparatus is generally included in the beacon. The packet format for data in communication is formed in the same manner as these, but the description is omitted here. FIG. 3A shows a packet format of a beacon notified from the antenna 12. Here, it is assumed that a beacon is notified from the first antenna 12a and the second antenna 12b among the antennas 12 of FIG.

  A beacon notified from the first antenna 12a is shown in the upper part, and a beacon notified from the second antenna 12b is shown in the lower part. In the upper part, “L-STF”, “L-LTF”, and “L-SIG” correspond to a known signal for timing estimation, a known signal for transmission path estimation, and a control signal, respectively, corresponding to the conventional system. In addition, “HT-SIG”, “HT-STF”, “HT-LTF”, “HT-DATA” are control signals corresponding to the MIMO system, known signals for timing estimation, known signals for transmission path estimation, Each corresponds to data.

  On the other hand, “L-STF + fixed CDD”, “L-LTF + fixed CDD”, “L-SIG + fixed CDD”, and “HT-SIG + fixed CDD” in the lower stage are “L-STF”, “ This corresponds to the result of executing CDD on “L-LTF”, “L-SIG”, and “HT-SIG”, respectively. The fixed shift amount may not be the same value. “HT-STF + variable CDD”, “HT-LTF + variable CDD”, “HT-DATA + variable CDD” are “HT-STF”, “HT-LTF”, “HT-DATA” depending on the variable shift amount. Corresponds to the result of executing the CDD. The variable shift amount may not be the same value. Here, in order to simplify the description, it is assumed that the fixed shift amount is the first shift amount. For the variable shift amount, the first shift amount and the second shift amount are alternately selected in units of packets. In addition, when a beacon is alert | reported from three or more antennas 12, it is prescribed | regulated that the shift amount with respect to the 2nd antenna 12b and the 3rd antenna 12c differs. For example, the shift amount for the second antenna 12b is defined as 50 nsec, and the shift amount for the third antenna 12c is defined as 100 nsec.

  FIG. 3B shows a packet format of a beacon processed inside the first radio apparatus 10a. The upper stage corresponds to the first series, and the lower stage corresponds to the second series. The first series has almost the same configuration as the upper stage of FIG. The second series has only “HT-LTF”. That is, in FIG. 3B, only “HT-LTF” is arranged in a plurality of sequences. FIG. 3C shows a packet format of a beacon notified from the antenna 12, which is a packet format corresponding to FIG. Upper “L-STF”, “L-LTF”, “L-SIG”, “HT-SIG” and lower “L-STF + fixed CDD”, “L-LTF + fixed CDD”, “L-SIG + fixed” “CDD” and “HT-SIG + fixed CDD” are the same as those in FIG.

  The upper “HT-STF ′” and the lower “HT-STF ″ + variable CDD” are obtained by multiplying “HT-STF” in FIG. This corresponds to the result of further execution of CDD. That is, “HT-STF” is multiplied by an orthogonal matrix to generate “HT-STF ′” and “HT-STF ″”, and CDD with a variable shift amount is applied to the lower stage. Has been. The same applies to "HT-LTF" "and" HT-DATA '"in the upper stage, and" HT-LTF "" + variable CDD "and" HT-DATA "+ variable CDD" in the lower stage.

  FIG. 4 shows the configuration of the first radio apparatus 10a. The first radio apparatus 10a includes a first radio unit 20a, a second radio unit 20b, a fourth radio unit 20d, a baseband processing unit 22, a modem unit 24, an IF unit 26, and a control unit 30, which are collectively referred to as a radio unit 20. Including. Further, as signals, a first time domain signal 200a, a second time domain signal 200b, a fourth time domain signal 200d, which are collectively referred to as a time domain signal 200, a first frequency domain signal 202a, which is collectively referred to as a frequency domain signal 202, and a second time domain signal 200b. It includes a frequency domain signal 202b, a third frequency domain signal 202c, and a fourth frequency domain signal 202d. The second radio apparatus 10b is configured to correspond to the first radio apparatus 10a.

  As a reception operation, the radio unit 20 performs frequency conversion on a radio frequency signal received by the antenna 12 and derives a baseband signal. The radio unit 20 outputs the baseband signal to the baseband processing unit 22 as a time domain signal 200. In general, baseband signals are formed by in-phase and quadrature components, so they should be transmitted by two signal lines. Here, for clarity of illustration, only one signal line is used. Shall be shown. An AGC (Automatic Gain Control) and an A / D conversion unit are also included. As a transmission operation, the radio unit 20 performs frequency conversion on the baseband signal from the baseband processing unit 22 and derives a radio frequency signal.

  Here, a baseband signal from the baseband processing unit 22 is also shown as a time domain signal 200. The radio unit 20 outputs a radio frequency signal to the antenna 12. Further, a PA (Power Amplifier) and a D / A converter are also included. The time domain signal 200 is a multicarrier signal converted into the time domain, and is a digital signal. In particular, the radio unit 20 broadcasts beacons using a plurality of subcarriers from a plurality of antennas 12 and having a packet format as shown in FIGS.

  As a reception operation, the baseband processing unit 22 converts each of the plurality of time domain signals 200 into the frequency domain, and performs adaptive array signal processing on the frequency domain signal. The baseband processing unit 22 outputs the result of adaptive array signal processing as the frequency domain signal 202. One frequency domain signal 202 corresponds to data included in each of a plurality of sequences transmitted from the second radio apparatus 10b (not shown). Further, as a transmission operation, the baseband processing unit 22 receives a frequency domain signal 202 as a frequency domain signal from the modulation / demodulation unit 24, converts the frequency domain signal to the time domain, and transmits the frequency domain signal to each of the plurality of antennas 12. The time domain signal 200 is output while being associated.

  It is assumed that the number of antennas 12 to be used in the transmission process is specified by the control unit 30. Here, the frequency domain signal 202, which is a frequency domain signal, includes a plurality of subcarrier components as shown in FIG. For the sake of clarity, it is assumed that the signals in the frequency domain are arranged in the order of subcarrier numbers to form a serial signal.

  FIG. 5 shows the structure of a signal in the frequency domain. Here, one combination of subcarrier numbers “−28” to “28” shown in FIG. 1 is referred to as an “OFDM symbol”. In the “i” th OFDM symbol, subcarrier components are arranged in the order of subcarrier numbers “1” to “28” and subcarrier numbers “−28” to “−1”. Also, the “i−1” th OFDM symbol is arranged before the “i” th OFDM symbol, and the “i + 1” th OFDM symbol is arranged after the “i” th OFDM symbol. And

  Returning to FIG. In addition, the baseband processing unit 22 performs CDD in order to generate a beacon. When FIG. 3B is input, orthogonal matrix multiplication is also executed. Here, the latter case will be described first. A beacon having the packet format shown in FIG. 3B is input to the baseband processing unit 22. The baseband processing unit 22 multiplies “HT-STF”, “HT-LTF”, and “HT-DATA” by a steering matrix. Here, the baseband processing unit 22 extends the order of the input data to the number of a plurality of sequences before performing multiplication.

  The number of input data is “1”, and is represented by “Nin” here. Therefore, the input data is indicated by a vector “Nin × 1”. The number of the plurality of sequences is “2”, and is represented by “Nout” here. The baseband processing unit 22 extends the order of the input data from Nin to Nout. That is, the vector “Nin × 1” is expanded to the vector “Nout × 1”. At that time, “0” is inserted into the components from the Nin + 1 line to the Nout line. Note that the same processing is performed for the second series of “HT-LTF”.

ステアリング行列は、「Ｎｏｕｔ×Ｎｏｕｔ」の行列である。また、Ｗは、直交行列であり、「Ｎｏｕｔ×Ｎｏｕｔ」の行列である。直交行列の一例は、ウォルシュ行列である。ここで、ｌは、サブキャリア番号を示しており、ステアリング行列による乗算は、サブキャリアを単位にして実行される。さらに、Ｃは、以下のように示される。

The steering matrix S is shown as follows.

The steering matrix is a “Nout × Nout” matrix. W is an orthogonal matrix, which is a “Nout × Nout” matrix. An example of an orthogonal matrix is a Walsh matrix. Here, l indicates a subcarrier number, and multiplication by the steering matrix is executed in units of subcarriers. Further, C is expressed as follows.

  Here, δ represents the shift amount. That is, the baseband processing unit 22 performs a cyclic time shift in the HT-STF or the like increased to the number of the plurality of sequences by the shift amount corresponding to each of the plurality of sequences for each sequence. The shift amount is set to a different value for each series. At this time, as described above, the shift amount is determined by switching to either the first shift amount or the second shift amount. On the other hand, in the case of “L-STF” and the like and FIG. 3A, the processing related to CDD is executed in the above description.

  The modem unit 24 performs demodulation and decoding on the frequency domain signal 202 from the baseband processing unit 22 as reception processing. Note that demodulation and decoding are performed in units of subcarriers. The modem unit 24 outputs the decoded signal to the IF unit 26. Further, the modem unit 24 performs encoding and modulation as transmission processing. The modem unit 24 outputs the modulated signal to the baseband processing unit 22 as the frequency domain signal 202. It is assumed that the modulation scheme and coding rate are specified by the control unit 30 during the transmission process.

  The IF unit 26 combines signals from the plurality of modulation / demodulation units 24 as a reception process to form one data stream. The IF unit 26 outputs a data stream. In addition, the IF unit 26 inputs one data stream as transmission processing and separates it. Further, the separated data is output to a plurality of modems 24.

  The control unit 30 controls the timing of the first radio apparatus 10a. Furthermore, the control part 30 performs control regarding the production | generation of a beacon. That is, as described above, the execution of CDD within the period in the time domain when a plurality of subcarriers are used is defined for each antenna 12 by the shift amount corresponding to each of the plurality of antennas 12. The “period in the time domain when a plurality of subcarriers are used” is a period defined based on the IFFT period and the guard interval period. The baseband processing unit 22 generates a beacon that is notified from each of the plurality of antennas 12 in accordance with the regulations. At that time, the control unit 30 causes the baseband processing unit 22 to generate a beacon while changing the shift amount corresponding to each of the plurality of antennas 12.

  In the packet format, the part for changing the shift amount is a part indicated by variable CDD in FIGS. The change in the shift amount is realized by switching the first shift amount and the second shift amount in units of packet signals. For example, when the “period in the time domain when using a plurality of subcarriers” is 3200 nsec, the first shift amount is defined as 50 nsec and the second shift amount is defined as 400 nsec. Further, as shown in FIGS. 3A and 3C, the control unit 30 includes a portion in which CDD is executed with a fixed shift amount in the packet signal, and switches the shift amount to the subsequent stage of the portion. However, the part where CDD is executed is included.

  In addition, when the control unit 30 uses the first shift amount, when deriving the channel coefficient for each subcarrier at the time of reception in L-SIG or HT-SIG, Information indicating permission of the smoothing processing of the propagation path coefficient is included. That is, the control unit 30 permits the wireless device 10 that should receive a beacon, for example, the second wireless device 10b, to perform a smoothing process on the channel coefficient between subcarriers for the received beacon. On the other hand, when the control unit 30 uses the second shift amount, the L-SIG or the HT-SIG receives the transmission line coefficient for each subcarrier at the time of reception. Include information indicating that the channel coefficient smoothing processing is prohibited. That is, the control unit 30 prohibits the wireless device 10 that should receive a beacon, for example, the second wireless device 10b, from performing smoothing processing on the channel coefficient between subcarriers for the received beacon.

  This configuration can be realized in terms of hardware by a CPU, memory, or other LSI of any computer, and in terms of software, it is realized by a program having a communication function loaded in the memory. Describes functional blocks realized by collaboration. Accordingly, those skilled in the art will understand that these functional blocks can be realized in various forms by hardware only, software only, or a combination thereof.

  FIG. 6 shows the configuration of the baseband processing unit 22. The baseband processing unit 22 includes a reception processing unit 50 and a transmission processing unit 52. The reception processing unit 50 executes a part corresponding to the reception operation among the operations in the baseband processing unit 22. That is, the reception processing unit 50 performs adaptive array signal processing on the time domain signal 200, and for that purpose, derivation of a reception weight vector. Further, the reception processing unit 50 outputs the result of array synthesis as the frequency domain signal 202.

  Specifically, the processing of the reception processing unit 50 will be described. The reception processing unit 50 receives a plurality of time domain signals 200 and performs a Fourier transform on each of them to derive a frequency domain signal. As described above, in a single frequency domain signal, signals corresponding to subcarriers are serially arranged in the order of subcarrier numbers.

  In addition, the reception processing unit 50 weights the frequency domain signal by the reception weight vector, and adds the plurality of weighted signals. Here, since the signal in the frequency domain includes a plurality of subcarriers, the above processing is also executed in units of subcarriers. As a result, the added signals are also serially arranged in the order of subcarrier numbers as shown in FIG. The added signal is the frequency domain signal 202 described above.

  The reception processing unit 50 derives a reception weight vector by an adaptive algorithm, for example, an LMS algorithm. Alternatively, a reception response vector may be derived by correlation processing, and a reception weight vector may be derived from the reception response vector. Here, the latter will be described. The frequency domain signal corresponding to the first time domain signal 200a is denoted by x1 (t), the frequency domain signal corresponding to the second time domain signal 200b is denoted by x2 (t), and the reference signal in the first sequence is denoted by S1 ( t), if the reference signal in the second series is denoted as S2 (t), x1 (t) and x2 (t) are represented as follows.

ここで、雑音は無視する。第１の相関行列Ｒ１は、Ｅをアンサンブル平均として、次のように示される。

参照信号間の第２の相関行列Ｒ２は、次のように計算される。

Here, noise is ignored. The first correlation matrix R1 is expressed as follows, where E is an ensemble average.

The second correlation matrix R2 between the reference signals is calculated as follows.

最終的に、第２の相関行列Ｒ２の逆行列と第１の相関行列Ｒ１を乗算することによって、受信応答ベクトルが導出される。

さらに、受信用処理部５０は、受信応答ベクトルから受信ウエイトベクトルを計算する。

Finally, the reception response vector is derived by multiplying the inverse matrix of the second correlation matrix R2 by the first correlation matrix R1.

Further, the reception processing unit 50 calculates a reception weight vector from the reception response vector.

  The transmission processing unit 52 executes a part corresponding to the transmission operation among the operations in the baseband processing unit 22. That is, the transmission processing unit 52 performs CDD and performs orthogonal matrix multiplication.

  FIG. 7 is a flowchart showing a beacon generation procedure by the first radio apparatus 10a. If the previous beacon has been generated with the first shift amount (Y in S10), the control unit 30 sets the second shift amount (S12). On the other hand, if the previous beacon has not been generated with the first shift amount (N in S10), the control unit 30 sets the first shift amount (S14). The control part 30 produces | generates a beacon with the baseband process part 22 based on the above settings (S16). The baseband processing unit 22 and the radio unit 20 transmit a beacon (S18).

  According to the embodiment of the present invention, since CDD is executed when a beacon is broadcast from a plurality of antennas, interference between beacons can be reduced. Further, by changing the shift amount when executing CDD, the requirements regarding the directivity of the antenna and the requirements regarding the correlation between subcarriers can be satisfied. By performing CDD while switching between the first shift amount and the second shift amount, the correlation of the channel coefficient between subcarriers can be increased in the case of the first shift amount, and the antenna directivity in the case of the second shift amount. Can be made omnidirectional. Because there is a timing that makes the antenna directivity close to omnidirectional, a beacon generated by CDD with the second shift amount is sent to a terminal device that cannot receive a beacon generated by CDD with the first shift amount. It can be received.

  In addition, since there is a timing for increasing the correlation between the subcarriers, a terminal device that cannot receive a beacon generated by CDD with the second shift amount and cannot turn off the smoothing process is connected to the terminal device. A beacon generated by CDD with one shift amount can be received. In addition, when generating a beacon by CDD with the first shift amount, by including information that permits the smoothing process, the smoothing process can be performed when the terminal device derives the channel coefficient. In addition, since the smoothing process can be executed, the influence of noise can be reduced. In addition, when a beacon is generated by CDD based on the second shift amount, a terminal device that cannot turn off the smoothing process can be interrupted by including information that prohibits the smoothing process. In addition, the power consumption of the terminal device can be reduced by interrupting the reception process.

  In the above, this invention was demonstrated based on the Example. This embodiment is an exemplification, and it will be understood by those skilled in the art that various modifications can be made to the combination of each component and each processing process, and such modifications are also within the scope of the present invention. .

  In the embodiment of the present invention, the control unit 30 selects either the first shift amount or the second shift amount as the shift amount. That is, a two-stage shift amount is defined according to the shift amount. However, the present invention is not limited to this, and for example, a shift amount of two or more steps may be defined. According to this modification, the shift amount can be controlled in detail. That is, it is sufficient that the shift amount includes a shift amount having a large value and a shift amount having a small value.

  In the embodiment of the present invention, the radio apparatus 10 transmits a beacon while variably adjusting the shift amount of the packet format of FIG. 3A, or variably changes the shift amount of the packet format of FIG. Sending beacons while adjusting. However, the present invention is not limited to this. For example, the packet format shown in FIG. 3A may be used for the first shift amount, and the packet format shown in FIG. 3C may be used for the second shift amount. At this time, information indicating which packet format is used may be included in the HT-SIG. In this case, various beacon packet formats can be defined. That is, it is sufficient that the shift amount includes a shift amount having a large value and a shift amount having a small value.

It is a figure which shows the spectrum of the multicarrier signal which concerns on the Example of this invention. It is a figure which shows the structure of the communication system which concerns on the Example of this invention. FIGS. 3A to 3C are diagrams showing packet formats in the communication system of FIG. It is a figure which shows the structure of the 1st radio | wireless apparatus of FIG. It is a figure which shows the structure of the signal of the frequency domain in FIG. It is a figure which shows the structure of the baseband process part of FIG. It is a flowchart which shows the production | generation procedure of the beacon by the 1st radio | wireless apparatus of FIG.

Explanation of symbols

  10 wireless devices, 12 antennas, 14 antennas, 20 wireless units, 22 baseband processing units, 24 modulation / demodulation units, 26 IF units, 30 control units, 50 reception processing units, 52 transmission processing units, 100 communication systems.

Claims (3)

A plurality of antennas each reporting a burst signal that includes a plurality of subcarriers and includes control information for communication;
Execution of a cyclic time shift within a period in the time domain when a plurality of subcarriers are used is defined for each antenna by a time shift amount corresponding to each of the plurality of antennas, and according to the regulations. However, a generation unit that generates burst signals broadcast from each of the plurality of antennas,
The generation unit generates a burst signal while changing a time shift amount corresponding to each of a plurality of antennas ,
The generation unit generates a burst signal while switching a predetermined time shift amount and a time shift amount longer than the predetermined time shift amount in units of burst signals,
The burst signal generated in the generation unit includes a portion where time shift is performed by a fixed time shift amount, and includes a portion where time shift is performed while switching the time shift amount after the portion. A wireless device characterized by the above. When the generation unit generates a burst signal with a predetermined time shift amount, a portion of the burst signal that is time-shifted with a fixed time shift amount is inserted between subcarriers at the time of reception. The radio apparatus according to claim 1 , further comprising information indicating permission of a smoothing process of a propagation path coefficient . When the generation unit generates a burst signal with a time shift amount longer than the predetermined time shift amount, a subcarrier at the time of reception is included in a portion where the time shift is performed with a fixed time shift amount. The wireless device according to claim 1 , further comprising: information indicating prohibition of smoothing processing of the channel coefficient between the two.

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