JP4770335B2 - Control device for DC-DC converter - Google Patents

Description

  The present invention relates to a control device for a DC-DC converter.

  Conventionally, in a control device for a DC-DC converter, a deviation between an output voltage command value and a detected value of the output voltage is obtained, and PI control is performed on the obtained deviation to obtain an output voltage value of the DC-DC converter. A technique for matching the voltage command value is known (see Non-Patent Document 1).

Improvement of DC voltage control characteristics of PWM inverter with current reversible chopper 2001 IEEJ National Convention

  However, in the conventional technique, since the control constant of PI control is set so that the fluctuation of the output voltage due to the change of the load current can be sufficiently suppressed, the output voltage is overshot with respect to the change of the voltage command value. Thus, there is a problem that it takes time to converge to the voltage command value.

(1) A control device for a DC-DC converter according to the present invention is a control device for a DC-DC converter having at least a reactor and a switching element, and a voltage detection means for detecting an output voltage of the DC-DC converter, and a DC A first current command value calculating means for calculating a first reactor current command value based on a difference between an output voltage command value for the DC converter and an output voltage detected by the voltage detecting means, and an output for the reactor current A controlled object model having a voltage transfer characteristic Gpv (s), an inverse filter having a transfer characteristic H (s) / Gpv (s) composed of the transfer characteristic Gpv (s) and a low-pass filter H (s); The difference between the result of inputting the reactor current command value to the model to be controlled and the output voltage detected by the voltage detection means is calculated. Add the second current command value calculation means that inputs the inverse filter and uses the output of the inverse filter as the second reactor current command value, the first reactor current command value, and the second reactor current command value. And adding means for setting the reactor current command value.
(2) A DC-DC converter control device according to the present invention is a DC-DC converter control device including at least a reactor and a switching element, and a voltage detection means for detecting an output voltage of the DC-DC converter; A first current command value calculating means for calculating a first reactor current command value based on a difference between an output voltage command value for the DC-DC converter and an output voltage detected by the voltage detecting means; (S) and an inverse filter having a transfer characteristic H (s) / Gpv (s) composed of a transfer characteristic Gpv (s) of the output voltage of the DC-DC converter with respect to the reactor current and a low-pass filter H (s) The result obtained by inputting the reactor current command value to the low-pass filter H (s) and the voltage detection means Second current command value calculation means for setting the difference between the results obtained by inputting the detected output voltage to the inverse filter as the second reactor current command value, the first reactor current command value, and the second reactor And adding means for adding a current command value to obtain a reactor current command value.
(3) A DC-DC converter control device according to the present invention is a DC-DC converter control device including at least a reactor and a switching element, and a voltage detection means for detecting an output voltage of the DC-DC converter; First current command value calculating means for calculating a first reactor current command value based on a difference between an output voltage command value for the DC-DC converter and an output voltage detected by the voltage detecting means, and for the reactor current An inverse filter having a transfer characteristic H (s) / Gpv (s) composed of a transfer characteristic Gpv (s) of the output voltage of the DC-DC converter and a low-pass filter H (s), and 1 / (1-H ( s)) having an integral filter having a transfer characteristic, which is detected by the first reactor current command value and the voltage detecting means. And a final current command value calculating means for inputting the difference between the results obtained by inputting the output voltage to the inverse filter to the integral filter and using the output result of the integral filter as the reactor current command value. To do.

  According to the DC-DC converter control apparatus of the present invention, it is possible to quickly converge and match the actual output voltage without overshooting the change in the output voltage command value.

-First embodiment-
FIG. 1 is a diagram showing a system configuration including a boost converter (DC-DC converter) controlled by a DC-DC converter control device according to the first embodiment. The DC voltage Vi of the secondary battery 1 is boosted to a voltage Vo (Vo> Vi) by the boost converter 2 and supplied to the load 3. The load 3 is, for example, an inverter and an AC motor.

  A capacitor C <b> 1 for smoothing the output voltage of the boost converter 2 is provided on the output side of the boost converter 2. Voltage sensor 5 detects output voltage Vo of boost converter 2.

  Boost converter 2 includes a reactor L1, NPN transistors Tr1 and Tr2, diodes D1 and D2, and a NOT gate 4. Reactor L1 has one end connected to power supply line 20 of secondary battery 1 and the other end connected to a connection point between transistors Tr1 and Tr2.

  The collector terminal of the NPN transistor Tr1 is connected to the power supply line 22, and the emitter terminal is connected to the collector terminal of the transistor Tr2. The emitter terminal of the transistor Tr2 is connected to the earth line 21. Diodes D1 and D2 are connected in parallel to the transistors Tr1 and Tr2, respectively, so that a current flows from the emitter terminal side to the collector terminal side. On / off of the transistors Tr1 and Tr2 is controlled by a converter control device 10 to be described later.

  The converter control device 10 can be constituted by, for example, a microcomputer, and supplies the DC voltage Vi of the secondary battery 1 to the load 3 by controlling on / off of the transistors Tr1 and Tr2 by PWM control. To a desired voltage. When the PWM duty ratio at which the lower-side transistor Tr2 is turned on is D, when D = 0, that is, when the upper-side transistor Tr1 is kept on, the output voltage Vo of the DC-DC converter 2 is the secondary It becomes substantially equal to the voltage Vi of the battery 1. As the duty ratio D is increased, the output voltage Vo increases, and when D = 50%, the output voltage Vo becomes almost twice the voltage Vi of the secondary battery 1.

ただし、Ｖｉは、昇圧コンバータ２の入力電圧、Ｖｏは、昇圧コンバータ２の出力電圧、ｉ_ＬはリアクトルＬ１に流れる電流、Ｄは、上述したＰＷＭデューティー比、ｉ_ｏは負荷３に流れる電流、Ｌは、リアクトルＬ１のインダクタンス、Ｃは、コンデンサＣ１の容量である。 Here, if the switching frequency of PWM control is set to be sufficiently large, the following equations (1) and (2) are established.

Where Vi is the input voltage of the boost converter 2, Vo is the output voltage of the boost converter 2, i _L is the current flowing through the reactor L1, D is the PWM duty ratio described above, _io is the current flowing through the load 3, and L Is the inductance of the reactor L1, and C is the capacitance of the capacitor C1.

式（３）は、リアクトル電流ｉ_Ｌと、昇圧コンバータ２の出力電圧Ｖｏとの関係を示す式であり、右辺第２項は、外乱として扱うことができるが、右辺第１項には、変数であるリアクトル電流ｉ_Ｌと、ＰＷＭデューティー比Ｄとの積が含まれており、非線形性の強い制御対象であることが分かる。 In the above equation (2), when the differential operator (Laplace operator) is s and D / (C × s) = Gpv (s), the following equation (3) is obtained.

Expression (3) is an expression showing the relationship between the reactor current i _L and the output voltage Vo of the boost converter 2, and the second term on the right side can be treated as a disturbance, but the first term on the right side contains a variable The product of the reactor current i _L and the PWM duty ratio D is included, and it can be seen that the control target is highly nonlinear.

FIG. 2 is a block diagram showing an internal configuration of converter control device 10 in the first embodiment. Converter control device 10 includes a voltage control unit 11 and a current control unit 12. The voltage control unit 11 obtains a reactor current command value i _L ^* for making the output voltage Vo of the boost converter 2 coincide with the voltage command value Vo ^* , and outputs the reactor current command value i _L ^* to the current control unit 12. Control is performed to match i _L with the reactor current command value i _L ^* , a PWM duty ratio D for turning on the transistor Tr2 is determined, and on / off of the transistors Tr1 and Tr2 is controlled.

Converter control device 10 in the first embodiment is characterized by the configuration of voltage control unit 11, and a reactor current command for making output voltage Vo of boost converter 2 coincide with voltage command value Vo ^* by a method described later. Determine the value i _L ^* . The voltage control unit 11 includes a subtractor 21, a control block 22 that multiplies a predetermined control constant Kpm, an adder 23, a control block 24 having a transfer characteristic of Gpv (s), a subtractor 25, and H (s ) / Gpv (s) and a control block 26 having an inverse filter having a transfer characteristic.

The transfer characteristic Gpv (s) is a control target model of the boost converter that represents the transfer characteristic of the output voltage Vo with respect to the current i _L flowing through the reactor L1, and as described above, Gpv (s) = D / (C × s ). The transfer characteristic H (s) is a characteristic of a low-pass filter with a first-order lag expressed by the following equation (4). Here, τh is a time constant, and s is a differential operator (Laplace operator).
H (s) = 1 / (1 + τh · s) (4)

In the control device for the DC-DC converter in the first embodiment, the current command value i _L ^* flowing through the reactor L1 is set by the following procedure. First, the difference between the output voltage command value Vo ^{* of} the DC-DC converter 2 and the voltage value Vo detected by the voltage sensor 5 is calculated by the subtractor 21, and the control block 22 controls the calculated voltage difference. A first reactor current command value is obtained by multiplying by a constant Kpm. Further, the subtractor 25 calculates the difference between the value obtained by passing the filter Gpv (s) in the control block 24 and the voltage value Vo detected by the voltage sensor 5 with respect to the reactor current command value i _L ^* . Then, the data is input to the control block 26, and the output of the control block 26 is set as the second reactor current command value. The first reactor current command value and the second reactor current command value are added to obtain a final reactor current command value i _L ^* .

  FIG. 3 is a diagram for explaining the control effect of converter control device 10 in the first embodiment. The adder 23, the control block 24, the subtractor 25, and the control block 26 illustrated in FIG. 3 correspond to the adder 23, the control block 24, the subtractor 25, and the control block 26 illustrated in FIG. The control block 31 represents the actual DC-DC converter 2.

When the above-described first reactor current command value is u1, and the second reactor current command value is u2, the reactor current command value i _L ^* that is the addition result of the adder 23 is expressed by the following equation (5). .
i _L ^* = u1 + u2 (5)

A disturbance d is input to the control block 31 representing the DC-DC converter 2 together with the reactor current command value i _L ^* . The disturbance d is, for example, a change in the load current _io or a modeling error. Therefore, the output of the control block 31, that is, the output voltage Vo of the DC-DC converter 2 is expressed by the following equation (6).
^{_{Vo = (i L * + d}} ) Gpv (s) (6)

Since the subtraction result e of the subtracter 25 is expressed by the equation (7), the relationship of the following equation (8) is established from the equation (6).
e = i _L ^* · Gpv (s) −Vo (7)
^{_{= I L * · Gpv (s}} ) - (i L * + d) Gpv (s)
= -D · Gpv (s) (8)

Since the second reactor current u2 is expressed by the following equation (9), the following equation (10) is obtained from the equation (8).
u2 = e · H (s) / Gpv (s) (9)
= -D · H (s) (10)
Substituting equation (10) into equation (5) yields the following equation (11).
^{_{i L * = u1-d ·}} H (s) (11)

Substituting equation (11) into equation (6) yields the following equation (12).
Vo = {(u1-d.H (s)) + d} Gpv (s)
= {U1 + (1-H (s)) d} Gpv (s) (12)

Here, in the transfer characteristic H (s) represented by the equation (4), if the time constant τh is set to a sufficiently small value, the H (s) approaches 1, so that the DC-DC converter is obtained from the equation (12). The output voltage Vo of 2 can be approximated by the following equation (13).
Vo = u1 · Gpv (s) (13)
As apparent from the above equation (13), by setting the time constant τh of the transfer characteristic H (s) to a sufficiently small value, the output voltage Vo of the DC-DC converter 2 is not affected by the disturbance d.

That is, by providing the adder 23, the control block 24, the subtractor 25, and the control block 26 shown in FIGS. 2 and 3, the output voltage Vo of the DC-DC converter 2 is not affected by the disturbance d. Since it can be considered that Vo = Gpv (s) · i _L ^* , the control model in FIG. 2 can be rewritten like the control model in FIG. In the control model of FIG. 4, the subtractor 21 and the control block 22 correspond to the subtractor 21 and the control block 22 shown in FIG. 2, respectively, and the control block 31 represents the actual DC-DC converter 2. This corresponds to the control block 31 shown in FIG.

In FIG. 4, the output voltage Vo of the DC-DC converter 2 is represented by the following equation (14).
Vo = Kpm · Gpv (s) · (Vo ^* −Vo) (14)
When the equation (14) is transformed, the following equation (15) is obtained.

Here, when Gpv (s) = D / (C × s) is substituted into the equation (15), the following equation (16) is obtained.

上式（１７）は、電圧指令値Ｖｏ^*に対して、昇圧コンバータ２の出力電圧Ｖｏが１次遅れの特性を有することを示している。 In Expression (16), if Kpm = C / (τv × D), Expression (16) can be expressed by the following Expression (17).

The above equation (17) indicates that the output voltage Vo of the boost converter 2 has a first-order lag characteristic with respect to the voltage command value Vo ^* .

  5 (a) to 5 (c) show that the command value of the output voltage is increased to 410V stepwise from the state where the input voltage to the boost converter 2 is controlled to 260V and the output voltage after the boost is controlled to 400V. FIG. 5 (a) shows a change in the reactor current, FIG. 5 (b) shows a change in the output voltage of the boost converter 2, and FIG. 5 (c) shows a duty cycle. It is a figure which shows the change of ratio. 5A to 5C, the control result of the conventional control method for matching the output voltage to the voltage command value by the PI control is indicated by a dotted line, and the control of the DC-DC converter in the first embodiment is performed. The control results by the device are shown by solid lines.

  As shown in FIG. 5B, in the conventional control method, when the output voltage command value is increased stepwise, the output voltage overshoots, and it takes time to converge to the voltage command value. It was hanging. However, according to the control method by the control device of the DC-DC converter in the first embodiment, when the output voltage command value changes, the output voltage does not overshoot and becomes a voltage command value with a first-order lag characteristic. Converge. Further, the time until the output voltage converges to the voltage command value is also shortened compared to the conventional control method.

  According to the DC-DC converter control device in the first embodiment, the first reactor current command value is based on the difference between the output voltage command value for the DC-DC converter and the output voltage of the DC-DC converter. And the difference between the result of inputting the reactor current command value to the controlled object model having the transfer characteristic Gpv (s) of the output voltage with respect to the reactor current and the output voltage of the DC-DC converter is expressed as the transfer characteristic Gpv (s ) And a low-pass filter H (s) and an output result obtained by inputting to an inverse filter having a transfer characteristic of H (s) / Gpv (s) is used as the second reactor current command value, and the first reactor The current command value and the second reactor current command value are added to obtain a reactor current command value. As a result, it is possible to quickly converge and match the actual output voltage without overshooting the change in the output voltage command value for the DC-DC converter.

-Second Embodiment-
FIG. 6 is a block diagram showing an internal configuration of converter control device 10a according to the second embodiment. The same components as those of the converter control device 10 shown in FIG.

  The configuration of voltage control unit 11a in converter control device 10a shown in FIG. 6 is equivalent to the configuration of voltage control unit 11 in converter control device 10 shown in FIG. In the voltage control unit 11 shown in FIG. 2, since the transfer characteristic Gpv (s) of the control block 24 is configured by an integrator represented by D / (C × s), an error input to the control block 24. Etc. accumulate for a long time, the integrator may overflow. However, in the voltage control unit 11a shown in FIG. 6, the transfer function H (s) of the control block 41 is a low-pass filter expressed by the equation (4), and the transfer function H (s) / Gpv ( s), the integrator Gpv (s) is included in the fractional denominator.

  That is, according to the control device for the DC-DC converter in the second embodiment, the integrator Gpv (s) is not provided as a single block in the converter control device 10a, so that no integral drift is caused. In addition, as with the DC-DC converter control device in the first embodiment, the output voltage command value for the DC-DC converter can be quickly converged without overshooting the actual output voltage. Can be matched.

-Third embodiment-
FIG. 7 is a block diagram illustrating an internal configuration of the voltage control unit 11b included in the converter control device according to the third embodiment. The same components as those of the voltage control unit 11 shown in FIG. The configuration of the voltage control unit 11b shown in FIG. 7 is an equivalent conversion of the configuration of the voltage control unit 11a shown in FIG. The reason why the configuration of the voltage control unit 11b shown in FIG. 7 is equivalent to the configuration of the voltage control unit 11 shown in FIG. 6 will be described below with reference to FIG.

  FIG. 8 is a diagram illustrating a configuration of a voltage control unit obtained by equivalently converting the configuration of the voltage control unit 11a illustrated in FIG. 6, and the control block 51 corresponds to the control block 42 illustrated in FIG. Corresponds to the control block 41 shown in FIG.

In FIG. 8, when the output of the adder 53 is y and the output of the subtractor 52 is x, the following equation (18) is established.
y = x + y × H (s) (18)
Solving equation (18) for y yields equation (19):

  That is, in the circuit of FIG. 8, the component including the adder 53 and the control block 54 can be replaced with a control block 61 having an integral system filter of 1 / (1-H (s)). From the above, the configuration of the voltage control unit 11b shown in FIG. 7 is equivalent to the configuration of the converter control device 11a shown in FIG.

FIG. 9 is a block configuration diagram showing an example of the current control unit 12 for making the current i _L flowing through the reactor L1 coincide with the reactor current command value i _L ^* . In current control unit 12 shown in FIG. 9, when the value of .tau.i transfer function s / (1 + τi × s ) of the control block 91 to set sufficiently small, substantially without delay, the reactor current i _L reactor current command value i _L ^* Can be followed.

  FIG. 10 is a diagram illustrating a configuration of a converter control device 10b including the voltage control unit 11b illustrated in FIG. 7 and the current control unit 12 illustrated in FIG. In the converter control device 10b shown in FIG. 10, the transfer function of the control block 100 is the transfer function 1 / (1-H (s)) of the control block 61 of the voltage control unit 11b and the control block 91 of the current control unit 12. It is a combination of the transfer function s / (1 + τis). That is, the transfer function 1 / (1-H (s)) of the control block 61 can be expressed as (1 + τhs) / τhs by substituting Equation (4). If s contained in the numerator of the transfer function is canceled by zero, the transfer function of the control block 100 is obtained.

  According to the control apparatus for a DC-DC converter in the third embodiment, the current control unit is included in the case where the current control unit provided in the subsequent stage of the voltage control unit does not have a steady term (has a differential element). Since a filter that cancels out the differential element and the integral element included in the integral system filter is provided, the integral element included in the voltage control unit and the differential element included in the current control unit must be connected in series. It is possible to avoid the calculation drift caused by. Further, similar to the control device for the DC-DC converter in the first embodiment, the actual output voltage can be quickly changed without overshooting the change in the output voltage command value for the DC-DC converter. Can converge and match.

-Fourth embodiment-
2, 6, and 7 described above all include a control block having a transfer characteristic of H (s) / Gpv (s). As described above, since the transfer characteristic Gpv (s) includes the duty ratio D that is the output of the converter control device 10, an algebraic loop occurs in the digital operation using an actual microcomputer or the like. FIG. 11 shows a configuration diagram for solving this problem. FIG. 11 is a diagram showing a control block 110 equivalent to the control block of transfer characteristics H (s) / Gpv (s).

The control block 110 includes a delay block 111, a divider 112, and a control block 113. H (s) / Gpv (s) is expressed by the following equation (20) when equation (4) and Gpv (s) = D / (C × s) are substituted.

  The delay block 111 inputs the duty ratio D calculated by the converter control device 10 to the divider 112 before one sampling. That is, the input value u to the control block 110 is divided by the duty ratio D before one sampling, and then passed through a filter Cs / (1 + τh × s) in the control block 113 to obtain an output result y. .

  The control block 110 can be replaced with the control block 42 shown in FIG. 6, the control block 51 shown in FIG. 7, and the control block 51 shown in FIG. That is, according to the converter control device in the fourth embodiment in which the control block having the transfer function of H (s) / Gpv (s) is replaced with the control block 110, the duty ratio D included in Gpv (s) is Since the duty ratio D before one sampling is used, generation of an algebraic loop can be avoided.

-Fifth embodiment-
The duty ratio D of the transistor Tr2 converges to the value of Vi / Vo as time passes. Therefore, the control block 110 shown in FIG. 11 can be replaced with the control block 120 shown in FIG. In FIG. 12, the control block 120 includes a multiplier 121, a divider 122, and a control block 113, and performs a process of multiplying Vo / Vi instead of dividing the input value by the duty ratio D. According to the converter control device in the fifth embodiment in which the control block 120 is incorporated instead of the control block 110 shown in FIG. 11, the stability of calculation can be improved.

-Sixth embodiment-
In the converter control device according to the fifth embodiment, a multiplier 121 that multiplies the output voltage Vo detected by the voltage sensor 5 and a divider 122 that divides the input voltage vi of the boost converter 2 are provided. In the converter control apparatus in the sixth embodiment, as shown in FIG. 13, a multiplier 131 that multiplies a voltage command value Vo ^* is provided instead of the multiplier 121 that multiplies the detection voltage Vo of the voltage sensor 5. According to this configuration, since the voltage command value Vo ^* is used as the calculation parameter instead of the voltage detection value Vo by the voltage sensor 5, the influence of noise or the like included in the voltage detection value can be eliminated.

  The present invention is not limited to the embodiments described above. For example, although a boost converter has been described as an example of a DC-DC converter, the present invention can be applied to a step-down converter or a converter that can perform step-up and step-down.

In the control device for the DC-DC converter in the first embodiment, by setting the control constant Kpm of the control block 22 to KpC / (τv × D), the output voltage Vo of the boost converter 2 with respect to the voltage command value Vo ^* . Is set to have a first-order lag characteristic represented by the equation (17). However, the value of the control constant Kpm can be set as long as a system that can quickly converge and match the output voltage Vo of the boost converter 2 without overshooting the voltage command value Vo ^* can be configured. The value is not limited.

  In the fourth embodiment, the duty ratio D before one sampling is used as the duty ratio D included in Gpv (s). However, the duty ratio before the predetermined sampling may be used. However, in order to increase the calculation accuracy, it is preferable to use the duty ratio D before one sampling.

  The correspondence between the constituent elements of the claims and the constituent elements of each embodiment is as follows. First, in correspondence with the constituent elements of claim 1, the voltage sensor 5 is the voltage detection means, the subtractor 21 and the control block 22 are the first current command value calculation means, the control block 24 is the control target model, The control block 26 constitutes an inverse filter, the subtractor 25 and the control block 26 constitute second current command value calculation means, and the adder 23 constitutes addition means. In correspondence with the constituent elements of claim 2, the voltage sensor 5 is the voltage detection means, the subtractor 21 and the control block 22 are the first current command value calculation means, the control block 41 is the low-pass filter, and the control block 42. Is an inverse filter, the control blocks 41 and 42 and the subtracter 25 constitute second current command value calculation means, and the adder 23 constitutes addition means. In correspondence with the constituent elements of claim 3, the voltage sensor 5 is the voltage detection means, the subtractor 21 and the control block 22 are the first current command value calculation means, the control block 51 is the inverse filter, and the control block 51 is , 61 and subtractor 52 constitute final current command value calculation means. In addition, the above description is an example to the last, and when interpreting invention, it is not limited to the correspondence of the component of said embodiment and the component of this invention at all.

The figure which shows the system configuration | structure including the step-up converter controlled by the control apparatus of the DC-DC converter in 1st Embodiment. The block diagram which shows the internal structure of the converter control apparatus in 1st Embodiment The figure for demonstrating the control effect of the converter control apparatus in 1st Embodiment Control model rewritten from the control model shown in FIG. FIGS. 5A to 5C are diagrams showing changes in each state when the output voltage command value of the boost converter is increased stepwise. FIG. 5A is a change in the reactor current, and FIG. (B) shows a change in the output voltage of the boost converter, and FIG. 5 (c) shows a diagram showing a change in the duty ratio. The block diagram which shows the internal structure of the converter control apparatus in 2nd Embodiment. The block diagram which shows the internal structure of the voltage control part contained in the converter control apparatus in 3rd Embodiment. The figure which shows the structure of the voltage control part which equivalently converted the structure of the voltage control part shown in FIG. Block configuration diagram showing an example of a current control unit for making the current flowing through the reactor coincide with the reactor current command value The figure which shows the structure of the converter control apparatus provided with the voltage control part shown in FIG. 7, and the current control part shown in FIG. The figure which shows the control block equivalent to the control block of transfer characteristic H (s) / Gpv (s) The figure which shows the control block substantially equivalent to the control block shown in FIG. FIG. 12 is a diagram for explaining an example in which the output voltage command value is used instead of the output voltage of the boost converter in the control block shown in FIG.

Explanation of symbols

DESCRIPTION OF SYMBOLS 1 ... Secondary battery, 2 ... Boost converter, 3 ... Load, 4 ... NOT gate, 5 ... Voltage sensor, 10 ... Converter control apparatus, 11, 11a, 11b ... Voltage control part, 12 ... Current control part, C1 ... Capacitor , L1... Reactor, Tr1, Tr2... NPN transistor, 21... Subtractor, 22, 24, 26... Control block, 23... Adder, 25. Control block, 41, 42 ... Control block, 51 ... Control block, 52 ... Subtractor, 53 ... Adder, 54 ... Control block, 61 ... Control block, 91 ... Control block, 92 ... Subtractor, 93 ... Control block, 94: Divider, 100 ... Control block, 110 ... Control block, 111 ... Delay block, 112 ... Divider 112, 113 ... Control block, 120 ... Control Block, 121 ... multiplier, 122 ... divider, 130 ... control block, 131 ... multiplier

Claims (9)

In a control device for a DC-DC converter including at least a reactor and a switching element,
Voltage detection means for detecting the output voltage of the DC-DC converter;
First current command value calculation means for calculating a first reactor current command value based on a difference between an output voltage command value for the DC-DC converter and an output voltage detected by the voltage detection means;
A controlled object model having a transfer characteristic Gpv (s) of the output voltage of the DC-DC converter with respect to the reactor current;
An inverse filter having a transfer characteristic H (s) / Gpv (s) composed of the transfer characteristic Gpv (s) and a low-pass filter H (s);
The difference between the result obtained by inputting the reactor current command value to the controlled object model and the output voltage detected by the voltage detecting means is input to the inverse filter, and the output of the inverse filter is input to the second reactor. A second current command value calculating means as a current command value;
The first reactor current command value calculated by the first current command value calculation means and the second reactor current command value calculated by the second current command value calculation means are added to obtain a reactor current A control device for a DC-DC converter, comprising: adding means for setting a command value. In a control device for a DC-DC converter including at least a reactor and a switching element,
Voltage detection means for detecting the output voltage of the DC-DC converter;
First current command value calculation means for calculating a first reactor current command value based on a difference between an output voltage command value for the DC-DC converter and an output voltage detected by the voltage detection means;
A low-pass filter H (s);
An inverse filter having a transfer characteristic H (s) / Gpv (s) composed of a transfer characteristic Gpv (s) of the output voltage of the DC-DC converter with respect to the reactor current and the low-pass filter H (s);
The difference between the result obtained by inputting the reactor current command value to the low-pass filter H (s) and the result obtained by inputting the output voltage detected by the voltage detecting means to the inverse filter is expressed as a second reactor. A second current command value calculating means as a current command value;
The first reactor current command value calculated by the first current command value calculation means and the second reactor current command value calculated by the second current command value calculation means are added to obtain a reactor current A control device for a DC-DC converter, comprising: adding means for setting a command value. In a control device for a DC-DC converter including at least a reactor and a switching element,
Voltage detection means for detecting the output voltage of the DC-DC converter;
First current command value calculation means for calculating a first reactor current command value based on a difference between an output voltage command value for the DC-DC converter and an output voltage detected by the voltage detection means;
An inverse filter having a transfer characteristic H (s) / Gpv (s) composed of a transfer characteristic Gpv (s) of the output voltage of the DC-DC converter with respect to the reactor current and the low-pass filter H (s);
An integral filter having a transfer characteristic of 1 / (1-H (s)), and the first reactor current command value and the output voltage detected by the voltage detection means are input to the inverse filter; A DC-DC converter control, comprising: a final current command value calculation means for inputting a difference from the obtained result to the integration system filter and using an output result of the integration system as a reactor current command value. apparatus. In the control apparatus of the DC-DC converter according to claim 3,
Reactor current control means for performing control to match the reactor current command value calculated by the final current command value calculation means and the actual reactor current,
A control apparatus for a DC-DC converter, comprising a filter that cancels out a differential element included in the reactor current control means and an integral element included in the integral system filter. In the control apparatus of the DC-DC converter in any one of Claims 1-4,
When the duty ratio for controlling on / off of the switching element included in the DC-DC converter is D, the capacitance of the capacitor for smoothing the output voltage of the DC-DC converter is C, and the differential operator is s. A control apparatus for a DC-DC converter, wherein the transfer characteristic Gpv (s) of the controlled object model is expressed as D / (C × s). In the control apparatus of the DC-DC converter according to claim 5,
As the duty ratio D, a duty ratio before a predetermined sample calculated by the control apparatus for the DC-DC converter is used. In the control apparatus of the DC-DC converter in any one of Claims 1-4,
When the input voltage of the DC-DC converter is Vi, the output voltage is Vo, the capacitance of the capacitor for smoothing the output voltage of the DC-DC converter is C, and the differential operator is s, the transfer characteristic Gpv of the model to be controlled is given. A control device for a DC-DC converter, wherein (s) is expressed as (Vi / Vo) / (C × s). In the control apparatus of the DC-DC converter in any one of Claims 1-4,
When the input voltage of the DC-DC converter is Vi, the output voltage command value is Vo ^* , the capacitance of the capacitor for smoothing the output voltage of the DC-DC converter is C, and the differential operator is s, A control apparatus for a DC-DC converter, wherein the transfer characteristic Gpv (s) is expressed as (Vi / Vo ^* ) / (C × s). In the control apparatus of the DC-DC converter in any one of Claims 1-8,
The control constant of the first current command value calculation means is set so that the response of the output voltage to the output voltage command value of the DC-DC converter has a first-order lag characteristic. Control device.

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