JP4354307B2 - Spread spectrum signal receiver - Google Patents

Description

  The present invention is used in a code phase locked loop or the like that maintains PN code tracking for a spread spectrum received signal.

  When receiving a signal whose spectrum is spread by a pseudo noise code (hereinafter referred to as PN code), the same PN code as that on the transmission side is generated in the receiver and despread, so that the information contained in the superimposed signal is displayed. Demodulate. In this case, in order to constantly demodulate information, a method of tracking a received signal using a code phase locked loop is generally used.

  Recently, there is also a method of performing spread spectrum using a spread code in which a plurality of PN codes are combined by time division. Even in the case of receiving a signal whose spectrum is spread by the time-divided PN code, a signal superimposed by generating and despreading a plurality of PN codes identical to those on the transmission side in the same manner as described above. The information contained in is demodulated.

First, the operation of the code phase locked loop of the PN code that is not time-divided will be described with reference to FIG.
In the spread spectrum signal receiving apparatus with respect to the received PN code 200, in order to constantly obtain a P (Punctual) phase code 210 in a state where it matches the phase of the PN code generated in the receiving apparatus, it is the same as the P phase. In the PN code sequence, a phase E (Early) code 220 earlier than the P phase and a phase L (Late) code 230 later than the P phase are generated. The accumulated correlation characteristic of each of the E phase code, the L phase code, and the received PN code has the characteristic indicated by 240, and the characteristic obtained by subtracting the L correlation characteristic from the E correlation characteristic is centered on the tracking point (P phase) as indicated by 250. In general, a code phase locked loop is formed by performing code phase discrimination using this characteristic.

The structure of the code phase locked loop will be described with reference to FIG.
A PN code sequence identical to the PN code sequence superimposed on the received signal 10 is generated using the PN code generation unit 20, and an E phase, a P phase, and an L phase are generated and generated by the code phase difference generation unit 30. The correlation between each of the PN codes and the input signal is performed by the correlator 40, and, for example, an integration correlation value is obtained by integration by the integration unit 50 during the repetition period of the PN code.

  Code phase tracking is performed by controlling the PN code generator 20 from the integrated correlation values R (P) and R (E) −R (L) obtained here.

Although not shown, in order to demodulate the actual received signal, tracking to the carrier wave component and decoding of the superimposed data are required. As the correlation values of the PN code phases E, P, L and the carrier orthogonal components I, Q, respectively, integrated correlation values R (Pa), R (Ea), R (La), R (P), R (E), R ( L).
Here, R (P) = √ (R (PI) ² + R (PQ) ² ), R (E) = √ (R (EI) ² + R (EQ) ² ), R (L) = √ ( R (LI) ² + R (LQ) ² ).

The PN code generation unit 20 tracks the PN code phase of the received signal 10 as a code phase tracking error value from the integrated correlation value, and demodulates the data that is constantly superimposed. As an example, the code phase tracking error value Δ is
Δ = 1/2 {(R (E) −R (L)) / (R (P) + ABS (R (E) −R (L)) / 2)}
It is possible to ask for.

  Here, paying attention to the code phase tracking characteristics, description of tracking to the carrier wave component and demodulation of the superimposed data is omitted.

Next, the code phase locked loop operation of a PN code time-divided into, for example, two time domains will be described with reference to FIG.
The PN code A (300) and the PN code B (310) are different series, and the repetition rate is different, but the chip rate is the same. The transmitting device transmits a PN code C (320) that is time-divisioned by switching between PN code A and PN code B at a frequency twice the chip rate, and the receiving device receives this PN code C and includes it in the signal. Each of the PN code A and PN code B to be despread is subjected to code phase tracking.

  Only the phase tracking loop for PN code A will be described below, but the same processing is performed for PN code B as well.

  As in the previous example, the PN code a of the same PN code sequence as the transmission source PN code A is generated in the receiving apparatus. However, since the transmitted signal is already time-shared, the PN code Since information on the PN code A is not included at the time allocation of B, the correlation may be obtained in the state where the code rate of the PN code B, that is, the code rate of the PN code C is thinned out for each code. For this reason, a PN code a (330 in FIG. 8) may be generated in the receiver, in which the correlation interval is +1 or −1 and the non-correlation interval is 0.

  If 330 in FIG. 8 is the P phase of the PN code a, an E phase code 340 earlier than the P phase and an L phase code 350 later than the P phase are generated in the same PN code sequence as the P phase, as in the previous example.

  In order to obtain the E-L integrated correlation characteristic, not only means for obtaining (E phase integrated correlation characteristic)-(L phase integrated correlation characteristic) but also (E phase code)-(P If an E-L phase code 360 having undergone the processing of (phase code) is generated and correlated with the received signal, then, for example, integration is performed for the period of the repetitive cycle of the PN code A, the E-L integrated correlation characteristic can be similarly obtained.

  The structure of the code phase locked loop is shown in FIG. 5 can be configured with the same structure as in FIG. 5 of the previous example. The difference is that the PN code generated in the PN code generator has three values with respect to the input signal 10a, and the PN code generator 20a, The code phase difference generation unit 30a, the correlation unit 40a, and the integration unit 50a each have a structure corresponding to ternary correlation processing.

  FIG. 8 shows an explanatory diagram of each PN code corresponding to the structural diagram 7. The problem here is that when the phase difference between the E phase and the P phase, and the P phase and the L phase is τ chips (τ << 0.5 chips), phase tracking is performed on the time-divided PN code A. In this case, the received signal in the section 341 earlier by τ chips than the transition point of the P phase signal of the E phase signal of the PN code a is information of the PN code B, does not include the information of the PN code A, and the PN code B and PN The code a is uncorrelated and becomes noise and adversely affects the phase tracking information. In the interval 342 from the (1-τ) chip to 1 chip from the P phase transition point, the PN code a is 0, and the PN code The correlation with the received signal of A is not taken, and information is missing.

Similarly, the problem is that the PN code a is 0 in the interval 351 later than the P phase signal transition point of the L phase signal of the PN code a, and the correlation with the received signal of the PN code A is not taken, so the information is not obtained. The received signal in the section 352 that is missing and is 1 chip to (1 + τ) chips later than the transition point of the P phase signal is PN code B information, and does not include PN code A information. The PN code a is uncorrelated and becomes noise, which adversely affects the phase tracking information.
This problem also occurs when phase tracking is performed on the PN code B.

JP-A-11-231036

It is an object of the present invention to establish a code phase synchronization method without losing information even when receiving a signal whose spectrum is spread by a time-division PN code.

In a spread spectrum signal receiving apparatus that tracks the phase of a time-divided PN code, the apparatus has a PN code generator, and is supplied from the PN code generator, a PN code E phase signal, a PN code L phase signal, or a PN code E The code sequence of the -L phase signal includes a correlation between one of the time-divided PN codes included in the received signal and the E-L phase signal of the other time-divided PN code generated by the PN code generator. It has a waveform shaping unit that performs waveform shaping to prevent mixing of noise components that occur . Further, in the above spread spectrum signal receiving apparatus according to the invention, a plurality in a time-divided PN code divided number minute during a phase tracking section for phase tracking, independently of divided each PN code time A phase control amount calculation control unit that switches between a phase tracking function, a function that mutually uses each phase tracking information, and a function that averages each phase tracking information is provided.

In the present invention, the EL component value waveform shaped by the waveform shaping unit does not include a noise component generated by the correlation between the PN code a generated in the receiver and the PN code B included in the received signal. There is an advantage that the correlation information between the PN code a generated in the receiver and the PN code A included in the received signal is doubled, and the code phase tracking performance is improved.
In the present invention, the amount of signal information is doubled and good phase tracking is achieved by controlling the phase control amount calculation control unit using the phase control amounts of both the PN code A and PN code B signals. realizable. Furthermore, when either the PN code A or PN code B signal cannot be acquired, or when it is re-acquired due to an interruption or the like, one of the phase control amounts is used to quickly shift to the acquisition state or the tracking state. There is an effect that can be.

FIG. 1 is a block diagram of a spread spectrum receiver according to Embodiment 1 of the present invention, and FIGS. 2 and 3 are explanatory diagrams thereof. In the first embodiment, a case where time division is performed in two time regions will be described as an example.
PN code A (100 in FIG. 2) and PN code B (110 in FIG. 2) are different series, and the repetition rate is different, but the chip rate is the same. The transmission source transmits the PN code C (120 in FIG. 2) by switching between the PN code A and the PN code B at a frequency twice the chip rate, and the receiving device receives the PN code C and receives the PN code C. Each of the PN code A and PN code B included in the signal is despread to perform code phase tracking. The received signal when this signal is received is assumed to be 10a in FIG.

  In the receiving apparatus, the PN code a of the same PN code sequence as the transmission source PN code A is generated as in the prior art. However, since the transmitted signal is already time-shared, the PN code B Since the information of the PN code A is not included at the time allocation, the correlation may be obtained in the state where the code rate of the PN code B, that is, the code rate of the PN code C is thinned out for each code. Therefore, the PN code generation unit 20a in FIG. 1 generates a PN code a (130 in FIG. 2) in which a section in which correlation is taken is set to +1 or −1 and a section in which no correlation is taken is set to 0.

  Next, an E phase code earlier than the P phase and an L phase L code later than the P phase are generated by the code phase difference generation unit 30a with the same PN code as the P phase. So far, it is the same as that of the prior art.

  In the present invention, when the phase difference between the E phase and the P phase and the phase difference between the P phase and the L phase is τ chips (τ << 0.5 chips), the waveform shaping unit 35a in FIG. The interval 141 earlier than the transition point of the P phase signal 130 of the E phase signal 140 of the PN code a is set to 0, and a process that does not correlate with the PN code B signal component is performed. The section 142 from (1-τ) chip to 1 chip from the phase transition point is set to the opposite sign to the P phase signal 130, and a process capable of performing correlation processing with the PN code A signal component is performed to generate an E ′ phase signal.

  In addition, by using the waveform shaping unit 35b of FIG. 1, the section 151 later than the transition point of the P phase signal 130 of the L phase signal 150 of the PN code a shown in FIG. In addition, the section 152 of the 1 phase to (1 + τ) chips from the P phase transition point of the L phase signal 150 is set to 0, and processing that does not correlate with the PN code B signal component is performed to generate the L ′ phase signal. Let

Then, the correlation between the received signal 10a and the PN code P phase signal 130 is performed by the correlation unit 40a, and the integration unit 50a performs integration for, for example, the repetition period of the PN code A to obtain the P phase integration correlation characteristic.
Similarly, the correlation between the reception signal 10a and the PN code E ′ phase signal 140 is performed by the correlation unit 40a, and the integration unit 50a performs integration for, for example, a repetition period of the PN code A to obtain an E ′ phase integration correlation characteristic.
Similarly, the correlation between the received signal 10a and the PN code L ′ phase signal 150 is performed by the correlation unit 40a, and the integration unit 50a performs integration for, for example, a repetition period of the PN code A to obtain an L ′ phase integration correlation characteristic.
Then, the control unit 60 performs code phase discrimination from the E ′ phase integration correlation characteristic−L ′ phase integration correlation characteristic, and controls the PN code generation unit 20a to form a code phase locked loop.

  In the above, the E′-L ′ characteristic is subtraction after integration, but E′−L is obtained by subtracting the L ′ phase PN code (150) from the E ′ phase PN code (140) before correlating with the received signal. By using the 'phase PN code (160) and calculating the correlation with the received signal, the same E'-L' integrated correlation characteristic as described above can be obtained.

  In order to explain the details of the effects of the waveform shaping sections 35a and 35b, the operation of one chip of the PN code A will be described in detail.

In FIG. 3, when divided into T0, T1, T2, T3, and T4 on the time axis, the E phase signal 171 of the conventional PN code a is changed to E0 to E3, L phase signal corresponding to the subscript of T. Assume that 172 is L1 to L4, the E phase signal 173 of the PN code a in this embodiment is E′0 to E′3, and the L phase signal 174 is L′ 1 to L′ 4.
Here, T0 = T1 = T3 = T4 = τ chip and T2 = (1-2 × τ) chip.

First, the operation in the state before the correlation waveform shaping in the prior art is as follows:
E phase correlation value = Bm × E0 + A0 × E1 + A0 × E2 + A0 × E3 (1)
Here, the PN code B and the PN code a are uncorrelated noise components, and the correlation value in this case is α (where α ≠ 0). Since E3 is 0, the correlation value between E3 and the received signal is 0.
E phase correlation value = A0 × (E1 + E2) + α (2)
And similarly,
L phase correlation value = A0 × L1 + A0 × L2 + A0 × L3 + B0 × L4 (3)
Here, similarly to the above, B0 × L4 which is the correlation between the PN code B and the PN code a is α ′ (where α ≠ α ′), and since L1 is 0, the correlation value between L1 and the received signal is 0. Therefore, Equation (3) is
L phase correlation value = A0 × (L2 + L3) + α ′ (4)
It becomes.
Next, the E-L characteristic is obtained by the equation (2)-(4),
E−L correlation value = A0 × (EI + E2−L2−L3) + α−α ′ (5)
Here, E2 and L2 are canceled because they are the correlation values of the same received signal and PN code,
E−L correlation value = A0 × (EI−L3) + α ″ (where α ″ = α−α ′) (6)
It becomes.

The operation of the state after correlation waveform shaping in the present embodiment will be described with the same technique.
E ′ phase correlation value = Bm × E′0 + A0 × E′1 + A0 × E′2 + A0 × E′3 (7)
Here, since E′0 = 0, the correlation value between E′0 and the received signal is 0.
E ′ phase correlation value = A0 × (E′1 + E′2 + E′3) (8)
And similarly,
L ′ phase correlation value = A0 × L′ 1 + A0 × L′ 2 + A0 × L′ 3 + B0 + L′ 4 (9)
Here, since L′ 4 = 0, the correlation value between L′ 4 and the received signal is 0.
L ′ phase correlation value = A0 × (L′ 1 + L′ 2 + L′ 3) (10)
It becomes.
Next, E'-L 'characteristics are obtained by the formula (8)-(10),
E′−L ′ correlation value = A0 × (E′1 + E′2 + E′3−L′1−L′2−L′3) (11)
Here, E′2 and L′ 2 are offset from the correlation value value of the same received signal and PN code,
E′−L ′ correlation value = A0 × (E′1 + E′3−L′1−L′3)
= A0 × {(E′1−L′1) + (E3′−L′3)} (12)
Here, since L′ 1 = −E′1 and E′3 = −L′3 generated by the waveform shaping units 35a and 35b, the equation (12) is further modified,
E′−L ′ correlation value = 2 × A0 × (E′1−L′3) (13)
Get.

  In contrast to the conventional E−L correlation value (6), the E′−L ′ correlation value (13) in this embodiment is obtained by using the PN code a generated in the receiver and the PN code B included in the received signal. There is an advantage that the noise component α ″ generated by the correlation of the PN code is not included, and there is an advantage that the correlation information between the PN code a generated in the receiver and the PN code A included in the received signal is doubled. Improvement is measured.

Further, as a modification of the present embodiment, as shown in FIG. 2, the E "phase signal 161 is subjected only to the process of setting the interval 164 earlier by τ chips than the transition point of the P phase signal of the E phase signal in the PN code a to 0. At the same time, a waveform shaping unit that generates an L ″ phase signal 162 that has been subjected only to the process of setting 0 in the section 165 from 1 chip to (1 + τ) chips from the P phase transition point of the L phase signal is used. Thus, it is possible to obtain the effect of only reducing the noise component α ″.
The detailed operation will be described using the same method with reference to 170, 175, and 176 in FIG.
When replacing E in Eq. (1) above with E ″,
E ″ phase correlation value = Bm × E ″ 0 + A0 × E ″ 1 + A0 × E ″ 2 × A0 × E ″ 3 (14)
Since E ″ 0 = 0, α = Bm × E ″ 0 = 0, which is the aforementioned noise component, and E ″ 3 is originally 0. ) Like the formula,
E ″ phase correlation value = A0 × (E ″ 1 + E ″ 2) (15)
It becomes.
Similarly, when replacing L in the expression (3) with L ″,
L ″ phase correlation value = A0 × L ″ 1 + A0 × L ″ 2 × A0 × L ″ 3 + B0 × L ″ 4 (16)
Here, since L ″ 4 = 0, α ′ = B0 × L ″ 4 = 0, which is the noise component described above, and L ″ 1 is originally 0. 4) When expressed similarly to the equation,
L ″ phase correlation value = A0 × (L ″ 2 + L ″ 3) (17)
It becomes.
Therefore, the E ″ −L ″ phase correlation value is obtained by the equations (15)-(17), and E ″ 2 and L ″ 2 are canceled by the same sign as described above,
E ″ −L ″ phase correlation value = A0 × (E ″ 1−L ″ 3) (18)
It becomes.
Comparing the equation (18) with the equation (6), there is an advantage that the noise component α ″ is not included.
It should be noted that the same effect can be obtained by using the E "-L" phase signal 163 obtained by subtracting the E "phase signal and the L" phase signal in advance.

  All the explanations so far have been explained for the PN code A. However, the PN code B is shifted by one chip on the time axis, the PN code b of the same code series as the PN code B is generated, and means for performing the same processing as the above explanation is provided in parallel. Therefore, the code phase tracking can be performed for the PN code B with the same effect.

FIG. 4 shows a configuration diagram of a spread spectrum receiving apparatus according to Embodiment 2 of the present invention.
The PN code A phase tracking unit 70 has the means described in the first embodiment for tracking to the PN code A in order to track the time-divided PN code PN code A and PN code B, respectively. The difference is that the control unit 61 is connected to the PN code a generation unit 21 a via the phase control amount calculation control unit 80. The PN code B phase tracking unit 71 is configured to track the PN code B with the same configuration, and the generated PN code is different.

PN codes a and b are generated inside the receiver for each of the time-division signals PN code A and PN code B, and integrated correlation values R (Pa), R (Ea), R (La), R ( It is assumed that Pb), R (Eb) R (Lb) are obtained.
Here, R (Pa) = √ (R (PIa) ² + R (PQa) ² ), R (Ea) = √ (R (EIa) ² + R (EQa) ² ), R (La) = √ ( R (LIa) ² + R (LQa) ² )
R (Pb) = √ (R (PIb) ² + R (PQb) ² ), R (Eb) = √ (R (EIb) ² + R (EQb) ² ), R (Lb) = √ (R (LIb ) ² + R (LQb) ² )
For example, the carrier signal component and the data modulation component are not considered for simplification of description.
In this case, the phase control amount of the PN code A is calculated from R (Pa), R (Ea), and R (La).
Δa = 1/2 {(R (Ea) −R (La)) / (R (Pa) + ABS (R (Ea) −R (La)) / 2)}
Similarly, the phase control amount of the PN code B is calculated from R (Pb), R (Eb), and R (Lb).
Δb = 1/2 {(R (Eb) −R (Lb)) / (R (Pb) + ABS (R (Eb) −R (Lb)) / 2)}
It is obtained by.

The PN code A phase tracking unit 70 and the PN code B phase tracking unit 71 perform phase tracking operations independently at the time of initial acquisition, but when the time division signal is transmitted from the same transmitter, the code phase tracking error is the same. Therefore, the amount of signal information can be increased by using both pieces of code phase tracking information.
For example, if the phase control amounts of both the PN code A and PN code B signals are input to the phase control amount calculation control unit 80 and the average value Δab = (Δa + Δb) / 2 is used as the phase control amount, the signal information amount is 2 Doubled improvement and good phase tracking can be realized.

Also, when either the PN code A or PN code B signal cannot be acquired, or when it is re-acquired due to an interruption or the like, one of the phase control amounts is used to shift to the acquisition state or the tracking state at high speed. be able to.
In addition, this system can obtain the same effect by using the E and L phase signals described in the prior art or the E′L ′ phase signal and the E ″ L ”phase signal described in the first embodiment.

Configuration diagram in Embodiment 1 of the present invention Explanatory drawing (1) in Example 1 of this invention Explanatory drawing (2) in Example 1 of this invention Configuration diagram of Embodiment 2 of the present invention Configuration diagram of the prior art (1) Explanatory drawing of prior art (1) Configuration diagram of the prior art (2) Explanatory drawing of prior art (2)

Explanation of symbols

10, 10a ... received signals 20, 20a ... PN code generator 21a ... PN code generator a
21a '... PN code generator b
30, 30a, 30a '... code phase difference generators 35a, 35b, 35a', 35b '... waveform shaping units 40, 40a, 40a' ... correlation units 50, 50a, 50a '... integration units 60, 61, 62 ... control Unit 70 ... PN code A phase tracking unit 71 ... PN code B phase tracking unit 80 ... phase control amount calculation control unit 100 ... source PN code A
110 ... Source PN code B
120 ... Received signal PN code C obtained by time-sharing PN code A and PN code B
130: Replica P phase PN code a generated in the receiver
140 ... E phase signal and E 'phase PN code a
141... Code value of E ′ phase signal in the section τ chip earlier than the transition point of the P phase signal 130 142... Code of E ′ phase signal in the section of (1−τ) chip to τ chip from the transition point of the P phase signal 130 Value 150 ... L phase signal and L 'phase PN code a
151... Code value 152 of L ′ phase signal in the section τ chip later than the transition point of the P phase signal 130... Code value 160 of L ′ phase signal in the section of 1 chip to (1 + τ) chip from the transition point of the P phase signal 130. ... E'-L 'phase PN code a obtained by subtracting L' phase PN code a from E 'phase PN code a
161 ... E phase signal and E "phase PN code a
162 ... L phase signal and L "phase PN code a
163 ... E "-L" phase PN code a obtained by subtracting L "phase PN code a from E" phase PN code a
164... Τ chips earlier than transition point of P phase signal 130 165... 1 chip to (1 + τ) chips later from transition point of P phase signal 130... Received signal PN code obtained by time division of PN code A and PN code B C
171 ... E phase PN code a according to the prior art
172 ... L phase PN code a according to the prior art
173 ... E 'phase PN code a which is an E phase signal according to the present invention
174... L ′ phase PN code a which is an L phase signal according to the present invention
175... E "phase PN code a which is an E phase signal according to the present invention
176... L "phase PN code b which is an L phase signal according to the present invention
200 ... received PN code 210 ... replica P phase PN code 220 having the same phase as the received PN code generated in the receiver ... replica E phase PN code 230 having a phase earlier than the P phase generated in the receiver ... generated in the receiver Replica L phase PN code 240 with phase slower than P phase ... Accumulated correlation characteristic 250 of received PN code and replica PN code (E phase, L phase) ... Code phase tracking discrimination characteristic obtained by subtracting L correlation characteristic from E correlation characteristic ( E-L)
300 ... Source PN code A
310 ... Source PN code B
320: Received signal PN code C obtained by time-sharing PN code A and PN code B
330: Replica P phase PN code a generated in the receiver with respect to PN code A
340 ... Replica E phase PN code a generated in the receiver with respect to PN code A
341... Τ chip earlier than the P phase signal transition point of the PN code aE phase signal 342... (1-τ) chip to 1 chip from the P phase signal transition point of the PN code aE phase signal 350. Replica L phase PN code a generated in-flight
351: section τ chip later than P phase signal transition point of PN code aL phase signal 352: section 1 chip to (1 + τ) chip from P phase signal transition point of PN code aL phase signal 360: E phase PN code a to L E-L phase PN code a obtained by subtracting phase PN code a

Claims (4)

In a spread spectrum signal receiving apparatus for phase tracking to a time-division pseudo noise code (hereinafter referred to as PN code),
A PN code E phase signal having a phase earlier than the PN code phase signal at the phase tracking point supplied from the PN code generation unit, and a PN code L having a phase slower than the PN code phase signal at the phase tracking point. A phase signal or a PN code E-L phase signal code sequence obtained by previously subtracting the PN code L phase signal from the PN code E phase signal, one of the time-divided PN codes included in the received signal, and A spread spectrum signal characterized by having a waveform shaping unit that performs waveform shaping to prevent mixing of noise components caused by correlation with the E-L phase signal of the other PN code that is time-division generated by the PN code generation unit Receiver device. In the case where the phase difference between the E phase and the P phase, and the P phase and the L phase is τ chips (τ << 0.5 chips),
For the PN code E phase signal, the E phase signal of one time-divided PN code is set to 0 in the section τ chips earlier than the P phase signal transition point, and the correlation with the other time-divided PN code signal component is In addition, the E phase signal has a (1-τ) chip to 1 chip interval from the P phase signal transition point to the opposite sign of the P phase signal, and the correlation with the one PN code signal component. Generate an E ′ phase signal that can be processed,
With respect to the PN code L phase signal, the time phase-divided L phase signal of one PN code is set to the opposite sign of the P phase signal in the interval τ chips later than the P phase signal transition point, and the one PN code signal component Further, the L phase signal is set to 0 in the section from 1 chip to (1 + τ) chips from the P phase signal transition point, and the correlation with the other time-divided PN code signal component is obtained. 2. The spread spectrum signal receiving apparatus according to claim 1, wherein an L ′ phase signal subjected to no processing is generated. In the case where the phase difference between the E phase and the P phase, and the P phase and the L phase is τ chips (τ << 0.5 chips),
For the PN code E phase signal, the E phase signal of one of the time-divided PN codes is set to 0 in the section τ chips earlier than the P phase signal transition point, and the correlation with the signal component of the other time-divided PN code E ”phase signal that has been processed without processing is generated,
For the PN code L phase signal, the L phase signal of one time-divided PN code is set to 0 in a section 1 chip to (1 + τ) chips later than the P phase signal transition point, and the other time-division PN code 2. The spread spectrum signal receiving apparatus according to claim 1, wherein an L ″ phase signal subjected to a process not taking a correlation process with a signal component is generated. The spread spectrum signal receiving apparatus,
There are as many time-division phase tracking units as phase tracking to a plurality of time-division PN codes,
A phase control amount calculation control unit that switches between a function for phase tracking independently for each time-divided PN code, a function for mutually using each phase tracking information, and a function for averaging each phase tracking information 2. The spread spectrum signal receiving apparatus according to claim 1, further comprising:

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