JP4265115B2 - Voltage control device for vehicle alternator - Google Patents

Description

[0001]
BACKGROUND OF THE INVENTION
The present invention relates to a voltage control device for an automotive alternator.
[0002]
[Prior art]
In Japanese Patent Laid-Open Nos. 55-127849 and 6-284598, the magnetic flux remaining in the iron core and interlinking with the armature winding is modulated by the rotation of the field pole when the rotating field pole type alternator rotates. An alternating voltage (also referred to as a residual magnetization armature winding induced voltage) induced in the armature winding is detected to detect the rotation of the alternator, that is, engine start.
[0003]
Japanese Patent Application Laid-Open Nos. 3-215200 and EP6646487 disclose two-phase AC voltages that are induced by a magnetic flux remaining in a rotating magnetic pole constituting a rotating field magnetic pole type alternator interlinked with a multiphase armature winding. It is disclosed that power generation is detected by detecting a potential difference between the two voltages. By using these power generation detection techniques, the IG wiring can be omitted, and there is an advantage that the alternator is not excited when the engine is not started despite the IG switch being turned on.
[0004]
[Problems to be solved by the invention]
However, in this type of rotation detection by the remanent magnetized armature winding induced voltage, when the amplitude of the remanent magnetized armature winding induced voltage exceeds a predetermined value, field current conduction to the field winding is started. Therefore, it is necessary to rectify the detected residual magnetization armature winding induced voltage and to compare this rectified voltage with a predetermined threshold voltage. The rectified voltage obtained by rectifying it is further reduced because it is very low, about 0.4 V, the detection accuracy of the rectified voltage in the vicinity of the power generation start rotational speed is lowered, and a complicated detection circuit is required for detection. A problem such as occurred. There is also a problem that a large field current suddenly flows in the vicinity of the power generation start rotational speed and the engine load torque increases.
[0005]
The present invention has been made in view of the above-described problems. It is possible to start power generation with high accuracy and early by suppressing deterioration of a signal voltage for detecting that the rotational speed has reached the power generation start rotational speed. It is an object of the present invention to provide a control device for a vehicle alternator that can smooth the change in driving torque of the vehicle alternator at the start.
[0006]
[Means for Solving the Problems]
The control apparatus for an AC generator for a vehicle according to claim 1 is a field winding in which a rotor having a field core formed with a plurality of field poles and a field current for magnetizing the field poles are fed. Vehicle having a wire, an armature having an armature core around which an armature winding having a plurality of phase windings is wound, and a rectifying circuit for rectifying a power generation voltage of the phase winding and outputting it as an output voltage In a control device for a vehicle alternator that is equipped in an AC generator for controlling the output voltage by adjusting the field current, switch means for intermittently switching the field current, and a signal related to the output voltage And a power supply circuit that controls the switch circuit to an operating state or a non-operating state. The power supply driving circuit includes: , another of each said phase winding 90 degrees by binarizing the voltage generated by the pair of phase windings having a phase difference to form a pulse voltage of twice the frequency of the generator voltage, the operating state only the power supply circuit a predetermined period from an edge of the pulse voltage It is characterized by doing.
[0007]
The phase winding here refers to an armature winding that generates an AC voltage of a predetermined phase.
[0008]
By adopting this configuration, when the peak value of the generated voltage finally reaches the threshold for binarization, the pulse width corresponding to the predetermined period and the pulse period corresponding to the rotation speed are used. Power generation at a prescribed duty ratio is started, and the duty ratio increases as the rotational speed increases. If the pulse period becomes equal to or less than the predetermined period as the rotational speed increases, continuous power generation can be performed.
As a result, the problem that a large field current flows suddenly in the vicinity of the power generation start rotational speed and the drive torque of the generator increases can be suppressed.
[0009]
In addition, according to the present invention, since it is not necessary to rectify the generated voltage of the field winding or armature winding (phase winding), the signal-to-noise ratio of the signal voltage linked to the rotational speed is improved to start power generation. Thus, the reliability of the power generation start operation can be improved, and power generation can be started from a low speed. In addition, since the circuit can be realized with a relatively simple hardware circuit, the circuit load is reduced. Furthermore, according to this configuration, power supply to the control circuit is controlled based on the detection of power generation, so that power consumption of the control circuit and the power supply circuit can be suppressed when the rotational speed is less than the power generation start rotational speed.
[0010]
In a preferred aspect, the generated voltage of the armature winding (phase winding) or the field winding is predetermined from both a rising edge and a falling edge of a pulse signal obtained by binarizing with a comparator or a differential amplifier circuit. It is preferable to output a constant output signal level only for a period. In this way, since the pulse period can be halved compared with the case where only one of both edges is used, the CR integration circuit, that is, the delay circuit can be reduced in size, and the digital circuit such as a multistage digital counter is omitted, and the circuit configuration Can be simplified and highly reliable. In order to output a constant output signal level for a predetermined period from both the rising edge and falling edge of the pulse signal, the output signal of the circuit that outputs the Hi signal for a predetermined time from the rising edge and the predetermined time from the falling edge. A logical sum signal with the output signal of the circuit that outputs the Hi signal may be formed.
[0011]
Note that the power supply circuit referred to in this specification may be a circuit that intermittently supplies power to the control circuit, and may be configured by a single switch.
[0012]
More specifically, in the present invention, the power supply driving circuit has a frequency that is a predetermined multiple of the generated voltage based on the generated voltage of a predetermined number of phase windings having a predetermined phase difference among the phase windings. And the power supply circuit is put into an operating state only for a predetermined period from the edge of the pulse voltage. Thereby, the detection accuracy of the rotational speed can be improved, and the circuit configuration of the delay circuit, that is, the timer for forming the predetermined period can be simplified. For example, the CR integration circuit, that is, the delay circuit can be reduced in size, and a digital circuit such as a multistage digital counter can be omitted to simplify the circuit configuration and increase the reliability.
[0013]
For example, if the generated voltages of the three phase windings of a three-phase armature winding are converted into binary signals (pulse signals) with different thresholds by different comparators, their edges become signals that are 120 degrees out of phase with each other. . A pulse signal having a period of 1/3 is formed by logical operation of these three pulse signals, a signal that becomes Hi for a predetermined period from the rising edge is synthesized, and power supply to the power supply circuit is controlled by this signal. That's fine.
[0014]
More specifically, in the present invention, the power supply drive circuit has a frequency that is twice the generated voltage based on the generated voltage of a pair of phase windings having a phase difference of 90 degrees among the phase windings. And the power supply circuit is put into an operating state only for a predetermined period from the edge of the pulse voltage. In this way, with a simple circuit configuration, it is possible to obtain a signal voltage (rotation-induced electrical signal) having a frequency twice that of the conventional signal voltage that is linked to the rotational speed, and a delay for forming the predetermined period described above. The circuit configuration of the circuit, that is, the timer can be simplified, and the rotational speed detection accuracy can be improved. For example, the CR integration circuit, that is, the delay circuit can be reduced in size, and a digital circuit such as a multistage digital counter can be omitted to simplify the circuit configuration and increase the reliability.
[0015]
In a preferred aspect, the power supply driving circuit includes a pair of comparators that convert the generated voltages of the pair of phase windings into binary signals (pulse signals), respectively, and either an exclusive OR signal or a coincidence signal of both the comparators. The power supply circuit is put into an operating state only for a predetermined period from the edge of the output signal of the frequency doubler circuit. In this way, the circuit can be simplified.
[0016]
For example, two sets of symmetry in which a rotor having 2p field poles and an iron core having 4pm slots arranged at equal intervals in the circumferential direction and its output terminals are wound electrically independently of each other Provide m-phase winding. p and m are positive integers. As a result, even a generator having an arbitrary number of phases can make a voltage waveform with a phase difference of 90 degrees exist, and a rectangular wave with a double frequency can be easily created without performing special signal processing.
[0017]
According to the configuration of the second aspect , the power supply driving circuit preferentially puts the main power supply circuit in the operation state when the output voltage of the rectifier circuit becomes equal to or higher than a predetermined value. Thereby, when the rotation speed of a generator becomes more than predetermined value, a main power supply circuit can be operated stably.
[0018]
According to the configuration of claim 3 , the power drive circuit includes a power switch that opens and closes between a battery terminal potential of the vehicle alternator and a power supply voltage input terminal of the power circuit, and the power switch The power supply circuit is temporarily brought into an operating state by controlling opening and closing of the power supply. Thereby, the control of the power supply to the main power supply circuit can be reliably performed.
[0019]
DETAILED DESCRIPTION OF THE INVENTION
Preferred embodiments of the control device for a vehicle alternator according to the present invention will be described in detail with reference to the following examples.
[0020]
[First embodiment]
FIG. 1 is a block diagram showing a circuit configuration of an automotive alternator of the first embodiment.
[0021]
DESCRIPTION OF SYMBOLS 1 is a vehicle alternator (alternator), 2 is a vehicle-mounted battery, 31 and 32 are armature windings, 41 and 42 are full-wave rectifier circuits connected to the output terminals of the armature windings 31 and 32, Reference numeral 5 denotes a smoothing capacitor, 6 denotes a field winding wound around a field iron core (not shown) having a field pole, and 7 adjusts the field current to control the output voltage of the alternator 1 within a predetermined range. This is a voltage control device.
[0022]
71 is a transistor connected in series with the field winding to interrupt the field current, 72 is a flywheel diode (circulating diode) that circulates the field current when the transistor 71 is off, 73 is a full-wave rectifier circuit 4 A control circuit that generates a signal for driving the power transistor 71 so that the output voltage falls within a predetermined range, and 74 is a power supply circuit that supplies power to maintain the voltage control circuit 73 in an operating state. , 75 is a power supply driving circuit for detecting the rotation of the rotor and generating a signal for driving the power supply circuit 74.
[0023]
The power supply circuit 74 itself is a conventional circuit that supplies power supply voltage to the control circuit 73. For example, the power supply circuit 74 may be constituted by a constant voltage circuit, and the power supply voltage input to the IG terminal of the power supply circuit is directly supplied to the control circuit 73. You may apply as a power supply voltage. The control circuit 73 includes a comparator that compares the battery voltage with a predetermined adjustment voltage and intermittently controls the transistor 71 based on the comparison result. Since the power supply circuit 74 and the control circuit 73 are the same as in the prior art, a detailed description is omitted.
[0024]
The armature windings 31 and 32 will be further described.
[0025]
The armature winding includes two phase windings, that is, a U-phase winding 31 and a V-phase winding 32, and the generated voltages of both phase windings 31 and 32 are electrically 90 degrees out of phase with each other. The first full-wave rectifier 41 full-wave rectifies the AC power of the U-phase winding, and the second full-wave rectifier 42 full-wave rectifies the AC power of the V-phase winding.
[0026]
An example of the power supply driving circuit 75 is shown in FIG.
[0027]
751 is a first comparator that compares a voltage at one end of the U-phase winding 31 (also referred to as U-phase voltage) with a predetermined reference potential Vref, and 752 is a voltage at one end of the V-phase winding 32. 753 is a second comparator that compares (also referred to as U-phase voltage) with a predetermined reference potential Vref.
Although it is an exclusive OR circuit that outputs an exclusive OR signal of the output signals of the comparators 751 and 752, it may be a coincidence circuit.
[0028]
Reference numeral 754 denotes a resistor group that divides the power supply voltage Vcc formed by a constant voltage circuit (not shown), and each resistance value is desirably set equal. 755 is a comparator that compares 2/3 of the power supply voltage Vcc with the output of the subsequent CR integration circuit 758, and 756 compares the output voltage of the exclusive OR circuit 753 with 1/3 of the power supply voltage Vcc. The comparator 757 is an RS flip-flop having the output of the comparator 755 as a reset input and the output of the comparator 756 as a set input, 758 is the above-mentioned CR integrating circuit formed by connecting the capacitor C1 and the resistor R2 in series, and 759 is a flip-flop. The transistor Q75 receives the anti-Q output of the transistor 755 through the base resistor Rb and discharges the capacitor C1.
[0029]
A comparator 761 compares the divided voltage VS of the DC output voltage Vb of the alternator 1 with a predetermined voltage Vref2. This is an analog switch that is driven by the output of, and intermittently supplies power supplied to the IG terminal of the power supply circuit 74.
[0030]
The operation of the power supply driving circuit 75 will be described below with reference to FIG.
[0031]
Magnetization remains in each iron core of the alternator 1, particularly the field iron core, by the previous power generation. As the rotor rotates, the U-phase winding 31 and the V-phase winding 32 are formed by a combined residual magnetization (particularly, a residual magnetization of the field core) of the residual magnetization of the field core and the residual magnetization of the armature core. As a result, the residual magnetic fluxes interlinking with the windings 31 and 32 are periodically changed, whereby an alternating voltage is induced in the windings 31 and 32.
The amplitude of this AC voltage is, for example, about 0.2 to 0.4 V, and the frequency is P1 · N / 60 [Hz] at N [rpm] when the number of rotating magnetic poles (the total number of field poles of the field core) is 2P1. Become.
[0032]
The comparator 751 outputs a rectangular wave pulse voltage in1 having a duty ratio of 50% and a frequency P1 · N / 60 as compared with the AC voltage of the U-phase winding 31 and the constant voltage Vref. The AC voltage is clamped to about −0.7 V in the negative half-wave period by the full-wave rectifier 41.
[0033]
The comparator 752 outputs a rectangular wave pulse voltage in2 having a duty ratio of 50% and a frequency P1 · N / 60 as compared with the AC voltage of the V-phase winding 32 and the constant voltage Vref. The AC voltage is clamped to about −0.7 V in the negative half-wave period by the full-wave rectifier 42.
[0034]
The exclusive OR circuit 753 outputs an exclusive OR signal in of the rectangular wave pulse voltages in1 and in2 to the comparator 756, and the comparator 756 compares it with the divided voltage Vcc / 3 and inputs the comparison result to the flip-flop 755 as a set input. Output to the end.
[0035]
The comparator 755 receives the output of the subsequent CR circuit 758 and compares it with the divided voltage 2 · Vcc / 3. That is, when the output of the CR circuit 758 reaches the divided voltage 2 · Vcc / 3, the comparator 755 outputs the Hi output and resets the flip-flop 757.
[0036]
When the output of the comparator 755 is Lo, that is, the output of the CR circuit is 2 · Vcc / 3 or less, the Q output of the flip-flop 757 is Hi, the anti-Q output is Lo, the transistor 759 is turned off, and the capacitor C1 is charged. Is done. When the capacitor C1 is charged and the potential Vc reaches 2 · Vcc / 3, the flip-flop 757 is reset, the transistor 759 is turned on, and the capacitor C1 is discharged. Eventually, the flip-flop 757 outputs Hi for a period during which the capacitor C1 is charged, that is, for a certain period substantially equal to the time constant of the CR circuit 758. When the output of the flip-flop 757 is Hi, the switch 760 that supplies power to the IG terminal of the power supply circuit 74 is maintained in the ON state, and the power supply circuit 74 becomes operable.
[0037]
When the rotation speed is low, the CR time constant of the CR circuit 758 is shorter than the cycle of the set input of the flip-flop 757. Therefore, when the flip-flop 757 is reset, that is, the potential of the capacitor C1 is 2 · Vcc / 3. At this point, the set input is Lo, and next, the Q output Out1 of the flip-flop 757 maintains Lo and the output Out of the power supply driving circuit 75 maintains Lo until the set input becomes Hi.
[0038]
When the rotation speed exceeds a predetermined value, the cycle of the set input of the flip-flop 757 becomes shorter than the CR time constant. Therefore, when the flip-flop 757 is reset, that is, when the potential of the capacitor C1 becomes 2 · Vcc / 3, Is also Hi, the flip-flop 757 maintains the Hi output, and the output Out of the power source driving circuit 75 maintains Hi. That is, as the rotational speed increases, the frequency of the voltage induced in the armature windings 31 and 32 becomes higher, and the off period of the output Out is gradually shortened, and eventually turns on continuously. That is, the power supply circuit 74 can be continuously maintained in the operating state. That is, the operation is intermittent in the low rotation range, and shifts to continuous operation at a certain rotation speed or higher.
[0039]
For example, in an alternator having 12 poles (six pole pairs) of rotating magnetic poles, when R2 = 100 kΩ and C1 = 0.1 μF are set, continuous operation is possible at about 1000 [rpm]. In general, when it is desired to operate the 2 · P1 pole alternator continuously at N1 [rpm], the time constant of the CR circuit 758 may be set to 60 / (P1 · N1) [sec].
[0040]
When the RS flip-flop 757 is used, the flip-flop output becomes indefinite when both the set and reset inputs are Hi. Therefore, in this embodiment, the output voltage (DC output voltage) of the alternator 1 is divided by a voltage dividing circuit (not shown), and a reference voltage higher than the open terminal voltage of the battery, for example, a reference voltage corresponding to 13.0 V, by the comparator 764. Compared with the value Vref, when the output voltage of the alternator 1 is higher than the reference voltage value Vref, Hi is output as the comparison result Out2, and the gate of the switch 760 is driven by the logical sum signal of this signal and the output Out1. Thus, the operation can be further stabilized.
[0041]
Further, the following effects can be obtained by passing the comparison result between the output voltage of the alternator 1 and the reference voltage higher than the open terminal voltage of the battery through the OR gate.
[0042]
Consider the process of stopping a vehicle-mounted engine after vehicle operation ends. Usually, since the battery is maintained in a substantially fully charged state, the terminal voltage thereof, that is, the input voltage of the comparator 761 is a value corresponding to approximately 14.5 V, and the output of the comparator 761 is Hi. When the driver stops the engine, the alternator 1 also immediately stops, but the main power supply of the voltage control device of the alternator 1 is still in the active state upon receiving the Hi signal from the comparator 761. Therefore, the exciting current is continuously supplied to the field winding 6 of the alternator 1 at an appropriate duty ratio. Eventually, the terminal voltage of the in-vehicle battery drops to approximately 12.8 V with no load voltage due to loss of charge polarization, etc., and the output of the comparator 761 is inverted to make the power supply circuit 74 inoperative. Since a general in-vehicle battery uses a chemical reaction, the power supply circuit 74 of the voltage control device is deactivated after the engine is stopped and power generation of the alternator 1 is stopped, and excitation that flows in the field winding 6 is performed. It takes ten to several tens of seconds until the current completely disappears.
[0043]
Therefore, in this embodiment, the phenomenon that the decay excitation current of the field winding 6 demagnetizes the armature core when the rotation stops is a phenomenon in which the supply of power to the control circuit based on the battery voltage, that is, the DC output voltage of the alternator 1 is stopped. Since the delay is realized, the voltage control device of the alternator 1 can be reliably returned to the standby state even at the next engine start. Of course, a delay in stopping power supply to the control circuit may be realized not by a change in the magnitude of the DC output voltage but by a change in its frequency or a change in the generated voltage or frequency of the armature winding.
[0044]
Although an example in which the timer function is realized by analog signal processing using the time constant of the CR circuit is shown here, the same effect can be obtained even if digital signal processing using various digital counters is performed. Of course. FIG. 3 shows each part potential state.
[0045]
In this way, the frequency can be doubled and the pulse period can be halved compared to the case where the signal Out is formed simply from the power generation voltage of one phase armature winding, that is, one phase winding. The capacity of the capacitor C1 of the CR circuit 758 can be halved, and a change in the rotational speed can be detected accurately.
[0046]
[Modification 1]
A modification of the first embodiment is shown in FIG.
[0047]
In the first embodiment described above, the induced AC voltage between the U-phase winding 31 and the V-phase winding 32 of the two-phase armature winding is detected and used as a trigger signal for awakening of the power supply circuit 74. In this modification, the phase voltages VF1 and VF2 of the two phase windings 81 and 82 having a phase difference of 90 degrees (π / 2) are input to the comparators 751 and 752, respectively.
[0048]
More specifically, in FIG. 4, reference numerals 811 to 813 denote phase windings that constitute the first symmetrical three-phase armature winding 81 having a phase difference of 120 degrees, that is, the X-phase winding and the Y-phase winding. , 814 to 816 are phase windings having a phase difference of 120 degrees from each other and constituting the second symmetrical three-phase armature winding 82, that is, U-phase winding, V-phase winding, W-phase winding. The U phase, V phase, W phase and X phase, Y phase, and Z phase each have a phase difference of 30 degrees.
[0049]
As shown in FIG. 5, each of the phase windings 811 to 816 is wound around the armature core so as to be housed in slots provided at equal intervals in the circumferential direction. It has 72 slots for 3 phases and 12 poles, 96 slots for 16 poles and 12 · P1 slots for 2P1 poles. Adjacent slots have an electrical phase difference of 30 degrees.
[0050]
In this way, the X phase and the W phase, the Y phase and the U phase, and the Z phase and the V phase each have a phase difference of 90 degrees. Therefore, a rectangular wave having a double frequency can be easily obtained.
[0051]
An example using two sets of symmetrical 5-phase armature windings is shown in FIG.
[0052]
FIG. 6 illustrates the case of two sets of symmetrical five-phase windings.
[0053]
The five phase windings X1, X2, X3, X4, and X5 constituting the first five-phase winding 91 have a phase difference of 72 degrees from the adjacent phase windings. The five phase windings U1, U2, U3, U4, and U5 constituting the second five-phase winding 92 also have a phase difference of 72 degrees from the adjacent phase windings. The first five-phase winding 91 and the second five-phase winding 92 are electrically wound around the iron core as shown in FIG. 7 with a phase difference of 18 degrees. There are 120 slots for 12 poles, 160 slots for 16 poles, 20 · P1 slots for 2P1 poles, and adjacent slots are electrically 18 degrees. In this case, the X1 phase and the U5 phase, the X2 phase and the U1 phase, the X3 phase and the U2 phase, the X4 phase and the U3 phase, and the X5 phase and the U4 phase have a phase difference of 90 degrees.
[0054]
[Modification 2]
Another modification of the first embodiment will be described below with reference to FIG.
[0055]
FIG. 8 shows that three U, V, W, X, Y, and Z phase voltages output from the total of six phase windings 81 to 86 in FIG. Three double frequency pulse voltages whose phases are different from each other by 120 degrees are produced from an OR circuit, and these three phase double frequency pulse voltages are processed by a logic circuit 754 to synthesize a pulse voltage in having a six times frequency. By using this pulse voltage in, the capacitance of the capacitor C1 can be reduced to 1/6. The change in potential of each part of the circuit of FIG. 8 is shown in the timing chart of FIG.
[0056]
[Modification 3]
In each of the embodiments described above, the power supply driving circuit 75 uses the output voltage that becomes the Hi level potential for a predetermined period from the rising edge of the pulse voltage input to the set input terminal of the flip-flop 757. An output voltage that becomes a Hi level potential for a predetermined period from the falling edge of the pulse voltage input to the input terminal may be used, or both may be used. That is, the frequency can be doubled as in the above embodiment by enabling the operation of the power supply circuit 74 for a predetermined period from the rising edge and falling edge of the pulse voltage in.
[0057]
An example of this circuit is shown in FIG.
[0058]
The phase voltage output from one phase winding of the armature winding or the generated voltage of the field winding is set to a binary voltage (pulse voltage) VX by the comparator 751, and the inverted voltage VY is obtained by the inverter circuit 770. Pulse voltages VX and VY are individually input to monostable multivibrators 771 and 772 having a small time constant, and short pulse voltages S1 and S2 that become Hi only for a very short period from the rising edges of pulse voltages VX and VY are obtained. These short pulse voltages S 1 and S 2 are added by an OR circuit 773 and input to a monostable multivibrator 774. The Hi output period of the monostable multivibrator 774 is made equal to the time constant of the CR circuit 758. By controlling the analog switch 760 with the output voltage of the monostable multivibrator 774, the power supply driving circuit 75 having the same double frequency function as in the above embodiment can be realized. This circuit can also be applied to a normal alternator having only one three-phase armature winding.
[0059]
(Modification)
FIG. 11 shows a modification in which the circuit of FIG. 10 is applied to each phase of two sets of independent three-phase armature windings shown in FIG.
[0060]
In this case, a pulse having a maximum 12-fold frequency can be formed, the capacitance of the capacitor can be further reduced, and the rotational speed detection accuracy can be further improved.
[Brief description of the drawings]
FIG. 1 is a block diagram illustrating a circuit configuration of an alternator according to a first embodiment.
2 is a circuit diagram showing an example of a power supply driving circuit shown in FIG.
FIG. 3 is a timing chart showing states of the respective parts of the power supply driving circuit shown in FIG. 2;
FIG. 4 is a circuit diagram showing a modification of the first embodiment.
FIG. 5 is a front view showing an armature core used in the modification of FIG. 4;
FIG. 6 is a circuit diagram showing another modification of the first embodiment.
7 is a front view showing an armature core used in the modified embodiment of FIG. 6. FIG.
FIG. 8 is a circuit diagram showing another modification of the first embodiment.
9 is a timing chart showing states of the respective parts of the power supply driving circuit shown in FIG.
FIG. 10 is a circuit diagram showing another modification of the first embodiment.
11 is a circuit diagram showing a modification in which the circuit shown in FIG. 10 is applied to each of two sets of three-phase windings.
[Explanation of symbols]
DESCRIPTION OF SYMBOLS 1 Vehicle generator 3 Armature winding 6 Field winding 7 Voltage control apparatus 71 Transistor (switch means)
73 control circuit 74 power supply circuit 75 power supply drive circuit

Claims (3)

A rotor having a field core formed with a plurality of field poles;
A field winding fed with a field current for magnetizing the field pole;
An armature having an armature core wound with an armature winding having a plurality of phase windings;
A rectifying circuit that rectifies the generated voltage of the phase winding and outputs it as an output voltage;
In a control device for a vehicle alternator that is mounted on a vehicle alternator and that controls the output voltage by adjusting the field current,
Switch means for interrupting the field current;
A control circuit for controlling the switch means in response to a signal related to the output voltage;
A power supply circuit for supplying power to the control circuit;
A power supply driving circuit for controlling the power supply circuit to an operating state or a non-operating state;
With
The power supply driving circuit includes:
Binarizing the generated voltage of a pair of phase windings having a phase difference of 90 degrees of each of the phase windings to form a pulse voltage having a frequency twice that of the generated voltage;
The pulse voltage drive dual AC generator control device characterized in that the operating state of the power supply circuit for a predetermined time period from the edge of. The power supply driving circuit includes:
The output voltage is the main power supply circuit according to claim 1 Symbol placement of the control device for a vehicle alternator, characterized in that the front SL operating state if it becomes more than a predetermined value of said rectifying circuit. The power supply driving circuit includes:
A power switch that opens and closes a battery terminal potential of the vehicle alternator and a power supply voltage input terminal of the power supply circuit;
3. The control apparatus for a vehicle alternator according to claim 1 or 2, wherein the power supply circuit is temporarily brought into an operating state by controlling opening and closing of the power switch.

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