JP4001880B2 - Spatial multiplex transmission equipment - Google Patents

Description

  The present invention relates to a spatial multiplexing transmission apparatus suitable for use in an environment where antenna placement is restricted when an antenna is mounted on a base station or a terminal.

In recent years, in mobile phones and wireless LAN (Local Area Network) systems, studies for realizing high-speed wireless communication of 100 Mbps or more in a limited frequency band have been conducted. In order to realize such a wireless communication system, not only the frequency, time, and code are divided for each user, but also the frequency utilization efficiency is improved by the technology using the spatial domain, and the transmission rate is improved. Consideration is being made.
The spatial multiplexing transmission device is a device that realizes high-speed transmission without increasing the frequency band by transmitting different signals from a plurality of antenna elements. FIG. 6 is a block diagram showing an example of the internal configuration of a spatial multiplexing transmission apparatus that can improve transmission quality by forming a conventional multi-beam (see, for example, Non-Patent Document 1).

  Further, as a technique for using the spatial multiplexing transmission apparatus as shown in FIG. 7 for wider band transmission, a method of combining the spatial multiplexing transmission apparatus with the orthogonal wave frequency division multiplexing scheme has been studied. The orthogonal wave frequency division multiplexing system is a multi-carrier transmission system that uses a plurality of carrier frequencies, and each carrier is orthogonal to each other, so that the spectrum of carriers is allowed to overlap and the frequency utilization efficiency is high. In wideband transmission, a long delay wave is a factor indicating deterioration in transmission characteristics. However, in the orthogonal wave frequency division multiplexing system, each carrier is a narrow band. However, it is known that good transmission characteristics can be obtained.

  A conventional spatial multiplexing transmission apparatus for forming a multi-beam will be described below with reference to FIG. In the configuration shown in FIG. 7, the serial / parallel converter unit 77 converts the serial data into parallel L × K signals of L frequency multiplexes and K spatial multiplexes. With this conversion process, K transmission signal sequences can be generated on each of L subcarriers. Next, each input signal is input to the multi-beam forming unit 78, and by multiplying each input signal by the eigenvector obtained from the weight calculation unit 74 and the weight selection unit 75 in the figure, the antenna directivity is input for each input. Multi-beams having different properties can be formed. This calculation is performed for each of the subcarriers f1 to fL, the output of the multibeam forming unit 78 is inversely converted by the inverse Fourier transform generating unit 79, and the signal is transmitted via the transmitter 80.

Hereinafter, a method for weighting will be described. First, singular value decomposition (H = UDV ^H ) of the transfer coefficient matrix H is performed to obtain a diagonal matrix having the unitary matrix V and the singular value √λ as diagonal elements. The number of transmitting antennas is N _T , the number of receiving antennas is N ^R , X is the smaller number of N _T and N _T , u1 to ux are N _T × 1 column vectors, and N _{T to} vx are N _R × 1. Assuming that the column vector and the superscript H represent conjugate transpose, the transfer coefficient matrix is represented by the following arithmetic expressions (1) and (2).

Here, the element Hij of the transmission coefficient matrix is a transmission coefficient when transmitted by the transmission antenna j and received by the reception antenna i. Next, K pieces having larger singular values are selected, column vectors v1 to vL. Of unitary matrix V corresponding to the singular values are selected as weights, and each column vector is used from K signals T1 to TL. Signals S _{1 to} S _N transmitted from each antenna element are formed by the following arithmetic expression (3).

The unitary matrix V is an eigenvector of the product HH ^H of the transfer coefficient matrix H and its complex conjugate transpose matrix H ^H.
By performing transmission using such weighting, it is possible to realize a transmission speed that is several times the number of antennas without increasing the frequency band, and to obtain a directivity gain. Since a good beam can be selected by forming (N ≧ K), a diversity effect can also be obtained. Transmission diversity is either Space-Time-Transmission-Diversity (Tachikawa's “W-CDMA mobile communication system” Maruzen) or Space-Time-Block-Code (Naguib, et.al “Space-Time-Block-Codes: code design criteria), Delay Diversity, etc. can be used.
Miyashita, K .; Nishimura, T .; Ohgane, T .; Ogawa, Y; Takatori, Y; Keizo Cho; "High data-rate transmission with eigenbeam-space division multiplexing (E-SDM) in a MIMO channel," Vehicular Technology Conference, 2002. Proceedings. VTC 2002-Fall. 2002 IEEE / 56th, Volume: 3, 24-28 Sept. 2002 Pages: 1302-1306 vol. 3 Yasuhiro Kishino, Kazuhiro Uehara, Kenichi Kagoshima, "Examination of Diversity with Null Forming Beam" 1997 IEICE Society Conference B-1-25.

  As shown in FIG. 7, when the above weighting calculation is applied to the orthogonal wave frequency division multiplexing system, it is necessary to obtain the weight for each subcarrier. In general, the subcarriers in the orthogonal wave frequency division multiplexing system are set so that the propagation characteristics of each subcarrier are flat fading, about 50 carriers in a wireless LAN system, and several hundred to several in terrestrial digital broadcasting. About 1000 subcarriers are set (for example, “Matsue, supervised by Morikura,“ 802. High-speed wireless LAN textbook ”, IDG Japan, p132, 2003”, “Supervised by Hirose,“ Next-generation digital modulation and demodulation. Technology ", triceps, pp 145-193"). As described above, when calculation such as singular value decomposition is performed in order to obtain the above weighting for each of a large number of subcarriers, there is a problem that the hardware scale of the apparatus becomes very large.

In order to realize a space division multiplex transmission apparatus, a plurality of antenna elements are required. Actually, however, depending on the installation environment of the antenna, for example, as shown in FIGS. The place where it can be placed is limited. Here, a mounting example on a PC card, a mounting example on a notebook PC, and a mounting example on an access point are shown.
In general, in indoor propagation environments, it has been reported that antenna arrangements for realizing space division multiplex transmission should be horizontally arranged with a wide spacing between antenna elements (this fact is described by Tachikawa et al., Electronics Information Disclosure Society Society Conference B-1-46, September 2003)). However, as shown in FIG. 8, since the size of the antenna is generally determined by the size of the wavelength of the communication frequency, in practice, the element spacing normalized by the wavelength of the antenna is not necessarily increased, or the horizontal arrangement is performed. You can't just mount an antenna.

Also, in the antenna arrangement limited by the installation environment of the base station, the size of the terminal, etc., as described above, it is possible to obtain eigenvectors for each subcarrier and use them as weighting for transmission. There is a problem that the transmission characteristics of the space division multiplex transmission apparatus cannot be improved, as well as the viewpoint of simplifying the operation scale in the transmission apparatus as much as possible. The reason for this is that the index of transmission characteristics in the space division multiplex transmission apparatus is determined by how much the space of the propagation path is widened, and this size greatly affects the antenna configuration such as antenna arrangement and element spacing. Because.
If the environment of the propagation path space seems to be large relative to the antenna arrangement, the propagation characteristics between subcarriers are also greatly different, so the effect of obtaining eigenvectors for each subcarrier can be obtained, but the antenna arrangement is different, In an environment where the spread of the propagation path space does not appear to be large, the propagation characteristics between subcarriers are nearly uniform, and even if eigenvectors different between subcarriers are used as transmission weights, the transmission characteristics are not greatly improved. Therefore, in order to realize a broadband spatial division multiplex transmission apparatus in consideration of a limited antenna arrangement, it has been a problem to realize a method for easily obtaining transmission weights.

  The present invention has been made in view of the various circumstances described above, and the hardware scale for the calculation is obtained by simply and efficiently executing the calculation of the transmission weight for each subcarrier in consideration of the antenna arrangement. It is an object of the present invention to provide a spatial multiplexing transmission apparatus that can reduce the above.

  In order to solve the above-described problems, the present invention is a spatial multiplexing transmission apparatus that performs transmission by F frequency multiplexing and K spatial multiplexing using an orthogonal frequency division multiplexing scheme using N antenna elements. An antenna group selection unit that is connected to the antenna element and performs selection for separating the plurality of antenna elements into a plurality of groups of arbitrary combinations, and is obtained from signals input to the selected groups. A frequency correlation calculation unit that obtains a frequency correlation using the eigenvector and a correlation value for each antenna group obtained by the frequency correlation calculation unit, and a weight for determining the number of eigenvectors used for transmission weighting for each antenna group A serial determination unit, a serial parallel conversion unit that performs serial parallel conversion on the transmission signal and inputs the transmission signal for each group, and the weight determination unit. Characterized by comprising a multi-beam forming portion, the to be transmitted by multiplying the transmission signal output weighted values are from the group of the serial-parallel conversion unit.

  In the present invention, the frequency correlation calculation unit generates a transfer coefficient matrix from at least two of the frequency-multiplexed received signals for each antenna selected by the antenna group selection unit from the antenna element. A coefficient matrix estimating means; an eigenvector calculating means for calculating eigenvectors obtained from the generated transfer coefficient matrix from at least two of the frequency multiplexes; and calculating a correlation value between the eigenvectors between the calculated frequency multiplexes. And a correlation calculation means.

  In the present invention, the weight determination unit may determine the number of eigenvectors in the transmission weight value for the frequency multiplexing number used for each antenna group based on the correlation bandwidth of the correlation value obtained from the frequency correlation calculation unit. It is characterized by determining.

  Further, in the present invention, the antenna element is composed of a vertically arranged antenna element group and a horizontally arranged antenna element group, and the antenna group selecting unit sets the vertically arranged antenna group and the horizontally arranged antenna group as the same antenna group. The weighting determination unit selects for classification, and sets a frequency multiplexing interval with a common eigenvector value based on a correlation bandwidth obtained between the vertically arranged antenna group and the horizontally arranged antenna group. It is characterized by.

  The present invention also relates to an apparatus for spatial multiplexing transmission that performs transmission by F frequency multiplexing using orthogonal frequency division multiplexing and K spatial multiplexing using N element antenna elements, in the vertical and horizontal directions. Connected to the antenna elements arranged in the vertical direction, and an antenna group selection unit that separates the plurality of antenna elements into a vertical element group and a horizontal element group, and perpendicular to the antenna element group arranged in the vertical direction. A weight determining unit for vertical arrangement for setting a weighting value so that a horizontal direction of the combined directivity of the arranged elements is in a substantially null state, and a weight determining unit for vertical arrangement with respect to the group of horizontally arranged antenna elements The eigenvector obtained from the transfer coefficient matrix in any one frequency carrier is obtained from the input signal obtained by taking into account the output result synthesized using the weighting values obtained in step 1). An arrangement weight determination unit, a serial / parallel conversion unit that serial-parallel converts a signal to be transmitted and inputs the transmission signal for each of the horizontally arranged antenna element groups, and a vertical arrangement and horizontal arrangement weight determination unit And a multi-beam forming unit that multiplies the transmission value output from each group of the serial / parallel conversion unit and transmits the resultant signal.

According to the present invention, by determining the number of transmission weights required using the frequency correlation for the eigenvector, the eigenvector calculation can be reduced compared to the conventional example in which only the number of subcarriers is required, For this reason, it is possible to expect a significant reduction in the amount of calculation, and the hardware scale required for this can be reduced.
Also, by dividing the weighting method used for transmission into vertical and horizontal antenna groups, weighting is set with only a fixed value for vertical arrangement, and any single subcarrier for horizontal arrangement. Since the weighting can be determined only by the eigenvector calculation focusing on the above, the amount of calculation for determining the transmission weighting can be greatly reduced, and the hardware scale can be reduced.

Hereinafter, the first embodiment and the second embodiment will be described in detail with reference to the drawings.
(First embodiment)
The configuration of the spatial multiplexing transmission apparatus according to the first embodiment of the present invention is shown in FIG. In the first embodiment, the total amount of calculation is reduced by omitting the number of transmission weights during wideband transmission using a difference in frequency correlation due to a difference in antenna arrangement. Here, an N-element antenna element 21 is provided. Moreover, although the antenna element 21 is comprised by the element of the perpendicular | vertical and horizontal arrangement | positioning, this is not limited to these arrangement | positioning.
In FIG. 1, Fourier transform is performed by the Fourier transform processing unit 13 in order to perform demodulation in the orthogonal frequency division multiplexing system on the signal received by the receiver 12. An antenna group selection unit 14 is provided to select an antenna element group in order to perform a frequency correlation calculation to be described later on the received signal of each subcarrier converted by the Fourier transform processing unit 13. This antenna element group is provided in order to investigate how different the frequency correlation differs depending on the combination of antennas. The antenna group selection unit 14 selects, for example, a combination of vertical arrangements, a combination of horizontal arrangements, adjacent elements, or the like, for each combination of antenna groups. However, although M types are prepared for the combinations here, the combination method is not particularly limited.

A frequency correlation calculation unit 15 is connected to the antenna group selection unit 14. FIG. 2 shows details of the frequency correlation calculation unit. As shown in FIG. 2, assuming that the received signal vector in antenna group m and frequency multiplex number j is Xmj, transfer coefficient matrix estimation means 151 obtains the transfer coefficient matrix described above from received signal vector Xmj. However, here, unlike the conventional example, the transfer coefficient matrix is not acquired for all frequency multiplexing numbers. In order to calculate a frequency correlation, which will be described later, it is only necessary to obtain a transfer coefficient matrix for at least two frequency multiplexing numbers. For example, assuming that the number of frequency multiplexing is L, two transfer coefficient matrices of subcarrier f1 and subcarrier fL that are most distant from each other may be acquired. In order to increase the accuracy, the transfer coefficient matrix in the center subcarrier may be obtained together.
Thereafter, an eigenvector is obtained from each transfer coefficient matrix in each antenna group by the eigenvector calculation means 152. The method for obtaining the eigenvector can be obtained by the same method as the method described in the arithmetic expressions (1) to (3) as in the prior art.

From the obtained eigenvector, the correlation calculation means 153 obtains the frequency correlation of the eigenvector between subcarriers in frequency multiplexing. If the eigenvectors of subcarrier # 1 and subcarrier #L are e ₁ and e _L , respectively, frequency correlation ρ can be given by the following arithmetic expression (4).

Next, the frequency correlation given by the above equation (4) is calculated for each antenna element group. When the correlation value of the frequency correlation is large, it can be considered that the propagation paths between the subcarriers in frequency multiplexing are almost the same. That is, the eigenvectors used for transmission may be the same among the subcarriers, and the portion obtained by the conventional calculation can be omitted. Conversely, if the frequency correlation is a small value, it can be determined that the propagation paths between the subcarriers are different. In this case, the eigenvector used for transmission is obtained for each subcarrier.
Strictly speaking, when the calculation formula (4) is obtained for each adjacent subcarrier interval, a strict correlation value is obtained. In this case, however, an eigenvector must be finally obtained for each subcarrier. Here, in order to avoid this, as described above, the calculation formula (4) is obtained between the subcarriers # 1 and #L, or between the subcarriers in the middle thereof, and thereafter, complementation is performed. To estimate the correlation value between them. Therefore, in the embodiment of the present invention, it is possible to estimate the number of transmission weights to be used for transmission by obtaining the frequency correlation without obtaining the transfer coefficient matrix and eigenvector in all subcarriers.

  Specifically, the weighting determination unit 16 shown in FIG. 1 calculates the above frequency correlation, and then determines the number of eigenvectors used for transmission for each antenna group. This dispersion is calculated from the correlation bandwidth obtained from the frequency correlation with respect to the frequency interval between the subcarriers. The correlation bandwidth usually indicates a frequency interval at which the frequency correlation value becomes a value of about 0.7 or 0.9. The number SL of eigenvectors used for transmission for each antenna group when the correlation bandwidth is BW, the number of subcarriers is L, and the signal band of one subcarrier is SBW is given by the following arithmetic expression (5).

Next, from the result obtained by the arithmetic expression (5), SL eigenvectors are calculated for each antenna group, and the SL eigenvectors are divided into L subcarriers. input. For example, FIG. 1 shows an example in which the correlation bandwidth of the frequency correlation of the antenna group # 1 is small and an eigenvector is set for each subcarrier. On the other hand, for antenna group #M, since the correlation bandwidth is large, an example in which a common eigenvector is set for each subcarrier is shown. For antenna group # 2, an example is shown in which a common eigenvector is used for every two subcarriers.
The multi-beam forming unit 18 multiplies the input eigenvector and the serially parallel transmission signal, and adds the multiplied signals for each antenna element. Finally, the signal output from the multi-beam forming unit 18 is subjected to inverse Fourier transform by the inverse Fourier transform generation unit 19, and this signal is transmitted via the transmitter 20 via the transmission / reception selection unit 11.

  According to the first embodiment described above, in order to determine the number of transmission weights required using the frequency correlation with respect to the eigenvector, the number of subcarriers L conventionally required to calculate eigenvectors is SL. The amount of calculation can be greatly reduced. For this reason, the hardware scale required for calculation can be reduced.

(Second Embodiment)
FIG. 3 shows the configuration of the spatial multiplexing transmission apparatus according to the second embodiment of the present invention. In FIG. 3, blocks with the same numbers as those in FIG. 1 are the same as those shown in FIG. The difference in configuration from FIG. 1 in which the first embodiment is shown here is based on the premise that the antenna elements are arranged in the vertical direction and the horizontal direction, and the antenna group selection unit (vertical / horizontal arrangement antenna group) In the selection unit 14), the antenna group is selected as the antenna element group of the vertical arrangement and the horizontal arrangement. The weight determination unit 16 shown in FIG. 3 includes a weight determination unit 161 for vertical arrangement elements and a weight determination unit 162 for horizontal arrangement elements.
The second embodiment is configured to reduce the amount of calculation of eigenvectors necessary for multi-beam formation by using the difference in antenna element arrangement between vertical and horizontal arrangement. Hereinafter, the second embodiment will be described in detail with reference to FIG.

In an environment such as an indoor environment, it is generally known that the angle spread of incoming waves differs depending on whether the antenna is arranged horizontally or vertically. FIG. 4 is a diagram showing the relationship between the delay time in the horizontal direction and the vertical direction, the arrival direction, and the received power in a room of 10 m × 10 m × 3 m (vertical × horizontal × height). The horizontal direction is shown in (a) and the vertical direction is shown in (b). The results shown in FIGS. 4A and 4B are obtained by calculation using a geometric optical method with a carrier frequency of 5 GHz. As can be seen from FIGS. 4 (a) and 4 (b), the angular spread for a long delayed wave is greatly different between the vertical direction and the horizontal direction.
In a wideband transmission environment, it is known that a long delay wave affects transmission quality. The directivity of the vertical plane is directed downward, and the horizontal direction is vertical so that the directivity is almost null. It has been reported that by weighting the amplitude and phase of the antenna elements on the surface, long delay waves coming from the horizontal direction can be removed with antenna directivity, and transmission quality can be greatly improved (Non-Patent Document) 2).
On the other hand, in the horizontal direction, even a long delayed wave has a certain degree of angular spread, and thus the long delayed wave cannot be removed with fixed directivity as in the vertical direction control.

The weight determination unit 16 in the second embodiment performs a control method using the difference in propagation characteristics caused by the difference between the vertical arrangement and the horizontal arrangement. FIG. 5 shows details of the internal configuration of the weight determination unit 16 in FIG.
In FIG. 5, the weights in the antenna elements and the vertically arranged elements are connected, but this is shown for convenience in explaining the principle. In fact, the connections shown in FIG. 3 are correct connections. For convenience, the number of antenna elements in the vertical direction is four and the number of antenna elements in the horizontal direction is J, but this number is not particularly limited. Hereinafter, the weight determination operation in the weight determination unit 16 will be described with reference to FIG.

In FIG. 5, the weight determining unit 16 first determines the weight for the antenna elements arranged in the vertical direction. As described above, since a long delayed wave in the vertical direction arrives from substantially the horizontal direction, weighting is performed so that the directivity in the horizontal direction, which is determined in advance by the number of antenna elements and the element spacing, is approximately Null. A value is prepared in advance in the weight setting memory 621, a weight value is set from the weight setting memory 621, weighting is performed for each vertically arranged antenna element, and then a combined output in the vertically arranged element is obtained. . From this combined output, the long delay wave component is substantially removed, and the propagation path is composed of only a short delay wave.
Next, the weighting determination unit 61 for horizontal arrangement takes out the reception signal obtained from the above-described combined output for each horizontal arrangement element component, and estimates the transfer coefficient matrix between the horizontal arrangement elements by the transfer coefficient matrix estimation unit 611. An eigenvector calculation unit 612 calculates an eigenvector from the transfer coefficient matrix. The important point here is that since the propagation environment can be regarded as a flat fading environment, it is not necessary to obtain a transfer coefficient matrix in all frequency-multiplexed subcarriers as in the conventional method. In the second embodiment of the present invention shown in FIG. 3, the transfer coefficient matrix is obtained using the information of subcarrier # 1, but in reality, information on any subcarrier between subcarriers # 1 to #L. The transfer coefficient matrix may be obtained from That is, here, it is possible to estimate the transfer coefficient matrix and reduce the calculation for obtaining the eigenvector to 1 / L compared to the conventional method.

  Returning to FIG. 3, finally, the weight obtained by the weight determination unit 16 is multiplied by the transmission signal parallel-converted by the serial / parallel conversion unit 17 by the multi-beam forming unit 18 and multiplied. Add the results for each antenna element. The signal output from the multi-beam forming unit 18 is subjected to inverse Fourier transform by the inverse Fourier transform generation unit 19, and this signal is transmitted via the transmitter 20 via the transmission / reception selection unit 11.

  According to the second embodiment of the present invention, the weighting method used for transmission is divided into vertically arranged and horizontally arranged antenna groups, so that the weighting is set with only a fixed value for the vertically arranged, and the horizontally arranged Since the weighting can be determined only by the eigenvector calculation focusing on one arbitrary subcarrier, the calculation for determining the transmission weight can be greatly reduced compared to the conventional method. Of course, the hardware scale for this purpose can also be reduced.

  As described above, the present invention reduces the total amount of calculation by omitting the number of transmission weights during wideband transmission using the difference in frequency correlation due to the difference in antenna arrangement (first embodiment), Alternatively, the amount of computation of eigenvectors necessary for multi-beam formation is reduced by utilizing the difference in antenna element arrangement between vertical and horizontal arrangements (second embodiment), thereby reducing the hardware scale. It is.

It is a figure which shows the structure of the apparatus for space division multiplex transmission based on the 1st Embodiment of this invention. It is a figure which shows an example of an internal structure of the frequency correlation calculating part shown in FIG. It is a figure which shows the structure of the apparatus for space division multiplex transmission based on the 2nd Embodiment of this invention. It is the figure which displayed the graph of an example of the relationship between the arrival direction of the vertical direction in an indoor environment, the horizontal direction, delay time, and received power by the geometric method. It is a figure showing the relationship between the weight determination part for vertical arrangement | positioning shown in FIG. 3, and the weight determination part for horizontal arrangement | positioning. It is a figure which shows an example of a structure of the conventional apparatus for space division multiplex transmission. It is a figure which shows an example of a structure of the conventional apparatus for space division multiplex transmission. It is a figure which shows an example of the form in actual antenna arrangement | positioning.

Explanation of symbols

DESCRIPTION OF SYMBOLS 11 ... Transmission / reception selection part, 12 ... Receiver, 13 ... Fourier-transform processing part, 14 ... Antenna group selection part, 15 ... Frequency correlation calculation part, 16 ... Weight determination part, 17 ... Serial parallel conversion part, 18 ... Multi-beam Forming unit, 19 ... Inverse Fourier transform generation unit, 20 ... Transmitter, 21 ... Antenna element

Claims (5)

A spatial multiplexing transmission apparatus that performs transmission by F frequency multiplexing and K spatial multiplexing using an orthogonal frequency division multiplexing system using N element antenna elements,
An antenna group selection unit that is connected to the antenna element and performs selection to sort the plurality of antenna elements into a plurality of groups of arbitrary combinations;
A frequency correlation calculation unit for obtaining a frequency correlation using an eigenvector obtained from signals input to each of the selected groups;
A weight determining unit that determines the number of eigenvectors used for transmission weighting for each antenna group from the correlation value for each antenna group obtained by the frequency correlation calculating unit;
Serial parallel conversion of transmission signals, serial parallel conversion unit for inputting the transmission signal for each group,
A multi-beam forming unit that multiplies and transmits the weight value obtained by the weight determination unit and the transmission signal output from each group of the serial-parallel conversion unit;
A spatial multiplexing transmission apparatus comprising: The frequency correlation calculator is
Transfer coefficient matrix estimation means for generating a transfer coefficient matrix from at least two of the frequency-multiplexed reception signals for each antenna selected by the antenna group selection unit from the antenna element;
Eigenvector computing means for calculating eigenvectors obtained from the generated transfer coefficient matrix from at least two of the frequency multiplexes;
Correlation calculating means for calculating a correlation value between eigenvectors between the calculated frequency multiplexes;
The spatial multiplexing transmission apparatus according to claim 1, comprising: The weight determination unit
3. The number of eigenvectors in a transmission weight value for the frequency multiplexing number used for each antenna group is determined based on a correlation bandwidth of a correlation value obtained from the frequency correlation calculation unit. The spatial multiplexing transmission device described in 1. The antenna element is composed of vertically arranged and horizontally arranged antenna element groups,
The antenna group selection unit selects the vertically arranged antenna group and the horizontally arranged antenna group as the same antenna group for classification,
The weighting determination unit sets a frequency multiplexing interval having a common eigenvector value based on a correlation bandwidth obtained between the vertically arranged antenna group and the horizontally arranged antenna group. The spatial multiplexing transmission apparatus according to claim 1. An apparatus for spatial multiplexing transmission that performs transmission by F frequency multiplexing using orthogonal frequency division multiplexing and K spatial multiplexing using N element antenna elements,
An antenna group selector connected to the antenna elements arranged in a vertical direction and a horizontal direction, and separating the plurality of antenna elements into a vertical element and a horizontal element group;
A weight determination unit for vertical arrangement that sets a weight value so that a horizontal direction of the combined directivity of the vertical arrangement elements is substantially null with respect to the antenna element group arranged in the vertical direction;
From an input signal obtained by considering an output result synthesized using a weighting value obtained by the weighting determination unit for vertical arrangement with respect to the group of horizontally arranged antenna elements, in any one frequency carrier A horizontal arrangement weighting determination unit for obtaining an eigenvector obtained from a transfer coefficient matrix; serial-parallel conversion of a signal to be transmitted; and a serial-parallel conversion unit for inputting the transmission signal for each of the horizontal arrangement antenna element groups;
A multi-beam forming unit that multiplies and transmits the weight value obtained by the vertical arrangement and horizontal arrangement weight determination unit and a transmission signal output from each group of the serial-parallel conversion unit;
A spatial multiplexing transmission apparatus comprising:

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