JP3818279B2 - Driving method of display panel - Google Patents

Description

[0001]
BACKGROUND OF THE INVENTION
The present invention belongs to a technical field of a transistor circuit including a plurality of transistors such as a thin film transistor (hereinafter referred to as TFT), a field effect transistor, and a bipolar transistor, and in particular, a source and a drain according to a voltage supplied to a gate. Transistor circuit comprising a driving transistor for controlling a driving current supplied to a driven element such as a current control type (current driving type) element via the source and drain by controlling the conductance between them Belongs to the technical field.
[0002]
[Prior art]
In general, a transistor has a voltage-current characteristic and a threshold value depending on various conditions such as a semiconductor film quality, film thickness, impurity concentration, diffusion region, gate insulating film quality, film thickness, operating temperature, etc. Variations occur in greater or lesser amounts. In the case of a bipolar transistor using crystal silicon, such a variation in threshold value is relatively small, but in the case of a TFT, such a variation is usually large. In particular, in the case of a large number of TFTs formed over a wide range on a TFT array substrate in a display panel such as a liquid crystal panel or an EL panel, such a variation in current-voltage characteristics and threshold values becomes very large. There are many. For example, even if this type of TFT is manufactured so that the threshold value is about 2V (volt) (+ 2V for N channel, -2V for P channel), the variation may be about ± several volts.
[0003]
Here, in the case of a voltage control (voltage drive) method for controlling the voltage of a pixel portion made of a liquid crystal or the like as in the case of a so-called TFT liquid crystal panel, the voltage-current characteristics in the driving TFT provided in each pixel portion It is relatively rare that variations in threshold value become a problem. In other words, in this case, even if there is some variation in the current-voltage characteristics and threshold value of the TFT, the accuracy of the voltage supplied from the outside to each pixel portion via the TFT can be increased as long as a sufficient switching time is provided. This is because the display density and brightness in each pixel portion can be controlled with high accuracy by increasing the value. Therefore, even in display TFT liquid crystal panels and the like where display density and brightness unevenness in each pixel portion are regarded as important, high-quality images are obtained by using TFTs having relatively large variations in current-voltage characteristics and threshold values. Display and so on.
[0004]
On the other hand, in recent years, a display panel having a current-controlled light emitting element such as an organic EL that emits light so that brightness changes according to the amount of current supplied in a pixel portion has been developed, and uses a backlight or reflected light. Therefore, the display panel is attracting attention as a display panel that can display images without power consumption, has low power consumption, has little viewing angle dependency, and sometimes realizes bendability. Also in the case of this EL panel, a driving TFT is used in each pixel portion in order to perform active matrix driving. For example, the drive TFT drain is connected to the EL element through the hole injection electrode, and the drive is supplied to the EL element from the power supply wiring connected to the source in accordance with the voltage of the data signal applied to the gate. It is configured to control (change) the current. When the driving TFT is used in this way, the driving current flowing through the EL element is controlled by controlling the conductance between the source and the drain in accordance with the voltage change of the input signal, and the brightness (luminance) in each pixel portion. Can be changed, and an image can be displayed.
[0005]
[Problems to be solved by the invention]
However, particularly in the case of a current control type element such as the EL panel described above, variations in voltage-current characteristics and threshold values in the driving TFT provided in each pixel portion become a problem. That is, in this case, even if the voltage accuracy of the data signal supplied to the driving TFT from the outside is increased to some extent, variations in the voltage / current characteristics and threshold values in the driving TFT are regarded as variations in the driving current with respect to the data signal. Since it appears as it is, the accuracy of the drive current is reduced. As a result, the brightness in each pixel portion also varies according to variations in the threshold value of the driving TFT. In particular, in the current low-temperature polysilicon TFT manufacturing technology, such variations in voltage-current characteristics and threshold values occur to a considerable degree, and this problem is very large in practical use.
[0006]
In order to solve this problem, if each TFT is manufactured so as to reduce variations in voltage-current characteristics and threshold values, the yield is lowered, and in particular, a device configured using a large number of TFTs such as a display panel. In this case, the yield is drastically reduced, which is contrary to the general demand for cost reduction. Alternatively, it is almost impossible to manufacture a TFT that reduces such variations. In addition, even if a circuit for compensating for variations in current-voltage characteristics and threshold values in each TFT is separately provided, the device is still complicated and large, and the power consumption is increased. In an arrayed display panel, it is expected that the yield will decrease again, or it will be difficult to meet the recent demands for lower power consumption and smaller and lighter devices.
[0007]
The present invention has been made in view of the above-described problems, and is a transistor circuit that performs conductance control in a driving transistor in accordance with the voltage of an input signal, and the conductance can be controlled by a relatively low voltage input signal. In addition, a transistor circuit that can compensate for variations in current-voltage characteristics and threshold characteristics of a driving transistor by using a relatively small number of transistors with relatively small power consumption, and a display panel using the transistor circuit Another object is to provide an electronic device.
[0008]
[Means for Solving the Problems]
The first array substrate of the present invention includes a plurality of scanning lines, a plurality of data lines, a plurality of transistor circuits provided corresponding to intersections of the plurality of scanning lines and the plurality of data lines, Each of the plurality of transistor circuits includes a first gate, a first source, and a first drain, and the first transistor is connected between the first source and the first drain according to an input signal supplied to the first gate. The first gate is reset to a predetermined voltage before the input signal is supplied, including a driving transistor whose conductance is controlled.
The second array substrate of the present invention includes a plurality of scanning lines, a plurality of data lines, a plurality of transistor circuits provided corresponding to intersections of the plurality of scanning lines and the plurality of data lines, Each of the plurality of transistor circuits includes a first gate, a first source, and a first drain, and the first transistor is connected between the first source and the first drain according to an input signal supplied to the first gate. Including a driving transistor whose conductance is controlled, and including reset means for setting the first gate to a predetermined voltage before the input signal is supplied.
The third array substrate of the present invention includes a plurality of scanning lines, a plurality of data lines, a plurality of transistor circuits provided corresponding to intersections of the plurality of scanning lines and the plurality of data lines, Each of the plurality of transistor circuits includes a first gate, a first source, and a first drain, and the first transistor is connected between the first source and the first drain according to an input signal supplied to the first gate. Including a driving transistor whose conductance is controlled, and having reset means for supplying a reset signal to the first gate before the input signal is supplied.
In the above array substrate, each of the plurality of transistor circuits may compensate for variations in threshold values of the driving transistors when the input signal is supplied.
The array substrate may include a compensation transistor that includes a second gate, a second source, and a second drain, and the second gate is connected to the first gate.
In the array substrate, the reset means is a reset transistor having a third gate, a third source, and a third drain provided in each of the plurality of transistor circuits, and the third source and the third drain. Is connected to the first gate, and when a reset timing signal is supplied to the third gate before the input signal is supplied, the reset signal is supplied to the first gate via the reset transistor. It may be supplied.
In the array substrate, each of the plurality of transistor circuits further includes a switching transistor having a fourth gate, a fourth source, and a fourth drain, and a scanning line corresponding to the fourth gate among the plurality of scanning lines. Are preferably connected.
In the array substrate, the reset signal may be set to a voltage that is greater than a maximum voltage of the input signal by a threshold voltage of the compensation transistor.
The transistor circuit of the present invention has a first gate, a first source, and a first drain, and conductance between the first source and the first drain is controlled in accordance with an input signal supplied to the first gate. Including a driving transistor
A reset means for resetting the first gate to a predetermined voltage before the input signal is supplied is provided.
A first display panel of the present invention includes the above-described array substrate and a light emitting element connected to one of the first source and the drain.
In the above display panel, a current driven element may be used instead of the light emitting element.
The second display panel of the present invention includes a plurality of scanning lines, a plurality of data lines, a plurality of transistor circuits provided corresponding to intersections of the plurality of scanning lines and the plurality of data lines, Each of the plurality of transistor circuits includes a first gate, a first source, and a first drain, and an input supplied to the first gate via a corresponding data line among the plurality of data lines. A drive transistor whose conductance is controlled between the first source and the first drain in response to a signal; and a light emitting element connected to either the first source or the first drain; Before the first gate is supplied to the first gate, the first gate is reset to a predetermined voltage.
The third display panel of the present invention includes a plurality of scanning lines, a plurality of data lines, a plurality of transistor circuits provided corresponding to intersections of the plurality of scanning lines and the plurality of data lines, Each of the plurality of transistor circuits includes a first gate, a first source, and a first drain, and an input supplied to the first gate via a corresponding data line among the plurality of data lines. A drive transistor whose conductance is controlled between the first source and the first drain in response to a signal; and a light emitting element connected to either the first source or the first drain; Is provided with reset means for resetting the first gate to a predetermined voltage before being supplied to the first gate.
A first display panel driving method of the present invention is a display panel driving method including a scanning line, a data line, and a transistor circuit, and includes a first gate, a first source, and a first source included in the transistor circuit. An input signal is supplied to the first gate of the driving transistor having one drain via the data line, and the first gate is reset to a predetermined voltage before supplying the input signal. .
A second display panel driving method of the present invention is a display panel driving method including a scanning line, a data line, and a transistor circuit, and a scanning signal is included in the transistor circuit via the scanning line. The switching transistor is supplied to the gate of the switching transistor, and is input to the first gate of the driving transistor having the first gate, the first source, and the first drain included in the transistor circuit through the data line and the switching transistor. After supplying a signal and supplying the scanning signal, a reset timing signal is supplied to a gate of a reset transistor, and a reset signal is supplied to the first gate through the reset transistor.
An electronic apparatus according to the present invention includes the display panel described above.
In order to solve the above-described problem, the transistor circuit of the present invention includes a first gate, a first source, and a first drain, and the first source and the first source according to the voltage of the input signal supplied to the first gate. A driving transistor whose conductance is controlled between the first drain, a second gate, a second source, and a second drain; and the second gate is connected to one of the second source and the second drain. The first signal is supplied to the first gate through the second source and the second drain, and the first gate is arranged in such a direction as to allow charge transfer in the direction of decreasing the conductance with respect to the first gate. And a compensation transistor connected to the gate.
[0009]
According to the transistor circuit of the present invention, one of the second source and the second drain of the compensation transistor is connected to the first gate of the driving transistor, and driving is performed via the second source and the second drain. An input signal is supplied to the first gate of the transistor for use. In the driving transistor, the conductance between the first source and the first drain is controlled according to the voltage of the input signal supplied to the first gate. Here, in the compensation transistor, the second gate is connected to the second drain, and the first gate is arranged in such a direction as to allow charge transfer in the direction of decreasing the conductance between the first source and the first drain with respect to the first gate. Connected to the gate. That is, the compensation transistor has a diode characteristic. For example, if the driving transistor is an N-channel type, it can be energized only in the direction from the first gate to the input signal source. Alternatively, if the driving transistor is a P-channel type, it can be energized in the direction from the input signal source to the first gate.
[0010]
For this reason, when the input signal is supplied to the transistor circuit, the gate voltage of the first gate is equal to the threshold value of the compensation transistor compared to the voltage of the input signal at the time of input to the compensation transistor. The voltage is boosted to the side where the conductance of the driving transistor is increased. Therefore, in order to obtain a desired conductance in the driving transistor, an input signal having a voltage lower than the gate voltage corresponding to the conductance by the threshold value (voltage) of the compensating transistor is supplied via the compensating transistor. You can do it. In this way, the gate voltage for the input signal can be boosted by the threshold value (voltage) of the compensation transistor, so that equivalent conductance control can be performed with a lower input signal voltage compared to the case without the compensation transistor. Can be done.
[0011]
In general, this input signal often has a higher frequency than other signals, and if a lower input signal is sufficient, a considerable reduction in power consumption can be expected.
[0012]
Further, the voltage of the input signal is boosted by the compensating transistor to the gate voltage at the first gate in this way through the source and drain whose conductance is controlled in the driving transistor when viewed as the entire transistor circuit. The threshold value of the input signal relative to the flowing drive current is lowered from the threshold voltage of the driving transistor by the threshold voltage of the compensation transistor, which is a boost from the input voltage to the gate voltage. That is, in the threshold value of the input voltage with respect to the drive current, the threshold value of the compensation transistor and the threshold value of the drive transistor are offset. Therefore, the threshold value of the input signal with respect to the drive current can be brought close to zero by bringing the threshold characteristics and voltage-current characteristics of the two closer.
[0013]
Furthermore, by canceling out the threshold value of the driving transistor and the threshold value of the compensating transistor in the entire transistor circuit in this way, the transistor circuit is independent of the magnitude of the threshold value of the driving transistor. The threshold value of the input signal as a whole can be brought close to a certain value (zero). That is, when a plurality of transistor circuits are formed using a plurality of driving transistors having different threshold values, the threshold values of the driving transistor and the compensating transistor in each transistor circuit are close to each other (ideal If the two are matched, the threshold difference between the transistor circuits is smaller than the threshold difference between the driving transistors (ideally, the difference is almost eliminated). ). Therefore, when creating a plurality of transistor circuits, it is possible to obtain a plurality of transistor circuits with little or no threshold variation even when a plurality of driving transistors having different threshold values are used. Become.
[0014]
In the transistor circuit according to the present invention, the reset signal having a voltage corresponding to a conductance value higher than the highest conductance value controlled according to the input signal with respect to the first gate is input to the first gate circuit. A reset means for supplying the signal before supplying the signal is provided.
[0015]
According to the transistor circuit of the present invention, before the input signal is supplied to the first gate of the driving transistor (or before the next input signal is supplied after one input signal is supplied), A reset signal having a voltage corresponding to a conductance value higher than the highest conductance value of the driving transistor controlled according to the input signal is supplied to the first gate by the reset means. As a result, the gate voltage of the driving transistor can be set to a constant value by the reset means regardless of the voltage value of the input signal, and in addition, after reset, the charge movement in the direction of decreasing the conductance can be performed. An input signal can be supplied to the first gate via the compensation transistor connected to the first gate.
[0016]
The transistor circuit of the present invention is characterized in that, in the above-described transistor circuit, the reset signal is set to a voltage larger than a maximum voltage of the input signal by a threshold voltage of the compensation transistor.
[0017]
According to the transistor circuit of the present invention, a reset signal having a voltage larger than the input signal is supplied to the first gate of the driving transistor by the reset means. In addition, since the voltage of the reset signal is set to be greater than the threshold voltage of the compensation transistor than the maximum voltage of the input signal, when the input signal is input after the reset, Regardless of the threshold value of the driving transistor, a voltage higher than the input signal voltage by the threshold voltage of the driving transistor is always applied to the first gate of the driving transistor via the compensation transistor. Can be supplied.
[0018]
In the transistor circuit of the present invention, in the above transistor circuit, the reset unit includes a third gate, a third source, and a third drain, and one of the third source and the third drain is connected to the first gate. And a reset transistor that supplies the reset signal to the first gate via the third source and the third drain when a reset timing signal is supplied to the third gate before the input signal is supplied. It is provided with.
[0019]
According to the transistor circuit of the present invention, when a reset timing signal is supplied to the third gate of the reset transistor, the reset transistor causes the reset signal to pass through the third source and the third drain. To the first gate. As a result, the gate voltage of the driving transistor can be reset to a constant value at the supply timing of the reset timing signal. Therefore, the subsequent operation described for the above-described transistor circuit is possible.
[0020]
The transistor circuit of the present invention is characterized in that, in the above-described transistor circuit, the driving transistor and the compensating transistor are the same type.
[0021]
According to the transistor circuit of the present invention, the driving transistor and the compensation transistor are the same type of transistor, but here, the “same type” means that if the driving transistor is an N-channel type, the compensation transistor If the transistor is also an N-channel type and the driving transistor is a P-channel type, it means that the compensation transistor is also a P-channel type. Accordingly, since the threshold value of the compensation transistor and the threshold value of the driving transistor are substantially equal to each other, these threshold values cancel each other out in the transistor circuit, and as a result, the input signal corresponding to the driving current. It is also possible to perform conductance control with the threshold value of approximately zero. Further, even when the plurality of transistor circuits are composed of a plurality of driving transistors having different threshold values, variations in threshold values can be compensated.
[0022]
Further, by making the design value including the channel width and channel length of the transistor, the device structure, the process condition, and the like equal between the driving transistor and the compensating transistor, more complete compensation can be achieved.
[0023]
The transistor circuit of the present invention has the fourth gate, the fourth source, and the fourth drain in the above-described transistor circuit, and when the switching timing signal is supplied to the fourth gate, the input signal is input to the fourth source, A switching transistor connected to supply to the compensation transistor through a fourth drain is further provided.
[0024]
According to the transistor circuit of the present invention, when the switching timing signal is supplied to the fourth gate of the switching transistor, the input signal is supplied to the compensation transistor through the fourth source and the fourth drain of the switching transistor. Is done. As a result, the input signal can be supplied to the driving transistor at the supply timing of the switching timing signal.
[0025]
The transistor circuit of the present invention is the above-described transistor circuit, further comprising a storage capacitor connected to the first gate.
[0026]
According to the transistor circuit of the present invention, when an input signal is supplied to the first gate, the voltage is held by the holding capacitor connected to the one gate. Therefore, even when the input signal is supplied for a certain period, the voltage applied to the first gate can be held for a longer period.
[0027]
In this configuration, it is possible to reduce the change in the potential applied to the first gate through the compensation transistor even when the switching transistor has a leakage current.
[0028]
The transistor circuit of the present invention is characterized in that, in the above-described transistor circuit, each of the transistors is formed of a thin film transistor formed over the same substrate.
[0029]
According to the transistor circuit of the present invention, the compensation thin film transistor can compensate for the influence of the current-voltage characteristic and the threshold characteristic on the drive current in the thin film transistor for driving formed on the same substrate. In particular, if both thin film transistors are formed on the same substrate in the same thin film formation process, the degree of similarity in characteristics between the two transistors generally increases, so that a plurality of transistor circuits with little variation in current-voltage characteristics and threshold characteristics are formed on the same substrate. Can be obtained above.
[0030]
The transistor circuit of the present invention is the above-described transistor circuit, wherein each of the transistors is composed of a bipolar transistor whose gate, source, and drain correspond to the base, collector, and emitter, respectively.
[0031]
According to the transistor circuit of the present invention, the compensation bipolar transistor can compensate for the influence of the current-voltage characteristics and the threshold characteristics on the drive current in the drive bipolar transistor. In particular, if both bipolar transistors are manufactured in the same manufacturing process, the degree of similarity in characteristics between the two transistors generally increases, so that it is possible to obtain a plurality of transistor circuits with little variation in current-voltage characteristics and threshold characteristics. .
[0032]
In the transistor circuit of the present invention, in the above transistor circuit, the input signal is a voltage signal whose voltage is controlled by an input signal source, and one of the first source and the first drain of the driving transistor is a current. It is connected to the control type element, and the current flowing through the current control type element is controlled by controlling the conductance.
[0033]
According to the transistor circuit of the present invention, when a voltage signal whose voltage is controlled by the input signal source is supplied as an input signal via the compensation transistor, the driving transistor responds to a voltage change of the voltage signal. The conductance between the first source and the first drain is controlled. Thereby, the current control type element connected to one of the first source and the first drain is current-controlled. Therefore, the current control type element can be driven with a relatively low voltage input signal, and a plurality of currents can be controlled regardless of variations in current-voltage characteristics and threshold characteristics among a plurality of driving transistors. It is also possible to accurately control the current of the driving element according to the voltage of the voltage signal.
[0034]
A display panel of the present invention includes a plurality of pixel portions each including the above-described transistor circuit and arranged in a matrix, and a current control type light emitting element is provided in each of the plurality of pixel portions as the current control type element. It is characterized by that.
[0035]
According to the display panel of the present invention, when an input signal is supplied via the compensation transistor in each pixel portion, the current control type light emitting element is current-controlled by the driving transistor according to the voltage of the input signal. Therefore, the brightness (brightness) of the current-controlled light-emitting element can be accurately controlled regardless of variations in current-voltage characteristics and threshold characteristics between driving transistors, and the entire screen display area of the display panel can be controlled. The uneven brightness can be reduced over a wide range. Further, the current-controlled light-emitting element can be controlled by a relatively low voltage input signal by boosting the gate voltage of the driving transistor using the compensation transistor.
[0036]
You may comprise an electronic device with the above-mentioned display panel.
[0037]
According to the above-described electronic device, since the above-described display panel is provided, it is possible to realize an electronic device that can be driven at a relatively low voltage with little uneven brightness over the entire surface of the display panel.
[0038]
Such an operation and other advantages of the present invention will become apparent from the embodiments described below.
[0039]
DETAILED DESCRIPTION OF THE INVENTION
Hereinafter, embodiments of the present invention will be described with reference to the drawings.
[0040]
(Transistor circuit)
First, an embodiment of a transistor circuit of the present invention will be described with reference to FIGS. FIG. 1 is a circuit diagram of a transistor circuit in this embodiment, and FIGS. 2A and 2B are timing charts showing timings and voltages of various signals in the transistor circuit, respectively.
[0041]
In FIG. 1, a transistor circuit 100 includes a driving TFT 110 (P channel type), a compensation TFT 120 (P channel type), a reset TFT 130 (N channel type), and a switching TFT 140 (N channel type). Yes. Hereinafter, the configuration of each transistor will be described in order.
[0042]
First, the driving TFT 110 that constitutes an example of the driving transistor includes a source 112 and a drain according to a gate voltage Vg applied to the gate 111 based on an input signal supplied via the switching TFT 140 and the compensation TFT 120. The conductance between 113 is controlled.
[0043]
In the compensation TFT 120 that constitutes an example of the compensation transistor, the gate 121 is connected to one of the source 122 and the drain 123 (the drain 123 in FIG. 1). That is, the compensation TFT 120 is so-called diode-connected. Then, the compensation transistor 120 is arranged in such a direction as to allow charge movement in a direction in which conductance is lowered with respect to the gate 111 so that an input signal is supplied to the gate 111 via the source 122 and the drain 123 (in FIG. 1). , The drain 123 side) is connected to the gate 111.
[0044]
In the reset TFT 130 that constitutes an example of the reset means, one of the source 132 and the drain 133 (the drain 133 in FIG. 1) is connected to the gate 111, and the gate 131 resets the voltage Vrscan as an example of the reset timing signal. When a scanning signal (hereinafter referred to as reset scanning signal Vrscan) is supplied before the input signal Vsig is supplied, a reset signal of voltage Vrsig (hereinafter referred to as reset signal Vrsig) is supplied to the gate 111 via the source 132 and drain 133. It is comprised so that it may supply.
[0045]
The switching TFT 140 that constitutes an example of a switching transistor receives an input signal (the voltage Vsig) when a scanning signal of a voltage Vscan (hereinafter referred to as a scanning signal Vscan) as an example of a switching timing signal is supplied to the gate 141. Hereinafter, the input signal Vsig) is connected between the input signal source and the compensation TFT 120 so as to be supplied to the compensation TFT 120 via the source 142 and the drain 143.
[0046]
One end of a current control type (current drive type) element 500 such as an EL element is connected to the source 112 of the driving transistor 110, and a negative potential of a predetermined potential is connected to the other end of the current control type element 500. The power source -Vc is connected. A positive power source + Vc having a predetermined potential is connected to the drain 113 of the driving transistor 110. Therefore, when the conductance control between the source 112 and the drain 113 is performed in the drive transistor 110, the drive current Id flowing through the current control type element 500 is controlled (that is, the drive current Id changes according to the change in conductance). .
[0047]
Further, a storage capacitor 160 is connected to the gate 111 of the driving transistor 110. For this reason, the gate voltage Vg once applied is held by the holding capacitor 160.
[0048]
Next, the operation of the transistor circuit 100 configured as described above will be described with reference to FIGS. 2 and 3 together with FIG.
[0049]
As shown in FIG. 2A, when the reset scanning signal Vrscan is input to the reset TFT 130, the reset TFT 130 is turned on, and the reset signal Vrsig is supplied to the gate 111 of the drive TFT 110. The gate voltage Vg of the gate 111 is set to a level substantially equal to the voltage Vrsig of the reset signal Vrsig. As a result, the gate voltage Vg of the driving TFT 110 can be reset to a constant voltage (that is, the voltage Vrsig) at the supply timing of the reset scanning signal Vrsig regardless of the magnitude of the voltage Vsig of the input signal Vsig.
[0050]
When the reset period ends and the scanning signal Vscan is supplied to the switching TFT 140, the switching TFT 140 is turned on, and the data signal Vsig is supplied to the gate 111 of the driving TFT 110 via the compensation TFT 120. Supplied. In this embodiment, since the gate 121 is connected to the drain 123 (that is, diode-connected) in the compensation TFT 120 in particular, a negative voltage is applied to the gate 111 to make it pass. The gate voltage Vg in the driving TFT 110, which is a P-channel TFT, is stepped down to the negative voltage side by the threshold voltage Vth2 of the compensation TFT 120 from the voltage Vsig of the data signal Vsig. The gate voltage Vg thus stepped down is held during the driving period by the holding capacitor 160 even after the supply of the scanning signal Vscan and the input signal Vsig is stopped.
[0051]
It should be noted that the reset period is sufficient if the gate voltage Vg is equal to the voltage Vrsig of the reset signal Vrsig. For this reason, the driving period can be set much longer than the reset period, so that even if the driving TFT 110 is set to the pass state by the reset signal Vrsig during the reset period, the source 112 of the driving TFT 110 is set during this period. And the influence of the current flowing through the drain 113 on the drive current Id can be reduced to a negligible level.
[0052]
As described above, according to the present embodiment, the gate voltage Vg corresponding to the input signal Vsig can be stepped down by the threshold voltage Vth2 of the compensation TFT 120, so that the input voltage is lower than that without the compensation TFT 120. It is possible to perform equivalent conductance control in the driving TFT 110 using the voltage Vsig of the signal Vsig.
[0053]
FIG. 2B is a timing chart in the case where both the driving TFT 110 and the compensation TFT 120 are composed of N-channel TFTs. In this case, a positive voltage is applied to the gate 111 so that the passing state is achieved. The gate voltage Vg in the driving TFT 110, which is an N-channel TFT, is set to the voltage Vrsig of the reset signal Vrsig at the time of reset, and then is more positive by the threshold voltage Vth2 of the compensating TFT 120 than the voltage Vsig of the input signal Vsig. Boosted to the voltage side.
[0054]
Here, if the input signal Vsig is directly input to the driving TFT 110 without going through the compensation TFT 120, that is, if the voltage Vsig of the input signal Vsig and the gate voltage Vg coincide with each other, FIG. Is the case where the driving TFT 110 is an N channel), the driving current Id has a characteristic of rising from the threshold voltage Vth1 of the driving TFT 110. For example, if the design reference value of the threshold voltage Vth1 is 2V, the variation in threshold value is about ± several volts. Then, variations in the threshold voltage Vth1 in the driving TFT 110 appear as variations in the drive current Id as they are.
[0055]
In contrast, in this embodiment, the input signal Vsig is input to the driving TFT 110 via the compensation TFT 120, that is, the voltage Vsig of the input signal Vsig is increased by the threshold voltage Vth2 of the compensation TFT 120. When the gate voltage Vg is used, the threshold voltage Vth2 of the compensation TFT 120 and the drive voltage are driven as shown in FIG. 3B (this is a case where the drive TFT 110 and the compensation TFT 120 are both N-channel). This cancels out the threshold voltage Vth1 of the TFT 110 and the threshold voltage Vth of the input signal Vsig for the entire transistor circuit 100 approaches zero. In particular, when both threshold voltages Vth1 and Vth2 substantially coincide with each other, the threshold voltage Vth becomes substantially zero. As described above, the threshold voltages Vth1 and Vth2 can be made relatively simple by, for example, configuring the driving TFT 110 and the compensating TFT 120 from the same type TFTs at close positions on the same semiconductor substrate. With this configuration, in both TFTs, the thickness of the gate insulating film and semiconductor film formed in a thin film, the planar shape of each component such as the channel length, the channel formation region, the source region, and the drain region As a result, the threshold voltage Vth1 and Vth2 of both TFTs can be matched completely or almost completely. In order to approximate the threshold characteristics, the channel lengths are preferably the same, but the channel widths are not necessarily the same.
[0056]
As described above, according to the present embodiment, the threshold characteristics and voltage-current characteristics of the driving TFT 110 and the compensation TFT 120 are brought close to each other (ideally by matching), so that the input signal Vsig with respect to the driving current Id It becomes possible to bring the threshold voltage Vth close to zero (ideally to match zero).
[0057]
Further, as can be seen from FIGS. 3A and 3B, even when the plurality of transistor circuits 100 are manufactured, even if the threshold voltage Vth1 in each driving TFT 110 varies from each other, this threshold is satisfied. Regardless of the magnitude of the value voltage Vth1, the threshold voltage Vth of each transistor circuit 100 is set to a value close to zero by the action of each compensation TFT 120. That is, a large number of transistor circuits 100 having a constant threshold voltage Vth can be manufactured. This is particularly useful for applications such as a display panel in which variations in threshold voltage Vth among a large number of transistor circuits 100 pose a problem as will be described later. In each transistor circuit 100, the threshold voltage Vth1 of the pair of driving TFTs 110 arranged close to each other and the threshold voltage Vth2 of the compensation TFT 120 are arranged separately with a distance therebetween. As described above, the threshold voltage Vth1 in each transistor circuit 100 is compensated by the compensating TFT 120 because it is much easier than making the threshold voltages Vth1 of the two driving TFTs 110 coincide with each other. Can be said to be extremely effective in reducing variation in the threshold voltage Vth among the plurality of transistor circuits 100.
[0058]
As described above, according to the present embodiment, when a plurality of transistor circuits 100 are formed, a plurality of driving TFTs 110 having different threshold voltages Vth1, that is, threshold voltages as design reference values (for example, 2 Even if a plurality of driving TFTs 110 each having a threshold voltage Vth1 that varies greatly from .5V) are used, a plurality of transistor circuits 100 with little or no variation in the threshold voltage Vth can be obtained. . For this reason, the conditions required for the TFT in terms of current-voltage characteristics are relaxed, and the yield can be improved and the manufacturing cost can be reduced.
[0059]
As can be seen from FIG. 3A and FIG. 3B, by making the threshold voltages Vth1 and Vth2 coincide with each other, the conductance control in each of the driving TFTs 110 is higher than the voltage Vsig of the input signal Vsig. The first effect of using Vg and the second effect of reducing variation in threshold voltage Vth among the plurality of transistor circuits 100 are remarkably exhibited. Even if the threshold voltage Vth1 of the TFT 110 and the threshold voltage Vth2 of the compensating TFT 120 are not completely matched, the two threshold voltages cancel each other, so that the two threshold voltages are similar. The first and second effects are exhibited to a certain extent.
[0060]
In the present embodiment, in particular, the reset signal Vrsig having a voltage corresponding to a conductance value higher than the highest conductance value controlled according to the input signal Vsig is supplied to the gate 111. Therefore, after the reset regardless of the voltage value Vsig of the input signal Vsig, the input signal Vsig is supplied to the gate 111 via the compensation TFT 120 connected to the gate 111 in a direction that enables charge transfer in the direction of decreasing the conductance. It becomes possible to supply to. Moreover, in this embodiment, the reset signal Vrsig is set to a voltage that is larger than the maximum voltage of the input signal Vsig by the threshold voltage Vth2 of the compensation TFT 120 or more. Therefore, when the input signal Vsig is input after resetting, the compensation voltage is always higher than the voltage Vsig of the input signal Vsig regardless of the magnitude of the voltage Vsig of the input signal Vsig or the threshold voltage Vth2 of the compensation TFT 120. A voltage higher by the threshold voltage Vth2 of the TFT 120 can be supplied to the gate 111.
[0061]
When the input signal Vsig, which is often used in the conventional liquid crystal display element, is inverted, the relationship of the reset signal Vsig also applies to all the input signals Vsig including the inverted input signal. It is desirable that
[0062]
The effect of the voltage setting of the reset signal Vrsig will be examined with reference to FIGS. Here, FIG. 4 shows that the threshold value design reference value is set to, for example, −2.5 V, and changes in the drive current Id with respect to the threshold voltage variation ΔVth from the reference value are (1) driven without the compensation TFT 120. When the input signal Vsig is directly supplied to the TFT for driving 110 (characteristic curve C1), (2) When the reset signal Vrsig is set to 5 V and the input signal Vsig is supplied to the driving TFT 110 via the compensating TFT 120 (characteristic curve C2), and (3) The case where the reset signal Vrsig is set to 0 V and the input signal Vsig is supplied to the driving TFT 110 via the compensation TFT 120 (characteristic curve C3) is shown respectively. 5A shows the fluctuation range of the gate voltage Vg corresponding to the characteristic curve C2, and FIG. 5B shows the fluctuation range of the gate voltage Vg corresponding to the characteristic curve C3. Here, Vsig = 7.5V, + Vc = 10V, and −Vc = 5V.
[0063]
In FIG. 4, as shown by the characteristic curve C1, when the compensation TFT 120 is not provided, the threshold voltage variation ΔVth appears as a variation in the drive current Id as it is.
[0064]
As shown by the characteristic curve C2, when the reset signal Vrsig is 5 V and the compensating TFT is used, the threshold voltage variation ΔVth is considerably compensated on the plus side, but on the minus side, the drive current It appears as a variation in Id. As shown in FIG. 5A, on the negative side, when the input signal Vsig is input after reset, the gate voltage Vg is set to the negative voltage side from the input signal Vsig by the threshold voltage Vth2. This is because the voltage cannot be lowered (compensated). This is because the compensation TFT 120, which is a diode, can move the gate voltage Vg from the reset signal Vrsig to the input signal Vsig, but cannot move it away.
[0065]
Further, as shown by the characteristic curve C3, when the compensation TFT is used with the reset signal Vrsig set to 0 V, the threshold voltage variation ΔVth hardly appears as the variation in the drive current Id. As shown in FIG. 5B, when the input signal Vsig is input after reset, the gate voltage Vg is stepped down to the negative voltage side by the threshold voltage Vth from the input signal Vsig (see FIG. 5B). This is because compensation can be made. Note that the above consideration holds for whether Vsig = 7.5 V given here can be compensated for all Vsigs when the minimum potential of the input signal Vsig is considered.
[0066]
As described above, in this embodiment, the threshold voltage Vth2 of the compensation TFT 120 is always higher than the voltage of the input signal Vsig regardless of the magnitude of the input voltage Vsig or the threshold voltage Vth2 of the compensation TFT 110. A voltage Vg that is lower by the amount can be applied to the gate 111 of the driving TFT 110.
[0067]
2A and 2B, the gate voltage Vg is held by the holding capacitor 160 during the driving period. For this reason, the storage capacitor 160 can also reduce (compensate) variations in retention characteristics of the gate voltage Vg between the plurality of transistor circuits 100.
[0068]
As described above with reference to FIGS. 1 to 5, according to the transistor circuit 100 of the present embodiment, the current control type element 500 such as the EL element can be driven with the input signal Vsig having a relatively low voltage. In addition, a plurality of current control elements 500 can be accurately controlled in accordance with the voltage of the input signal Vsig, regardless of variations in current-voltage characteristics and threshold characteristics among the plurality of driving TFTs 110. .
[0069]
In the example shown in FIG. 1, a P-channel TFT and an N-channel TFT are mixed, but all TFTs may be composed of N-channel TFTs or all TFTs. May be composed of a P-channel TFT. However, from the viewpoint of compensating the current-voltage characteristics and threshold characteristics of the driving TFT 110 with the compensating TFT 120, it is advantageous to configure the driving TFT 110 and the compensating TFT 120 as the same type TFT by the same process. In particular, if both TFTs are formed in the same thin film forming process, the degree of similarity of characteristics between the two TFTs generally increases, so that the transistor circuit 100 having little or no variation in current-voltage characteristics and threshold characteristics is formed on the same substrate. Can be obtained. On the other hand, the reset TFT 130 and the switching TFT 140 may be either a P channel type or an N channel type regardless of whether the driving TFT 110 is a P channel type or an N channel type. However, it is often advantageous in manufacturing to make all TFTs of the same type.
[0070]
In addition, the various TFTs 110 to 140 in the present embodiment may be configured by any type of field effect transistor (FET) such as a junction type or a parallel / series connection.
[0071]
Furthermore, as shown in FIG. 6, the transistor circuit as described above may be composed of bipolar transistors. In this case, the gate, source, and drain are made to correspond to the base, emitter, and collector, respectively, and the driving transistor 110 ′ is formed from the bipolar transistor, and the compensation transistor 120 ′ is formed from the bipolar transistor. 'And it is sufficient. In general, in the case of a bipolar transistor, the threshold voltage is, for example, about 0.7 V, and its variation is smaller than that of a TFT. However, even with this configuration, the current-voltage characteristics and The influence of the variation in threshold characteristics on the drive current Id can be compensated for by the compensation transistor 120 ′. Furthermore, driving by the driving transistor 110 ′ can be performed at a relatively low voltage. In particular, if the driving transistor 110 ′ and the compensation transistor 120 ′ are manufactured in the same manufacturing process, the degree of similarity of characteristics between the two transistors generally increases, so there is almost no variation in current-voltage characteristics and threshold characteristics. Alternatively, a reduced number of transistor circuits 100 ′ can be obtained.
[0072]
Examples of the current control element 500 in the above embodiment include various elements such as current control light emitting elements such as organic EL elements and inorganic EL elements, and current control thermal transfer elements.
[0073]
(Display panel)
Embodiments of the display panel of the present invention will be described with reference to FIGS. FIG. 7 is a block diagram illustrating the entire configuration of the display panel, and FIG. 8 is a plan view of one pixel portion in the display panel. FIGS. 9A, 9B, and 9C. Are AA ′, BB ′ and CC ′ sectional views, respectively, and FIG. 10 is a circuit diagram of four pixel units adjacent to each other.
[0074]
The display panel in this embodiment includes a plurality of pixel portions each including the above-described transistor circuit of the present invention and arranged in a matrix, and each of the plurality of pixel portions includes an example of a current-controlled light-emitting element. EL elements 50 are respectively provided.
[0075]
As shown in FIG. 7, the display panel 200 includes a TFT array substrate 1, and a screen display area in which a plurality of pixel portions 2 are arranged in a matrix on the TFT array substrate 1 extends in the Y direction. A plurality of data lines 11 arranged in the X direction, a plurality of scanning lines 12 extending in the X direction and arranged in the Y direction, and a plurality of common lines arranged in parallel with the plurality of data lines 11. And an electric wire 13. The display panel 1 further includes a data line driving circuit 21 for supplying a data signal to each data line 11, a pair of scanning line driving circuits 22 for supplying a scanning signal to each scanning line 12, And an inspection circuit 23 for inspecting poor passage, insulation failure, element defect, and the like in the pixel portion 2. In the present embodiment, each drive circuit is formed on the TFT array substrate 1 by a process common to the pixel portion 2, but may be a circuit that is not on the TFT array substrate 1 or a pixel. It may be formed in a separate process from the part 2.
[0076]
As shown in FIG. 8, each pixel unit 2 is provided with the driving TFT 110, the compensation TFT 120, the reset TFT 130, the switching TFT 140, and the storage capacitor 160 described with reference to FIGS. 1 to 6. The scanning line 12b in the previous stage becomes the wiring for the reset scanning signal Vrscan in FIG. 1, the scanning line 12a in the previous stage becomes the wiring for the scanning signal Vscan and the wiring for the reset signal Vrsig in FIG. Reference numeral 11a is a wiring for the input signal Vsig (data signal) in FIG. Further, the common power supply line 13 is connected to the positive power source + V, the EL element 50 is connected between the driving TFT 110 and a counter electrode described later, and the counter electrode is connected to the negative power source −V. .
[0077]
As shown in FIG. 9A, the switching TFT 140, the compensation TFT 120, and the storage capacitor 160 are arranged on the TFT array substrate 1 along the AA ′ cross section of FIG. A gate insulating film 5 made of a silicon oxide film or a silicon nitride film, a Ta (tantalum) film 6, a first interlayer insulating film 7 made of a silicon oxide film or a silicon nitride film, and an Al film 8 are formed. In place of the Ta film 6 for forming the gate electrode, a low resistance polysilicon film may be formed.
[0078]
More specifically, the switching TFT 140 is a top gate type TFT having a gate 141 made of a polysilicon film 6, and the semiconductor layer 4 portion facing the gate 141 through the gate insulating film 5 is defined as a channel formation region. As shown in FIG. 4, the TFT is configured as an N-channel TFT having a source 142 and a drain 143 which are heavily doped n-type on both sides. The source 142 is connected to the data line 11 a made of the Al film 8 through a contact hole opened in the gate insulating film 5 and the first interlayer insulating film 7. The drain 143 is connected to the compensating TFT 120 through the contact hole and the Al film 8 opened in the gate insulating film 5 and the first interlayer insulating film 7.
[0079]
The compensation TFT 120 is a top gate type TFT having a gate 121 made of a Ta film 6. The semiconductor film 4 portion facing the gate 121 through the gate insulating film 5 is used as a channel formation region, and p-type is formed on both sides thereof. It is configured as a P-channel TFT having a source 122 and a drain 123 that are highly doped. The contact hole and the Al film 8 opened in the gate insulating film 5 and the first interlayer insulating film 7 are relayed to be connected to the switching TFT 140, the storage capacitor 160, and the gate 111 of the driving TFT 110.
[0080]
In addition, the storage capacitor 160 is configured such that the semiconductor film 4, the Ta film 6, and the Al film 8 are opposed to each other with the gate insulating film 5 and the first interlayer insulating film 7 interposed therebetween so as to have a double capacitor configuration. ing. The portion of the semiconductor film 4 constituting the storage capacitor is connected to the Al film 8 through a contact hole opened in the gate insulating film 5 and the first interlayer insulating film 7, and the Ta film 6 constituting the storage capacitor. The portion is connected to the Al film 8 through a contact hole opened in the first interlayer insulating film 7.
[0081]
As shown in FIG. 9B, the reset TFT 130 has a semiconductor film 4, a gate insulating film 5, a Ta film 6 and a first interlayer insulating film on the TFT array substrate 1 along the BB ′ cross section of FIG. It is composed of a film 7 and an Al film 8.
[0082]
More specifically, the reset TFT 130 is a top gate type TFT having a gate 131 made of a Ta film 6, and the semiconductor layer 4 portion facing the gate 131 through the gate insulating film 5 is used as a channel formation region. The n-type TFT includes a source 132 and a drain 133 which are heavily doped n-type on both sides. The source 132 and the drain 133 relay the contact hole and the Al film 8 opened in the gate insulating film 5 and the first interlayer insulating film 7, and the scanning line 12 a and the driving TFT 110 made of the Ta film 6. The gates 111 are respectively connected.
[0083]
Further, as shown in FIG. 9C, the driving TFT 110 includes the semiconductor film 4, the gate insulating film 5, the Ta film 6, and the first film on the TFT array substrate 1 along the CC ′ cross section of FIG. It is composed of an interlayer insulating film 7 and an Al film 8. On the second interlayer insulating film 9, an ITO film 51 connected to the drain 113 of the driving TFT 110 through the contact hole and the Al film 8 is formed, and an EL element 50 is formed thereon. . On the other hand, the source 112 of the driving TFT 110 is connected to the common power supply line 13 made of the Al film 8 through a contact hole. Further, the EL elements 50 in the adjacent pixel portions 2 are separated by an electrically insulating bank 52. Preferably, the bank 52 has a light shielding property. The bank 52 is made of, for example, a light-shielding resist, and the bank 52 may be provided also in a peripheral parting area that covers the periphery of the screen display area of the display panel 200. On the EL element 50, a counter electrode (upper electrode) 56 made of a low resistance metal such as Al or ITO is provided.
[0084]
As shown in FIG. 10, in the display panel 200, in particular, a configuration in which the positive power supply + V is supplied to both of the pixel units 2 adjacent to each other in the X direction by the common power supply line 13 is used. Compared with the case where the power supply wiring is simply provided for each column of the pixel portion 2, the number of power supply wirings is about ½. Further, the reset scanning signal Vrscan input to the gate 131 of the reset TFT 130 is supplied by the preceding scanning line 12b, and the reset signal Vrsig input to the reset TFT 130 is supplied by the scanning line 12b. Thus, the number of signal lines is reduced as compared with the case where a line dedicated to the reset scanning signal Vrscan and a line dedicated to the reset signal Vrsig are provided. Thus, by not increasing the number of power supply lines and the number of signal lines, it is possible to secure a space for providing the compensation TFT 120 and the reset TFT 130 that are not provided in the conventional display panel. Of course, unlike this embodiment, a common power supply line is provided for each pixel, the same pattern is provided for each pixel, a wiring dedicated to the reset scanning signal Vrscan, and a wiring dedicated to the reset signal Vrsig. The idea of the present invention can be applied to the above.
[0085]
In the case of the display panel 200 using the EL element 50 which is a current-driven light emitting element as in the present embodiment, the light emitting element can be used without increasing the pixel opening area as in a liquid crystal panel, for example. If the amount of current to be supplied is increased, self-emission occurs according to this, so that the brightness necessary for image display can be obtained. Therefore, as in the present embodiment, a space occupied by the wiring may be saved to secure a space for forming various TFTs in the pixel portion 2, and various EL elements 50 may be reduced by reducing the size of each EL element 50. A space for forming the TFT in the pixel portion 2 may be secured.
[0086]
Next, the operation of the display panel 200 of this embodiment will be described with reference to FIGS.
[0087]
When the scanning signal Vscan is supplied from the scanning line driving circuit 22 to the preceding scanning line 12b, this is input to the gate 131 of the reset TFT 130 at this stage as the reset scanning signal Vrscan at this stage. In parallel with this, the reset signal Vrsig is supplied from the scanning line driving circuit 22 to the scanning line 12a at this stage, and the gate voltage Vg of the driving TFT 110 at this stage is set to the potential of the reset signal Vrsig (FIG. 2). (See (A)). At this time, the reset signal Vrsig may be the same as the OFF potential of the scanning signal Vscan. Subsequently, when the scanning signal Vscan is supplied from the scanning line driving circuit 22 to the scanning line 12a at this stage, this is input to the gate 141 of the switching TFT 140 at this stage. In parallel with this, an input signal Vsig (data signal) is supplied from the data line driving circuit 21 to the data line 11 a of this stage, and this voltage Vsig is applied to the compensation TFT 120 via the switching TFT 140 and the compensation TFT 120. The voltage is stepped down by the threshold voltage Vth2 and supplied as the gate voltage Vg to the gate 111 of the driving TFT 110 at this stage (see FIG. 2A). As a result, the conductance between the source 112 and the drain 113 of the driving TFT 110 is controlled according to the stepped down gate voltage Vg, and the driving current flowing through the EL element 50 between the positive power source + V and the negative power source −V. Id is controlled.
[0088]
Therefore, the variation in the threshold voltage Vth1 in the driving TFT 110 provided in each pixel portion 2 is compensated by the threshold Vth2 in the compensating TFT 120, and the data signal Vsig corresponding to the driving current Id between the plurality of pixel portions 2 is compensated. There is almost no variation in threshold value, and uniform image display with uniform brightness over the entire screen display area of the display panel 200 is possible. Further, the drive current Id can be controlled by using the data signal Vsig having a relatively small voltage by the step-down action by the compensating TFT 120.
[0089]
In the above embodiment, the gate voltage Vg is reset by the reset TFT 130 before the input signal Vsig is supplied. For example, during the period when a still image is displayed, the gate voltage Vg is driven over a plurality of frames by the same input signal Vsig. Since the current Id may be controlled, it is not necessary to perform the reset operation for each scan. Further, the gate voltage Vg may be reset by light irradiation instead of the electrical reset signal Vrsig (set to a predetermined reset voltage). Furthermore, the reset signal Vrsig may be supplied via the switching TFT 140 or the compensation TFT 120 instead of the reset TFT 130. On the other hand, it is needless to say that the switching TFT 140 and the switching operation are unnecessary for an application that does not perform switching such as active matrix driving.
[0090]
(Electronics)
Next, an embodiment of an electronic device including the display panel 200 described in detail above will be described with reference to FIGS.
[0091]
First, FIG. 11 shows a schematic configuration of an electronic apparatus including the display panel 200 as described above.
[0092]
In FIG. 11, the electronic apparatus includes a display information output source 1000, a display information processing circuit 1002, a drive circuit 1004, a display panel 1006, a clock generation circuit 1008, and a power supply circuit 1010.
[0093]
The display panel 200 in the above-described embodiment corresponds to the display panel 1006 and the drive circuit 1004 in this embodiment. Therefore, the drive circuit 1004 may be mounted on the TFT array substrate constituting the display panel 1006, and the display information processing circuit 1002 or the like may be further mounted. Alternatively, the driving circuit 1004 may be externally attached to the TFT array substrate on which the display panel 1006 is mounted.
[0094]
The display information output source 1000 includes a ROM (Read Only Memory), a RAM (Random Access Memory), a memory such as an optical disk device, a tuning circuit that tunes and outputs a television signal, and the like. Based on this, display information such as an image signal in a predetermined format is output to the display information processing circuit 1002. The display information processing circuit 1002 is configured to include various known processing circuits such as an amplification / polarity inversion circuit, a phase expansion circuit, a rotation circuit, a gamma correction circuit, and a clamp circuit, and a display input based on a clock signal. A digital signal is sequentially generated from the information and output to the drive circuit 1004 together with the clock signal CLK. The drive circuit 1004 drives the display panel 200. The power supply circuit 1010 supplies predetermined power to the above-described circuits.
[0095]
Next, specific examples of the electronic apparatus configured as described above are shown in FIGS.
[0096]
In FIG. 12, a laptop personal computer (PC) 1200 compatible with multimedia, which is another example of an electronic device, includes the above-described display panel 200 in a top cover case 1206, and further includes a CPU, a memory, and a modem. And a main body 1204 in which a keyboard 1202 is incorporated.
[0097]
As shown in FIG. 13, in the case of a display panel 1304 that does not include the drive circuit 1004 or the display information processing circuit 1002, the TCP 1324 including the drive circuit 1004 and the display information processing circuit 1002 mounted on the polyimide tape 1322 (Tape Carrier Package) 1320 can be physically and electrically connected to the periphery of the TFT array substrate 1 through an anisotropic conductive film to produce, sell, use, etc. as a display panel Is possible.
[0098]
In addition to the electronic devices described above with reference to FIGS. 12 to 13, a television, viewfinder type or monitor direct-view type video tape recorder, car navigation device, electronic notebook, calculator, word processor, engineering workstation (EWS) ), A mobile phone, a video phone, a POS terminal, a device equipped with a touch panel, and the like are examples of the electronic device shown in FIG.
[0099]
As described above, according to the present embodiment, it is possible to realize various electronic devices that have little brightness unevenness over the entire surface of the display panel and can be driven at a relatively low voltage.
[0100]
【The invention's effect】
According to the transistor circuit of the present invention, the gate voltage can be stepped down or stepped up with respect to the voltage of the input signal by the threshold voltage of the compensation transistor, so conductance control in the driving transistor is performed by the voltage of the low input signal. be able to. Furthermore, by bringing the threshold characteristics and voltage / current characteristics of the compensation transistor and the driving transistor closer, the threshold voltage of the input signal with respect to the driving current can be made closer to zero. Furthermore, when a plurality of transistor circuits are formed using a plurality of driving transistors having different threshold characteristics, a plurality of driving transistors having different threshold voltages, that is, greatly differ from the design reference value. Even if a plurality of driving transistors each having a threshold voltage are used, it is possible to obtain a plurality of transistor circuits with little or no variation in threshold voltages among the plurality of transistor circuits.
[0101]
According to the display panel of the present invention, an image display with reduced brightness unevenness can be realized using a low-voltage input signal.
[0102]
Further, according to the electronic device of the present invention, various electronic devices such as a personal computer and a pager capable of displaying a high-quality image can be realized.
[Brief description of the drawings]
FIG. 1 is a circuit diagram in an embodiment of a transistor circuit.
2 is a timing chart of various signals in the transistor circuit of FIG. 1 (FIG. 2A) and a timing chart of various signals in a modification of the transistor circuit of FIG. 1 (FIG. 2B).
FIG. 3 is a characteristic diagram (FIG. 3A) showing threshold characteristics in a comparative example including a driving TFT, and threshold characteristics in the present embodiment including a compensation TFT and a driving TFT. FIG. 3 is a characteristic diagram (FIG. 3B).
FIG. 4 is a characteristic diagram showing changes in drive current Id with respect to threshold value variation ΔVth in various cases.
FIG. 5 is a timing chart (FIG. 5A) showing the step-down action by the compensation TFT when the reset signal Vrsig is 5 V in this embodiment, and the compensation TFT when the reset signal Vrsig is 0 V. 6 is a timing chart (FIG. 5B) showing a hypotensive action.
FIG. 6 is a circuit diagram in another embodiment of a transistor circuit.
FIG. 7 is a plan view showing an overall configuration of an embodiment of a display panel.
8 is a plan view of one pixel portion of the display panel of FIG.
9 is a cross-sectional view taken along the line AA ′ of FIG. 8 (FIG. 9A), a cross-sectional view taken along the line BB ′ (FIG. 9B), and a cross-sectional view taken along the line CC ′ (FIG. 9C). .
10 is a circuit diagram of four pixel units adjacent to each other in the display panel of FIG.
FIG. 11 is a block diagram showing a schematic configuration of an embodiment of an electronic apparatus according to the present invention.
FIG. 12 is a front view illustrating a personal computer as an example of an electronic apparatus.
FIG. 13 is a perspective view showing a liquid crystal device using TCP as another example of an electronic apparatus.
[Explanation of symbols]
1 ... TFT array substrate
2. Pixel part
11 ... Data line
12 ... Scanning line
13 ... Common feeder
21: Data line driving circuit
22 Scanning line drive circuit
23. Inspection circuit
50 ... EL element
100: Transistor circuit
110 ... Driving TFT
120 ... TFT for compensation
130 ... Reset TFT
140 ... TFT for switching
160: Retention capacity

Claims (3)

A display panel driving method including a scanning line, a data line, and a transistor circuit,
A reset timing signal is supplied to a gate of a reset transistor included in the transistor circuit, and a driving gate having a first gate, a first source, and a first drain included in the transistor circuit via the reset transistor. A first step of supplying a reset signal to the first gate of a transistor to set the first gate to a predetermined voltage;
A scanning signal is supplied to the gate of a switching transistor included in the transistor circuit via the scanning line, and is the same channel type as the driving transistor included in the data line, the switching transistor, and the transistor circuit. A second step of setting an input signal to the first gate through a diode-connected transistor to set a voltage of the first gate;
And a third step of driving the current driving element connected in series with the driving transistor by supplying a current through the driving transistor. Providing the input signal to a source of the diode-connected transistor in the second step;
The method for driving a display panel according to claim 1 or 2. The reset signal is set to a voltage greater than the maximum voltage of the input signal by a threshold voltage of the compensation transistor;
The method for driving a display panel according to claim 4.

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