JP3720690B2 - Beam array circuit for phased array antenna, phased array antenna and amplifier arrangement method - Google Patents

Description

【００２１】
図３はビームポートにおける信号を棒グラフとして示したものであり、横軸に端子Ａ〜Ｈをとり、縦軸に振幅をとる。なお、給電電力の合計は１となるように規格化している。信号ｆ_１（１），ｆ_１（２），ｆ_１（３），ｆ_１（４）は各々の第１段ハイブリッドに入力した給電信号がハイブリットの出口において強め合うように分配・合成された場合の振幅値を表している。信号ｆ_２（１），ｆ_２（２）は第１段ハイブリッドを通過した信号が第２段ハイブリッドの出口において強め合うように分配・合成された場合の振幅値を表している。図２に示した楕円は信号ｆ_１（１），ｆ_１（２），ｆ_１（３），ｆ_１（４）および、信号ｆ_２（１），ｆ_２（２）が対象としている信号経路の場所を示している。なお、信号ｆ_１（１），ｆ_１（２），ｆ_１（３），ｆ_１（４）の最大値は０．４１６０２５であり、信号ｆ_２（１），ｆ_２（２）の最大値は０．４９０２９である。
【００２２】
図４および図５はそれぞれ図２において楕円で示した領域の第１段ハイブリッド−第２段ハイブリッド間の信号分布、第２段ハイブリッド−第３段ハイブリッド間の信号分布を具体的に個々の線路について計算して棒グラフとして示したものである。図６はエレメントポートにおける信号を棒グラフとして示したものである。図４〜図６では、横軸に端子Ａ〜Ｈをとり、縦軸に振幅をとる。なお、給電信号のポート間位相差は信号の電力集中が最も大きくなるように（２ｑ−（Ｎ＋１））π／Ｎより決定した。この場合は５番目（ｑ＝５）のエレメントポートＥに電力が集中しているが、他のエレメントポートに信号が集中する場合も信号振幅の最大値は同じ値となる。なお、ビームポートにおける信号の最大振幅値は０．５８８３４８、第１段ハイブリット−第２段ハイブリット間の信号の最大振幅値は０．４１６０２５、第２段ハイブリット−第３段ハイブリット間の信号の最大振幅値は０．４９０２９であり、エレメントポートにおける最大振幅値は０．６９３３７５である。これらの結果から明らかなように、信号ｆ_Ｌ（ｉ），｛ｉ＝１，２，３，．‥，２^{Ｋ−Ｌ−１}，２^Ｋ−Ｌ｝の最大値がもっとも小さくなるＬの値は１であり、電力集中の度合いが最も小さくなる、第１段ハイブリッドと第２段ハイブリッドの間に増幅器を配置することによって増幅器にかかる負荷が均一化され、増幅器に要求される出力を小さくすることができる。
【００２３】
以上のことから、本発明の増幅器配置方法はエレメントポートまたはビームポートを通過する信号強度に偏りがある場合でも各々の増幅器を通過する信号強度を平坦化することを可能とするものである。このことにより、特定の増幅器に電力集中した場合の最大電力値を低減して増幅器に要求される出力を小さくするとともに、増幅器にかかる負荷が均一化することから増幅器全体を比較的高効率で動作させることが可能となる。また、本方法によって、増幅器を配置することを特徴とするビーム形成回路を具備するフェーズドアレーアンテナは増幅器に要求される出力を小さくすることで軽量化および低コスト化が可能となる。また、増幅器にかかる負荷を均一化することでフェーズドアレーアンテナのビーム方向やビーム数に関わり無く、常に高い出力を得ることが可能になる。なお、複数種類の増幅器を用意しなくとも単一種類の増幅器を用いて増幅器全体を比較的高効率で動作させることが可能となることから、ＢＦＮの設計および調整が比較的容易であると同時に低消費電力化が実現される。
【００２４】
すなわち、本発明の第一の観点は、素子アンテナが接続される端子を備えたエレメントポートと、この素子アンテナに信号給電を行う端子を備えたビームポートと、このビームポートの信号給電を行う端子の位置によって前記エレメントポートの隣接端子間の位相差を変化させる手段とを含むマトリクス回路を備えたフェーズドアレーアンテナのビーム形成回路である。
【００２５】
ここで、本発明の特徴とするところは、前記位相差を変化させる手段は、多段に接続されたハイブリッドを含み、このハイブリットの段数をＫとし、前記ビームポート側のハイブリットから順番に第１段ハイブリット，第２段ハイブリット，…，第Ｋ段ハイブリツトとし、前記マトリクス回路の前記ビームポートにおける給電信号をｆ_０（ｉ），｛ｉ＝１，２，３，…，２^Ｋ−１，２^Ｋ｝とし、パラメータＬ＝１，２，…，Ｋ−１に関して信号ｆ_Ｌ（ｉ）＝２^−１／２×ｆ_Ｌ−１（ｉ）＋２^−１／２×ｆ_Ｌ−１（ｉ＋２^Ｋ−Ｌ），｛ｉ＝１，２，３，…，２^{Ｋ−Ｌ−１}，２^Ｋ−Ｌ｝を定義し、信号ｆ_Ｌ（ｉ），｛ｉ＝１，２，３，…，２^{Ｋ−Ｌ−１}，２^Ｋ−Ｌ｝の最大値がもっとも小さくなるＬの値をＬ_ｍｉｎとしたとき、第Ｌ_ｍｉｎ段ハイブリットと第（Ｌ_ｍｉｎ＋１）段ハイブリットとの間に増幅器が配置されたところにある。
【００２６】
本発明の第二の観点は、本発明のビーム形成回路を具備することを特徴とするフェーズドアレーアンテナである。
【００２７】
本発明の第三の観点は、増幅器配置方法であって、素子アンテナが接続される端子を備えたポートをエレメントポートと呼び、この素子アンテナに信号給電を行う端子を備えたポートをビームポートと呼び、このビームポートの信号給電を行う端子の位置によって前記エレメントポートの隣接端子間の位相差を変化させるマトリクス回路に含まれる多段に接続されたハイブリッドの段数をＫとし、前記ビームポート側のハイブリットから順番に第１段ハイブリット，第２段ハイブリット，…，第Ｋ段ハイブリツトとし、前記マトリクス回路の前記ビームポートにおける給電信号をｆ_０（ｉ），｛ｉ＝１，２，３，…，２^Ｋ−１，２^Ｋ｝とし、パラメータＬ＝１，２，…，Ｋ−１に関して信号ｆ_Ｌ（ｉ）＝２^−１／２×ｆ_Ｌ−１（ｉ）＋２^−１／２×ｆ_Ｌ−１（ｉ＋２^Ｋ−Ｌ），｛ｉ＝１，２，３，…，２^{Ｋ−Ｌ−１}，２^Ｋ−Ｌ｝を定義し、信号ｆ_Ｌ（ｉ），｛ｉ＝１，２，３，…，２^{Ｋ−Ｌ−１}，２^Ｋ−Ｌ｝の最大値がもっとも小さくなるＬの値をＬ_ｍｉｎとしたとき、第Ｌ_ｍｉｎ段ハイブリットと第（Ｌ_ｍｉｎ＋１）段ハイブリットとの間に増幅器を配置することを特徴とする。
【００２８】
【発明の実施の形態】
本発明実施例のビーム形成回路の構成を図１を参照して説明する。図１は本発明のビーム形成回路を用いたフェーズドアレーアンテナの構成図である。
【００２９】
本発明は、図１に示すように、素子アンテナａｎｔが接続される端子Ａ〜Ｐを備えたエレメントポートと、この素子アンテナａｎｔに信号給電を行う端子＃１〜＃１６を備えたビームポートと、このビームポートの信号給電を行う端子＃１〜＃１６の位置によって前記エレメントポートの隣接端子間の位相差を変化させる手段とを含むマトリクス回路ｍａｔおよびビーム制御回路ｃｏｎを備えたフェーズドアレーアンテナのビーム形成回路である。
【００３０】
ここで、本発明の特徴とするところは、前記位相差を変化させる手段は、多段に接続されたハイブリッドｈｙｂを含み、このハイブリットｈｙｂの段数をＫとし、前記ビームポート側のハイブリットｈｙｂから順番に第１段ハイブリット，第２段ハイブリット，…，第Ｋ段ハイブリツトとし、マトリクス回路ｍａｔの前記ビームポートにおける給電信号をｆ_０（ｉ），｛ｉ＝１，２，３，…，２^Ｋ−１，２^Ｋ｝とし、パラメータＬ＝１，２，…，Ｋ−１に関して信号ｆ_Ｌ（ｉ）＝２^−１／２×ｆ_Ｌ−１（ｉ）＋２^−１／２×ｆ_Ｌ−１（ｉ＋２^Ｋ−Ｌ），｛ｉ＝１，２，３，…，２^{Ｋ−Ｌ−１}，２^Ｋ−Ｌ｝を定義し、信号ｆ_Ｌ（ｉ），｛ｉ＝１，２，３，…，２^{Ｋ−Ｌ−１}，２^Ｋ−Ｌ｝の最大値がもっとも小さくなるＬの値をＬ_ｍｉｎとしたとき、第Ｌ_ｍｉｎ段ハイブリットと第（Ｌ_ｍｉｎ＋１）段ハイブリットとの間に増幅器ａｍｐが配置されたところにある。図１に示すように、本発明のビーム形成回路を具備して本発明のフェーズドアレーアンテナが構成される。
【００３１】
以下では、本発明実施例をさらに詳細に説明する。
【００３２】
（第一実施例）
本発明第一実施例を図１および図７〜図１２を参照して説明する。第一実施例では、ハイブリットの段数Ｋ＝４（１６ポートマトリクス回路）のマトリクス回路において、エッジテーパ−１０ｄＢのガウス分布でビームポートの中央１０ポート（ポート４，５，６，…，１２，１３）を用いて信号給電する場合について示す。
【００３３】
図７は本実施例を説明するために、１６ポートマトリクス回路（Ｋ＝４，Ｎ＝１６）を流れる信号の経路を示した結線図である。なお、図面の簡略化のため位相器は省いて示している。図７に示した楕円は信号ｆ_１（１），ｆ_１（２），ｆ_１（３），…，ｆ_１（７），ｆ_１（８）、信号ｆ_２（１），ｆ_２（２），ｆ_２（３），ｆ_２（４）および、信号ｆ_３（１），ｆ_３（２）が対象としている信号経路の場所を示している。表２は、エッジテーパ−１０ｄＢのガウス分布でビームポートの中央１０ポートに信号を給電した場合における、信号ｆ_Ｌ（ｉ）の計算結果を示したものである。
【００３４】
【表２】

【００３５】
図８はビームポートにおける給電信号を棒グラフとして示したものであり、横軸に端子Ａ〜Ｐをとり、縦軸に振幅をとる。なお、給電電力の合計は１となるように規格化している。この場合は、信号ｆ_Ｌ（ｉ），｛ｉ＝１，２，３，…，２^{Ｋ−Ｌ−１}，２^Ｋ−Ｌ｝の最大値がもっとも小さくなるＬの値は１（Ｌ_ｍｉｎ＝１）であり、電力集中の度合いが最も小さくなる、第１段ハイブリットと第２段ハイブリットの間に増幅器を配置する。
【００３６】
図９、図１０、図１１は本手法の確認のためにそれぞれ第１段ハイブリット−第２段ハイブリット間の信号分布、第２段ハイブリット−第３段ハイブリット間の信号分布、および第３段ハイブリット−第４段ハイブリット間の信号分布を具体的に個々の線路について計算して棒グラフとして示したものである。図１２はエレメントポートにおける信号を棒グラフとして示したものである。図９〜図１２では、横軸に端子Ａ〜Ｐをとり、縦軸に振幅をとる。なお、給電信号のポート間位相差は９番目のポートＩに電力集中するようにπ／１６（１１．２５度）とした。図９〜図１１から明らかなように、増幅器にかかる負荷が均一化され、増幅器に要求される出力を小さくすることができる。
【００３７】
図１は本方法により増幅器を配置したビーム形成回路を具備するフェーズドアレーアンテナを示したものである。この場合には、電力集中の度合いが最も小さくなる第１段ハイブリットと第２段ハイブリットの間に増幅器を配置することによって増幅器にかかる負荷が均一化され、フェーズドアレーアンテナのビーム方向やビーム数に関わり無く、常に高い出力を得ることが可能になる。また、増幅器に要求される出力を小さくすることで軽量化および低コスト化が可能となる。
【００３８】
（第二実施例）
本発明第二実施例を図１３〜図１８を参照して説明する。第二実施例では、ハイブリットの段数Ｋ＝４（１６ポートマトリクス回路）のマトリクス回路において、エッジテーパ−２５ｄＢのガウス分布でビームポートの中央１０ポート（ポート４，５，６，…，１２，１３）を用いて信号給電する場合について示す。
【００３９】
図７は本実施例を説明するために、１６ポートマトリクス回路（Ｋ＝４，Ｎ＝１６）を流れる信号の経路を示した結線図である。なお、図面の簡略化のため位相器は省いて示している。図７に示した楕円は第一実施例で説明したように信号ｆ_１（１），ｆ_１（２），ｆ_１（３），…，ｆ_１（７），ｆ_１（８）、信号ｆ_２（１），ｆ_２（２），ｆ_２（３），ｆ_２（４）および、信号ｆ_３（１），ｆ_３（２）が対象としている信号経路の場所を示している。表３は、エッジテーパ−２５ｄＢのガウス分布でビームポートの中央１０ポートに信号を給電した場合における、信号ｆ_Ｌ（ｉ）の計算結果を示したものである。
【００４０】
【表３】

【００４１】
図１３はビームポートにおける給電信号を棒グラフとして示したものであり、横軸に端子Ａ〜Ｐをとり、縦軸に振幅をとる。なお、給電電力の合計は１となるように規格化している。この場合には、信号ｆ_Ｌ（ｉ），｛ｉ＝１，２，３，…，２^{Ｋ−Ｌ−１}，２^Ｋ−Ｌ）の最大値がもっとも小さくなるＬの値は２（Ｌ_ｍｉｎ＝２）であり、電力集中の度合いが最も小さくなる第２段ハイブリットと第３段ハイブリットの間に増幅器を配置する。
【００４２】
図１４、図１５、図１６は本手法の確認のためにそれぞれ第１段ハイブリット−第２段ハイブリット間の信号分布、第２段ハイブリット−第３段ハイブリット間の信号分布、および第３段ハイブリット−第４段ハイブリット間の信号分布を具体的に個々の線路について計算して棒グラフとして示したものである。図１７はエレメントポートにおける信号を棒グラフとして示したものである。図１４〜図１７では、横軸に端子Ａ〜Ｐをとり、縦軸に振幅をとる。なお、給電信号のポート間位相差は９番目のポートＩに電力集中するようにπ／１６（１１．２５度）とした。図１３〜図１７から明らかなように、増幅器にかかる負荷が均一化され、増幅器に要求される出力を小さくすることができる。
【００４３】
図１８は本方法により増幅器を配置したビーム形成回路を具備するフェーズドアレーアンテナを示したものである。この場合には、電力集中の度合いが最も小さくなる第２段ハイブリットと第３段ハイブリットの間に増幅器を配置することによって増幅器にかかる負荷が均一化され、フェーズドアレーアンテナのビーム方向やビーム数に関わり無く、常に高い出力を得ることが可能になる。また、増幅器に要求される出力を小さくすることで軽量化および低コスト化が可能となる。
【００４４】
【発明の効果】
以上説明したように、本発明によれば、マトリクス回路のエレメントポートまたはビームポートを通過する信号強度に偏りがある場合でも各々の増幅器を通過する信号強度を平坦化することが可能であり、特定の増幅器に電力集中した場合の最大電力値を低減して増幅器に要求される出力を小さくするとともに、増幅器にかかる負荷が均一化することから増幅器全体を比較的高効率で動作させることが可能となる。また、本方法によって、増幅器を配置することを特徴とするビーム形成回路を具備するフェーズドアレーアンテナは増幅器に要求される出力を小さくすることで軽量化および低コスト化が可能である。また、増幅器にかかる負荷を均一化することでフェーズドアレーアンテナのビーム方向やビーム数に関わり無く、常に高い出力を得ることが可能である。なお、複数種類の増幅器を用意しなくとも単一種類の増幅器を用いて増幅器全体を比較的高効率で動作させることが可能となることから、ＢＦＮの設計および調整が比較的容易であると同時に低消費電力化が実現される。
【図面の簡単な説明】
【図１】本発明第一実施例のビーム形成回路を用いたフェーズドアレーアンテナの構成図。
【図２】本発明技術を説明するための８ポートマトリクス回路の結線図。
【図３】ビームポートにおける信号を棒グラフとして示した図。
【図４】第１段ハイブリットと第２段ハイブリットの間の信号分布を示す図。
【図５】第２段ハイブリットと第３段ハイブリットの間の信号分布を示す図。
【図６】エレメントポートにおける信号分布を示す棒グラフ。
【図７】本発明実施例を説明するための１６ポートマトリクス回路の結線図。
【図８】第一実施例のビームポートにおける信号を棒グラフとして示した図。
【図９】第一実施例の第１段ハイブリットと第２段ハイブリットの間の信号分布を示す図。
【図１０】第一実施例の第２段ハイブリットと第３段ハイブリットの間の信号分布を示す図。
【図１１】第一実施例の第３段ハイブリットと第４段ハイブリットの間の信号分布を示す図。
【図１２】第一実施例のエレメントポートにおける信号分布を示す棒グラフ。
【図１３】第二実施例のビームポートにおける信号を棒グラフとして示した図。
【図１４】第二実施例の第１段ハイブリットと第２段ハイブリットの間の信号分布を示す図。
【図１５】第二実施例の第２段ハイブリットと第３段ハイブリツトの間の信号分布を示す図。
【図１６】第二実施例の第３段ハイブリットと第４段ハイブリットの間の信号分布を示す図。
【図１７】第二実施例のエレメントポートにおける信号分布を示す棒グラフ。
【図１８】本発明第二実施例のビーム形成回路を用いたフェーズドアレーアンテナの構成図。
【図１９】従来構成の８ポートマトリクス回路を説明する図。
【図２０】マトリクス回路を用いた直接放射型アンテナのＢＦＮを説明する図。
【図２１】マトリクス回路を用いたクラスタ給電型アンテナのＢＦＮを説明する図。
【図２２】反射鏡を用いたクラスタ給電型アンテナを説明する図。
【図２３】従来技術の増幅器位置を説明する図（エレメントポートと素子アンテナの間に増幅器を配置する場合）。
【図２４】従来技術の増幅器位置を説明する図（ビームポートとビーム制御回路の間に増幅器を配置する場合）。
【符号の説明】
１、２、３ ビームポートにおける給電信号の振幅分布（それそれ位相面５、６、７に対応）
４ エレメントポートにおける信号の振幅分布
５ 振幅分布１に対応するエレメントポートにおける信号の位相面
６ 振幅分布２に対応するエレメントポートにおける信号の位相面
７ 振幅分布３に対応するエレメントポートにおける信号の位相面
８ ビームポートにおける給電信号の振幅分布
９、１０、１１ ビームポートにおける給電信号の位相面（それそれ励振分布１２、１３、１４に対応）
１２ 位相面９に対応する素子アンテナにおける励振分布
１３ 位相面１０に対応する素子アンテナにおける励振分布
１４ 位相面１１に対応する素子アンテナにおける励振分布
１５ 励振分布１２に対応するアンテナビーム方向
１６ 励振分布１３に対応するアンテナビーム方向
１７ 励振分布１４に対応するアンテナビーム方向
＃１〜＃１６、Ａ〜Ｐ 端子[0001]
BACKGROUND OF THE INVENTION
The present invention relates to a beam forming circuit using a matrix circuit in which the phase difference between adjacent ports on the output side changes depending on the position of a signal input port, and in particular, the matrix circuit includes a hybrid and a phase shifter. Arrangement method when there is an FFT (Fast Fourier Transform) relationship between the output signal and the output signal, a beam forming circuit in which the amplifier is arranged using this method, and a phased circuit including this beam forming circuit Related to array antenna.
[0002]
[Prior art]
A matrix circuit composed of a hybrid and a phase shifter is called a Butler matrix circuit, and the phase difference between adjacent ports on the output side changes depending on the position of the signal input port. It is used as a beam forming circuit (BFN) for an antenna capable of forming a directed beam [Reference: IEICE “Antenna Engineering Handbook”, Chapter 5, Ohm Co.].
[0003]
FIG. 19 shows an 8-port matrix circuit composed of three hybrid stages (K = 3). The number of ports N in a matrix circuit composed of K-stage hybrids is 2 ^K In the case of FIG. 19, N = 8 (= 2 ³ )
[0004]
In FIG. 19, the numerical value described in the square representing the phase shifter indicates the phase delay amount (unit: degree). In general, when a matrix circuit is used as an antenna BFN, a terminal to which an element antenna is connected is referred to as an element port, and a terminal for feeding a signal on the side opposite to the element port is referred to as a beam port. The alphabets written in the element port and the numbers written in the beam port indicate the position of the element port and the position of the beam port when the matrix circuit is used as the BFN of the antenna, and the input signal at the beam port (or element port) Butler matrix circuit is sometimes called a network FFT circuit because there is an FFT relationship between the output signal at the element port (or beam port).
[0005]
Signals input to the matrix circuit are distributed in the matrix circuit and output with a phase difference between ports corresponding to the position of the input beam port. Since the phase gradient (phase difference between ports) generated on the output side differs depending on the port position where the signal is input, the port position of the matrix circuit that feeds power when an element antenna is connected to the output port to form an array antenna The beam direction changes according to the above.
[0006]
FIG. 20 is a diagram for explaining a BFN of a direct radiation antenna using a matrix circuit. In this case, in order to obtain a low sidelobe pattern, power is supplied to each beam using a plurality of beam ports. In the figure, numeral 2 represents the amplitude distribution of the feed signal at the beam port, and numerals 4 and 6 represent the amplitude distribution and phase plane of the signal at the element port, respectively. Note that the phases of the feed signals at the beam port are all in phase. As is clear from the fact that there is an FFT relationship between the input signal and the output signal of the matrix circuit, the position of the beam port to be fed is shifted laterally while maintaining the amplitude distribution of the feed signal of the beam port. In this case, the amplitude distribution of the signal at the element port remains the same, and only the phase inclination changes to form beams in different directions. Numerical symbols 1 and 3 represent the amplitude distribution of the feed signal when the position of the beam port to be fed is shifted, and numeric symbols 5 and 7 represent the phase plane of the signal at the corresponding element port [ Literature: “A method of constructing a multi-beam matrix antenna having good pattern characteristics”, Shingaku Sodai, B-1-70, September 1998].
[0007]
FIG. 21 is a diagram for explaining the BFN of a cluster-fed antenna using a matrix circuit, and FIG. 22 is a diagram for explaining a cluster-fed antenna using a reflecting mirror. In this case, the element antenna is located in the vicinity of the focal point of the reflecting mirror, and the beam direction is changed by changing the position of the excited element antenna. Reference numerals 12, 13, and 14 are excitation distributions in the element antenna (or element port), and reference numerals 15, 16, and 17 indicate antenna beam directions corresponding to the excitation distributions 12, 13, and 14, respectively. Since the BFN of the cluster-fed antenna needs to change the position of the signal distribution at the element port, the direct radiation antenna BFN described in FIG. 20 has a relationship between the signal distribution of the element port and the signal distribution of the beam port. The appearance is reversed. The numerical symbol 8 shown in FIG. 21 represents the amplitude distribution of the feed signal at the beam port, and the numeric symbols 9, 10, and 11 represent the phase plane of the feed signal at the beam port corresponding to the excitation distributions 12, 13, and 14. [Literature: "A design method for cluster-fed BFN for beam scanning antennas", Shingaku Sodai, B-1-201, March 2000].
[0008]
23 and 24 show the positions of the amplifiers in the prior art in the beam forming circuit using the matrix circuit. FIG. 23 shows a case where an amplifier is arranged between the element port and the element antenna, and FIG. 24 shows a case where an amplifier is arranged between the beam port and the beam control circuit. In general, a direct radiation type antenna BFN often employs the configuration of FIG. 23, and a cluster-feed antenna BFN often employs the configuration of FIG.
[0009]
In the configuration of FIG. 23, when the amplitude distribution of the signal at the element port is substantially uniform, each amplifier is almost equally loaded, and as a whole, the amplifier can be operated with high efficiency. However, when the amplitude distribution of the signal at the element port is not uniform but biased (for example, when a low side lobe is required in a direct radiation antenna or a cluster-fed antenna), each amplifier As a whole, it becomes difficult to operate the amplifier with high efficiency.
[0010]
In the configuration of FIG. 24, when the amplitude distribution of the signal at the beam port becomes a substantially uniform distribution, each amplifier is subjected to a uniform load, and the amplifier can be operated with high efficiency as a whole. . However, when the amplitude distribution of the signal at the beam port is not uniform and is biased (for example, when a low-sidelobe primary radiation beam is required in a cluster-fed antenna, or in a direct radiation antenna) Therefore, a large variation occurs in the load of each amplifier, and it becomes difficult to operate the amplifier with high efficiency as a whole.
[0011]
In general, regardless of the direct radiation type or cluster feed type antenna configuration, the beam formed by the BFN often requires low sidelobe characteristics, and the signal amplitude distribution at the element port or beam port is not uniform. , Will be biased.
[0012]
When a plurality of types of amplifiers with different outputs are arranged, the amount of delay and temperature characteristics of the passing phase differ depending on the type of amplifier, so that the amplitude phase accuracy of the BFN is deteriorated and adjustment becomes difficult. Further, in order to realize an increase in development cost and a redundant configuration, it is necessary to prepare a plurality of types of spare amplifiers, resulting in a problem that a redundant configuration circuit for improving reliability becomes large-scale. Also, when amplifying using the same type of amplifier, it is necessary to arrange an amplifier with a high output that can handle the port with the largest load on each amplifier. The operation is performed with low efficiency, and the efficiency of the amplifier as a whole is reduced. Furthermore, a high-power amplifier represented by a high-power solid-state amplifier (SSPA) for communication is expensive, and an amplifier having an output twice as high is generally more than twice as expensive. For this reason, BFN is expensive.
[0013]
[Problems to be solved by the invention]
As described above, in the conventional amplifier arrangement method, due to the deviation of the signal intensity passing through the element port or beam port, a part of the power is concentrated, which requires a high-power amplifier and increases the cost. At the same time, there is a problem that the efficiency of the amplifier of the entire BFN deteriorates. In addition, when a plurality of types of amplifiers having different outputs are used, the amount of delay and temperature characteristics of the passing phase differ depending on the type of amplifier, so that the amplitude phase accuracy of the BFN is deteriorated and adjustment becomes difficult, and at the same time, the amplifier is designed and developed There was a problem that the cost increased. Further, when a plurality of types of amplifiers are used, there is a drawback that a redundant configuration circuit for improving reliability becomes large-scale.
[0014]
The present invention has been made against such a background, and even when the signal intensity passing through the element port or beam port of the matrix circuit is biased, the signal intensity passing through each amplifier can be flattened. It is possible to reduce the maximum power value when power is concentrated on a specific amplifier to reduce the output required for the amplifier, and the load on the amplifier is made uniform, so that the entire amplifier can be operated with relatively high efficiency. In addition, the phased array antenna equipped with the beam forming circuit characterized by the arrangement of the amplifier can be reduced in weight and cost by reducing the output required for the amplifier by this method. In addition, by equalizing the load on the amplifier, regardless of the beam direction and the number of beams of the phased array antenna, In addition, since it is possible to operate the entire amplifier with relatively high efficiency using a single type of amplifier without preparing a plurality of types of amplifiers, An object of the present invention is to provide a beam forming circuit for a phased array antenna and a method for arranging a phased array antenna and an amplifier, which are relatively easy to design and adjust and at the same time realize low power consumption.
[0015]
[Means for Solving the Problems]
As explained above, in the prior art amplifier arrangement method, due to the deviation of the signal intensity passing through the element port or beam port, a part of the power is concentrated and a high output amplifier is required. There is a problem that the efficiency of the amplifier of the entire BFN deteriorates at the same time as the cost increases. In addition, when a plurality of types of amplifiers having different outputs are used, the amount of delay and temperature characteristics of the passing phase differ depending on the type of amplifier, so that the amplitude phase accuracy of the BFN is deteriorated and adjustment becomes difficult. There was a problem that increased. Further, when a plurality of types of amplifiers are used, there is a drawback that a redundant configuration circuit for improving reliability becomes large-scale.
[0016]
In the amplifier arrangement method of the present invention, the number of hybrid stages constituting the matrix circuit used in the BFN is K, and the first-stage hybrid, the second-stage hybrid,..., The K-stage hybrid in order from the hybrid on the beam port side. And the power supply signal at the beam port of the matrix circuit is f ₀ (I), {i = 1, 2, 3, ..., 2 ^K-1 , 2 ^K } And the signal f for the parameters L = 1, 2,..., K−1. _L (I) = 2 ^-1/2 × f _L-1 (I) +2 ^-1/2 × f _L-1 (I + 2 ^KL ), {I = 1, 2, 3, ..., 2 ^KL-1 , 2 ^KL } And define the signal f _L (I), {i = 1, 2, 3, ..., 2 ^KL-1 , 2 ^KL } The value of L that minimizes the maximum value of _min L _min Stage hybrid and second (L _min +1) The most important feature is that an amplifier is arranged between the hybrid stages.
[0017]
This makes it possible to flatten the frequency of signals passing through each amplifier even when the signal intensity passing through the element port or beam port is biased. This reduces the maximum power value when power is concentrated on a specific amplifier, reduces the output required for the amplifier, and equalizes the load on the amplifier, so that the entire amplifier operates with relatively high efficiency. It becomes possible to make it.
[0018]
FIG. 2 is a connection diagram showing a path of a signal flowing through an 8-port matrix circuit (K = 3, N = 8) in order to explain the technique of the present invention. Note that the phaser is omitted for simplification of the drawing. In a matrix circuit, a signal input to any one port is distributed by the hybrid and then output to all ports on the opposite side with a certain phase gradient (phase difference between ports) determined by the port position where the signal is input. The On the contrary, signals input to a plurality of ports with a constant phase gradient (phase difference between ports) are distributed and synthesized by the hybrid, and then output to a port position corresponding to the phase gradient of the input signal. . When the signal power is concentrated on only one port on the output side, the inter-port phase difference (2q− (N + 1)) π / N, {q = 1, 2, 3,... This is when a signal is input with an equal amplitude.
[0019]
Table 1 shows the signal f when the signal is fed to the central four ports (terminals # 3, # 4, # 5, and # 6) of the beam port with an amplitude ratio of 2: 3: 3: 2. _L The calculation result of (i) is shown.
[0020]
[Table 1]

[0021]
FIG. 3 shows the signal at the beam port as a bar graph. The horizontal axis represents terminals A to H, and the vertical axis represents amplitude. It should be noted that the total of the supplied power is standardized to be 1. Signal f ₁ (1), f ₁ (2), f ₁ (3), f ₁ (4) represents the amplitude value when the power supply signal input to each first-stage hybrid is distributed and combined so as to strengthen each other at the exit of the hybrid. Signal f ₂ (1), f ₂ (2) represents the amplitude value when the signals that have passed through the first stage hybrid are distributed and combined so as to strengthen each other at the exit of the second stage hybrid. The ellipse shown in FIG. ₁ (1), f ₁ (2), f ₁ (3), f ₁ (4) and signal f ₂ (1), f ₂ (2) shows the location of the target signal path. The signal f ₁ (1), f ₁ (2), f ₁ (3), f ₁ The maximum value of (4) is 0.416025, and the signal f ₂ (1), f ₂ The maximum value of (2) is 0.49029.
[0022]
4 and 5 respectively show the signal distribution between the first-stage hybrid and the second-stage hybrid and the signal distribution between the second-stage hybrid and the third-stage hybrid in the regions indicated by ellipses in FIG. Is calculated and shown as a bar graph. FIG. 6 shows the signal at the element port as a bar graph. 4 to 6, the horizontal axis represents terminals A to H, and the vertical axis represents amplitude. Note that the phase difference between the ports of the power feeding signal was determined from (2q− (N + 1)) π / N so that the power concentration of the signal was the largest. In this case, the power is concentrated on the fifth (q = 5) element port E, but the maximum value of the signal amplitude is the same when the signal is concentrated on other element ports. The maximum amplitude value of the signal at the beam port is 0.588348, the maximum amplitude value of the signal between the first stage hybrid and the second stage hybrid is 0.416025, and the maximum signal value between the second stage hybrid and the third stage hybrid is maximum. The amplitude value is 0.49029, and the maximum amplitude value at the element port is 0.693375. As is clear from these results, the signal f _L (I), {i = 1, 2, 3,. 2 ^KL-1 , 2 ^KL }, The smallest value of L is 1, and the degree of power concentration is the smallest. By placing the amplifier between the first stage hybrid and the second stage hybrid, the load on the amplifier is made uniform. Thus, the output required for the amplifier can be reduced.
[0023]
From the above, the amplifier arrangement method of the present invention makes it possible to flatten the signal intensity passing through each amplifier even when the signal intensity passing through the element port or beam port is biased. This reduces the maximum power value when power is concentrated on a specific amplifier, reduces the output required for the amplifier, and equalizes the load on the amplifier, so that the entire amplifier operates with relatively high efficiency. It becomes possible to make it. Further, according to this method, a phased array antenna having a beam forming circuit characterized by arranging an amplifier can be reduced in weight and cost by reducing the output required for the amplifier. Further, by making the load applied to the amplifier uniform, it is possible to always obtain a high output regardless of the beam direction and the number of beams of the phased array antenna. Since it is possible to operate the entire amplifier with relatively high efficiency using a single type of amplifier without preparing a plurality of types of amplifiers, the design and adjustment of the BFN is relatively easy. Low power consumption is realized.
[0024]
That is, according to the first aspect of the present invention, an element port having a terminal to which an element antenna is connected, a beam port having a terminal for feeding a signal to the element antenna, and a terminal for feeding a signal to the beam port And a beam forming circuit for a phased array antenna having a matrix circuit including means for changing a phase difference between adjacent terminals of the element port according to the position of the element port.
[0025]
Here, a feature of the present invention is that the means for changing the phase difference includes hybrids connected in multiple stages, where the number of stages of the hybrid is K, and the first stage in order from the hybrid on the beam port side. A hybrid, a second-stage hybrid,..., A K-stage hybrid, and a power supply signal at the beam port of the matrix circuit is f ₀ (I), {i = 1, 2, 3, ..., 2 ^K-1 , 2 ^K } And the signal f for the parameters L = 1, 2,..., K−1. _L (I) = 2 ^-1/2 × f _L-1 (I) +2 ^-1/2 × f _L-1 (I + 2 ^KL ), {I = 1, 2, 3, ..., 2 ^KL-1 , 2 ^KL } And define the signal f _L (I), {i = 1, 2, 3, ..., 2 ^KL-1 , 2 ^KL } The value of L that minimizes the maximum value of _min L _min Stage hybrid and second (L _min +1) An amplifier is placed between the hybrid stage.
[0026]
A second aspect of the present invention is a phased array antenna comprising the beam forming circuit of the present invention.
[0027]
A third aspect of the present invention is an amplifier arrangement method, wherein a port having a terminal to which an element antenna is connected is called an element port, and a port having a terminal for feeding a signal to the element antenna is a beam port. The number of hybrid stages connected in multiple stages included in a matrix circuit that changes the phase difference between adjacent terminals of the element port according to the position of the terminal that feeds the signal of the beam port is defined as K, and the hybrid on the beam port side To the first-stage hybrid, the second-stage hybrid,..., The K-stage hybrid, and the feed signal at the beam port of the matrix circuit is f ₀ (I), {i = 1, 2, 3, ..., 2 ^K-1 , 2 ^K } And the signal f for the parameters L = 1, 2,..., K−1. _L (I) = 2 ^-1/2 × f _L-1 (I) +2 ^-1/2 × f _L-1 (I + 2 ^KL ), {I = 1, 2, 3, ..., 2 ^KL-1 , 2 ^KL } And define the signal f _L (I), {i = 1, 2, 3, ..., 2 ^KL-1 , 2 ^KL } The value of L that minimizes the maximum value of _min L _min Stage hybrid and second (L _min +1) An amplifier is arranged between the hybrid stage.
[0028]
DETAILED DESCRIPTION OF THE INVENTION
The configuration of the beam forming circuit according to the embodiment of the present invention will be described with reference to FIG. FIG. 1 is a block diagram of a phased array antenna using a beam forming circuit of the present invention.
[0029]
As shown in FIG. 1, the present invention includes an element port having terminals A to P to which an element antenna ant is connected, and a beam port having terminals # 1 to # 16 for feeding signals to the element antenna ant. A phased array antenna including a matrix circuit mat and a beam control circuit con including means for changing a phase difference between adjacent terminals of the element port according to the positions of terminals # 1 to # 16 for feeding signals to the beam port. It is a beam forming circuit.
[0030]
Here, the feature of the present invention is that the means for changing the phase difference includes hybrid hyb connected in multiple stages, where the number of stages of the hybrid hyb is K, and the hybrid hyb on the beam port side in order. The first-stage hybrid, the second-stage hybrid,..., The K-stage hybrid, and the power supply signal at the beam port of the matrix circuit mat is f ₀ (I), {i = 1, 2, 3, ..., 2 ^K-1 , 2 ^K } And the signal f for the parameters L = 1, 2,..., K−1. _L (I) = 2 ^-1/2 × f _L-1 (I) +2 ^-1/2 × f _L-1 (I + 2 ^KL ), {I = 1, 2, 3, ..., 2 ^KL-1 , 2 ^KL } And define the signal f _L (I), {i = 1, 2, 3, ..., 2 ^KL-1 , 2 ^KL } The value of L that minimizes the maximum value of _min L _min Stage hybrid and second (L _min The amplifier amp is disposed between the +1) stage hybrid. As shown in FIG. 1, the phased array antenna of the present invention is configured by including the beam forming circuit of the present invention.
[0031]
In the following, embodiments of the present invention will be described in more detail.
[0032]
(First Example)
A first embodiment of the present invention will be described with reference to FIG. 1 and FIGS. In the first embodiment, in a matrix circuit with a hybrid stage number K = 4 (16 port matrix circuit), the center 10 ports (ports 4, 5, 6,. A case where signal power supply is performed using will be described.
[0033]
FIG. 7 is a connection diagram showing a path of a signal flowing through a 16-port matrix circuit (K = 4, N = 16) for explaining the present embodiment. Note that the phaser is omitted for simplification of the drawing. The ellipse shown in FIG. ₁ (1), f ₁ (2), f ₁ (3), ..., f ₁ (7), f ₁ (8), signal f ₂ (1), f ₂ (2), f ₂ (3), f ₂ (4) and signal f ₃ (1), f ₃ (2) shows the location of the target signal path. Table 2 shows the signal f when the signal is fed to the central 10 ports of the beam port with a Gaussian distribution of edge taper of 10 dB. _L The calculation result of (i) is shown.
[0034]
[Table 2]

[0035]
FIG. 8 shows the power supply signal at the beam port as a bar graph. The horizontal axis represents terminals A to P, and the vertical axis represents amplitude. It should be noted that the total of the supplied power is standardized to be 1. In this case, the signal f _L (I), {i = 1, 2, 3, ..., 2 ^KL-1 , 2 ^KL }, The value of L with the smallest maximum value is 1 (L _min = 1), and an amplifier is disposed between the first-stage hybrid and the second-stage hybrid where the degree of power concentration is the smallest.
[0036]
9, FIG. 10 and FIG. 11 show the signal distribution between the first-stage hybrid and the second-stage hybrid, the signal distribution between the second-stage hybrid and the third-stage hybrid, and the third-stage hybrid, respectively, for confirmation of this method. -The signal distribution between the fourth-stage hybrids is specifically calculated for each line and shown as a bar graph. FIG. 12 shows the signal at the element port as a bar graph. 9 to 12, the horizontal axis represents terminals A to P, and the vertical axis represents amplitude. The phase difference between the ports of the power feeding signal was set to π / 16 (11.25 degrees) so that the power concentrated on the ninth port I. As is clear from FIGS. 9 to 11, the load applied to the amplifier is made uniform, and the output required for the amplifier can be reduced.
[0037]
FIG. 1 shows a phased array antenna having a beam forming circuit in which an amplifier is arranged according to the present method. In this case, by placing the amplifier between the first-stage hybrid and the second-stage hybrid that minimize the power concentration, the load applied to the amplifier is made uniform, and the beam direction and number of beams of the phased array antenna are adjusted. Regardless of it, it becomes possible to always obtain a high output. Further, it is possible to reduce the weight and the cost by reducing the output required for the amplifier.
[0038]
(Second embodiment)
A second embodiment of the present invention will be described with reference to FIGS. In the second embodiment, in the matrix circuit having the number of hybrid stages K = 4 (16 port matrix circuit), the center 10 ports (ports 4, 5, 6,..., 12, 13) of the beam port with a Gaussian distribution with an edge taper of 25 dB. A case where signal power supply is performed using will be described.
[0039]
FIG. 7 is a connection diagram showing a path of a signal flowing through a 16-port matrix circuit (K = 4, N = 16) for explaining the present embodiment. Note that the phaser is omitted for simplification of the drawing. The ellipse shown in FIG. 7 is the signal f as described in the first embodiment. ₁ (1), f ₁ (2), f ₁ (3), ..., f ₁ (7), f ₁ (8), signal f ₂ (1), f ₂ (2), f ₂ (3), f ₂ (4) and signal f ₃ (1), f ₃ (2) shows the location of the target signal path. Table 3 shows the signal f when the signal is fed to the central 10 ports of the beam port with a Gaussian distribution of 25 dB of edge taper. _L The calculation result of (i) is shown.
[0040]
[Table 3]

[0041]
FIG. 13 shows the feed signal at the beam port as a bar graph. The horizontal axis represents terminals A to P, and the vertical axis represents amplitude. It should be noted that the total of the supplied power is standardized to be 1. In this case, the signal f _L (I), {i = 1, 2, 3, ..., 2 ^KL-1 , 2 ^KL ) Is the smallest L value is 2 (L _min = 2), and an amplifier is arranged between the second-stage hybrid and the third-stage hybrid where the degree of power concentration is the smallest.
[0042]
FIG. 14, FIG. 15 and FIG. 16 show the signal distribution between the first-stage hybrid and the second-stage hybrid, the signal distribution between the second-stage hybrid and the third-stage hybrid, and the third-stage hybrid, respectively, for confirmation of this method. -The signal distribution between the fourth-stage hybrids is specifically calculated for each line and shown as a bar graph. FIG. 17 shows the signal at the element port as a bar graph. 14 to 17, the horizontal axis represents terminals A to P, and the vertical axis represents amplitude. The phase difference between the ports of the power feeding signal was set to π / 16 (11.25 degrees) so that the power concentrated on the ninth port I. As apparent from FIGS. 13 to 17, the load applied to the amplifier is made uniform, and the output required for the amplifier can be reduced.
[0043]
FIG. 18 shows a phased array antenna having a beam forming circuit in which an amplifier is arranged according to the present method. In this case, by placing the amplifier between the second stage hybrid and the third stage hybrid where the degree of power concentration is the smallest, the load on the amplifier is made uniform, and the beam direction and the number of beams of the phased array antenna are adjusted. Regardless of it, it becomes possible to always obtain a high output. Further, it is possible to reduce the weight and the cost by reducing the output required for the amplifier.
[0044]
【The invention's effect】
As described above, according to the present invention, it is possible to flatten the signal intensity passing through each amplifier even when the signal intensity passing through the element port or beam port of the matrix circuit is biased. The maximum power value when the power is concentrated on the amplifier of this amplifier is reduced to reduce the output required for the amplifier, and the load on the amplifier is made uniform, so that the entire amplifier can be operated with relatively high efficiency. Become. Further, according to this method, a phased array antenna having a beam forming circuit characterized by arranging an amplifier can be reduced in weight and cost by reducing the output required for the amplifier. Further, by making the load applied to the amplifier uniform, it is possible to always obtain a high output regardless of the beam direction and the number of beams of the phased array antenna. Since it is possible to operate the entire amplifier with relatively high efficiency using a single type of amplifier without preparing a plurality of types of amplifiers, the design and adjustment of the BFN is relatively easy. Low power consumption is realized.
[Brief description of the drawings]
FIG. 1 is a configuration diagram of a phased array antenna using a beam forming circuit according to a first embodiment of the present invention.
FIG. 2 is a connection diagram of an 8-port matrix circuit for explaining the technique of the present invention.
FIG. 3 is a bar graph showing signals at the beam port.
FIG. 4 is a diagram showing a signal distribution between the first-stage hybrid and the second-stage hybrid.
FIG. 5 is a diagram showing a signal distribution between the second-stage hybrid and the third-stage hybrid.
FIG. 6 is a bar graph showing a signal distribution at an element port.
FIG. 7 is a connection diagram of a 16-port matrix circuit for explaining an embodiment of the present invention.
FIG. 8 is a bar graph showing signals at the beam port of the first embodiment.
FIG. 9 is a diagram showing a signal distribution between the first-stage hybrid and the second-stage hybrid in the first embodiment.
FIG. 10 is a diagram showing a signal distribution between the second-stage hybrid and the third-stage hybrid in the first embodiment.
FIG. 11 is a diagram showing a signal distribution between the third-stage hybrid and the fourth-stage hybrid in the first embodiment.
FIG. 12 is a bar graph showing a signal distribution in the element port of the first embodiment.
FIG. 13 is a graph showing signals at the beam port of the second embodiment as a bar graph.
FIG. 14 is a diagram showing a signal distribution between the first-stage hybrid and the second-stage hybrid of the second embodiment.
FIG. 15 is a diagram showing a signal distribution between the second-stage hybrid and the third-stage hybrid in the second embodiment.
FIG. 16 is a diagram showing a signal distribution between the third-stage hybrid and the fourth-stage hybrid in the second embodiment.
FIG. 17 is a bar graph showing a signal distribution in the element port of the second embodiment.
FIG. 18 is a configuration diagram of a phased array antenna using a beam forming circuit according to a second embodiment of the present invention.
FIG. 19 is a diagram illustrating an 8-port matrix circuit having a conventional configuration.
FIG. 20 is a diagram illustrating a BFN of a direct radiation antenna using a matrix circuit.
FIG. 21 is a diagram for explaining the BFN of a cluster-fed antenna using a matrix circuit.
FIG. 22 is a diagram for explaining a cluster-fed antenna using a reflecting mirror.
FIG. 23 is a diagram for explaining the position of a conventional amplifier (when an amplifier is arranged between an element port and an element antenna).
FIG. 24 is a diagram for explaining a position of an amplifier in the prior art (when an amplifier is disposed between a beam port and a beam control circuit).
[Explanation of symbols]
1, 2, 3 Amplitude distribution of feed signal at beam port
4 Amplitude distribution of signal at element port
5 Signal phase plane at element port corresponding to amplitude distribution 1
6 Phase plane of signal at element port corresponding to amplitude distribution 2
7 Phase plane of signal at element port corresponding to amplitude distribution 3
8 Amplitude distribution of feed signal at beam port
9, 10, 11 Phase plane of feed signal at beam port (corresponding to excitation distribution 12, 13, 14 respectively)
12 Excitation distribution in the element antenna corresponding to the phase plane 9
13 Excitation distribution in the element antenna corresponding to the phase plane 10
14 Excitation distribution in the element antenna corresponding to the phase plane 11
15 Antenna beam direction corresponding to excitation distribution 12
16 Antenna beam direction corresponding to excitation distribution 13
17 Antenna beam direction corresponding to excitation distribution 14
# 1 to # 16, A to P terminals

Claims (3)

An element port having a terminal to which the element antenna is connected, a beam port having a terminal for feeding a signal to the element antenna, and an adjacent terminal of the element port depending on the position of the terminal for feeding a signal to the beam port And a beam outputted from the element antenna by generating a bias in the signal amplitude inputted to the beam port or the signal amplitude or phase difference outputted to the element port. In the beam forming circuit of a phased array antenna that controls the pattern or beam direction ,
The means for changing the phase difference includes hybrids connected in multiple stages,
The number of stages of the hybrid and K, the first stage hybrid in order from hybrid of the beam port side, a second-stage hybrid, ..., and the K-stage hybrid DOO,
The power supply signal at the beam port of the matrix circuit is f ₀ (i), {i = 1, 2, 3,..., 2 ^K−1 , 2 ^K }, and the parameters L = 1, 2,. With respect to the signal f _L (i) = ^{2−1 / 2} × f _L−1 (i) + ^{2−1 / 2} × f _L−1 (i + 2 ^K−L ), {i = 1, 2, 3,... ^K-L-1 , ^2K-L },
When the value of L that minimizes the maximum value of the signal f _L (i), {i = 1, 2, 3,..., 2 ^KL−1 , 2 ^KL } is L _min ,
An amplifier is disposed between the L _min -th hybrid and the (L _min +1) -th hybrid.   A phased array antenna comprising the beam forming circuit according to claim 1. A port having a terminal to which an element antenna is connected is referred to as an element port, and a port having a terminal for supplying power to the element antenna is referred to as a beam port. The number of hybrid stages connected in multiple stages included in the matrix circuit that changes the phase difference between adjacent terminals of the port is represented by K,
The first stage hybrid in order from hybrid of the beam port side, a second-stage hybrid, ..., and the K-stage hybrid DOO,
The power supply signal at the beam port of the matrix circuit is f ₀ (i), {i = 1, 2, 3,..., 2 ^K−1 , 2 ^K }, and the parameters L = 1, 2,. With respect to the signal f _L (i) = ^{2−1 / 2} × f _L−1 (i) + ^{2−1 / 2} × f _L−1 (i + 2 ^K−L ), {i = 1, 2, 3,... ^K-L-1 , ^2K-L },
Signal _{f L (i), {i} = 1,2,3, ..., 2 K-L-1, 2 K-L} When the value of the maximum value of the most smaller L was _{L min,} the _{L min} An amplifier is arranged between the stage hybrid and the (L _min +1) th stage hybrid,
An amplifier arrangement characterized by controlling the beam pattern or beam direction output from the element antenna by generating a bias in the signal amplitude input to the beam port or the signal amplitude or phase difference output to the element port Method.

Images