JP3500328B2 - Inverter device - Google Patents

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an inverter device for driving and controlling a permanent magnet motor having, for example, a fan or a pump as a load.

[0002]

One of the driving methods in this type of inverter device is to detect the position of the rotor of a brushless motor, which is a permanent magnet motor, to obtain a position signal, and to fix the position signal based on the position signal. There is one that determines the conduction phase angle (commutation timing) with respect to the child winding. In such a drive system, the phase of the position signal shifts according to the number of rotations of the motor, the load torque, and the like, so that there is a problem that the shift also occurs in the energization phase and the efficiency of the motor decreases.

As a conventional technique for solving this problem, there is one disclosed in, for example, Japanese Patent Application Laid-Open No. 7-111795. In this conventional technique, the number of rotations of the motor and the load torque are detected, and the microcomputer reads a correction phase value corresponding to the detected values from the data map of the storage device. Then, by calculating the time corresponding to the correction phase value and correcting the output timing of the energization switching signal, the motor is energized and driven by 120 ° in the optimum phase.

However, in this conventional technique,
In order to obtain the time corresponding to the correction phase value, the microcomputer needs to perform a complicated calculation, and it is necessary to create a control program for performing the calculation. Further, in order to perform the calculation, a storage device for storing various data including a map is also required. Further, even when the phase is optimally corrected, there is a problem that vibration and noise are generated because the motor is energized by 120 ° with a rectangular wave.

The present invention has been made in view of the above circumstances, and an object thereof is to make it possible to optimally correct the energization phase for a permanent magnet motor with a simple structure without performing complicated calculations, and An object of the present invention is to provide an inverter device that can drive a magnet motor with low vibration and low noise.

[0006]

In order to achieve the above object, an inverter device according to a first aspect of the present invention is an induction device which is generated in stator windings of a plurality of phases according to a rotational position of a rotor constituting a permanent magnet motor. A Hall IC that outputs a position signal having a constant phase relationship with the voltage, a period measuring unit that measures a changing period of the position signal, and a pulse generating unit that generates a plurality of clock pulses within the changing period. A phase estimating means for estimating the phase of the rotor based on a count value of the counter, which includes a counter that counts the number of generated clock pulses, and that uses a timing at which the position signal changes as a reference; Phase correction means for setting a correction value in the counter to correct the phase of the rotor, and the phase correction means based on the corrected phase
PWM for applying a sinusoidal current to the stator winding
Means for outputting a signal and driven by the PWM signal
And an inverter main circuit composed of transistors .

According to this structure, the pulse generating means is
A plurality of pulses are generated within the change cycle of the position signal, and the phase estimating means counts the number of clock pulses generated by the pulse generating means by the counter. Then, the phase of the rotor is estimated based on the count value of the counter based on the timing of changing the position signal, and the sine wave is applied to the stator winding.
A PWM signal for energizing a wavy current is output .

That is, since the phase of the rotor can be obtained with a finer resolution than the change cycle of the position signal, vibrations, noises, etc. generated in the permanent magnet motor can be obtained according to the detailed phase of the rotor. A PWM signal that can be suppressed more than the energization signal can be formed. Further, since the phase correction unit corrects the phase by setting the correction value in the counter at the reference timing of the position signal, the phase correction unit can be appropriately operated without using a storage device for performing complicated calculation or storing data. It is possible to energize the stator winding at various commutation timings.

[0009]

[0010]

[0011]

[0012]

[0013]

[0014]

[0015]

[0016]

[0017]

[0018]

[0019]

[0020]

[0021]

[0022]

BEST MODE FOR CARRYING OUT THE INVENTION A first embodiment of the present invention will be described below with reference to FIGS. In FIG. 1 showing the electrical configuration, a DC power supply 1 is generated by full-wave rectifying a commercial AC power supply with a diode bridge or the like and smoothing it with a smoothing capacitor (neither is shown). Both the positive and negative terminals of the DC power supply 1 are connected to the DC bus 2a,
It is connected to the power source input terminal of the inverter main circuit (driving means) 3 via 2b.

The inverter main circuit 3 is composed of six transistors 4U, 4V, 4W and 4X, 4Y, 4Z connected in a three-phase bridge, and a flywheel diode is provided between the collector and the emitter of each transistor 4. 5U,
5V, 5W and 5X, 5Y, 5Z are connected. Output terminals 3U, 3V, 3W of the inverter main circuit 3 are, for example, in a permanent magnet motor 6 such as a brushless motor, each phase stator winding (hereinafter simply referred to as winding) 6U, 6V having one end star-connected. , 6W are connected to the other terminals, respectively.

Further, the permanent magnet motor 6 has a rotor 6R which is arranged so as to have a predetermined air gap with the windings 6U, 6V, 6W, and is constituted by a permanent magnet. Then, inside the permanent magnet motor 6, a position detector (position signal output means) 7 (7U, 7V, 7W) composed of a Hall IC is arranged in order to detect the rotational position of the rotor 6R. There is. Then, the position detector 7 (7U, 7V, 7
The position signals Hu, Hv, Hw output by W) are
Cycle measuring circuit (cycle measuring means) 8, phase correcting circuit (phase correcting means) 9 and rotational speed detecting circuit (rotating speed detecting means) 1
It is given to 0.

The position signals Hu, Hv, Hw are, as shown in FIG. 2, high level and negative half wave during the positive half-wave period of the induced voltages Eu, Ev, Ew generated in the windings 6U, 6V, 6W of the respective phases. For a signal whose period is low level, for example, an electrical angle of 3
The position detectors 7U, 7V, 7W are arranged so as to be output as signals having a 0 ° phase delay.

The cycle measuring circuit 8 includes position signals Hu, Hv,
A rising edge or a falling edge, which is the timing when any one of the Hw signal levels changes, is detected, and their output intervals, that is, the time corresponding to the change cycle T (see FIG. 3B) is counted (not shown). To count. And
The count value is output to the pulse generation circuit (pulse generation means) 11 as cycle data TD.
The count cycle of the counter is set to be sufficiently shorter than the change cycle T. The change cycle T corresponds to an electrical angle of 60 °.

The pulse generating circuit 11 is, for example, a digital P
It is configured as a frequency multiplication circuit to which the LL circuit is applied. For example, when a frequency corresponding to the change period T of the position signals Hu to Hw is f, a frequency 32f (cycle T / 32) obtained by multiplying the frequency f by 32 is obtained. The clock pulse CK is generated and output (see FIG. 3C).

Specifically, for example, when the period data TD given from the period measuring circuit 8 is latched and right-shifted by 5 bits to obtain the period data TD / 32, the period data TD / 32 is obtained.
Are down-counted in the same count cycle as the counter of the cycle measuring circuit 8. Then, when the count value becomes 0, a clock pulse is generated and output to the phase estimating circuit (phase estimating means) 12, and at the same time, the next given period data TD is latched and shifted, and then down. Set in the counter. By repeating the above processing, the clock pulse CK having the frequency 32f is generated and output.

The phase estimation circuit 12 uses, for example, the position signal Hu.
The rising edge of is used as a reference (count value “0”) to count the number of clock pulse CK inputs by the counter, and the count value CNT estimates the detailed rotation position (phase) of the rotor 6R of the permanent magnet motor 6. . That is, the count value “1” is the electrical angle 60 ° / 32 = 1.8.
This corresponds to 75 °. Therefore, the phase estimation circuit 1
2 is an electrical angle of 360 ° when "192" is counted
(See FIG. 3D), the rising edge of the position signal Hu of the next cycle is given. The count value CNT counted by the phase estimation circuit 12 is supplied to the voltage signal forming circuit (voltage signal forming means) 13.

The voltage signal forming circuit 13 is composed of, for example, a ROM and a D / A conversion circuit. As shown in FIG. 3E, the waveform data of the voltage signal VSIN having the amplitude ratio of the sine wave is stored. Has been done. An offset is added so that the negative maximum value of the AC amplitude of the voltage signal VSIN becomes the data "0". Then, the count value CNT given from the phase estimation circuit 12 is given as a read address of the waveform data of the voltage signal VSIN, and the rotor 6R.
The waveform data corresponding to the rotational position of is read.

A voltage command (not shown) is externally applied to the voltage signal forming circuit 13, and the waveform data value of the read voltage signal VSIN is:
A coefficient according to the voltage command is multiplied. The analog voltage signal obtained by D / A converting the waveform data value is a drive signal forming circuit (drive signal forming means) 1
4 is output. Further, for example, when the voltage signal forming circuit 13 reads the waveform data value of the voltage signal VSIN corresponding to the U phase with reference to the position signal Hu,
The waveform data values corresponding to the 120 ° and 240 ° delayed phases with respect to the waveform data values are set as the waveform data values corresponding to the V phase and the W phase. Then, each is D / A converted and output to the drive signal forming circuit 14.

Triangle wave generating circuit (carrier wave generating means) 15
As shown in FIG. 3E, generates a triangular wave VTR which is a carrier of the PWM signal and outputs it to the drive signal forming circuit 14. The drive signal forming circuit 14 is composed of a comparator or the like, and has a level of the voltage signal VSIN given from the voltage signal forming circuit 13 and the triangular wave VTR.
And outputs the PWM signals Su, Sv, Sw that are high level when the former level is high (see FIG. 3 (f)). The PWM signal is passed through a base drive circuit (not shown) including a photocoupler and the like, and the transistors 4U, 4V, 4W of the inverter main circuit 3 are supplied.
To be given as a base signal. Further, the transistors 4X, 4Y, and 4Z are supplied with the inverted base signal level as a base signal.

On the other hand, the rotation speed detection circuit 10 uses the position signal H
For any one of u to Hw, for example, the number of rising edge outputs per second is counted as the number of revolutions of the permanent magnet motor 6, and a voltage signal Vf having a level corresponding to the number of revolutions is added by an adding circuit (adding means). F / by outputting to 18
V conversion is performed. Here, as shown in FIG. 4, the permanent magnet motor 6 is assumed to be operated in the rotation speed range of 0 to 60 Hz, and the range of the output voltage Vf is, for example, 0 to 2.5 V depending on the rotation speed range. Is set to output linearly. When the rotation speed exceeds 60 Hz, the voltage Vf is output at a constant 2.5V.

A current sensor (current detecting means, torque detecting means) 16 such as a current transformer is inserted in the DC bus 2 b, and a detection signal of the current sensor 16 is given to a peak hold circuit 17. ing. The DC power supply current detected by the current sensor 16 is a current (DC link current) obtained by rectifying and smoothing the AC power supply.
The level of V T fluctuates at the AC power supply frequency as shown in FIG. The peak hold circuit (current value processing means, torque detection means) 17 is a well-known circuit including a capacitor and an operational amplifier, and holds the peak level Vp of the detection signal of the current sensor 16 and outputs it to the addition circuit 18. It is like this.

Here, as shown in FIG. 6, the permanent magnet motor 6 is assumed to be operated in a load torque range of 0 to 1 N · m, and the range of the output voltage VT is, for example, 0 according to the load torque range. It is set to output linearly at ~ 2.5V. Further, when the load torque exceeds 1 N · m, VT is output at a constant 2.5V.

The adder circuit 18 is composed of an operational amplifier, a resistor, and the like, and adds the voltage signal levels respectively output from the rotation speed detection circuit 10 and the peak hold circuit 17 in an analog manner to generate an A / D conversion circuit ( A / D conversion means) 1
It is designed to output to 9. A / D conversion circuit 19
Is an analog voltage signal given by the adder circuit 18
The D / D conversion is performed and the digital data is output to the phase correction circuit 9. Here, as shown in FIG.
The D conversion circuit 19 converts the voltage range of the input signal of 0 to 5V by 5 bits and outputs digital data of "0" to "32".

The phase correction circuit 9 loads the digital data output from the A / D conversion circuit 19 into the counter of the phase estimation circuit 12 as the phase correction value PC, triggered by the rising edge of the position signal Hu. There is. That is, the counter of the phase estimation circuit 12 originally has a count value of "0" at the rise of the position signal Hu,
The data loaded by the phase correction circuit 9 is set as an initial value (see FIG. 3D).

Next, the operation of this embodiment will be described with reference to FIG. When a start command signal is output from the outside, a start signal generating circuit (not shown) connected to the drive signal forming circuit 14 outputs a 120 ° energization signal for a certain period of time to rotate the permanent magnet motor 6. Then, winding 6
Induced voltage is generated in U, 6V, 6W, and position detector 7U,
The 7V and 7W detect the change in the magnetic field generated in the rotor 6R with the generation of the induced voltage, and detect the position signals Hu and H.
v, Hw are output.

The cycle measuring circuit 8 includes position signals Hu, Hv,
The rising and falling edges of Hw are detected, the time corresponding to the change cycle T (see FIG. 3B) is counted, and the cycle data TD as the count value is counted by the pulse generation circuit 1
Output to 1. The pulse generation circuit 11 uses the position signals Hu ...
A clock pulse CK having a frequency 32f, which is obtained by multiplying the frequency f according to the change period T of Hw by 32, is generated and output to the phase estimation circuit 12 (see FIG. 3C), and the phase estimation circuit 12
Counts the number of clock pulse CK inputs based on the rising edge of the position signal Hu.

At this time, the phase correction circuit 9 is loaded with the phase correction value PC as an initial value in the phase estimation circuit 12. As described above, the phase correction value PC is obtained by A / D converting the sum of the detection signal levels of the rotation speed of the permanent magnet motor 6 and the load torque. When the rotation speed of the permanent magnet motor 6 increases, the output voltage Vf of the rotation speed detection circuit 10 increases, and when the load torque of the permanent magnet motor 6 increases, the output voltage Vp of the peak hold circuit 17 increases.
Rises. Therefore, the phase correction value PC increases as either the rotational speed or the load torque increases, and is corrected so that the energization phase (commutation timing) for the permanent magnet motor 6 is on the leading side.

That is, the windings 6U, 6 of the permanent magnet motor 6
V and 6W have a time constant determined by resistance and inductance, and the currents flowing through these windings 6U, 6V, and 6W are delayed with respect to the applied voltage by a time corresponding to the time constant. Since this delay time is constant regardless of the rotation speed of the permanent magnet motor 6, the higher the rotation speed, the larger the phase delay of the current. Further, the torque of the permanent magnet motor 6 is generated by the product of the induced voltage and the winding current. Therefore, if a phase delay occurs in the winding current, the torque is reduced and the efficiency is reduced. May get out of step.

Based on the above, the phase correction value PC is set and output so that the energization phase to the permanent magnet motor 6 is on the leading side in response to an increase in either the rotational speed or the load torque.

The count value CNT counted by the phase estimating circuit 12 is given to the voltage signal forming circuit 13,
The voltage signal forming circuit 13 reads the waveform data of the voltage signal VSIN according to the count value CNT, performs D / A conversion, and outputs it to the drive signal forming circuit 14. Then, the drive signal forming circuit 14 compares the level of the voltage signal VSIN with the level of the triangular wave VTR to compare the PWM signals Su, Sv, Sw.
Is output (see FIGS. 3 (e) and 3 (f)).

Then, the output terminal 3 of the inverter main circuit 3
As shown in FIG. 8B, U, 3V, and 3W have drive voltages Vu, Vv, and V having PWM waveforms based on the amplitude ratio of the sine wave.
w is generated and the permanent magnet motor 6 rotates. At this time, a sinusoidal energization current flows through each phase winding 6U, 6V, 6W.

As described above, according to the present embodiment, the pulse generating circuit 11 outputs 3 times within the change period T of the position signals Hu to Hw.
The phase estimation circuit 12 generates two clock pulses CK.
Counts the number of the clock pulses CK with reference to the rising edge of the position signal Hu and determines the permanent magnet motor 6
Estimate the phase of the rotor 6R. Then, the voltage signal forming circuit 13 reads out a predetermined voltage signal VSIN corresponding to the phase of the rotor 6R from the memory and forms it.

That is, the phase of the rotor 6R is changed to the position signal Hu
Since it can be obtained with a resolution more detailed than the change period T of Hw to Hw, the voltage signal forming circuit 13 has a voltage signal V having a sinusoidal amplitude ratio according to the detailed phase of the rotor 6R.
It is possible to form SIN and output the energization signal waveform (PWM signal) based on the voltage signal VSIN from the drive signal forming circuit 14. Then, by supplying a sinusoidal current to each phase winding 6U, 6V, 6W of the permanent magnet motor 6, it is possible to suppress the generation of vibration, noise and the like as much as possible.

Further, the phase correction circuit 9 corrects the phase by setting the phase correction value PC in the counter of the phase estimation circuit 12 at the rising edge of the position signal Hu, and the phase correction value PC is set to the phase correction value PC. 6 was used as the A / D conversion value of the added value of the voltage signal level according to the rotation speed and the voltage signal level according to the load torque. Therefore, the phase shift varying depending on the rotational speed of the permanent magnet motor 6 and the load torque is corrected to correct each phase winding 6U to 6U at appropriate commutation timing.
By energizing 6 W, the permanent magnet motor 6 can be operated with high efficiency. Further, since it is not necessary to perform a complicated calculation using a microcomputer or to use a storage device for storing data, the configuration is simplified and the correction process can be performed in a short time.

Further, the phase correction circuit 9 sets the phase correction value PC so as to increase when either the rotation speed or the load torque of the permanent magnet motor 6 increases, so that the phase correction value PC increases in accordance with the increase in the rotation speed or the load torque. The operating efficiency of the permanent magnet motor 6 can be improved by correcting the energizing current phase of the permanent magnet motor 6 that causes a delay to the leading side.

Further, according to this embodiment, the current of the DC power supply 1 is detected by the current sensor 16, and the peak level of the detection signal is held by the peak hold circuit 17. Therefore, the load torque of the permanent magnet motor 6 is appropriately reflected in the phase correction value PC by appropriately sampling the fluctuating detection level of the DC power supply current, performing A / D conversion, and outputting it to the phase correction circuit 9 . be able to.

9 and 10 show a second embodiment of the present invention. The same parts as those in the first embodiment are designated by the same reference numerals and the description thereof will be omitted. Only different parts will be described below. As shown in FIG. 9, in the electrical configuration of the second embodiment, the addition circuit 18, the current sensor 16 and the peak hold circuit 17 are deleted from the configuration of the first embodiment, and the speed control circuit (speed control means) 20 and Phase control circuit (phase control means) 21
Is added.

That is, the speed command of the permanent magnet motor 6 is externally given to one input terminal of the speed control circuit 20 as a voltage signal, and the other input terminal is supplied with the F signal by the rotation speed detection circuit 10. / V converted voltage signal Vf
Is given. Then, the speed control circuit 20 generates a voltage command according to the difference between the speed command and the voltage signal Vf from the rotation speed detection circuit 10 so that they match each other, and the voltage signal forming circuit 13 and the phase control circuit 21. It is designed to output to.

The phase control circuit 21 also has another input terminal to which the voltage signal Vf from the rotation speed detection circuit 10 is applied. And
The phase control circuit 21 differentially amplifies the difference between the voltage command from the speed control circuit 20 and the voltage signal Vf from the rotation speed detection circuit 10 to generate a phase command, and outputs the phase command to the A / D conversion circuit 19. It has become. Other configurations are similar to those of the first embodiment.

Next, the operation of the second embodiment will be described with reference to FIG. FIG. 10 shows the relationship between the voltage signal Vf output by the rotation speed detection circuit 10 and the voltage command output by the speed control circuit 20 when the permanent magnet motor 6 is operated without load. As shown in FIG. 10, the F / V conversion rate in the rotation speed detection circuit 10 is adjusted so that the voltage signal Vf and the voltage command have the same voltage when there is no load.

Then, in the case of controlling at a constant rotation speed (speed), when a load is applied to the permanent magnet motor 6, the speed control circuit 20 increases the voltage command value in order to keep the speed constant. Then, in the phase control circuit 21, the difference between the voltage command and the voltage signal Vf from the rotation speed detection circuit 10 becomes large, so that the phase command value output from the phase control circuit 21 also increases in accordance with the difference. The A / D conversion circuit 19
Since the data obtained by A / D converting the phase command value is output to the phase correction circuit 9 , the correction is performed so as to advance the commutation timing as the load torque of the permanent magnet motor 6 increases.

As described above, according to the second embodiment, the speed control circuit 20 causes the speed command given from the outside and the result that the permanent magnet motor 6 is driven according to the speed command.
The voltage command is set in accordance with the difference from the voltage signal Vf output from the rotation speed detection circuit 10, and the phase control circuit 21 differentially amplifies the difference between the voltage command and the voltage signal Vf from the rotation speed detection circuit 10. Then, the phase command is generated. Then, the phase correction circuit 9 sets the digital data obtained by A / D converting the phase command as the phase correction value PC.

Therefore, as the load torque of the permanent magnet motor 6 increases, the commutation timing can be corrected so as to advance. Further, the rotation speed of the permanent magnet motor 6 can be controlled so as to match the speed command given from the outside as much as possible.

FIG. 11 shows the third embodiment of the present invention and shows the electrical construction of the main part. In the third embodiment, a voltage signal forming circuit (voltage signal forming means) 22 that replaces the voltage signal forming circuit 13 is arranged. The voltage signal forming circuit 22 includes, for example, a series resistance circuit 23 in which n resistors 23R are connected in series, and a selection circuit 24.

One end P0 of the series resistance circuit 23 is connected to the ground, and the other end Pn is given a voltage command from the outside. The connection point P0 of each resistor 23R
Pn is connected to the input terminal of the selection circuit 24. The selection circuit 24 outputs the voltage signal VSIN to the drive signal forming circuit 14 by selecting any one of the connection points P0 to Pn according to the count value CNT given from the phase estimation circuit 12. .

The resistance values of the resistors 23R are not the same, and the selection circuit 24 selects the connection point P0 according to the count value CNT.
Each resistance ratio is set so that one of Pn to Pn can be selected to output the voltage signal VSIN. Further, as in the first embodiment, the count value CNT is "192" and the electrical angle is 36
When it becomes 0 °, the connection number n of the resistor 23R is set to, for example, n.
= 192/2 = 96. Although not specifically shown, the series resistance circuit 23 is actually provided for each phase, and the selection circuit 24 uses the count value CNT.
The connection points P0 to Pn are selected for each phase in accordance with the above.

According to the third embodiment configured as described above, the selection circuit 24 determines the connection point P according to the count value CNT.
By selecting any of 0 to Pn, it is possible to output the voltage signal VSIN having a signal level corresponding to the amplitude ratio of the sine wave. In this case, the maximum amplitude level of the voltage signal VSIN is set directly by the voltage command. Therefore, the permanent magnet motor 6 can be driven with low vibration and low noise as in the first or second embodiment. Further, the voltage signal forming circuit 22 is similar to the voltage signal forming circuit 13 in the ROM and the D / A.
It can be configured at a lower cost without using a conversion circuit.

The present invention is not limited to the embodiments described above and shown in the drawings, but the following modifications and expansions are possible. In the first embodiment, the cycle measuring circuit 8 measures the cycle in which the signal level of any of the position signals Hu to Hw changes, but it may measure the cycle of any one of the position signals. The position detectors 7U to 7W may be provided for any one phase. The pulse generator is
The change cycle is not limited to 32 times, and any number of integers of 2 or more may be used. Further, if the phase estimating means obtains the generation timing information of each pulse in advance, it is not limited to one in which the change cycle is multiplied by a plurality, but for example, a configuration in which a plurality of pulses are generated within one change cycle is provided. Is also good.
The output signal of the peak hold circuit 17 and the output signal of the rotation speed detection circuit 10 are A / D converted by separate A / D conversion means, and the digital data output by each A / D conversion means are added. , May be output to the phase correction circuit 12. Further, in the addition circuit 18, instead of adding the output signals of both, a signal selection means for selectively outputting the one having a higher internal signal level to the A / D conversion circuit 19 may be provided. In that case, the voltage range on the vertical axis shown in FIGS. 4 and 6 may be set to 0-5V.

Further, in the first embodiment, the rotation speed detection circuit 10 and the addition circuit 18 are deleted, and the current sensor 16 is removed.
And only the peak hold circuit 17 side may be provided,
Alternatively, the adder circuit 18, the current sensor 16, and the peak hold circuit 17 may be deleted and only the rotation speed detection circuit 10 side may be provided. Instead of the peak hold circuit 17, as the current value processing means, the detection voltage level output from the current sensor 16 may be averaged by an integrating circuit, or a sample hold circuit for sample holding at a predetermined timing may be arranged. Is also good .

The carrier wave generating means is not limited to the triangular wave, but may be one that generates a sawtooth wave as a carrier wave.
In the second embodiment, the speed control circuit 20 may be omitted and the speed command may be directly applied as a voltage signal to be given to the phase control circuit 21. The position signal output means is the position detector 7
Not only U, 7V, 7W, but also those that output a position signal by detecting the zero cross point (polarity change point) of the induced voltage waveform generated in the windings 6U to 6V by using a voltage dividing resistor or a comparator good. The voltage signal forming circuit 13 includes U,
A ROM is provided for each phase of V and W, and the same address of the counter output from the phase estimation circuit 12 is delayed by 120 ° from the ROM corresponding to the V phase to the ROM corresponding to the U phase. So that the waveform data value of
24 from the ROM corresponding to the W phase to the ROM corresponding to the U phase
The data may be stored so that the waveform data value delayed by 0 ° is read.

[0064]

According to the inverter device of the present invention, the pulse generating means has a constant value with respect to the induced voltage generated in the stator windings of a plurality of phases according to the rotational position of the rotor constituting the permanent magnet motor. A plurality of pulses are generated within the change period of the position signal having a phase relationship, and the phase estimating means counts the number of clock pulses generated by the pulse generating means by a counter. Then, the phase of the rotor is estimated based on the count value of the counter based on the timing of changing the position signal, and a sinusoidal current is applied to the stator winding.
To output a PWM signal for .

[0065] That is, it is possible to obtain the detailed resolution than the variation cycle of the position signal a phase of the rotor, depending on the detailed rotor phase of that, vibrations generated in the permanent magnet motor, noise, etc. It is possible to form a PWM signal that can be suppressed more than the 120 ° energization signal. Then, the PWM signal can be supplied to the stator winding to drive the permanent magnet motor with low vibration and low noise. Further, since the phase correction means corrects the phase of the rotor by setting the correction value in the counter at the reference timing of the position signal, it is possible to perform complicated calculation using a microcomputer and to store data. The permanent magnet motor can be operated with high efficiency by correcting the phase and energizing the stator winding with an appropriate phase without using a storage device.

[Brief description of drawings]

FIG. 1 is a functional block diagram showing an electrical configuration according to a first embodiment of the present invention.

FIG. 2 is a diagram showing a relationship between an induced voltage generated in a stator winding of a permanent magnet motor and a position signal.

FIG. 3 is a timing chart of each signal

FIG. 4 is a graph showing frequency (permanent magnet motor rotation speed) -voltage conversion characteristics in a rotation speed detection circuit.

FIG. 5 is a waveform diagram of a DC power supply current detected by a current sensor.

FIG. 6 is a diagram showing a relationship between a hold level in a peak hold circuit and a load torque of a permanent magnet motor.

FIG. 7 is a diagram showing A / D conversion characteristics in an A / D conversion circuit.

FIG. 8A shows a voltage signal VSIN and a carrier signal VT.
R, (b) are terminal voltage of each phase of the permanent magnet motor, (c) is a diagram showing a U-V phase voltage waveform .

FIG. 9 is a view corresponding to FIG. 1 showing a second embodiment of the present invention.

FIG. 10 is a diagram showing a relationship between an F / V conversion voltage signal output by a rotation speed detection circuit and a voltage command output by a speed control circuit during no-load operation .

FIG. 11 is an electrical configuration diagram of an essential part showing a third embodiment of the present invention.

Claims (24)

(57) [Claims] 1. A ho which outputs a position signal having a constant phase relationship with induced voltages generated in stator windings of a plurality of phases according to a rotational position of a rotor constituting a permanent magnet motor.
An IC , a cycle measuring means for measuring a change cycle of the position signal, a pulse generating means for generating a plurality of clock pulses in the change cycle, and a counter for counting the number of clock pulses generated, Phase estimating means for estimating the phase of the rotor based on the count value of the counter based on the timing of changing the position signal, and at the timing, a correction value is set in the counter to set the phase of the rotor. Phase correction means for correcting, and a sinusoidal wave on the stator winding based on the corrected phase.
A means for outputting a PWM signal for passing a current, and a transistor driven by the PWM signal
Inverter apparatus characterized by comprising an inverter main circuit to be. 2. The inverter device according to claim 1 , wherein the number of Hall ICs is three . 3. A transistor constituting an inverter main circuit.
Motor, the inverter apparatus according to claim 1 or 2, wherein the 6 Kodea Rukoto. 4. The position signal changing cycle is 60 degrees in electrical angle.
The inverter apparatus according to any one of claims 1 to 3, wherein that you correspond to. 5. The cycle measuring means is used when the cycle corresponds to the change cycle.
Equipped with a counter that counts the intervals, the pulse generation means multiplies the frequency according to the change period.
A multiplier circuit that generates and outputs a clock pulse of frequency
It is comprised including, It is characterized by the above-mentioned.
The inverter device according to any one of claims. 6. The frequency multiplication circuit has a cow which cycle measuring means has.
Cycle data corresponding to the change cycle counted by the
1/32 of the counter value is down counted at the same cycle as the counter.
Clock, and when the count value reaches zero, the clock
The inverter device according to claim 5 , wherein a pulse is generated . 7. The phase correcting means has a phase estimating means.
A special feature is that the correction value is set as an initial value in the counter.
The inverter apparatus according to any one of claims 1 to 6, characterized in that a symptom. 8. The phase correction means sets the correction value to the rotation of the motor.
The inverter device according to any one of claims 1 to 6, wherein the inverter device is increased in accordance with a rolling speed and a load torque of the motor . 9. A motor rotation speed is determined based on a position signal.
9. The inverter device according to claim 8 , wherein the inverter device is detected . 10. The load torque of the motor is controlled by a DC power source.
Inserted in the DC bus for supplying the inverter main circuit
10. The inverter device according to claim 8 or 9 , wherein the detection is performed based on a detection signal of the current sensor . 11. The motor rotation speed and load torque
The inverter device according to any one of claims 8 to 10, further comprising an adding circuit that outputs a corresponding voltage signal . 12. The voltage output by the adder circuit is A
/ D inverter according to claim 1 1, wherein further comprising an A / D converter circuit for converting. 13. A rotor of a rotor constituting a permanent magnet motor.
Induced voltage generated in multi-phase stator windings depending on the transposition position
To output a position signal that has a constant phase relationship with
Equipped with an internal IC and receives the position signal as an input
PW for driving the transistors that make up the main circuit
In an inverter device which outputs an M signal, a period measuring means for measuring a change period of the position signal and a power generation unit for generating a plurality of clock pulses within the change period.
And a counter for counting the number of clock pulses generated.
And using the timing at which the position signal changes as a reference
The phase of the rotor based on the count value of the counter
Setting a phase estimating means for estimating, at the timing, the correction value to the counter
And a phase correction means for correcting the phase of the rotor by means of a motor, and a sinusoidal wave on the stator winding based on the corrected phase.
Means for outputting the PWM signal for passing a current
And the period measuring means are adjacent to each other with respect to the position signal.
It features and to Louis <br/> inverter device to measure the distance between the level change edge. 14. A position signal output by a Hall IC
14. The inverter device according to claim 13 , wherein the number is for three phases . 15. The PWM signal is output in 6 systems.
The inverter device according to claim 13, wherein: 16. The position signal changing cycle is 60 in terms of electrical angle.
16. What according to claim 13 to 15, characterized in that it corresponds to degrees.
Inverter device described there. 17. The cycle measuring means corresponds to the change cycle.
Equipped with a counter that counts time, the pulse generation means multiplies the frequency according to the change period.
A multiplier circuit that generates and outputs a clock pulse of frequency
13. A structure comprising:
6. The inverter device according to any one of 6. 18. A frequency multiplication circuit is provided in a cycle measuring means.
The cycle data corresponding to the change cycle counted by the counter
1/32 of the data value is downloaded at the same cycle as the counter.
When the count value reaches zero, the clock is
18. A pulse generator according to claim 17, wherein the pulse pulse is generated.
Inverter device. 19. The phase correcting means has a phase estimating means.
The counter to set the correction value as the initial value.
Any one of claims 13 to 18 characterized by the above-mentioned.
The inverter device according to claim 1. 20. The phase correction means sets the correction value of the motor.
Increase corresponding to rotation speed and motor load torque
The method according to any one of claims 13 to 19, characterized in that
Inverter device. 21. The rotation speed of a motor is based on a position signal.
21. The inverter according to claim 20, wherein the inverter is detected.
Data device. 22. The load torque of the motor is controlled by the DC power supply.
Inserted in the DC bus for supplying the inverter main circuit
Characterized by detecting based on the detection signal of the current sensor
22. The inverter device according to claim 20 or 21. 23. The rotation speed and load torque of a motor
It is equipped with an adder circuit that outputs a corresponding voltage signal.
The inverter according to any one of claims 20 to 22,
apparatus. 24. The voltage output by the adder circuit is A
A / D conversion circuit for D / D conversion is provided.
The inverter device according to claim 23.