JP3447934B2 - Portable power supply - Google Patents

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a portable power supply device used as a single-phase AC power supply of commercial frequency or the like.

[0002]

2. Description of the Related Art Conventionally, as a portable power supply device used for emergency power supply, outdoor work, leisure, etc., for example, a combination of a small engine and a synchronous generator is often used.

[0003]

In such a conventional engine generator, since the output frequency depends on the engine speed, for example, 50 Hz (or 60 Hz in the case of a two-pole machine).
Hz) to obtain an AC output of 300 rpm
It is necessary to keep it at 0 rpm (or 3600 rpm), the engine speed is relatively low and the operating efficiency is not very good, and the generator has to be made large, so the overall weight will be very large. There was a problem.

On the other hand, in recent years, the engine is operated at a relatively high rotational speed to obtain high-output AC power from the generator, the AC power is once converted to DC, and then commercialized by an inverter device. A so-called inverter-type generator that converts to an alternating current of a frequency and outputs it is also becoming popular (as related applications, for example, Japanese Patent Publication No. 7-67229 and Japanese Patent Laid-Open No. 4-35567).
There is one described in Japanese Patent No. 2).

By the way, in the above-mentioned inverter type generator, there are two electric powers, a direct current converting portion for converting alternating current power into direct current and an alternating current converting portion for converting this direct current power into alternating current of a predetermined frequency again. Since a converter is needed and a circuit that temporarily stores DC power is needed, many expensive power circuit components must be used, which makes the generator even smaller and lighter. However, there is a problem in that the manufacturing cost is high and the manufacturing cost is high.

In order to solve such a problem, the present applicant further discloses in Japanese Patent Application No. 8-218141, etc. that the inverter device of the inverter type generator is replaced with a cycloconverter device, and a high frequency alternating current generated by the generator is used. The above problem has been solved by proposing direct conversion of electric power into AC power of a predetermined frequency such as a commercial frequency.

However, even if the inverter device of the inverter type generator is replaced with a cycloconverter device, there are the following problems.

That is, an accurate synchronizing signal is required for switching control of the cycloconverter device, and a special three-phase winding for the three-phase synchronizing signal is provided so as not to be affected by load fluctuation. Although it has to be provided, when the three-phase winding for the three-phase synchronizing signal is provided, there is a problem that the device configuration becomes complicated. Further, when the load current supplying 3-phase windings are arranged on both sides of the 3-phase synchronizing signal 3-phase winding, the 3-phase synchronizing signal 3-phase winding and the load current supplying 3-phase winding are provided. Since the magnetic path is shared with the winding, there is a problem that a stable synchronizing signal cannot be obtained.

Therefore, an object of the present invention is to provide a portable power supply device capable of simplifying the device configuration and obtaining a stable synchronization signal in order to solve the above problems.

[0010]

In order to achieve the above object, a portable power supply unit according to claim 1 is a multi-pole magnet generator having three-phase output windings and is synchronized with the output frequency of the generator. And a pair of variable control bridge circuits that are connected to the three-phase output windings and are connected in antiparallel with each other to form a cycloconverter that outputs a single-phase alternating current. The variable control bridge circuits connected in anti-parallel with each other are alternately switched every half cycle of an alternating current having a target frequency to be supplied to the load, based on a signal from the synchronizing signal forming means, so that the variable control bridge circuits have a predetermined frequency. In a portable power supply device having a bridge drive circuit for outputting a three-phase alternating current, the three-phase output winding provided in the magnetic pole of the magneto-generator is not wound.
A single-phase subcoil that forms a signal extraction winding is wound around two magnetic poles, and the signal extraction winding is provided.
The three-phase output windings are wound around the magnetic poles on both sides of the magnetic pole.
The synchronization signal forming means forms a three-phase synchronization signal for sequentially driving the variable control bridge circuit from the single-phase signal extracted from the single-phase subcoil.

According to this structure, a single-phase winding for forming a signal is formed on one magnetic pole provided in the magnetic pole of the magneto-generator and not wound with the three-phase output winding. sub coil are wound Rutotomoni, the signal extraction wound
The three-phase output windings on the magnetic poles on both sides of the magnetic pole having a wire.
Is wound so that a three-phase synchronizing signal for sequentially driving the variable control bridge circuit is formed from the single-phase signal extracted from the single-phase sub-coil.

According to a second aspect of the present invention, in the portable power source device according to the first aspect, the synchronization signal forming means divides one cycle of a single-phase signal extracted from the signal extracting winding into six equal parts. Alternatively, it is characterized in that a three-phase synchronizing signal for sequentially driving the variable control bridge circuit is formed by dividing the half cycle into three equal parts.

According to this structure, a three-phase synchronizing signal for sequentially driving the variable control bridge circuit is obtained by dividing one cycle of the single-phase signal extracted from the signal extraction winding into six equal parts or three half parts. It is formed.

A portable power supply device according to a third aspect is the portable power supply device according to the first or second aspect, wherein the three-phase synchronization signal has a predetermined phase shift with respect to the single-phase signal. To do.

A portable power supply device according to a fourth aspect is the portable power supply device according to any one of the first to third aspects, in which the DC power supply for the variable control bridge circuit is provided by the output of the signal extracting winding. A direct current power supply forming circuit is provided.

According to this structure, the DC power source for the variable control bridge circuit is formed by the output of the signal extracting winding.

The portable power supply device according to a fifth aspect of the present invention is the portable power supply device according to any one of the first to fourth aspects, wherein the magnetic poles on both sides of the magnetic pole provided with the signal extracting winding are directed to the outside. It is characterized by comprising a winding for forming a DC power supply for supplying a DC output.

According to this structure, the windings for forming the DC power supply for supplying the DC output to the outside are provided to the magnetic poles on both sides of the magnetic pole provided with the signal extracting winding.

[0019]

BEST MODE FOR CARRYING OUT THE INVENTION Embodiments of the present invention will be described in detail below with reference to the drawings.

FIG. 1 is a block diagram showing a schematic configuration of a portable power supply device according to an embodiment of the present invention.

In FIG. 1, 1 and 2 are output windings independently wound around the stator of the AC generator.
Is a three-phase main output winding (hereinafter, referred to as “three-phase main coil”), and 2 is a single-phase auxiliary output winding (hereinafter, referred to as “single-phase sub-coil”).

FIG. 2 is a sectional view of the AC generator,
In the figure, the three-phase main coil 1 has two
The single-phase sub-coil 2 is composed of a four-pole coil, and has a region A.
It is composed of a central one-pole coil among the three-pole coils in 2. Then, the rotor R is formed with eight pairs of magnetic poles of permanent magnets, and is configured to be rotationally driven by an internal combustion engine (not shown). The rotor R also serves as the flywheel of the engine.

Returning to FIG. 1, the three output terminals U, V, W of the three-phase main coil 1 are connected to a cycloconverter (Cyclo).
converter) CC is connected to the input terminals U, V, and W.

FIG. 3 is an electric circuit diagram in which only the cycloconverter CC portion of FIG. 1 is taken out. As shown in FIG. 3, the cycloconverter CC has 12 thyristors S.
CRk ± (k = 1, ..., 6). 1
6 thyristors S out of 2 thyristors SCRk ±
The bridge circuit (hereinafter, referred to as “positive converter”) BC1 composed of CRk + mainly outputs a positive current,
A bridge circuit (hereinafter, referred to as a “negative converter”) BC2 including the remaining six thyristors SCRk− mainly outputs a negative current.

When the three-phase AC output of the above-described three-phase generator is input to the cycloconverter CC, eight cycles of AC can be obtained for one revolution of the crankshaft. Then, the engine speed range is set to, for example, 1200 rpm to 45 rpm.
When set to 00 rpm (that is, 20 Hz to 75 Hz), the frequency of the three-phase AC output is 160 Hz to 600 Hz, which is eight times the engine speed.

Returning to FIG. 1, the three output terminals U, V, W of the three-phase main coil 1 have positive and negative converters BC, respectively.
1, BC2 are connected to input terminals U, V and W, the output side of the cycloconverter CC is connected to an LC filter 3 for removing harmonic components of its output current, and the output side of the LC filter 3 is This output is connected to an output voltage detection circuit 5 for detecting a voltage corresponding to the current from which the harmonic component has been removed. The negative input terminal of the output voltage detection circuit 5 is connected to the ground GND of the control system, and is configured to obtain a single-phase output from both the positive and negative input terminals of the output voltage detection circuit 5. There is.

The output side of the output voltage detection circuit 5 is connected to an approximate effective value calculation circuit 8 which calculates and outputs the approximate effective value of the output voltage. The output side of the approximate effective value calculation circuit 8 is a comparator 9 It is connected to the negative input terminal of. A reference voltage output circuit 10 that outputs the reference voltage value of the power supply device is connected to the positive input terminal of the comparator 9, and the output side of the comparator 9 is
Control function according to the result of this comparison (eg proportional function)
A control function calculation circuit 11 for calculating and outputting is connected.

The output side of the control function arithmetic circuit 11 is connected to the amplitude control circuit 12 for controlling the amplitude of the sine wave output from the sine wave oscillator 13 and having a commercial frequency of 50 Hz or 60 Hz, for example. The output side of the sine wave oscillator 13 is also connected to. The amplitude control circuit 12 outputs an amplitude control signal for controlling the amplitude of the sine wave output from the sine wave oscillator 13 according to the control function output from the control function calculation circuit 11.

The output side of the amplitude control circuit 12 is connected to a target wave output circuit 14 which outputs a target wave according to this output signal (amplitude control signal), and the output side of the target wave output circuit 14 is a cycloconverter CC. Thyristor SC that composes
Conduction angle control unit 15 for controlling the conduction angle of each gate of Rk ±
And the positive side input terminal of the comparator 16.

The output side of the output voltage detection circuit 5 and the output side of the target wave output circuit 14 are the detection wave of the single-phase AC output output from the output voltage detection circuit 5 and the target wave output circuit 14.
It is connected to a power factor detection circuit 19 for detecting a power factor by comparing with a target wave output from the power factor detection circuit 19, and the output side of the power factor detection circuit 19 is connected to the negative side input terminal of the comparator 9.

FIG. 4 is a diagram showing an example of the detection wave of the single-phase AC output output from the output voltage detection circuit 5 and an example of the target wave output from the target wave output circuit 14, and FIG. The detection wave and the target wave when the factor is 1 are shown, (b) shows the detection wave and the target wave when the power factor is smaller than 1 and the load is in the lag phase, and (c) shows the power factor 1 The detection wave and the target wave that are smaller and show the case where the load is in the advanced phase are shown.

When the power factor is 1, as shown in FIG. 4 (a), the detected wave is delayed from the target wave by a fixed time x corresponding to the phase delay generated in the power supply device of the present embodiment. When the power factor is less than 1 and the load is delayed, the detected wave has a delay of the fixed time x, but the phase corresponding to the power factor advances as compared with the target wave, while the power factor is less than 1. When the load is small and the phase is advanced, the detected wave is delayed by the fixed time x, and further, the phase corresponding to the power factor is delayed as compared with the target wave.

FIG. 5 is a diagram for explaining a method in which the power factor detection circuit 19 detects a signal corresponding to the power factor from the detected wave and the target wave. FIG. 5A shows the target wave of FIG. 4A. The detected wave and the target wave when delayed by a fixed time x are shown in FIG.
The detection wave and the target wave when the target wave of (b) is delayed by a fixed time x are shown. The target wave delayed by this fixed time x is referred to as target wave 2.

First, in FIGS. 5A and 5B, the output value of the target wave 2 is subtracted from the output value of the detected wave (see FIG.
(C), (d)), the subtraction wave indicating the subtracted output value and the output value of the target wave 2 are compared at the same time, and the output value of the subtraction wave and the output value of the target wave 2 are the same. In the case of the sign, the output value of the subtraction wave is calculated (FIG. 5 (f)), and the absolute value of the calculated output value of the subtraction wave is calculated (FIG. 5 (h)). Since the output value of the subtraction wave whose absolute value is taken includes noise generated in the power supply device of the present embodiment, the offset value corresponding to this noise is subtracted from the output value of the subtraction wave, and the result is When it becomes a negative value, the value is replaced with 0, the area of the subtracted wave of the positive output value in the predetermined section is calculated, and the moving average of this area is calculated. As a result, a signal corresponding to the power factor can be detected.

On the other hand, when the output value of the subtraction wave and the output value of the target wave 2 have different signs, the output value of the subtraction wave is set to 0 (see FIG. 5).
(E)), and then the absolute value of the output value of the subtracted wave is calculated (see FIG.
(G)), the offset value corresponding to noise is subtracted from the output value of the subtracted wave whose absolute value is taken, and when the result becomes a negative value, the value is replaced with 0 and the predetermined interval It is possible to detect a signal corresponding to the power factor by calculating the area of the subtracted wave of the positive output value of, and further calculating the moving average of this area. In this case, the power factor is 1 and the subtracted wave Since the output value of 1 and the output value of the target wave 2 always have different signs, a signal corresponding to the power factor does not occur.

In this way, the power factor detection circuit 19 detects a signal corresponding to the power factor, and adjusts the approximate execution value of the approximate effective value calculation circuit 8 based on the detected signal. In the case of a low power factor load, the approximate execution value of the approximate effective value calculation circuit 8 is lowered to adjust the output voltage.

Returning to FIG. 1, the conduction angle control unit 15 controls the conduction angle of the gate of each thyristor SCRk + of the positive converter BC1 (hereinafter referred to as "positive gate") and the negative converter BC2. Each thyristor S
The CRk- gate (hereinafter, referred to as "negative gate") is configured by a negative gate control unit 15b that controls a conduction angle.

Each of the gate controllers 15a and 15b has six comparators (not shown), and each comparator compares the target wave with a synchronization signal (reference sawtooth wave) described later, When the two match, the gate is fired.

The output side of the output voltage detection circuit 5 is connected to the negative side input terminal of the comparator 16, and the output side of the comparator 16 has a positive gate controller 15a and a negative gate controller 15b.
It is connected to the. The comparator 16 includes the output voltage detection circuit 5
The voltage output from the target wave is compared with the target wave, and a high (H) level signal or a low (L) level signal is output according to the comparison result.

When the H level signal is output from the comparator 16, the positive gate control section 15a operates, while the negative gate control section 15b stops, and when the L level signal is output, conversely, The positive gate controller 15a is stopped while the negative gate controller 15b is activated.

The output side of the single-phase sub-coil 2 is connected to the sync pulse forming circuit 20, and the sync pulse forming circuit 20 is connected.
The output side of is connected to the synchronization signal calculation forming circuit 21. The synchronization pulse forming circuit 20 forms a pulse signal from the single phase output signal of the single phase sub-coil 2 and outputs it to the synchronization signal calculation forming circuit 21. The synchronization signal calculation forming circuit 21
One cycle of the pulse signal formed by the synchronous pulse forming circuit 20 is measured, and this one cycle is divided into six equal parts or half cycles into three equal parts to obtain the next one-phase three-phase timing by calculation.

Further, the output side of the single-phase sub-coil 2 is connected to a direct-current power supply forming circuit 100 (not shown in FIG. 1) which forms a direct-current power supply for the conduction angle controller 15 from the single-phase output signal of the single-phase sub-coil 2. It is connected.

FIG. 6 is an electric circuit diagram showing an example of the DC power supply forming circuit 100 and the synchronization pulse forming circuit 20. As shown in the figure, the single-phase sub-coil 2 is originally provided to obtain a DC power source by the DC power source forming circuit 100, and this is used for forming a sync pulse. Therefore, in the present embodiment, it is not necessary to newly provide a sub-coil dedicated to forming a synchronization signal as in the conventional power supply device, and the device configuration can be simplified.

FIG. 7 is a diagram showing an example of signals formed by the sync pulse forming circuit 20 and the sync signal calculation forming circuit 21. FIG. 7A shows the single-phase subcoil 2 at the input point α of the sync pulse forming circuit 20. Shows an example of a single-phase output signal of
(B) is a synchronization pulse forming circuit 2 for converting the single-phase output signal of (a) into
1 shows an example of a pulse signal formed by conversion by 0, that is, an output signal at the output point β of the synchronous pulse forming circuit 20, (c) is formed by the synchronous signal calculation forming circuit 21 based on the pulse signal of (b). FIG.

That is, at the input point α, of the single-phase output signal of the single-phase sub-coil 2, only the half wave on the positive side is extracted (see FIG. 7).
(A)), the synchronous pulse forming circuit 20 forms a pulse signal in which the section corresponding to the positive half wave is low (FIG. 7B). Then, one cycle T of the pulse signal of (b) is obtained, for example, by measuring the falling edge to the falling edge of the pulse of (b), or the half cycle T / 2 of the pulse signal of (b) is For example, it is obtained by measuring from the falling edge to the rising edge of the pulse in (b), and the timing is obtained by calculation in order to divide 1 cycle T into 6 equal parts or half cycle T / 2 into 3 parts, and shown in (c). So the next one
A pulse signal indicating three-phase timing of a cycle (timing for changing the phase of each sawtooth wave described later) is formed.

Further, the synchronization signal calculation forming circuit 21 makes each thyristor SC, as will be described later, based on the formed pulse signal obtained by dividing one period into six equal parts or half a period into three equal parts.
A sawtooth wave is formed as a synchronizing signal for controlling the conduction angle α of the gate of Rk ±. This synchronization signal calculation forming circuit 21
By the processing of (3), the three-phase synchronization signal is reliably formed from the pulse signal.

Next, a method of controlling the conduction angle α will be described.

FIG. 8 is a diagram showing a reference sawtooth wave formed by the synchronization signal calculation forming circuit 21 for controlling the conduction angle α.

Thyristor SCR1 of the positive converter BC1
The reference sawtooth wave corresponding to + has a conduction angle α of 120 ° ~
In the range of −60 °, the sawtooth wave that becomes 0 V when α = 0 ° corresponds. Then, the sawtooth waves having a phase difference of 60 ° are generated by thyristors SCR1 +, 6+, 2 respectively.
It corresponds to each thyristor SCRk + in the order of +, 4+, 3+, 5+. The sawtooth wave corresponding to the thyristor SCR1 + has the same phase as the pulse signal formed by the synchronous pulse forming circuit 20, and the sawtooth wave corresponding to the thyristor SCR6 + is 60 ° from the pulse signal formed by the synchronous pulse forming circuit 20. Phase shift occurs. The sawtooth wave that causes such a phase shift can be easily formed based on the pulse signal indicating the three-phase timing formed by the synchronization signal calculation forming circuit 21.

On the other hand, the thyristor S of the negative converter BC2
For CR1-, a sawtooth wave that is vertically symmetrical with respect to the thyristor SCR1 + and has a phase shift of 180 ° is formed. Then, similarly to the positive converter BC1, sawtooth waves having a phase difference of 60 ° are generated in the thyristor SCR1.
It corresponds to each thyristor SCRk- in the order of-, 6-, 2-, 4-, 3-, 5-.

As described above, the reference waveform is composed of twelve sawtooth waves corresponding to the thyristors SCRk ± of the positive and negative converters BC1 and BC2. These sawtooth waves are compared with the target waveform r by a 12-system comparator (not shown), and the intersection point becomes the conduction angle of each thyristor SCRk ±.

By taking a sine wave as the target wave and changing the conduction angle α into a sine wave, a sine wave output can be obtained from the cycloconverter CC.

FIG. 9 shows each thyristor SCR of the positive or negative converters BC1 and BC2 with the conduction angle α = 120 ° and 60 °.
It is a figure which shows the waveform output from the cycloconverter CC when igniting k ±.

In the figure, (a) shows the conduction angle α = 12.
The waveform output from the cycloconverter CC when each thyristor SCRk + of the positive converter BC1 is ignited at 0 ° is shown in (b), and each thyristor SCRk− of the negative converter BC2 is ignited at the conduction angle α = 120 °. Shows the waveform output from the cycloconverter CC when
(C) shows a waveform output from the cycloconverter CC when each thyristor SCRk + of the positive converter BC1 is fired at a conduction angle α = 60 °, and (d) shows a negative converter at a conduction angle α = 60 °. Each thyristor SCR of BC2
The waveform output from the cycloconverter CC when k-is fired is shown.

For example, when each thyristor SCRk + of the positive converter BC1 is ignited at the conduction angle α = 120 °, the waveform output from the cycloconverter CC is a full-wave rectified waveform as shown in FIG. 9 (a). Becomes Further, each thyristor S of the positive converter BC1 has a conduction angle α = 60 °.
When CRk + is ignited, the waveform output from the cycloconverter CC is a waveform including a large amount of harmonic components as shown in FIG. 9C, but the cycloconverter C
When a high cut filter is connected to the output side of C, this harmonic component is removed and the average voltage is output. As described above, when the input generator is a 24-pole three-phase generator and the engine speed is 3600 rpm, the frequency of the fundamental wave of the harmonic is as follows.

60 Hz (= 3600 rpm) × 8th harmonic ×
3 phases × 2 (full wave) = 2.88 kHz and the conduction angle α of the positive converter BC1 is 0 ° to 120.
By changing in the range of °, the cycloconverter CC can output any positive voltage whose average voltage is in the range of 0V to the full-wave rectified voltage. Further, by changing the conduction angle α of the negative converter BC2 in the same manner, the cycloconverter CC can output an arbitrary negative voltage whose average voltage is in the range of 0 V to −full-wave rectified voltage.

On the other hand, in FIG. 8, the control range of the conduction angle α is
The conventional 120 ° to 0 ° is expanded to 120 ° to −60 °. The reason for expanding the control range of the conduction angle α will be described below.

When the conduction angle α is controlled in the range of 120 ° to 0 °, when a capacitive load is connected to the output terminal of the cycloconverter CC and there is a positive potential on the load side,
If control is performed to reduce the output voltage, each thyristor S
In some cases, a discontinuity occurs in the relationship between the conduction angle of CRk ± and the output voltage, and the output voltage cannot be stably maintained. That is, in order to reduce the output voltage when there is a positive potential on the load side, it is necessary to absorb the positive charge of the load.
Since the conduction angle α is limited to the range of 120 ° to 0 °, the positive converter BC1 cannot absorb the positive charge of the load and must therefore be absorbed by the negative converter BC2. When the negative converter BC2 absorbs this positive charge, the output current from the negative converter BC2 is −full-wave rectified voltage to 0V as described above, so the positive potential of the load sharply drops to 0V. As a result, a discontinuity occurs in the output voltage. At this time, if the conduction angle is expanded to 120 ° to −60 °, the negative converter BC
Since the charge of the load can be absorbed up to a positive voltage by 2, the discontinuity does not occur in the output voltage and the control stability can be maintained.

However, when the conduction angle is expanded to the negative side in this way, as shown in FIG. 10, the positive and negative converters BC are
Since the output ranges of 1 and BC2 overlap, the intersection of the target wave r and the sawtooth wave is 2 of TO1 and TO2.
It was a point, and it was not possible to determine which of the positive or negative converters BC1 and BC2 was selected to ignite the gate of the corresponding thyristor SCRk ±. Therefore, in the present embodiment, as described above, either one of the positive or negative converters BC1 and BC2 is selected according to the comparison result of the comparator 16.

Returning to FIG. 1, the output side of the sync signal calculation forming circuit 21 has a positive gate control section 15a and a negative gate control section 1.
It is connected to 5b. Here, each connection line that connects the synchronization signal calculation forming circuit 21 and each gate control unit 15a and 15b is composed of six signal lines, and each signal line is the gate control units 15a and 15 respectively.
b, the sawtooth wave having the timing described in FIG. 8 is supplied to each comparator.

The outputs of the six comparators of the positive gate controller 15a are respectively connected to the thyristors S of the positive converter BC1.
The output side of the six comparators of the negative gate controller 15b, which are connected to the gate of CRk +, are respectively connected to the negative converter BC2.
Is connected to the gate of each thyristor SCRk-.

The operation of the portable power supply device configured as described above will be described below.

When the rotor R is rotationally driven by the engine, a voltage is applied between the phases of the three-phase main coil 1 as described above. When each gate of the thyristor SCRk ± is fired by the conduction angle control unit 15, a current is output from the cycloconverter CC in response to this, the harmonic component of this current is removed by the filter 3, and the output voltage is increased. The voltage is detected by the detection circuit 5. Each voltage thus detected is calculated by the approximate effective value calculation circuit 8 and output.

The approximate effective value voltage is
It is compared with the reference voltage value output from the reference voltage output circuit 10, and a control function (proportional function) is calculated by the control function calculation circuit 11 according to the comparison result and output. Specifically, the control function calculation circuit 11 increases the output value from the comparator 9, that is, the reference voltage output circuit 10
The proportional function is calculated and output such that the proportional coefficient increases as the difference between the reference voltage output from the device and the approximate effective value from the approximate effective value calculation circuit 8 increases.

According to the calculated and output control function, the amplitude control circuit 12 generates a control signal for controlling the amplitude of the sine wave of 50 Hz or 60 Hz output from the sine wave oscillator 13, and outputs the control signal. The wave output circuit 14 outputs a target wave according to this control signal.

Here, the power factor detection circuit 19 compares the detected wave of the single-phase AC output output from the output voltage detection circuit 5 with the target wave output from the target wave output circuit 14 and determines the power factor. The signal is detected, and the approximate execution value of the approximate effective value calculation circuit 8 is adjusted based on the detected signal. In the case of a low power factor load, the approximate execution value of the approximate effective value calculation circuit 8 is lowered to adjust the output voltage.

Upper and lower limit values are provided for the output value from the target wave output circuit 14, and the target wave output circuit 14 is designed so that it cannot output a value larger than the predetermined upper limit value or smaller than the predetermined lower limit value. It is configured. That is, as the output value from the comparator 9 increases and the proportional coefficient of the proportional function output from the control function arithmetic circuit 11 increases, the shape of the target wave output from the target wave output circuit 14 changes from a sine wave. It is transformed into a rectangular wave.

The target wave output from the target wave output circuit 14 is compared with the detection voltage output from the output voltage detection circuit 5 by the comparator 16, and when the voltage of the target wave is higher than the detection voltage, the comparison is performed. The H-level signal is output from the comparator 16, and the positive gate controller 15a is selected to operate. On the other hand, when the voltage of the target wave is lower than the detection voltage, the L-level signal is output from the comparator 16. , The negative gate controller 15b is selected to operate.

In each comparator of the gate control units selected from the positive gate control unit 15a and the negative gate control unit 15b, the target wave from the target wave output circuit 14 and the sawtooth wave from the synchronization signal calculation forming circuit 21 are detected. Are compared, and when they match, a one-shot pulse having a predetermined width is output to the gate of the thyristor SCRk ±.
Conduction angle control is performed.

FIG. 11 is a diagram showing an example of an output waveform of 50 Hz generated by the power supply device of this embodiment,
(A) shows an output waveform at no load, (b) shows an output waveform at a rated load, and (c) shows an output waveform at an overload.

As shown in the figure, when, for example, a temporary overload occurs, the reference voltage output from the reference voltage output circuit 10 and the approximate effective value calculation circuit 8 will depend on the state of the overload. The output waveform is transformed from a sine wave to a rectangular wave according to the difference from the approximate effective value.

In the present embodiment, the shape of the target wave is changed from the sine wave to the rectangular wave according to the load condition, but the present invention is not limited to this, and the output voltage is limited to the maximum amplitude. When the power supply device is configured as described above, the amplitude of the target wave may be increased according to the state of the load.

As described above, in the present embodiment, the synchronization pulse forming circuit 20 forms a pulse signal from the single-phase output signal output from the single-phase sub-coil 2, and the synchronization signal operation forming circuit 21 forms the formed pulse. Since the three-phase synchronizing signal that drives the conduction angle control unit 15 sequentially and controls the switching of the cycloconverter CC is formed based on the signal, the three-phase sub-coil is not required to form the three-phase synchronizing signal as in the conventional case, The device configuration can be simplified.

Further, since the three-phase synchronizing signal for controlling the switching of the cycloconverter CC is formed from the single-phase output signal of the single-phase sub-coil 2 wound independently of the three-phase main coil 1, the waveform is deformed due to the adverse effect of switching. And stable synchronization timing can be obtained.

In the present embodiment, the power factor detection circuit 1
Although 9 is configured by hardware, the control processing performed by the power factor detection circuit 19 is not limited to this, and may be performed by, for example, a microcomputer and software.

Further, the power factor detection method of the present embodiment is not effective only for the power supply device to which the cycloconverter is applied, but it is a power supply device for controlling the output voltage based on the target wave. It is effective as long as it is provided with a detecting means.

Furthermore, in the present embodiment, as shown in FIG. 2, the three-phase main coil 1 is composed of the 24-pole coils in the area A1, and the central one of the 3-pole coils in the area A2.
The single-phase sub-coil 2 is composed of the coils of the poles.
2, the single-phase sub-coil 2 is used as a single-phase sub-coil 30 for the circuit power supply and the synchronizing signal, and the remaining two-pole coils in the area A2 excluding the single-phase sub-coil 2 are, for example, a 12V (volt) battery. By operating the power supply device of the present embodiment as a DC coil 31 for supplying a DC output used for charging or the like to the outside and a three-phase main coil 1 as a three-phase main coil 32 for AC output, a single-phase Since the sub-coil 30 is arranged between the two DC coils 31, the single-phase sub-coil 30 and the three-phase main coil 32
Does not share a magnetic path, and a stable synchronization signal can be obtained.

The reason why a stable synchronization signal can be obtained will be described more specifically.

The three-phase main coil 32 for AC output undergoes severe waveform deformation due to the operation of the thyristor SCRk ±, and also deforms the waveform of the adjacent pole which is a part of the magnetic path. Therefore, when the single-phase sub-coil 30 for the circuit power supply and the synchronizing signal is arranged next to the three-phase main coil 32, the synchronizing signal is greatly disturbed and normal control becomes difficult. On the other hand, since the DC coil 31 is in a stable load state such as battery charging, even if the single-phase sub-coil 30 is arranged between the two DC coils 31, the disturbance of the synchronization signal is small. Therefore, the single-phase sub-coil 30 and the three-phase main coil 3 are arranged by disposing the single-phase sub-coil 30 between the two DC coils 31.
2 does not share a magnetic path, and a stable synchronization signal can be obtained.

As described in detail above, according to the portable power supply device of claim 1, one magnetic pole provided in the magnetic poles of the magneto-generator is not wound with the three-phase output winding. A single-phase subcoil that forms a signal extraction winding is wound around the three-phase synchronization signal that sequentially drives the variable control bridge circuit from the single-phase signal extracted from the single-phase subcoil. In order to form a three-phase synchronizing signal, there is no need for a three-phase output winding for signal extraction, and the device configuration can be simplified. Further, since the signal extracting winding is provided independently of the three-phase output winding, a stable synchronizing signal can be obtained. Furthermore, on the magnetic poles on both sides of the magnetic pole equipped with the signal extraction winding
Is configured so that the three-phase output winding is not wound
The signal extraction winding and the load current supply winding are magnetic paths.
Not to share and get a more stable sync signal
You can

According to the portable power supply device of the second aspect, one cycle of the single-phase signal taken out from the signal taking-out winding is set to 6 times.
Since the three-phase synchronization signal for sequentially driving the variable control bridge circuit is formed by dividing the equal period or half period into three equal parts,
The three-phase synchronization signal is formed more reliably.

According to the portable power supply device of the fourth aspect, since the DC power supply for the variable control bridge circuit is formed by the output of the signal extracting winding, the device structure can be further simplified.

According to the portable power supply device of the fifth aspect, since the windings for forming the DC power supply for supplying the DC output to the outside are provided to the magnetic poles on both sides of the magnetic pole provided with the signal extracting winding, The extraction winding and the load current supply winding do not share a magnetic path, and a more stable synchronization signal can be obtained.

[Brief description of drawings]

FIG. 1 is a block diagram showing a schematic configuration of a portable power supply device according to an embodiment of the present invention.

2 is a cross-sectional view of the AC generator of FIG.

FIG. 3 is an electric circuit diagram showing only the cycloconverter portion of FIG.

FIG. 4 is a diagram showing a detected wave of a single-phase AC output output from an output voltage detection circuit 5 and a target wave output from a target wave output circuit 14.

FIG. 5 is a diagram showing a method of detecting a signal according to a power factor from a detected wave and a target wave.

6 is an electric circuit diagram showing an example of a synchronization pulse forming circuit 20. FIG.

FIG. 7 is a diagram showing an example of a single-phase output signal of the single-phase sub-coil 2 and a pulse signal formed by the synchronization pulse forming circuit 20.

FIG. 8 shows a reference sawtooth wave generated to control the conduction angle.

FIG. 9 is a diagram showing a waveform output from the cycloconverter when each thyristor of the positive or negative converter is fired at the conduction angles α = 120 ° and 60 °.

FIG. 10 is a diagram for explaining a problem that occurs when the conduction angle is 120 ° to −60 °.

FIG. 11: 50 generated by the portable power supply device of FIG.
It is a figure which shows an example of the output waveform of Hz.

FIG. 12 is a cross-sectional view of an AC generator.

[Explanation of symbols]

1 3-phase main coil (3-phase output winding) 5 Output voltage detection circuit 14 Target wave output circuit (output voltage adjustment circuit) 15 Conduction angle control unit (bridge drive circuit) 16 Comparator 19 Power factor detection circuit 20 Synchronous pulse forming circuit (synchronous signal forming means) 21 Synchronous signal calculation forming circuit (synchronous signal forming means) BC1 Positive converter (variable control bridge) BC2 Negative converter (variable control bridge) CC cyclo converter

─────────────────────────────────────────────────── --- Continuation of the front page (56) References JP-A-50-114159 (JP, A) JP-A-50-32433 (JP, A) JP-A-10-52046 (JP, A) Actual development Sho-63- 51573 (JP, U) Actually developed 58-105792 (JP, U) Actually developed 56-139389 (JP, U) US Patent 4295085 (US, A) (58) Fields investigated (Int.Cl. ⁷ , DB) Name) H02P 9/42 H02M 5/27

Claims (5)

(57) [Claims] 1. A multi-pole magnet generator having a three-phase output winding, a synchronization signal forming means for forming a signal synchronized with an output frequency of the generator, and a three-phase output winding connected to the three-phase output winding. A pair of variable control bridge circuits that are antiparallel connected to each other and that form a cycloconverter that outputs a single-phase alternating current; and variable control bridge circuits that are antiparallel connected to each other,
A bridge drive circuit that outputs a single-phase alternating current of a predetermined frequency by alternately performing switching operation every half cycle of an alternating current of a target frequency to be supplied to a load based on a signal from the synchronization signal forming means. In the portable power supply device, a single-phase sub-coil forming a signal extraction winding is wound around one magnetic pole provided inside the magnetic pole of the magneto-generator and not wound with the three-phase output winding. together to do so, before
For the magnetic poles on both sides of the magnetic pole equipped with the signal extraction winding,
The three-phase output winding is configured not to be wound , and the synchronization signal forming means forms a three-phase synchronization signal for sequentially driving the variable control bridge circuit from a single-phase signal extracted from the single-phase subcoil. A portable power supply device characterized by: 2. The synchronizing signal forming means sequentially drives the variable control bridge circuits by dividing one cycle of a single-phase signal extracted from the signal extraction winding into six equal parts or three half cycles. The portable power supply device according to claim 1, wherein a three-phase synchronization signal is formed. 3. The three-phase synchronization signal has a predetermined phase shift with respect to the single-phase signal.
Alternatively, the portable power supply device according to item 2. 4. The DC power supply forming circuit for forming a DC power supply for the variable control bridge circuit with an output of the signal extracting winding, according to any one of claims 1 to 3. Portable power supply. 5. The magnetic poles on both sides of the magnetic pole provided with the signal extracting winding are provided with windings for forming a DC power source for supplying a DC output to the outside. A portable power supply device according to item 1.