JP3333883B2 - PWM controller for three-level inverter - Google Patents
PWM controller for three-level inverterInfo
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- JP3333883B2 JP3333883B2 JP18880295A JP18880295A JP3333883B2 JP 3333883 B2 JP3333883 B2 JP 3333883B2 JP 18880295 A JP18880295 A JP 18880295A JP 18880295 A JP18880295 A JP 18880295A JP 3333883 B2 JP3333883 B2 JP 3333883B2
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- pulse
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- command
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Description
【0001】[0001]
【産業上の利用分野】本発明は、直流を交流に変換する
3レベルインバータのPWM制御装置に係り、特に交流
電圧の連続制御に好適なPWM制御に関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a PWM control device for a three-level inverter for converting DC to AC, and more particularly to a PWM control suitable for continuous control of AC voltage.
【0002】[0002]
【従来の技術】3レベルインバータは、直流電源電圧
(架線電圧)を直列接続されたコンデンサで2つの直流
電圧に分圧することにより、正(高電位),零(中間電
位)及び負(低電位)の3つの電圧レベルを作り、主回
路スイッチング素子のオン・オフ動作により、これら3
レベルの電圧をインバータ出力端子に選択的に導出する
ことにより出力電圧を制御するものである。この3レベ
ルインバータの出力電圧のPWM制御法として、例え
ば、特開平5−146160 号に示されたダイポーラ変調(出
力電圧の半周期内にパルスを零電圧を介して正負交互に
出力することにより出力電圧を表現),ユニポーラ変調
(出力電圧の半周期中に単一極性のパルスを出力するこ
とにより出力電圧を表現),部分ダイポーラ変調(上記
ダイポーラ変調とユニポーラ変調が1周期中に混在)を
用いた方法が知られている。2. Description of the Related Art A three-level inverter divides a DC power supply voltage (an overhead line voltage) into two DC voltages by using a capacitor connected in series, so that a positive (high potential), a zero (intermediate potential) and a negative (low potential). ), And these three voltage levels are generated by turning on and off the main circuit switching elements.
The output voltage is controlled by selectively deriving the level voltage to the inverter output terminal. As a PWM control method of the output voltage of the three-level inverter, for example, a dipolar modulation disclosed in Japanese Patent Laid-Open No. 5-146160 (output is performed by alternately outputting positive and negative pulses via a zero voltage within a half cycle of the output voltage). Uses voltage, unipolar modulation (expresses the output voltage by outputting a pulse of a single polarity during the half cycle of the output voltage), and partial dipolar modulation (the above dipolar modulation and unipolar modulation are mixed in one cycle) The method used was known.
【0003】[0003]
【発明が解決しようとする課題】上記従来技術のPWM
制御では、正負にシフトした2本の変調波のシフト量に
相当するバイアスBを連続可変することにより、ダイポ
ーラ変調とユニポーラ変調の連続移行を部分ダイポーラ
変調を介して実現している。この部分ダイポーラ変調
は、ダイポーラ変調とユニポーラ変調が同一周期内に交
互に混在するモードである。The above prior art PWM
In the control, a continuous transition between dipolar modulation and unipolar modulation is realized through partial dipolar modulation by continuously varying the bias B corresponding to the shift amount of the two modulated waves shifted to the positive and negative sides. This partial dipolar modulation is a mode in which dipolar modulation and unipolar modulation are alternately mixed in the same cycle.
【0004】図3にダイポーラ変調領域での変調波と出
力電圧の波形の一例を示す。このPWM制御では、出力
電圧基本波に比例した基本変調波a(図3(a))を2分
割して、振幅1/2でバイアスBだけ正負にシフトした
正負バイアス変調波abp及びabn(図3(b))を
正負出力電圧パルス(図3(c))の瞬時指令(瞬時出
力電圧指令)に用いている。FIG. 3 shows an example of a modulated wave and an output voltage waveform in a dipolar modulation region. In this PWM control, the positive / negative bias modulation waves abp and abn (FIG. 3) in which the basic modulation wave a (FIG. 3 (a)) proportional to the output voltage fundamental wave is divided into two, and the amplitude is 1/2 and the bias B is shifted positive and negative by the bias B. 3 (b)) is used as an instantaneous command (instantaneous output voltage command) of the positive / negative output voltage pulse (FIG. 3 (c)).
【0005】ここで、図3(b)における±ΔAの範囲
は、主回路を構成するスイッチング素子の特性によって
定まる最小オンパルス幅よりも出力パルスが狭くなる領
域であり、このようなパルス幅の設定指令が来てもこの
領域ではパルス幅を最小オンパルス幅に制限して、素子
故障を避けるようにPWM制御装置を構成している。こ
のため、図3(b)の斜線で示した部分の電圧が制御で
きず、トータルとして図3(d)に示す電圧分だけ出力
電圧が減少する。このような電圧低下は、ダイポーラ変
調から部分ダイポーラ変調へ移行する際に発生し、特に
電圧低下量が最大となるのは、ダイポーラ変調から部分
ダイポーラ変調へ移行する直前である。例えば、キャリ
ア周波数3kHz,ダイポーラ変調で出力電圧30%
(方形波電圧出力となる1パルスを出力電圧100%と
する)までをカバーするものとすると、この電圧低下量
は最大約3%となる。このような電圧低下により、出力
電流やトルクの変動などの問題が生じる。Here, the range of ± ΔA in FIG. 3B is a region where the output pulse is narrower than the minimum on-pulse width determined by the characteristics of the switching elements constituting the main circuit. Even if a command is received, the pulse width is limited to the minimum on-pulse width in this area, and the PWM control device is configured to avoid element failure. For this reason, the voltage of the shaded portion in FIG. 3B cannot be controlled, and the output voltage is reduced by the voltage shown in FIG. 3D in total. Such a voltage drop occurs when shifting from dipolar modulation to partial dipolar modulation. In particular, the amount of voltage drop is greatest immediately before shifting from dipolar modulation to partial dipolar modulation. For example, a carrier frequency of 3 kHz and an output voltage of 30% by dipolar modulation
Assuming that up to (a single pulse that becomes a square-wave voltage output is assumed to be an output voltage of 100%), this voltage drop amount is about 3% at the maximum. Such a voltage drop causes problems such as fluctuations in output current and torque.
【0006】本発明の目的は、PWM制御としてダイポ
ーラ変調と部分ダイポーラ変調を用いたものおいて、瞬
時の電圧指令に忠実に出力電圧を連続制御可能な3レベ
ルインバータのPWM制御装置を提供することにある。An object of the present invention is to provide a PWM control apparatus for a three-level inverter capable of continuously controlling an output voltage faithfully in response to an instantaneous voltage command in a case where dipolar modulation and partial dipolar modulation are used as PWM control. It is in.
【0007】[0007]
【課題を解決するための手段】上記目的は、直流電圧を
PWM制御により正の電圧パルスと負の電圧パルス及び
零電圧の3つの電位を有する交流相電圧に変換して交流
端子に導出する3レベルインバータであって、ダイポー
ラ変調により前記交流相電圧の半周期内で零電圧を介し
て正、負電圧パルスを交互に発生させるPWM制御を有
する3レベルインバータの制御装置において、前記正負
いずれか一方の出力電圧パルスの指令が所定のパルス幅
以下となったとき、当該指令のパルス幅には前記所定の
パルス幅を確保し、逆極性側の電圧パルスの指令の幅を
零電圧期間が短くなる方向に当該パルス幅を広げるよう
に調整する補正手段を備えることにより、達成される。SUMMARY OF THE INVENTION An object of the present invention is to convert a DC voltage into an AC phase voltage having three potentials of a positive voltage pulse, a negative voltage pulse and zero voltage by PWM control, and to lead the AC voltage to an AC terminal. A control device for a three-level inverter having a PWM control for generating a positive voltage pulse and a negative voltage pulse alternately via a zero voltage within a half cycle of the AC phase voltage by a dipolar modulation, wherein the positive or negative one is provided. When the command of the output voltage pulse becomes equal to or less than the predetermined pulse width, the predetermined pulse width is secured in the pulse width of the command, and the width of the command of the voltage pulse on the opposite polarity side is reduced to zero voltage period. This is achieved by providing correction means for adjusting the pulse width so as to increase in the direction.
【0008】[0008]
【作用】上記補正手段は、正負の電圧パルスが零電圧を
介して交互に出力される期間で、PWM制御された出力
パルスが最小パルス幅に制限される領域では、このパル
ス幅の制限によって生じる電圧不足分を補うように逆極
性側のパルス幅を調整する。これにより、瞬時の出力電
圧指令に忠実に出力電圧の制御が可能となる。The above-mentioned correcting means is generated by the limitation of the pulse width in a period where the output pulse subjected to the PWM control is limited to the minimum pulse width during a period in which the positive and negative voltage pulses are alternately output via the zero voltage. Adjust the pulse width on the opposite polarity side to compensate for the voltage shortage. As a result, it is possible to control the output voltage faithfully according to the instantaneous output voltage command.
【0009】[0009]
【実施例】図1に本発明の一実施例を示す。FIG. 1 shows an embodiment of the present invention.
【0010】図1において、Gは直流電圧源である電車
線(架線)、61,62は直流電圧源Gの電圧から交流
出力側の零電位に相当する中間電圧(中性点電圧)を作
り出すため分割したコンデンサ(分圧コンデンサ)であ
る。ここでは、分圧コンデンサ電圧はEd/2であるも
のとした。70〜73は還流用の整流素子を備えた自己
消弧可能なスイッチング素子(この例ではIGBTとし
たが、GTO,トランジスタ等でも良い)、74,75
はコンデンサの中性点電圧を導出する補助整流素子であ
り、7aでU相一相分のスイッチングアームを構成す
る。7b及び7cは、7aと同様で、それぞれV相分と
W相分を構成する。8は誘導電動機で、誘導電動機負荷
の場合を示した。In FIG. 1, G is a train line (a wire) which is a DC voltage source, and 61 and 62 generate an intermediate voltage (neutral point voltage) corresponding to zero potential on the AC output side from the voltage of the DC voltage source G. Therefore, it is a capacitor (voltage dividing capacitor) divided. Here, the voltage of the voltage dividing capacitor is assumed to be Ed / 2. Reference numerals 70 to 73 denote self-extinguishing switching elements having a rectifying element for reflux (in this example, IGBTs, but GTOs, transistors, etc.), 74, 75
Is an auxiliary rectifying element for deriving the neutral point voltage of the capacitor, and a switching arm for one phase of the U phase is constituted by 7a. 7b and 7c are the same as 7a, and constitute a V phase component and a W phase component, respectively. Numeral 8 denotes an induction motor, which shows the case of an induction motor load.
【0011】スイッチングアーム7a〜7cは、それぞ
れ相毎に独立に動作可能であり、スイッチング素子の選
択的なオン・オフ制御により3レベルの出力電圧を発生
する。The switching arms 7a to 7c can operate independently for each phase, and generate three levels of output voltages by selective on / off control of switching elements.
【0012】なお、3レベルインバータの主回路の詳細
は特開昭51−47848 号公報,特開昭56−74088 号公報な
ど、また、PWM制御の詳細は特願平3−301512 号など
に記載されている。The details of the main circuit of the three-level inverter are described in JP-A-51-47848 and JP-A-56-74088, and the details of PWM control are described in Japanese Patent Application No. 3-301512. Have been.
【0013】次に、PWM制御部について説明する。Next, the PWM control unit will be described.
【0014】図1において、基本波電圧指令発生器1は
インバータ出力電圧の周波数指令Fi*,出力電圧実効
値指令E*及び直流電圧Edを入力し瞬時のインバータ
出力電圧指令A・sinθを求め振幅指令分配器2に出力
する。In FIG. 1, a fundamental wave voltage command generator 1 receives a frequency command Fi * of an inverter output voltage, an output voltage effective value command E *, and a DC voltage Ed to obtain an instantaneous inverter output voltage command A · sin θ and an amplitude. Output to the command distributor 2.
【0015】振幅指令分配器2は、インバータ出力電圧
指令A・sinθ を1/2して、さらにバイアス設定器2
1によって基本波振幅指令値A(変調率)に応じて設定
されたバイアス量Bを加算または減算して、正側バイア
ス指令abp及び負側バイアス指令abnを発生する。The amplitude command distributor 2 halves the inverter output voltage command A · sin θ and further sets the bias setter 2
By adding or subtracting the bias amount B set according to 1 in accordance with the fundamental wave amplitude command value A (modulation rate), a positive bias command abp and a negative bias command abn are generated.
【0016】極性判別分配器3は正側バイアス指令ab
p及び負側バイアス指令abnを正負パルスのための正
負電圧指令ap及びanに分配し、パルス発生器4で主
回路スイッチング素子70と73のPWM信号を作り、
それらの信号を反転して1相分のPWM信号S1〜S4
を作る。The polarity discriminating distributor 3 outputs a positive bias command ab.
p and the negative bias command abn are distributed to positive and negative voltage commands ap and an for positive and negative pulses, and the pulse generator 4 generates PWM signals for the main circuit switching elements 70 and 73,
These signals are inverted to provide one-phase PWM signals S1 to S4.
make.
【0017】これらのPWM信号を受けて、ゲート論理
部5は最小オン・オフ時間の確保や素子短絡を防止する
非ラップ時間等を管理したPWMパルス列を生成し、図
示してないゲートドライバを介して主回路スイッチング
素子にゲート信号を送る。In response to these PWM signals, the gate logic unit 5 generates a PWM pulse train in which a minimum on / off time is secured and a non-wrap time for preventing a short circuit of the element is managed, and the gate pulse is transmitted via a gate driver (not shown). Sends a gate signal to the main circuit switching element.
【0018】本実施例では、極性判別分配器3の中で3
0,31,33,34に示した極性判別分配器の働きに
よって、本発明の効果が発揮される。図2に、極性判別
分配器3の構成例を示す。信号分配器30,31,33
及び34は、±ΔAの範囲に入った正側バイアス指令a
bpまたは負側バイアス指令abnの無効分を逆極性側
バイアス指令に重畳するように働く。その結果、正負バ
イアス指令は図3(e)に示すような波形と等価になり、
正負バイアス指令が±ΔAの範囲に入る領域では所定の
パルス幅を確保しつつ、電圧無効分は逆極性側パルス列
で補正される。これにより、電圧指令に対する実電圧と
の誤差が縮小され、出力電圧の正弦波性も保たれる(正
負バイアス変調波の和が図3(a)の基本変調波と一致
する)。一方、PWM信号S1〜S4を直接調整するこ
とによっても同様の補正が可能である。図4に、パルス
幅の補正例を示す。この例では、負側のパルス幅が所定
の最小オンパルス幅Ton以下となった場合を示してい
る。PWM信号S1〜S4に、図4(a)に示すような
狭幅のパルスが発生すると、パルス発生器4の後段に設
けたゲート論理部5によってこの狭幅パルスが所定の最
小オンパルス幅Tonに制限される。そのため、負の電
圧が実際の指令電圧よりも増大してしまう。そこで本実
施例では、図4(b)に示すように、最小オンパルス幅
を確保するために調整されたパルス幅ΔTだけ、反対側
(この例では正側)のパルス幅を補正する。これによ
り、電圧指令通りの出力電圧を実現可能となる。In the present embodiment, 3
The effects of the present invention are exerted by the functions of the polarity discriminating distributors 0, 31, 33, and 34. FIG. 2 shows a configuration example of the polarity discriminating distributor 3. Signal distributors 30, 31, 33
And 34 are positive bias commands a within the range of ± ΔA.
bp or the invalid part of the negative bias command abn is superimposed on the reverse polarity bias command. As a result, the positive / negative bias command becomes equivalent to a waveform as shown in FIG.
In a region where the positive / negative bias command falls within the range of ± ΔA, the invalid voltage is corrected by the reverse-polarity side pulse train while securing a predetermined pulse width. As a result, the error between the voltage command and the actual voltage is reduced, and the sinusoidal property of the output voltage is maintained (the sum of the positive and negative bias modulation waves matches the basic modulation wave in FIG. 3A). On the other hand, the same correction can be made by directly adjusting the PWM signals S1 to S4. FIG. 4 shows an example of correcting the pulse width. In this example, a case where the pulse width on the negative side becomes equal to or smaller than a predetermined minimum on-pulse width Ton is shown. When a narrow pulse as shown in FIG. 4A is generated in the PWM signals S1 to S4, the narrow pulse is reduced to a predetermined minimum on-pulse width Ton by the gate logic unit 5 provided at the subsequent stage of the pulse generator 4. Limited. Therefore, the negative voltage increases more than the actual command voltage. Therefore, in the present embodiment, as shown in FIG. 4B, the pulse width on the opposite side (the positive side in this example) is corrected by the pulse width ΔT adjusted to secure the minimum on-pulse width. As a result, an output voltage according to the voltage command can be realized.
【0019】以上の実施例は誘導電動機を例にとって説
明したが、この他の交流電動機でも同様である。また、
ここではインバータにおける実施例を示したが、これら
のインバータの出力端子をリアクタンス要素を介して交
流電源と接続し、交流を直流に変換する自励式コンバー
タとして動作(回生動作)させることも可能である。こ
の場合も、インバータの場合と同様の効果が期待でき
る。Although the above embodiment has been described taking an induction motor as an example, the same applies to other AC motors. Also,
Although the embodiments of the inverters are shown here, the output terminals of these inverters can be connected to an AC power supply via a reactance element to operate as a self-excited converter that converts AC to DC (regeneration operation). . In this case, the same effect as that of the inverter can be expected.
【0020】当然ながら、マイクロプロセッサ等を用い
れば、上記パルス発生手段の一部または全てをプログラ
ム化して、ソフトウェア的に実現することが可能であ
る。Naturally, if a microprocessor or the like is used, a part or all of the pulse generating means can be programmed and realized as software.
【0021】[0021]
【発明の効果】本発明によれば、正負の電圧パルスが零
電圧を介して交互に出力される期間で、PWM制御され
た出力パルスが最小パルス幅に制限される領域で、この
パルス幅の制限によって生じる電圧不足分を補うように
逆極性側のパルス幅を調整することにより、瞬時の出力
電圧指令に忠実に出力電圧の制御が可能となり、出力電
圧の連続制御を実現できる。According to the present invention, during the period in which the positive and negative voltage pulses are alternately output via the zero voltage, the PWM-controlled output pulse is limited to the minimum pulse width, and the pulse width of this pulse width is set to the minimum pulse width. By adjusting the pulse width on the opposite polarity side to compensate for the voltage shortage caused by the limitation, the output voltage can be controlled faithfully in response to the instantaneous output voltage command, and continuous control of the output voltage can be realized.
【図1】本発明の一実施例を示す構成図。FIG. 1 is a configuration diagram showing one embodiment of the present invention.
【図2】図1の極性判別分配器の構成例を示す図。FIG. 2 is a diagram showing a configuration example of a polarity discrimination distributor of FIG. 1;
【図3】本発明のパルス幅の補正原理を説明する図。FIG. 3 is a view for explaining a principle of correcting a pulse width according to the present invention.
【図4】本発明の第2の実施例を示す図。FIG. 4 is a diagram showing a second embodiment of the present invention.
1…基本波電圧指令発生器、2…振幅指令分配器、3…
極性判別分配器、4…パルス発生器、5…ゲート論理
部、G…直流電圧源(架線)、7a,7b,7c…スイ
ッチングアーム、8…誘導電動機、21…バイアス設定
器、30,31,33,34…信号分配器、61,62
…分圧コンデンサ、70〜73…スイッチング素子、7
4,75…補助整流素子。1. Basic wave voltage command generator, 2. Amplitude command distributor, 3.
Polarity discriminating distributor, 4 pulse generator, 5 gate logic unit, G DC voltage source (overhead wire), 7a, 7b, 7c switching arm, 8 induction motor, 21 bias setting device, 30, 31, 33, 34 ... signal distributors, 61, 62
... voltage dividing capacitors, 70-73 ... switching elements, 7
4,75 ... Auxiliary rectifying element.
───────────────────────────────────────────────────── フロントページの続き (56)参考文献 特開 平6−98559(JP,A) 特開 平5−49263(JP,A) 特開 平5−146160(JP,A) 特開 平6−311759(JP,A) (58)調査した分野(Int.Cl.7,DB名) H02M 7/48 H03K 7/08 ────────────────────────────────────────────────── ─── Continuation of front page (56) References JP-A-6-98559 (JP, A) JP-A-5-49263 (JP, A) JP-A-5-146160 (JP, A) JP-A-6-98559 311759 (JP, A) (58) Field surveyed (Int. Cl. 7 , DB name) H02M 7/48 H03K 7/08
Claims (3)
ルスと負の電圧パルス及び零電圧の3つの電位を有する
交流相電圧に変換して交流端子に導出する3レベルイン
バータであって、ダイポーラ変調により前記交流相電圧
の半周期内で零電圧を介して正、負電圧パルスを交互に
発生させるPWM制御を有する3レベルインバータの制
御装置において、 前記正負いずれか一方の出力電圧パルスの指令が所定の
パルス幅以下となったとき、当該指令のパルス幅には前
記所定のパルス幅を確保し、逆極性側の電圧パルスの指
令の幅を零電圧期間が短くなる方向に当該パルス幅を広
げるように調整する手段を備えた3レベルインバータの
PWM制御装置。1. A three-level inverter for converting a DC voltage into an AC phase voltage having three potentials of a positive voltage pulse, a negative voltage pulse, and a zero voltage by PWM control and leading the AC voltage to an AC terminal, wherein the dipolar modulation is performed. In the control device for a three-level inverter having PWM control for alternately generating a positive voltage pulse and a negative voltage pulse via a zero voltage within a half cycle of the AC phase voltage, a command of one of the positive and negative output voltage pulses is When the pulse width becomes equal to or less than the predetermined pulse width, the predetermined pulse width is secured for the pulse width of the command, and the width of the command of the voltage pulse on the opposite polarity side is increased in a direction in which the zero voltage period becomes shorter. PWM control device for a three-level inverter, comprising:
ルスの調整分の合計が零となるように、前記電圧パルス
の幅を調整した3レベルインバータのPWM制御装置。2. The PWM control device for a three-level inverter according to claim 1, wherein the width of the voltage pulse is adjusted such that the sum of the adjustments of the positive and negative output voltage pulses becomes zero.
ルスと負の電圧パルス及び零電圧の3つの電位を有する
交流相電圧に変換して交流端子に導出する3レベルイン
バータであって、ダイポーラ変調により前記交流相電圧
の半周期内で零電圧を介して正、負電圧パルスを交互に
発生させるPWM制御を有する3レベルインバータの制
御装置において、 正の出力電圧パルスを発生させるための正の瞬時電圧指
令と負の出力電圧パルスを発生させるための負の瞬時電
圧指令を備え、正負いずれか一方の瞬時出力電圧指令の
絶対値が所定値以下となったとき、逆極性側の瞬時電圧
指令を前記所定値を超える分増やすように調整する手段
を備えた3レベルインバータのPWM制御装置。3. A three-level inverter for converting a DC voltage into an AC phase voltage having three potentials of a positive voltage pulse, a negative voltage pulse, and a zero voltage by PWM control and leading the AC voltage to an AC terminal, wherein the inverter is a dipolar modulation. In the control device of the three-level inverter having the PWM control in which the positive and negative voltage pulses are alternately generated via the zero voltage within the half cycle of the AC phase voltage, the positive moment for generating the positive output voltage pulse A voltage command and a negative instantaneous voltage command for generating a negative output voltage pulse are provided, and when the absolute value of either the positive or negative instantaneous output voltage command becomes less than or equal to a predetermined value, the instantaneous voltage command on the opposite polarity side is output. A PWM controller for a three-level inverter, comprising: means for adjusting so as to increase by an amount exceeding the predetermined value.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP18880295A JP3333883B2 (en) | 1995-07-25 | 1995-07-25 | PWM controller for three-level inverter |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP18880295A JP3333883B2 (en) | 1995-07-25 | 1995-07-25 | PWM controller for three-level inverter |
Publications (2)
Publication Number | Publication Date |
---|---|
JPH0947031A JPH0947031A (en) | 1997-02-14 |
JP3333883B2 true JP3333883B2 (en) | 2002-10-15 |
Family
ID=16230065
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP18880295A Expired - Fee Related JP3333883B2 (en) | 1995-07-25 | 1995-07-25 | PWM controller for three-level inverter |
Country Status (1)
Country | Link |
---|---|
JP (1) | JP3333883B2 (en) |
Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
EP3382882A1 (en) * | 2017-03-28 | 2018-10-03 | Schneider Electric IT Corporation | Multistate pwm command for 3 level inverters |
Families Citing this family (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN113839587B (en) * | 2020-06-23 | 2023-06-16 | 美的威灵电机技术(上海)有限公司 | Polarity judging method, judging device and motor control system |
-
1995
- 1995-07-25 JP JP18880295A patent/JP3333883B2/en not_active Expired - Fee Related
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
EP3382882A1 (en) * | 2017-03-28 | 2018-10-03 | Schneider Electric IT Corporation | Multistate pwm command for 3 level inverters |
US10461575B2 (en) | 2017-03-28 | 2019-10-29 | Schneider Electric It Corporation | Multistate PWM command for 3 levels inverters |
Also Published As
Publication number | Publication date |
---|---|
JPH0947031A (en) | 1997-02-14 |
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