JP3226656B2 - AD converter - Google Patents
AD converterInfo
- Publication number
- JP3226656B2 JP3226656B2 JP07368593A JP7368593A JP3226656B2 JP 3226656 B2 JP3226656 B2 JP 3226656B2 JP 07368593 A JP07368593 A JP 07368593A JP 7368593 A JP7368593 A JP 7368593A JP 3226656 B2 JP3226656 B2 JP 3226656B2
- Authority
- JP
- Japan
- Prior art keywords
- signal
- output
- reference signal
- modulator
- analog input
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
Links
Description
【0001】[0001]
【産業上の利用分野】本発明はΔΣモジュレータを用い
たゲインエラーのないAD(アナログデジタル)変換器
に関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a gain error-free AD (analog-to-digital) converter using a ΔΣ modulator.
【0002】[0002]
【従来の技術】ΔΣモジュレータを用いてAD変換する
AD変換器は、アナログ入力信号(変換信号)とリファ
レンス信号とを積分する積分手段、この積分手段の出力
信号を量子化する量子化手段およびこの量子化手段の出
力に応じてリファレンス信号を正転または反転して積分
するように制御するフィードバック手段からなるΔΣモ
ジュレータと、このΔΣモジュレータの出力信号を入力
するデジタルフィルタとを有する。このようなAD変換
器においては、AD変換するアナログ入力信号の範囲
(AD変換範囲)がリファレンス信号によって与えられ
る。ΔΣモデュレーダが発振することを抑えるため、ア
ナログ入力信号をリファレンス信号の1/n倍にとり、
ΔΣモジュレータの後段のデジタルフィルタでn倍のゲ
イン補正を行い、結果として出力されるコードのアナロ
グ入力信号に対するゲインを所定の値とする(米国特許
No.4581841)。2. Description of the Related Art An A / D converter for performing A / D conversion using a .DELTA..SIGMA. Modulator includes an integrating means for integrating an analog input signal (converted signal) and a reference signal, a quantizing means for quantizing an output signal of the integrating means, and an integrating means. A ΔΣ mode comprising feedback means for controlling the reference signal to invert or invert according to the output of the quantization means and to integrate the reference signal.
The modulator has a durator and a digital filter for inputting an output signal of the ΔΣ modulator . In such an AD converter, a range of an analog input signal to be AD-converted (AD conversion range) is given by a reference signal. To suppress the Δ と り modulator from oscillating, take the analog input signal as 1 / n times the reference signal,
A gain correction of n times is performed by a digital filter at the subsequent stage of the ΔΣ modulator, and the gain of the resulting code with respect to the analog input signal is set to a predetermined value (US Pat. No. 4,518,841).
【0003】[0003]
【発明が解決しようとする課題】しかしながら、上述の
従来例においては、ΔΣモジュレータにアナログ入力信
号を導入するための素子とリファレンス信号を導入する
ための素子とが別個になっていた。そのため、素子の個
体間のばらつきによって、ΔΣモジュレータにおけるア
ナログ入力信号とリファレンス信号との比が1/nでな
く1/(n+α)となることがあった。この場合、デジ
タルフィルタ部でn倍のゲイン補正を行うと、出力コー
ドは所定の値からn/(n+α)倍のゲインエラーを含
んでしまうことになった。これをさらに補正するために
は、個々のAD変換器において、ゲインエラーをあらか
じめ算出しておいて、その算出値を記憶し、この記憶値
に基づいて各々のAD変換値に補正計算を施さなければ
ならない。したがって、あらかじめゲインエラーを算出
するための時間および補正計算を行うための時間がかか
ることになり、また、このゲインエラーの算出を行うた
めの回路、ゲインエラーを記憶する回路、補正計算をす
るための回路が必要になるという問題があった。However, in the above-mentioned conventional example, an element for introducing an analog input signal into the ΔΣ modulator and an element for introducing a reference signal are separate. Therefore, the ratio between the analog input signal and the reference signal in the ΔΣ modulator may be 1 / (n + α) instead of 1 / n due to the variation between the individual elements. In this case, if the digital filter section performs n-times gain correction, the output code includes an n / (n + α) -times gain error from a predetermined value. In order to further correct this, in each AD converter, a gain error is calculated in advance, the calculated value is stored, and correction calculation is performed on each AD conversion value based on the stored value. Must. Therefore, it takes time to calculate the gain error and time to perform the correction calculation in advance, and furthermore, a circuit for calculating the gain error, a circuit for storing the gain error, and a circuit for performing the correction calculation. There is a problem that the circuit of the above is required.
【0004】そこで本発明の目的は以上のような問題を
解消し、ゲインエラーのないAD変換器を提供すること
にある。An object of the present invention is to solve the above-mentioned problems and to provide an AD converter free from a gain error.
【0005】[0005]
【課題を解決するための手段】上記目的を達成するため
本発明は、アナログ入力信号とリファレンス信号とを積
分する積分手段、該積分手段の出力信号を量子化する量
子化手段および該量子化手段の出力に応じて前記リファ
レンス信号を正転または反転して積分するように制御す
るフィードバック手段からなるΔΣモジュレータと、前
記ΔΣモジュレータの出力信号を入力するデジタルフィ
ルタとからなるAD変換器において、前記アナログ入力
信号と前記リファレンス信号とのいずれかを選択して前
記積分手段の共通の入力素子に出力する選択手段を備
え、当該選択手段は、前記量子化手段の判定時刻の間に
前記アナログ入力信号と前記リファレンス信号とを所定
の比率で時分割で前記積分手段の共通の入力素子に出力
することを特徴とする。In order to achieve the above object, the present invention provides an integrating means for integrating an analog input signal and a reference signal, a quantizing means for quantizing an output signal of the integrating means, and the quantizing means. AD converter comprising a Δ フ ィ ー ド バ ッ ク modulator comprising feedback means for controlling the reference signal to perform normal or inverted inversion in accordance with the output, and a digital filter to which the output signal of the ΔΣ modulator is inputted. The analog input
Signal and the reference signal
Selection means for outputting to the common input element of the integration means is provided.
In addition, the selection means is provided between the determination times of the quantization means.
The analog input signal and the reference signal are predetermined.
Output to the common input element of the integrating means in time division
Characterized in that it.
【0006】[0006]
【作用】本発明によればアナログ入力信号とリファレン
ス信号とを共通の素子を介して選択的に積分手段に与え
るので、入力素子間のばらつきによるゲインエラー補正
のための記憶素子や回路を必要としなくなる。According to the present invention, the analog input signal and the reference signal are selectively supplied to the integrating means via a common element, so that a memory element or a circuit for correcting a gain error due to a variation between input elements is required. Disappears.
【0007】[0007]
【実施例】以下、図面を参照して本発明の実施例を詳細
に説明する。Embodiments of the present invention will be described below in detail with reference to the drawings.
【0008】図1は本発明の実施例を示す。このAD変
換器は、アナログ入力信号(変換信号)とAD変換範囲
を設定するためのリファレンス信号とを入力し、これら
のいずれかを選択信号によって時分割選択し出力する選
択手段1と、この選択手段1からの出力信号を入力する
ΔΣモジュレータ2と、このΔΣモジュレータ2からの
出力信号を入力してAD変換コードを出力するデジタル
フィルタ3とを有する。FIG. 1 shows an embodiment of the present invention. The AD converter receives an analog input signal (conversion signal) and a reference signal for setting an AD conversion range, selects one of them by time-division using a selection signal, and outputs the selected signal. It has a ΔΣ modulator 2 for inputting an output signal from the means 1 and a digital filter 3 for inputting an output signal from the ΔΣ modulator 2 and outputting an AD conversion code.
【0009】図2は選択手段1およびΔΣモジュレータ
2の具体例を示し、ΔΣモジュレータ2はスイッチドキ
ャパシタフィルタにより構成したものである。図3はそ
の動作を示すタイミング図である。本例は、CMOSプ
ロセスによるLSIとして製造され、各スイッチはMO
Sトランジスタによるトランスファゲートからなってい
る。FIG. 2 shows a specific example of the selection means 1 and the ΔΣ modulator 2, and the ΔΣ modulator 2 is constituted by a switched capacitor filter. FIG. 3 is a timing chart showing the operation. This example is manufactured as an LSI by a CMOS process, and each switch is an MO.
It consists of a transfer gate using an S transistor.
【0010】図2に示すように選択手段1はスイッチS
W1,SW2およびインバータ4を有する。ΔΣモジュ
レータ2は、コンデンサC1〜C6、スイッチSW2〜
SW18、オペアンプA1,A2、コンパレータCPお
よびロジック回路5を有する。[0010] As shown in FIG.
W1, SW2 and an inverter 4 are provided. The ΔΣ modulator 2 includes capacitors C1 to C6, switches SW2
SW18, operational amplifiers A1 and A2, comparator CP and logic circuit 5 are provided.
【0011】各スイッチは、図3に示すような関係を有
するクロックS1〜S6によって開閉する。変換信号と
リファレンス信号は、SW1,SW2によって、クロッ
クS1の周期に対して1対3の割合で交互に選択され
る。すなわち、SW1が1に対してSW2が3の割合で
閉じることになり、まず選択信号が1のとき変換信号が
SW1を通してΔΣモジュレータに出力され、ついで選
択信号が0のときリファレンス信号がSW2を通してΔ
Σモジュレータに出力される。これを受けて、ΔΣモジ
ュレータにおいては、ロジック回路5が、選択信号また
は後述のようにして得られるコンパレータCPからの判
定出力(“1”または“0”)に応答して、次のように
してS1,S2に基づいてS5,S6を作成し、S1,
S2,S5,S6によって、C1の両側のSW3〜SW
6を開閉してC1に信号電荷を蓄積し、C2に対してC
1の電荷を加算または減算する。Each switch is opened and closed by clocks S1 to S6 having a relationship as shown in FIG. The conversion signal and the reference signal are alternately selected by SW1 and SW2 at a ratio of 1: 3 with respect to the cycle of the clock S1. That is, when SW1 is 1, SW2 is closed at a ratio of 3. First, when the selection signal is 1, the conversion signal is output to the Δ を 通 し て modulator through SW1, and when the selection signal is 0, the reference signal is output through SW2.
出力 Output to the modulator. In response to this, in the ΔΣ modulator, the logic circuit 5 responds to the selection signal or the judgment output (“1” or “0”) from the comparator CP obtained as described later, as follows. S5 and S6 are created based on S1 and S2,
By S2, S5 and S6, SW3 to SW on both sides of C1
6 is opened and closed to accumulate signal charges in C1, and C2 is stored in C2.
One charge is added or subtracted.
【0012】(1)選択信号が1のとき、S5,S6は
S5=S1,S6=S2となり、まずS1のタイミング
でC1に変換信号が蓄積され、ついでS2のタイミング
でC1に蓄積された電荷がC2に積分される。(1) When the selection signal is 1, S5 and S6 become S5 = S1 and S6 = S2. First, the converted signal is stored in C1 at the timing of S1, and the charges stored in C1 at the timing of S2. Is integrated into C2.
【0013】(2)選択信号が0で、コンパレータCP
の判定出力が1の場合、S5=S2,S6=S1とな
り、まずS1のタイミングでC1の両側がアナロググラ
ンドに接続され、ついでS2のタイミングでC1に蓄積
されたリファレンス信号電荷をC2から減算する。この
動作を図3に示すように、選択信号が1になるまで、3
回行う。(2) When the selection signal is 0 and the comparator CP
Is S1, S5 = S2, S6 = S1. First, both sides of C1 are connected to the analog ground at the timing of S1, and the reference signal charge stored in C1 is subtracted from C2 at the timing of S2. . This operation is repeated until the selection signal becomes 1 as shown in FIG.
Do it twice.
【0014】(3)選択信号が0で、コンパレータCP
の判定出力が0の場合、S5=S1,S6=S2とな
り、まず、S1のタイミングでC1にリファレンス信号
電荷を蓄積し、ついでS2のタイミングでC1に蓄積さ
れたリファレンス信号電荷をC2に加算する。この動作
を図3に示すように、選択信号が1になるまで3回行
う。(3) When the selection signal is 0 and the comparator CP
Is S0 = S1 and S6 = S2, the reference signal charge is first stored in C1 at the timing of S1, and the reference signal charge stored in C1 is added to C2 at the timing of S2. . This operation is performed three times until the selection signal becomes 1 as shown in FIG.
【0015】以上によって、図2中のノードA点の電圧
は図3のように変化する。ΔΣモジュレータのサンプリ
ング周期はS3,S4で示されるようにS1の4倍とな
っており、C1による4回の積分動作と一致する。S
3,S4に従って開閉するSW7〜SW10によってA
点の電圧情報はC3,C4に蓄積、積分される。この結
果得られるノードB点の電圧は図3のように変化する。As described above, the voltage at the node A in FIG. 2 changes as shown in FIG. The sampling period of the ΔΣ modulator is four times S1 as shown by S3 and S4, which coincides with four integration operations by C1. S
3, SW7 to SW10 that open and close according to S4
The point voltage information is accumulated and integrated in C3 and C4. The resulting voltage at node B changes as shown in FIG.
【0016】A点およびB点の電圧情報は、S3,S4
に従って開閉するSW11〜SW18およびC5,C6
を用いた加算器で算出され、その結果はノードC点の電
圧情報として図3に示すように得られる。コンパレータ
CPは図3のΔに示す判定時刻にC点の電圧情報の判定
出力を更新し、前述のようにロジック回路5に入力す
る。The voltage information at the points A and B is represented by S3, S4
SW11 to SW18 and C5, C6 that open and close according to
, And the result is obtained as voltage information at the node C as shown in FIG. The comparator CP updates the judgment output of the voltage information at the point C at the judgment time indicated by Δ in FIG. 3, and inputs the same to the logic circuit 5 as described above.
【0017】本実施例では、変換信号範囲値とリファレ
ンス信号との比が1/3になっているため、後段のデジ
タルフィルタ3は3倍のゲインを与えるようになってお
り、したがって、出力コードの変換信号(アナログ入力
信号)に対するゲインは所定の1倍となる。また、リフ
ァレンス信号と変換信号範囲値との比は、整数同士の比
とすることが望ましく、この場合は共通の入力素子をこ
の整数に対応する回数ずつ使用して入力を与えることが
できる。In this embodiment, since the ratio between the converted signal range value and the reference signal is 1/3, the digital filter 3 at the subsequent stage gives a gain of three times. The gain with respect to the converted signal (analog input signal) becomes 1 times the predetermined value. Further, the ratio between the reference signal and the converted signal range value is desirably a ratio between integers. In this case, an input can be given by using a common input element by the number of times corresponding to the integer.
【0018】[0018]
【発明の効果】以上説明したように本発明によれば、ア
ナログ入力信号とリファレンス信号とを共通の素子を介
して選択的に積分手段に与えるので、入力素子間のばら
つきによるゲインエラー補正のための記憶素子や回路を
必要とせずにゲインエラーのないAD変換器を提供する
ことができる。As described above, according to the present invention, the analog input signal and the reference signal are selectively supplied to the integrating means via the common element, so that the gain error due to the variation between the input elements can be corrected. And an AD converter free of a gain error without the need for the storage element or circuit.
【図1】本発明の実施例の構成を示す図である。FIG. 1 is a diagram showing a configuration of an embodiment of the present invention.
【図2】同実施例のブロック図である。FIG. 2 is a block diagram of the embodiment.
【図3】同実施例の動作説明図である。FIG. 3 is an operation explanatory diagram of the embodiment.
C1,C2 コンデンサ SW1〜SW18 スイッチ C1, C2 Capacitor SW1 to SW18 Switch
Claims (1)
を積分する積分手段、該積分手段の出力信号を量子化す
る量子化手段および該量子化手段の出力に応じて前記リ
ファレンス信号を正転または反転して積分するように制
御するフィードバック手段からなるΔΣモジュレータ
と、 前記ΔΣモジュレータの出力信号を入力するデジタルフ
ィルタとからなるAD変換器において、前記アナログ入力信号と前記リファレンス信号とのいず
れかを選択して前記積分手段の共通の入力素子に出力す
る選択手段を備え、当該選択手段は、前記量子化手段の
判定時刻の間に前記アナログ入力信号と前記リファレン
ス信号とを所定の比率で時分割で前記積分手段の共通の
入力素子に出力する ことを特徴とするAD変換器。1. An analog input signal and a reference signal
Integrating means for integrating the output signal, and quantizing an output signal of the integrating means.
The quantization means and the output according to the output of the quantization means.
Control to integrate the reference signal forward or reverse.
Control meansΔΣ modulator
And saidΔΣ modulatorDigital output
In the AD converter consisting of the filterAny of the analog input signal and the reference signal
And outputs it to the common input element of the integrating means.
Selection means, wherein the selection means is
During the judgment time, the analog input signal and the reference
Signal and a common ratio of the integrating means in a predetermined ratio by time division.
Output to input element An AD converter characterized in that:
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP07368593A JP3226656B2 (en) | 1993-03-31 | 1993-03-31 | AD converter |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP07368593A JP3226656B2 (en) | 1993-03-31 | 1993-03-31 | AD converter |
Publications (2)
Publication Number | Publication Date |
---|---|
JPH06291666A JPH06291666A (en) | 1994-10-18 |
JP3226656B2 true JP3226656B2 (en) | 2001-11-05 |
Family
ID=13525320
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP07368593A Expired - Lifetime JP3226656B2 (en) | 1993-03-31 | 1993-03-31 | AD converter |
Country Status (1)
Country | Link |
---|---|
JP (1) | JP3226656B2 (en) |
-
1993
- 1993-03-31 JP JP07368593A patent/JP3226656B2/en not_active Expired - Lifetime
Also Published As
Publication number | Publication date |
---|---|
JPH06291666A (en) | 1994-10-18 |
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