JP3160894B2 - Musical sound effect giving device - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an effect imparting apparatus for imparting a musical effect to a musical tone signal, and more particularly, to a musical tone signal which combines a delay time modulation (flanger) and a phase shift amount modulation (phasor). The present invention relates to a musical sound effect giving device which can be given to a sound.

[0002]

2. Description of the Related Art Conventionally, a so-called flanger using delay time modulation and a so-called phaser using phase shift amount modulation have been known as an effect imparting device for imparting a musical effect to a musical tone signal.

FIG. 9 shows a configuration example of a flanger. The flanger includes an adder 91, a delay (delay) circuit 92, a multiplier 94, a modulator 95, and a mixer 96.

[0004] Input tone signal (hereinafter referred to as "original tone")
Is input to an adder 91, and the output of the adder 91 is input to a delay circuit 92. The delay circuit 92 delays the original sound by a predetermined time and outputs it. The output of the delay circuit 92 is
Is multiplied by a predetermined constant (feedback coefficient), and is fed back to the adder 91. The adder 91 adds the original sound and the multiplication result of the multiplier 94 and outputs the result. Mixer 9
6 adjusts and balances the balance between the original sound and the output signal from the delay circuit 92, and outputs an addition result (tone signal with an effect).

The delay time of the delay circuit 92 is modulated according to a modulation signal output from a modulator 95. Delay circuit 9
2 is a BBD (Buck) when configured with an analog circuit.
In the case where an electronic device such as an electronic device (EtBridge Device) is configured by a digital circuit, a shift register, a RAM (read only memory), or the like may be used.

FIG. 10A is a graph 1 showing the relationship between the frequency f of the original sound and the phase delay φ due to the delay of the delay circuit 92.
01 is shown. In the figure, the horizontal axis represents the frequency f of the original sound (note that the frequency f is represented on a logarithmic (log) scale), and the vertical axis represents the phase delay φ. Assuming that the delay time of the delay circuit 92 is D, φ = 2π · D · f, and the phase delay φ
Is proportional to the frequency f of the original sound.

In FIG. 10 (a), the frequency f =
(1 / D), that is, the delay time D of the delay circuit 92
Is equal to the period of the original sound, the phase delay becomes φ = 2π. Similarly, when the frequency f of the original sound f = (2 / D), the phase delay φ = 4π, when the frequency f of the original sound f = (4 / D), the phase delay φ = 8π, and so on.

FIG. 10B shows a frequency characteristic obtained by mixing the output from the delay circuit 92 whose phase is delayed and the original sound by the mixer 96 as described above. The horizontal axis is the frequency f of the original sound
(Logarithmic axis), the vertical axis indicates the output amplitude level.

In the frequency characteristic of the mixing result, the phase delay φ due to the delay of the delay circuit 92 is 2nπ (n = 0,
(1, 2, 3,...) Are peaks. Therefore, as shown in the solid line graph 102 of FIG. 10B, the frequency f is (1 / D), (2 / D), (4 / D)
A peak appears at a position such as Further, the phase delay φ due to the delay of the delay circuit 92 is (2n + 1) π (n =
(0, 1, 2, 3, ...) are valleys (notches). Therefore, as shown in the solid-line graph 102 in FIG. 10B, a notch appears at a position where the frequency f becomes (1 / 2D), (3 / 2D), or the like.

In the circuit of FIG. 9, the output of the delay circuit 92 is
The signal is fed back to the adder 91 via the multiplier 94. With such feedback, the peak in the frequency characteristic of FIG. 10B is further emphasized. FIG.
The graph indicated by the dotted line 103 in (b) shows the frequency characteristics when the feedback amount is large. Frequency f is (1 / D),
Peaks at positions such as (2 / D) and (4 / D) are more emphasized. This is the same characteristic as a so-called comb filter.

When the modulator 95 modulates the delay time D of the delay circuit 92, the frequency characteristic in FIG. 10B moves in parallel on the horizontal axis. That is, the graph of FIG. 10B moves to the right as the delay time D decreases, and to the left as the delay time D increases, on the horizontal axis (frequency f axis) which is a logarithmic axis. As a result, the timbre of the original sound changes, and an effect is given to the original sound.

FIG. 11 shows a configuration example of a phasor. The phasor includes an adder 111, a phase shifter 113, a multiplier 114, a modulator 115, and a mixer 116.

The original sound is input to the adder 111 and the adder 1
The output of 11 is input to the phase shifter 113. Phase shifter 113
Shifts (phase shifts) the phase of the original sound by a predetermined amount and outputs it. The output of the phase shifter 113 is multiplied by a predetermined constant in a multiplier 114 and fed back to an adder 111.
The adder 111 adds the original sound and the multiplication result of the multiplier 114 and outputs the result. The mixer 116 adjusts and balances the balance between the original sound and the output signal from the phase shifter 113, and outputs an addition result (an effect-added musical sound signal).

The amount of phase shift of the phase shifter 113 is
The signal is modulated in accordance with the modulation signal output from 15. As the phase shifter 113, an all-pass filter is often used. FIG. 12 is an example of a first-order all-pass filter used as the phase shifter 113. In the case of such a first-order all-pass filter, since only a maximum phase shift amount of π can be obtained per stage, it is usually used in cascade connection in multiple stages such as four stages or eight stages. Hereinafter, the phase shifter 113 in FIG. 11 will be described assuming that the primary all-pass filter in FIG. 12 is cascaded in eight stages.

FIG. 13A is a graph 131 showing the relationship between the frequency f of the original sound and the phase delay φ by the phase shifter 113. In the figure, the horizontal axis represents the frequency f of the original sound (however,
The logarithmic (log) scale is assumed), and the vertical axis indicates the phase delay φ.

In the first-order all-pass filter of FIG. 12, a frequency at which the phase of the original sound is delayed by (π / 2) is referred to as a reference frequency fc. Phase shifter 1 of FIG.
Reference numeral 13 denotes an eight-stage cascade connection of the primary all-pass filters shown in FIG. 12, so that when the frequency of the original sound is the reference frequency fc, the phase delay is 4π.

When p> 0, the transfer function of the first-order all-pass filter is represented by T (s) = (sp) / (s + p).
Where each frequency of the input signal is p (radian / s)
Since the phase is delayed by (π / 2) at the position, the reference frequency fc can be expressed as fc = (p / 2π) by using this p.

In FIG. 13A, the frequency f =
At fc, that is, when the frequency f of the original sound matches the reference frequency fc of the phase shifter 113, the phase delay becomes φ = 4π. As the frequency f of the original sound decreases, the phase delay φ approaches zero. As the frequency f of the original sound increases, the phase delay φ approaches 8π.

FIG. 13B shows a frequency characteristic (graph 132) of a result obtained by mixing the output from the phase shifter 113 with a delayed phase and the original sound by the mixer 116 as described above. The horizontal axis indicates the frequency f of the original sound (logarithmic axis), and the vertical axis indicates the amplitude level of the output. In the graph 132 of this figure, the phase shifter 113
Are peaks at positions where the phase delay φ due to the delay of 2π, 2π, 4π, and 6π. In addition, positions where the phase delay φ due to the delay of the phase shifter 113 becomes π, 3π, 5π, 7π are valleys (notches).

In the circuit shown in FIG. 11, the output of the phase shifter 113 is fed back to the adder 111 via the multiplier 114. With such feedback, FIG.
The peak in the frequency characteristic of (b) is further emphasized. A graph indicated by a dotted line 133 in FIG. 13B shows frequency characteristics when the feedback amount is large. It can be seen that the peak is more emphasized.

When the reference frequency of the phase shifter 113 is modulated by the modulator 115 (actually, the parameter of the all-pass filter is modulated to change the reference frequency fc), FIG.
The frequency characteristic of (b) moves in parallel on the horizontal axis. That is, in the graph of FIG. 13B, when the reference frequency fc decreases, the graph moves to the left, when the reference frequency fc increases, to the right.
The parallel movement is performed on a horizontal axis (frequency f axis) which is a logarithmic axis.

[0022]

By the way, in the case of the flanger of FIG. 9 as described above, the peak in the frequency characteristic is a harmonic overtone sequence as described with reference to FIG. 10B. Therefore, only the sound of a certain note name is likely to be emphasized.
This is particularly noticeable when the feedback amount is increased.

In the frequency characteristic shown in FIG. 10B, it is necessary to increase the delay time D of the delay circuit 92 in order to locate the notch even in a low frequency band. However, if the delay time D is lengthened, notches become too large in a high frequency band, and especially when the feedback is increased, the impulse response becomes longer and the sound tends to be annoying.

As a result, with a flanger with a short delay time D, a change in tone color (effect imparting) at a low frequency is hardly obtained.

On the other hand, in the case of the phasor of FIG. 11 described above, if the reference frequency fc of the phase shifter (all-pass filter) 113 is lowered as shown in FIG. Can be brought, and a tone change at a low frequency can be easily obtained. However, increasing the number of notches requires a multi-stage all-pass filter, which is more expensive than a flanger that only requires changing the delay time. Further, in a high frequency band, a sufficient number of notches cannot be obtained, so that an effect as intense as a flanger cannot be obtained.

In view of the above-mentioned problems in the conventional example, the present invention can provide a uniform effect without emphasizing a specific note name, and can provide an effect with a sufficient modulation feeling from a low frequency band to a high frequency band. It is an object of the present invention to provide an effect giving device capable of giving an effect.

[0027]

In order to achieve this object, the invention according to claim 1 is directed to a tone signal input from tone signal generating means for generating a tone signal having a pitch based on performance information. A loop circuit having delay means for delaying a signal uncorrelated with the pitch; a phase shift means arranged in the loop circuit for shifting a phase of a signal circulating through the loop circuit; Control means for modulating and controlling the shift amount.

[0028]

Since the input tone signal is delayed and its phase is shifted, the peak frequency can be shifted from the harmonic harmonic train. Further, by combining the delay time modulation and the phase amount modulation, a sufficient modulation feeling can be obtained in a range from a low frequency range to a high frequency range.

[0029]

Embodiments of the present invention will be described below with reference to the drawings.

FIG. 1 shows a block configuration of an effect imparting device according to a first embodiment of the present invention. The device shown in this figure includes an adder 11, a delay circuit 12, a phase shifter 13, a multiplier 14, a modulator 15, and a mixer 16.

The original sound is input to an adder 11,
Is input to the delay circuit 12. The delay circuit 12 delays the original sound by a predetermined time and outputs it. The output of the delay circuit 12 is input to the phase shifter 13. The phase shifter 13 shifts the phase of the input signal by a predetermined amount and outputs it. The output of the phase shifter 13 is multiplied by a predetermined constant in a multiplier 14,
1 is fed back.

The adder 11 adds the original sound and the result of the multiplication by the multiplier 14 and outputs the result. The mixer 16 includes the original sound and the phase shifter 1
3 is adjusted and added to the balance with the output signal, and the result of the addition (tone signal with effect added) is output.

The delay time of the delay circuit 12 and the phase shifter 13
Is modulated in accordance with the modulation signal output from the modulator 15. The delay circuit 12 may be the same as the delay circuit 92 in FIG. The phase shifter 13 is normally arranged as shown in FIG.
Of the first order all-pass filter (A
PF) may be used by cascading one to several stages. In addition, a higher-order all-pass filter or a bulk all-pass filter (bulk APF) may be used. FIG. 2 shows the bulk A used as the phase shifter 113.
It is an example of PF.

Hereinafter, it is assumed that the delay circuit 12 of FIG. 1 is the same as the delay circuit 92 of FIG. 9 and has the phase delay of FIG. The phase shifter 13 in FIG.
The following all-pass filter is provided with one stage.

FIG. 3 is a graph showing the relationship between the frequency f of the original sound and the phase delay φ caused by the delay circuit 12 and the phase shifter 13. In this figure, the horizontal axis represents the frequency f of the original sound (however, it is represented on a logarithmic (log) scale), and the vertical axis represents the phase delay φ. Assuming that the delay time of the delay circuit 12 is D, the phase delay φ of the delay circuit 12 is represented by a dotted line 31. This is the same graph as the graph 101 in FIG.

3 shows the relationship between the frequency f of the original sound and the phase delay φ of the phase shifter 13. Since the phase shifter 13 is one stage of a first-order all-pass filter,
The phase delay is 0 to π.

The reference frequency fc of the phase shifter 13 is f
It is assumed that c = (1 / D). Therefore, in the graph 32, when the frequency f of the original sound is f = (1 / D), that is, when the frequency f of the original sound is the reference frequency fc of the phase shifter 13, fc = (1
/ D), the phase delay φ = (π / 2). As the frequency f of the original sound decreases, the phase delay φ approaches zero. As the frequency f of the original sound increases, the phase delay φ approaches π.

The solid line 33 in FIG. 3 represents the result of the delay by the delay circuit 12 and the phase shift by the phase shifter 13.
9 is a graph showing the amount of phase delay of the output from the control unit. This graph 33 is obtained by adding the dotted line graphs 31 and 32.

FIG. 4 shows a frequency characteristic obtained by mixing the output delayed by the delay circuit 12 and the phase shifter 13 and the original sound by the mixer 16. First, a dotted line graph 41 shows frequency characteristics as a result of mixing the delayed output and the original sound by the mixer 16 when only the delay circuit 12 is provided and the phase shifter 13 is not provided. This corresponds to the graph 102 in FIG.
Is the same as

A solid line graph 42 in FIG. 4 is a graph showing a frequency characteristic of a result obtained by mixing the output delayed by the delay circuit 12 and the phase shifter 13 and the original sound by the mixer 16 in the apparatus of FIG. . As described above, in FIG. 3, the graph 33 of the phase shift delay is obtained by adding the graph 31 (phase delay by the delay circuit) and the graph 32 (phase delay by the phase shifter). Accordingly, the graph 42 of FIG.
The graph 41 for only 2 is shifted to a lower frequency side. This shift is caused by the phase shift in the phase shifter 13.

As a result, in the graph 42, the positions of the peaks are shifted from the harmonic harmonic train. Further, the peaks and notches are shifted to the lower frequency side. This notch is
When the reference frequency fc of the phase shifter 13 is lowered, the frequency shifts to a lower frequency side. In particular, the frequency of the first notch (leftmost) is such that the phase shift amount of the phase shifter 13 is 0 to π.
It can be located in the range from (1 / 2D) to 0. Since this band often contains a fundamental frequency component of a musical tone, modulation of the notch position in this band has a very large effect on tone color change. Further, in a high frequency range, the peak is (1 / D) · n to (1 / D) · (2n−
1) Deviate.

Normally, the modulation of the delay circuit 12 and the phase shifter 13
Is preferably used in combination with the above modulation. For example, when the delay time of the delay circuit 12 is increased and the reference frequency of the phase shifter 13 is modulated in a lowering direction, an effect of smoothly changing in a direction in which the entire delay amount increases can be provided.

The phase shifter 13 may not be modulated and may be fixed. Even so, there is an effect of shifting the notch to the lower frequency side, so that the change in tone color is affected. Further, when the phase shifter 13 is modulated in the opposite direction to the delay circuit 12 (in a direction in which the reference frequency of the phase shifter 13 is increased when the delay time by the delay circuit 12 becomes longer), the effect of the phase shifter 13 is reduced. It will be modulated in the direction, but it is useful as a special effect.

Next, a second embodiment of the present invention will be described.

FIG. 5 shows a block diagram of an effect applying apparatus according to a second embodiment of the present invention. The device shown in this figure includes an adder 51, a delay circuit 52, a phase shifter 53, a multiplier 54, a modulator 55, a mixer 56, and a phase inverter (inverter) 57. Each part of numbers 51 to 56 is shown in FIG.
And the description is omitted. It is assumed that the phase shifter 53 also includes a single-stage primary all-pass filter similar to the phase shifter 13 of FIG.

The difference between the device of FIG. 5 and the device of FIG. 1 is that the output of the phase shifter 53 is inverted by an inverter 57. The inverter 57 inverts the phase of the input signal,
Thereby, it can be seen that the phase of the input signal is delayed by π, and conversely, it can be seen that the phase of the input signal has been advanced by π. In the following, a description will be given assuming that the phase is delayed by π by the inverter 57. As explained in FIG.
The phase delay caused by the phase shifter 53 (one-stage first-order all-pass filter) is in the range of 0 to π. When this phase shifter 53 and the inverter 57 are combined, the phase delay is in the range of π to 2π.

FIG. 6 shows the frequency f of the original sound, the delay circuit 52, the phase shifter 53, and the inverter 57 in the second embodiment.
6 is a graph showing a relationship with a phase delay φ due to the following. The meaning of the vertical and horizontal axes is the same as in FIG. The dotted line 61 in FIG.
FIG. 3 is a graph showing the phase delay φ caused by the delay circuit 52.
And the graph 31 of FIG. 10A and the graph 101 of FIG. A graph indicated by a dotted line 62 shows a phase delay φ caused by the phase shifter 53 and the inverter 57. As described above, the phase delay is in the range of π to 2π. The graph 62 is obtained by shifting the graph 32 of FIG. 3 downward by π.

It should be noted that, similarly to the first embodiment, the phase shifter 13
Is fc = (1 / D).

The solid line graph 63 in FIG.
2 is a graph showing a phase delay caused by a phase shifter 53 and an inverter 57. The graph 63 is obtained by adding the dotted line graphs 61 and 62.

FIG. 7 shows an output processed by the delay circuit 52, the phase shifter 53 and the inverter 57 and the original sound.
6 shows frequency characteristics as a result of mixing. First, the dotted line graph 71 shows the frequency characteristics as a result of mixing the delayed output and the original sound when only the delay circuit 52 is provided and the phase shifter 53 and the inverter 57 are not provided. This is shown in FIG.
10 and the graph 102 of FIG. 10B.

A graph 72 shown in FIG. 7 is a graph showing a frequency characteristic as a result of mixing the output processed by the delay circuit 52, the phase shifter 53, and the inverter 57 with the original sound in the mixer 56 in the apparatus of FIG. It is. As described above, in FIG. 6, the graph 63 indicating the phase shift delay is obtained by adding the graph 61 (phase delay by the delay circuit) and the graph 62 (phase delay by the phase shifter and the inverter). Accordingly, the graph 72 in FIG. 7 is obtained by shifting the graph 71 in the case of only the delay circuit 52 to a lower frequency side.

For example, a graph 71 in FIG.
The notch 73 of the (only) is shifted to the notch 74 of the graph 72. In the high frequency band, the peaks and notches are almost 2π shifted, and as a result, it can be seen that there is almost no shift. Therefore, in a high frequency band, the same effect as the conventional flanger can be obtained.

As described above, it can be seen that the phase is advanced by π by the inverter 57. In this case, the peak and the notch hardly shift in the high frequency band, and the peak and the notch are high in the low frequency band. It will be seen that it shifts to the frequency side. That is, it can be seen that the notch 75 in the graph 71 in FIG. 7 is shifted to the notch 74 in the graph 72.

In any case, the first notch 7
4 according to the reference frequency of the phase shifter 53.
/ 2D) to (3 / 2D). Since this band often contains a fundamental frequency component of a musical tone, modulation of the notch position in this band has a very large effect on tone color change.

Further, in a conventional analog flanger or the like, a high-pass filter having a direct current (DC) cut (having an effect of advancing a phase) is often used to provide a unique effect, as described above. Since it can be seen that the phase is advanced by the phase shifter 53 and the inverter 57, the device shown in FIG. 5 can provide a unique effect similar to that of such an analog flanger.

In the first or second embodiment,
Although a single-stage all-pass filter is used as the phase shifter, it may be a multi-stage instead of a single-stage. In this case, since the frequency characteristic pattern differs depending on the number of stages and the polarity, specific effects can be obtained. Further, an all-pass filter may be mainly used, and a delay circuit may be used as an auxiliary.

Next, a third embodiment of the present invention will be described.

The third embodiment clarifies a more specific structure based on the first and second embodiments. FIG. 8 shows a block configuration of an effect applying apparatus according to the third embodiment.

The effect imparting device of FIG. 8 uses a low-frequency oscillator (L
FO) 801, low-pass filter (LPF) 802, multipliers 803 and 804, exponential converter 805, adder 80
6, multiplier 807, adder 808, nonlinear table 80
9, delay circuit 810, LPF 811, APF 812, high-pass filter (HPF) 813, multipliers 814, 81
5,816, and an adder 817.

The LFO 801 sequentially generates the amplitude value of each sample point of the waveform as indicated by reference numeral 821. LFO8
01 is input to the LPF 802. LPF802
Is for smoothing the peak of the LFO waveform as indicated by reference numeral 821.

The output of LPF 802 is input to multiplier 803. The multiplier 803 adds the depth DE to the output of the LPF 802.
Multiply PTH. The result of the multiplication is exponentially converted by exponential converter 805, and as a result, MOD is output to delay circuit 810.

The exponential function unit 805 has a table as shown by reference numeral 823, and based on this table, an output on the vertical axis with respect to an input on the horizontal axis is formed and output. As a result, an output as indicated by reference numeral 824 is obtained.

On the other hand, the output of the LPF 802 is
Enter 4 as well. The multiplier 804 multiplies the output of the LPF 802 by a predetermined value CON for amplitude adjustment. The multiplication result is input to the adder 806. The adder 806 adds the offset OF to the output of the multiplier 804, and shifts by the offset. Multiplier 804 and adder 806
Thus, the output of the adder 806 is in the range of 0 to 1. The output of the adder 806 is input to the APF 812.

The original sound is multiplied by a predetermined constant in a multiplier 807 and input to an adder 808. The output of the adder 808 is input to the non-linear table 809. The non-linear table 809 is a table having characteristics as indicated by reference numeral 822. Based on the characteristics, an output on the vertical axis with respect to an input on the horizontal axis is formed and output.

As described later, the output of the HPF 813 is fed back to the input side via the multiplier 814.
Due to this feedback, the output of the adder 808 may cause bit overflow and the sound may be distorted. In order to suppress such bit overflow, the output level is suppressed when the input level is high by the non-linear table 809.

The output of the non-linear table 809 is input to the delay circuit 810. The delay circuit 810 delays the original sound by a predetermined time and outputs it. The delay amount is calculated by the exponential converter 80
5 is modulated according to the output MOD. Output MOD
Changes smoothly when the value of MOD is large, and changes sharply when the value of MOD is small, as indicated by reference numeral 824. As a result, the frequency characteristic of the delay circuit 810 becomes
When the MOD value is small and the frequency characteristic shifts to the right, the frequency characteristic changes rapidly (shift), and when the MOD value is large and the frequency characteristic shifts to the left, the frequency characteristic changes slowly. It will change linearly upward. The output of the delay circuit 810 is input to the LPF 811. The LPF 811 is provided for tone processing such as suppressing a sudden tone change due to a notch or the like of the delay circuit 810.

The output of the LPF 811 is input to the APF 812. The APF 812 functions as a phase shifter, and shifts the phase of an input signal by a predetermined amount and outputs the shifted signal. APF81
The phase amount of 2 is modulated based on the output of the adder 806. If the output of the adder 806, which is a signal for modulation, changes significantly, the output of the adder 806 is logarithmically converted and the result is used as a signal for modulation by the APF.
812 may be input.

The output of the APF 812 is input to the HPF 813. The HPF 813 is provided for tone processing such as cutting a DC component and cutting a metallic sound. H
The output of the PF 813 is multiplied by the feedback coefficient FB in the multiplier 814 and fed back to the adder 808. The adder 808 adds the original sound and the multiplication result of the multiplier 814 and outputs the result.

The output of the HPF 813 is multiplied by a predetermined constant WET in a multiplier 815 and input to an adder 817.
The original sound is multiplied by a predetermined constant DRY in a multiplier 816 and input to an adder 817. The output of the multiplier 815 is so-called wet, and the output of the multiplier 816 is so-called dry. Multipliers 815 and 816 are provided to adjust the balance between wet and dry. The adder 817 outputs the output of the multiplier 815 and the multiplier 8
16 and outputs the result of the addition (tone signal to which the effect is added).

The frequency of the LFO 801 of the embodiment described above,
Various coefficients such as DEPTH and CON are arbitrarily set by the user using an operator (not shown), but may be set in advance.

It should be noted that the apparatus of each of the embodiments described above uses a DSP
(Digital signal processor).

[0072]

As described above, according to the present invention, the following effects can be obtained by combining delay time modulation and phase shift amount modulation.

Since the peak frequency can be shifted from the harmonic overtone sequence in the frequency characteristic, a sound having a specific note name is not emphasized, and a uniform effect can be obtained.

In the conventional flanger, when the delay time of the delay circuit is short, the modulation feeling may hardly be obtained in a low frequency band. However, according to the present invention, the phase shift is performed together with the delay. A modulation feeling can be obtained.

Although the conventional phasor cannot obtain a strong effect in a high frequency band, according to the present invention, a delay is performed together with the phase shift. The effect can be obtained.

Various effects can be imparted to the musical sound by changing the manner of modulating the delay time of the delay circuit and the reference frequency of the phase shifter, or by changing the combination of the respective modulations.

[Brief description of the drawings]

FIG. 1 is a block configuration diagram of an effect imparting device according to a first embodiment of the present invention.

FIG. 2 is a block diagram showing an example of a bulk APF used as a phase shifter;

FIG. 3 is a diagram showing a relationship between the frequency of an original sound and a phase delay caused by a delay circuit and a phase shifter;

FIG. 4 is a diagram showing a frequency characteristic as a result of mixing an output delayed by a delay circuit and a phase shifter with an original sound;

FIG. 5 is a block diagram of an effect applying apparatus according to a second embodiment of the present invention.

FIG. 6 is a diagram illustrating a relationship between a frequency of an original sound and a phase delay by a delay circuit and a phase shifter in the second embodiment.

FIG. 7 is a diagram showing a frequency characteristic as a result of mixing the inverter output and the original sound in the second embodiment.

FIG. 8 is a block diagram of an effect applying apparatus according to a third embodiment of the present invention.

FIG. 9 is a block diagram showing a configuration example of a conventional flanger.

FIG. 10 is a diagram showing a phase delay due to a delay of a delay circuit in a conventional flanger and a frequency characteristic as a result of mixing an output from the delay circuit with an original sound;

FIG. 11 is a block diagram showing a configuration example of a conventional phaser.

FIG. 12 is a block diagram illustrating an example of a first-order all-pass filter used as a phase shifter;

FIG. 13 is a diagram showing a phase delay by a phase shifter in a conventional phaser and a frequency characteristic as a result of mixing an output from the phase shifter with an original sound;

[Explanation of symbols]

11 adder, 12 delay circuit, 13 phase shifter, 14
Multiplier, 15 modulator, 16 mixer, 51 adder,
52: delay circuit, 53: phase shifter, 54: multiplier, 55 ...
Modulator, 56: Mixer, 57: Phase inverter (inverter), 801: Low frequency oscillator (LFO), 802: Low pass filter (LPF), 803, 804: Multiplier, 8
05: exponential converter, 806: adder, 807: multiplier
808: adder, 809: non-linear table, 810: delay circuit, 811: LPF, 812: APF, 813: high-pass filter (HPF), 814, 815, 816 ...
Multiplier, 817: Adder.

──────────────────────────────────────────────────続 き Continuation of the front page (56) References JP-A-3-43799 (JP, A) JP-A-4-96000 (JP, A) JP-A-1-321486 (JP, A) JP-A-62-1987 187392 (JP, A) (58) Fields studied (Int. Cl. ⁷ , DB name) G10H 1/043

Claims (1)

(57) [Claims] 1. A loop circuit having delay means for delaying a tone signal input from tone signal generation means for generating a tone signal at a pitch based on performance information, the signal being uncorrelated with the pitch. A tone effect comprising: a phase shifter disposed in the loop circuit for shifting a phase of a signal circulating in the loop circuit; and a controller for modulating and controlling a phase shift amount of the phase shifter. Applicator.