JP2986905B2 - Control device for charging generator - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION [Industrial Application Field] The present invention relates to a charging generator control device built in a vehicle-mounted charging generator.

[Conventional technology]

As described in Japanese Patent Application Laid-Open No. Sho 62-171419, the conventional device has a fail-safe mechanism that detects the impedance of an external control device to detect disconnection and disconnection of a signal line, and switches to auxiliary voltage detection when an abnormality occurs. Was.

[Problems to be solved by the invention]

In the above conventional technique, the detection can be performed by detecting the impedance of the external control signal line. No consideration is given to failures other than disconnection or disconnection of the signal line, so short-circuiting of the signal line to the ground plane or power supply line,
In the event of a failure such as an abnormality in the duty control signal (fixed to 'H' or 'L' level) due to a malfunction of the external control device, the control of the charging generator is not performed normally, resulting in poor power generation or excessive voltage generation. There was a problem that a trouble could occur. Here, the potential fluctuation of the ground plane will be supplemented. In a system using a vehicle body as a ground plane in a vehicle or the like, the potential of the ground plane fluctuates due to a circuit current flowing through the ground plane. In particular, as shown in FIG.
In a charging generator in which the ground terminal is coupled to the ground surface by bolting the bracket and the engine, the potential of the bracket (ground terminal) fluctuates due to the circuit current output by the generator itself. . Therefore, when the output current is controlled by the external control signal,
If the earth connection resistance of the charging generator is increased due to loosening of the bolts, etc., a positive or negative loop is applied, and the output control of the charging generator may become unstable, diverging or attenuating. There is.

An object of the present invention is to prevent a malfunction of a charging generator due to the above-described problem of input of an external control signal.

[Means for solving the problem]

In order to achieve the above-mentioned object, when the external control signal is a signal having no predetermined time change, a means for preventing the field current from being controlled according to the external control signal is provided.

[Action]

The means for preventing the control according to the external control signal operates so as to detect the failure of the external control signal by a change with time. The malfunction of the external control due to the failure of the signal line due to the fluctuation can be prevented.

〔Example〕

Hereinafter, an embodiment of the present invention will be described with reference to FIG. FIG. 1 is a system connection diagram showing the internal connection and the input / output connection of the charging generator 1. The charging generator 1 in FIG. 1 is driven by an engine via a belt, and supplies power to the battery 2 and other electric loads (not shown). Reference numeral 5 denotes an external control device of the charging generator 1, which is incorporated in a control device of an engine or the like.
Reference numeral 4 denotes an ignition key switch. Charging generator 1
Inside, armature winding 11, three-phase full-wave rectifier 12, field winding
13, when there is no predetermined external control signal input to the external control signal input terminal (C terminal), a field current flowing through the field winding 13 by the field current control device 14. The current is controlled according to the voltage (voltage of battery 2) input to the IG terminal, and output terminals B (positive side) and E (negative side)
Outputs a DC power of a predetermined voltage. Now, the field current control device 14 will be described in more detail. The field current control device 14 includes a flywheel diode 141, an output switch (here, an IGBT) 142, transfer gates 143, 144,
It comprises a voltage control circuit 145, a power supply circuit 150, and an external control signal determination circuit 146 which is a feature of the present invention. Next, the operation of the field current control device 14 will be described. First, when the ignition key switch 4 is closed, the power supply circuit 150 is turned off.
Operates, and the internal power supply of the field current control device 14 is activated.
Thereby, each circuit and element inside the voltage adjustment circuit 14 can be operated. (Note that the power supply circuit 150 is configured by a Zener diode, a resistor, a transistor, and the like, and is a circuit that receives a voltage of the IG terminal as an input and outputs a voltage (for example, 8 V) that is controlled to be constant. When a signal having a predetermined frequency is not input to the external control signal input terminal (C terminal), the output line 148 of the external control signal determination circuit 146 goes to “H” level and the transfer gate 1
43 turns on and 144 turns off. Accordingly, the output switch 142 for turning on / off the field current turns on / off according to the output (147) of the voltage control circuit 145. The voltage control circuit 145 includes a comparator 145e, resistors 145a, b, c, and a Zener diode 145d as shown in FIG. With the above-described configuration, the voltage control circuit 145 compares the value obtained by dividing the voltage of the IG terminal with the resistors 145a and 145b with the voltage value obtained by the Zener diode 145d by the comparator 145e. If it is larger, set the output 147 to 'L' level,
If the value is smaller than the predetermined value, an “H” level is output. For example, if the voltage dividing ratio of the resistors 145a and 145b is 1/2 and the Zener voltage of the Zener diode 145d is 7.2V, the voltage of the IG terminal becomes
When the voltage is larger than 14.4V, the output 147 becomes "L" level, and when smaller than 14.4V, it becomes "H" level. That is, the output switch 142
Turns on when the output line 147 is at the 'H' level and increases the field current, and conversely, turns off when the output line 147 is at the 'L' level and reduces the field current. It will be controlled to a constant value of 14.4V.

Next, an operation when a control signal of a predetermined frequency is externally input to the C terminal will be described. When a signal having a predetermined frequency is input to the C terminal, an external control signal determination circuit
The output 148 of 146 becomes “L” level, the transfer gate 143 turns off, and 144 turns on. Therefore, the output switch
142 turns on / off according to the input signal of the C terminal. That is, when an external control signal having a predetermined frequency is input to the C terminal, the field current control device 14 stops the function of controlling the output voltage (here, the IG terminal voltage) of the charging generator 1 to be constant. To turn on / off the field current in response to the external control signal.
Functions as a switch to turn off. Next, two examples of the configuration of the internal circuit of the external control signal determination circuit 146 will be described with reference to FIGS. FIG. 3 shows an external control signal determination circuit 146.
Shows the internal connection. Reference numeral 146a denotes a frequency / voltage converter (F / V converter), which includes, for example, a one-shot multivibrator and a smoothing circuit, and outputs a voltage corresponding to the frequency of the input signal. 146d is a comparator, 146b is a resistor, and 146c is a Zener diode. 151 is connected to the output of the power supply circuit 150. With such a configuration,
The external control signal determination circuit 146 sets the output 148 to an “L” level when the frequency of the C terminal signal is higher than a predetermined value, and to an “H” level when the frequency is lower than the predetermined value. For example, when the output voltage of the F / V converter is set to 3 V when the frequency of the C terminal (input) signal is 100 Hz, and when the zener voltage of the zener diode 146c is set to 3 V, the output 148 is set.
Becomes "L" level when the frequency of the C terminal signal is higher than 100 Hz, and becomes "H" level when the frequency is lower than 100 Hz. Next, another example of the internal circuit of the external control signal determination circuit 146 will be described.
This will be described with reference to the drawings. FIG. 4 shows an external control signal determination circuit 146.
146a is an F / V converter similar to 146a in FIG. 3, 146e, 146h, 146i are resistors, 146f is a Zener diode, 146j and 146k are comparators, and 1
46l is an OR gate. In the external control signal determination circuit 146 shown in FIG. 4, the output voltage of the F / V converter 146a is compared by two comparators (146j, 146k) and a window comparator using an OR gate 146l. , Its output line
148 is the frequency of the C terminal signal within a certain range (for example, 1
00Hz to 200Hz), it becomes 'L' level and out of the specified range (100
(Less than 200 Hz or less).

In the present embodiment, the field current control device 14 of the charging generator 1
By providing an external control signal determination circuit 146, only an external control signal (C terminal signal) having a predetermined frequency is determined as a normal signal, and in that case, the field current is controlled according to the external control signal. However, in the other signals, the field current is controlled by the voltage control circuit 145 inside the field current control device 14 regardless of the external control signal. Disconnection, short-circuit to the power supply line or ground, etc.)
When the circuit current flowing to the ground plane changes due to turning off and the like, and the ground potential fluctuates, the power generation of the predetermined voltage is continued without any trouble such as abnormal rise of the generated voltage or stop of the power generation. be able to. In particular, the external control signal determination circuit 146 is constituted by a circuit as shown in FIG.
When the upper and lower limits of the effective range of the external control signal are set, malfunctions due to noise having relatively high frequency components, such as ripples in the generated voltage, can also be avoided. In the present embodiment, the determination of the external control signal is performed based on the height of the frequency. However, it is possible to adopt a method of detecting and determining the period of the signal. In this case, the F / V converter 146a shown in FIGS. 3 and 4 may be changed to a period-voltage converter.

Next, another embodiment of the present invention will be described with reference to FIGS. FIG. 5 shows the field current control device 14 shown in FIG.
FIG. 13 is a connection diagram illustrating another example of an internal circuit. The field current control device 14 shown in FIG. 5 connects the terminals B, F, IG, C and E shown in FIG.
By connecting to the terminal of the same symbol in the figure, the field current control device 14 in FIG. 1 can be replaced. In FIG. 5, 141 is the first
A flywheel diode 142a similar to that shown in FIG.
This is a power switch that works the same as the 142. (Here, bipolar transistor), 149a is an AND gate, 149k,
149l is an OR gate, 149l is a comparator, 149c and 149d are analog switches, 149s, 149u and 149q are inverter gates,
149m, 149n, 149o, 149p are D type flip flops (DF
F), 149f is a Zener diode, 149r is a capacitor, 1
49v is a constant current source, and 149i, 149j, 149e, 149g, 149h, 14
9s is the resistance. The power supply lines of the comparator 149b, the analog switches 149c and 149d, the respective gates, and the DFF are connected to the IG terminal on the positive side and to the E terminal on the negative side (not shown).

The field current control device of FIG. 5 comprising the above components
The operation of 14 will be described below. The field current control device 14 controls the field current by turning on or off the output switch 142a. The output switch 142a is driven by the output of the AND gate 149a. The output of the AND gate 149a is determined by the output of the comparator 149b and the output of the OR gate 149k. The output of the comparator 149b is determined according to the voltage of the IG terminal and a reference voltage for voltage control as described later, and the output of one OR gate 149k is determined according to the input of the C terminal. In other words, a comparator that performs voltage control
The power switch 142a is driven by the logical product of the output of 149b and the output of the OR gate 149k whose output value is determined according to the external control signal input to the C terminal. The inverting input of this comparator 149b is connected to the voltage of the IG terminal by resistors 149i and 149j.
When the duty signal is not input to the C terminal of the non-inverting input, the output of the OR gate 149l becomes the "H" level as described later.
When the analog switch 149d is turned on, 149c is turned off and a value obtained by dividing the Zener voltage of the Zener diode 149f by the resistors 149g and 149h is input, and when the duty signal is input to the C terminal, the OR gate 149l is turned on. Since the output becomes the “L” level, the analog switch 149c is turned on and the analog switch 149d is turned off, and the zener voltage of the zener diode 149f is input. Here, the duty signal means a signal which periodically repeats the 'H' / 'L' level.
Therefore, for example, the voltage dividing ratio of the resistors 149i and 149j is 1/2,
Assuming that the voltage dividing ratio R149h / (R149h + R149g) between j and 149h is 7/8 and the Zener voltage of the Zener diode 149f is 8V, the non-inverting input voltage of the comparator 149b is 7V when no duty signal is input to the C terminal. When the IG terminal voltage is higher than 14V, the comparator 149
When the output of h is 'L' level, when it is smaller than 14V, it becomes 'H' level. Further, under the same conditions, when the duty signal is input to the C terminal, the output of the comparator 149h becomes the “L” level when the IG terminal is higher than 16V, and becomes the “H” level when the output is lower than 16V. That is, when the duty signal is not input to the C terminal, the comparator 149b connects the IG terminal to the 14th terminal.
The output level is changed so as to keep V constant, and when a duty signal is input to the C terminal, the IG terminal is
The output level is changed so as to be constant at 16 V, that is, the voltage reference value input to the non-inverting input is switched by the C terminal signal, and the voltage control signal is output. On the other hand, the output level of the OR gate 149k is determined in accordance with the C terminal input signal. However, when the duty signal is not input to the C terminal, the OR gate 149l becomes the “H” level as described later. , The OR gate 149k goes to the “H” level, and when the duty signal is input to the C terminal, the OR gate 149k
Becomes the “L” level, and the OR gate 149k outputs the C terminal input signal as it is. Next, the C terminal input signal that determines the output of the OR gate 149l and the operation of each unit (the circuit surrounded by the dashed line in FIG. 5) according to the input signal will be described. The time change of the C terminal input signal is detected by DFFs (149m, 149n, 149o, 149p), and a common clock pulse is supplied to all the clock pulse inputs (CP) of the DFFs.
The clock pulse is generated by an oscillation circuit including inverter gates 149t and 149u, a resistor 149s, and a capacitor 149r. In this configuration, when the C terminal is kept at the “H” level, the output of the inverter gate 149q is at the “L” level, so that the output Q of the DFF 149n first becomes “H” when the clock pulse goes to the “H” level. When the clock pulse goes low, the output Q of DFF 149m goes high, and at the same time, the OR gate 149l goes high. Where DFF149
n, 149p is DFF149m, 14 when clock pulse is 'H' level
Reference numeral 9o denotes a flip-flop in which the output Q changes when the clock pulse is at the "L" level. Also, when the C terminal is kept at the 'L' level, the output of the inverter gate 149q is at the 'H' level, so that the output Q of the DFFs 149p and 149o changes to the 'H' level in response to the clock pulse, When the output Q goes high, the output of the OR gate 149l goes high. When the C terminal is open, the constant current source
Since the C terminal is maintained at the “L” level by 149v, the output of the OR gate 149l becomes the “H” level as in the case where the C terminal is kept at the “L” level. Next, when a duty signal having a cycle shorter than a half cycle of the clock pulse is input to the C terminal, when the C terminal is at the “H” level, DFF149o, 14
9p reset input (R) becomes 'H' level, and both DF
The output Q of F is reset to "L" level, and when the output Q is at "L" level, the reset input (R) of the DFFs 149m and 149n becomes "H" level because the inverter gate 149q is at "H" level. Since the outputs of both DFFs are reset to the "L" level, the C terminal is at the "H" level or the DFFs 149n and 149m do not transmit the "H" level to the input of the OR gate 149l. 'L' level status is ORed by DFF149P, 149o
Since it is not transmitted to the other input of the gate 149l as the “H” level, the output of the OR gate 149l is maintained at the “L” level. The field current control device 14 shown in FIG.
Operates as described above, so that the output characteristics of the charging generator 1 shown in FIG. 1 are as shown in FIG. FIG. 6 is a characteristic diagram showing the load characteristics of the charging generator 1, with the horizontal axis representing the output current of the charging generator 1 and the vertical axis representing the output voltage.
In FIG. 6, a represents the case where the duty signal is not input to the terminal C of FIG. 5, that is, the case where the control of the field current is performed by the voltage control circuit alone in the field current control device 14 of FIG. 4 shows load characteristics. Note that when no duty signal is input to the C terminal, the voltage reference value is set to 14V. In FIG. 6, b and c show the load characteristics when the utility signal is input to the C terminal. The characteristic b shows that the duty of the C terminal signal is almost 100% (for example, 99%).
(Duty = “H” level time / one cycle of the duty signal), and the characteristic c represents the characteristic when the duty is 50%. When a duty signal is input to the C terminal, the reference value of the voltage control is set to 16V. As shown by the characteristics b and c, when the duty signal is input to the C terminal, the control voltage reference value becomes 16
It is switched to V, and the maximum output current is further limited according to the duty (for example, the maximum output current at an output voltage of 14 V is about 80 A when the duty is close to 100% and about 40 A when the duty is 50%) ing. When the load characteristics of the charging generator 1 are represented by a, b, and c, for example, when a load having the characteristic shown by d in FIG. , Point t (output voltage = 14
V), the characteristic b determines the output voltage and the output current at the point s (output voltage = 16 V), and the characteristic c determines the output voltage and the output current at the point u (output voltage = 12.7 V). When the field signal is externally controlled by inputting the duty signal to the C terminal in this manner, the output voltage of the charging generator 1 becomes zero (for example, when duty = 1%).
It is possible to change continuously from to 16V.

In this embodiment, since the continuation state of the input value of the input signal of the external control signal input terminal (C terminal) of the field current control device 14 is detected and the reference voltage of the voltage control circuit is switched,
Even if a failure such as a short circuit or a disconnection of the signal line to the power supply line or the ground occurs, the output voltage of the charging generator 1 can be stably controlled without being affected by the failure of the external control signal line.

Next, another embodiment of the present invention will be described with reference to FIGS. 7 and 8. FIG. FIG. 7 shows an internal circuit of the field current control device 14, and FIG. 8 shows the field current control device 14 shown in FIG.
5 shows the operation waveform of the internal circuit of FIG. The field current controller 14 shown in FIG. 7 operates in place of the field current controller 14 shown in FIG. In FIG. 7, 141 is a flywheel diode, 142a is an output switch, 14a is an AND gate, 14b is a comparator, 14g is an inverter gate, 14d is a Zener diode, 14c, 14e, and 1f are resistors, and 14h is a resistor 14h1.
And a high-pass filter consisting of a capacitor 14h2.
The field current control device 14 including the above components outputs an output signal such that the voltage of the IG terminal is adjusted to a predetermined value by the voltage control circuit when the duty signal is not input to the external control signal input terminal (C terminal). The switch 142a is turned on / off to control the field current, and when a duty signal of a predetermined frequency or higher (frequency sufficiently higher than the cut-off frequency of the high-pass filter) is input to the C terminal, the output switch 142a
Is turned on / off by a logical product of a voltage control circuit and a value corresponding to an external control signal. In FIG. 7, the voltage control circuit includes a comparator 14b, resistors 14e, 14f, 14c, and a Zener diode 14d. Figure 8 shows the comparator 1
4b, a timing chart showing the operation of the C terminal input signal, the input and output of the inverter gate 14g, and the operation of the AND gate 14a. As shown in FIG. 8, in this embodiment, when the C terminal input signal is a duty signal and is at the “H” level,
The output of the AND gate 14a is set to the "L" level (the output switch is turned off). When the output is at the "L" level, the output of the AND gate 14a is not affected. If the C terminal input signal is not a duty signal having a predetermined frequency, the C terminal input signal does not affect the output of the AND gate 14a even if it is at the “H” level (time t _{1 in} FIG. 8). Or later). In other words, when the C terminal input signal is a duty signal of a predetermined frequency or higher and the ratio of the "H" level increases, the field current of the charging generator decreases, and the output voltage decreases. On the other hand, when the C terminal input signal is fixed at the “H” or “L” level or when the terminal is in the open state, the field current is controlled so that the IG terminal voltage becomes a predetermined value. As described above, the field current control device 14 shown in FIG. 7 operates, so that even if a failure occurs in the C terminal signal line (such as a short circuit to the power supply line or the ground plane), the output voltage of the charging generator remains at a predetermined level. Controlled by value. In the present embodiment, unlike the above-described two embodiments, the detection and determination of the time change of the external control signal is not performed, and the means for removing the duty signal of a predetermined frequency or less is used to control the field control device 14 due to the failure of the signal line. Since the malfunction is prevented, the circuit provided for preventing the malfunction can be simplified. However, in this embodiment, the control method of the field current and the control variables cannot be switched by the external control signal. Therefore, the external control signal can only control the field current depending on the voltage control.
Incidentally, in the field current control device 14 shown in FIG. 7, the output switch 142a is obtained by the logical product of the voltage control output (the output of the comparator 14b) and the output corresponding to the C terminal input (the output of the inverter gate 14g). However, if the output switch 142a is driven by a logical sum, the magnitude of the field current can be made larger than the value adjusted by the voltage control output. Output voltage of the machine
It can be raised by inputting a duty signal to the terminal. Further, in the embodiment of FIG. 7, the low-pass filter 14h is used as the input circuit for the C terminal signal, but a band-pass filter may be used. When a bandpass filter is used, noise removal for high frequency component noise can be performed. Also,
In all the embodiments, the voltage control is on / off control using a comparator. However, a method of performing PWM control of a variable frequency in which a constant frequency is within a predetermined range may be adopted. In this case, the cycle of the external control signal and the cycle of the PWM control are separated from each other, so that malfunction due to noise due to switching of the field electromagnetic current can be reduced.

 The external signals include the following.

Power generation cut control when air conditioner is loaded Power generation cut control when accelerating Power generation cut control when starting Fuel cut control when fuel cut cover Charging control when decelerating Constant power generation cut control A compressor is connected to the engine, and the load on the engine increases accordingly. Therefore, the field current flowing through the field winding is temporarily controlled to a predetermined low current state to reduce the amount of power generation and reduce the generator load on the engine.

In this case, when the vehicle is accelerated, the load on the engine increases accordingly. Therefore, the power generation amount is temporarily reduced in the same manner as in the above case, and the generator load on the engine is reduced.

In the case of, when the generator is started when the engine is started, the generator may become a load on the engine and the engine may not start smoothly. To effectively apply the driving force of the starter to the engine so that the engine can be started smoothly.

In this case, when the injector that supplies fuel to the engine shifts from the fuel cut state to the resumption of fuel supply according to the operation information of the engine, at this time, the engine needs a lot of torque for traveling. Therefore, it is necessary to temporarily set the generator serving as a load for reducing the torque to a low load state.

At this time as well, the object is achieved by reducing the field winding current.

In this case, when the engine is decelerated, it is preferable that the load on the engine is increased so that the deceleration can be achieved early, and the inertial rotational energy of the engine during the deceleration is recovered and effectively used. For this reason, the field winding current of the generator is set to a predetermined large current state, the generator load on the engine is increased, and extra energy of the engine is obtained by rapidly charging the battery with the generated output. to recover.

In this case, when the vehicle is in a steady running state and the battery is sufficiently charged, it is no longer necessary to operate the generator.In this case, too, the field current is controlled by the predetermined low current state to control the engine load. And reduce the amount of fuel supply.

In this case, when the engine speed drops to a predetermined low speed, it is necessary to reduce the load on the engine so as not to cause engine stall. Therefore, the current flowing through the field winding of the generator is set to a predetermined low current state, and the generator load on the engine is temporarily reduced.

The above control can be performed independently of each other, or the control condition can be determined by combining two or more conditions.

In this case, the external control signal can be given as a pulse signal having a predetermined frequency.
The duty ratio is set between 100% and 0%, depending on the operating conditions, and the combination thereof, and the duty ratio can be arbitrarily changed to control the transfer gate.

It should be noted that there is a problem that it is difficult to determine whether the state signal has not changed for a predetermined period or an abnormality has occurred in the signal line because the duty signal continues to be in the 100% duty state or the 0% duty state. Conceivable.

Therefore, the maximum value of this duty signal is set to, for example, 99
If the% duty and the minimum value are set to, for example, 1% duty, the above-mentioned problem can be solved since the state change of the pulse signal always occurs at least during one cycle of the duty signal.

In this embodiment, the amplitude of the duty signal is set to about 2 V with respect to the ground potential.However, if the ground potential rises due to loosening of the volts as described above, the amplitude of the duty signal becomes apparently small. , Below the threshold level for detecting the duty signal. In this case, even though the state of the duty signal has changed within a predetermined period, the point cannot be detected. Therefore, it is determined that the state does not change within the predetermined period. Thus, even if the state is changing at the predetermined duty,
In the case of such an abnormality, it can be determined that the abnormality is accurate.

Next, an example in which the present invention is applied to an intelligent IC regulator will be described with reference to the drawings.

As shown in Fig. 10, various loads such as a battery as a DC current and a DC load using the battery as a power source or an AC load using the AC output of the generator as a direct power source are connected to the generator for the vehicle. Have been. Naturally, the battery itself is one of the loads of the generator 1.

The generator 1 is driven by the engine of the automobile and outputs a three-phase alternating current. This alternating current is rectified by the rectifier 12 and supplied to the battery. A plurality of DC load groups are connected to the battery via a switch group. The loads include a car air conditioner, a lighting device, an audio device, a fuel control electromagnetic device, and a diff logger.

In some cases, a load that uses the AC output of the generator as a direct power source is connected. For example, there is a quick clear glass system for rapidly melting ice on a window.

The generator 1 has a field winding 13, and the output voltage (current) of the generator is sufficient to maintain the voltage of the battery 6 at a predetermined value by controlling the current flowing through the field winding. The generator is controlled so that is obtained.

 2a is a flywheel diode.

 Hereinafter, the control of the field winding current will be described.

The voltage of the battery is detected by the voltage detection circuit 130. The signal _VBd corresponding to the detection voltage is the battery setting voltage (14.
6 is compared with ± 0.25V) V _BC, and outputs a voltage deviation signal epsilon ₂ amplifies the deviation in the deviation amplifier 120.

Voltage - current command value conversion circuit 110 in accordance with the voltage deviation signal epsilon _2, and outputs a current command value I _f1 corresponding to the field current (target field current) needed to maintain a set voltage of the battery voltage.

Switching circuit 170, the current command value I _f2 from the initial excitation circuit 140 to be described later, the load current command value from the response control circuit I _f3, target current command value I _f4 current command value of the throat from the temperature detection circuit 160 current Select whether to output as command value _If0 and switch.

Deviation amplifier circuit 100 compares the actual current value signal I _ff from the field current detection circuit 90 to be described later target current command value I _f0 amplifies the deviation, a current deviation signal as a final current command value epsilon ₁ Is output.

The current supply circuit 70 is, for example, a PWM (Pulse Width Modulatio).
n) a control circuit and a chopper-driven eg FET driven by this output
(Field effect transistor), and the current deviation signal ε
_The field winding current iCH is chopper-controlled by the duty corresponding to ₁ .

The current detection circuit 90 detects the current flowing therethrough from the terminal voltage of the current detection resistor 8 connected in series with the field winding circuit, and outputs a constant current signal _Iff according to the detected current.

There are two types of field current sources, a DC current rectified by the rectifier 3 and a DC current from the battery, and are self-excited by the output current of the rectifier 12 during normal operation.

When the number of revolutions NG of the generator is low, such as when the engine is started, a sufficient generated current cannot be obtained, and at this time, the current is supplied from the battery.

Initial excitation circuit 140, when such a speed is the predetermined value N _GO such operating conditions as the driving torque of lower than the generator load on the engine of the engine, must minimize as field current shown in FIG. 4 the current of the current command value I _fm to a value having a function of excisional the I _fL.

The load response circuit 150 detects the load application by a sudden change in the battery voltage. When the engine speed is low, such as the idle speed, the load response circuit 150 changes the current command value to 2 to 3 as shown in FIG. A ramp-shaped current command value _If3 that is gradually increased to the target current command value _Ifa over a second is output.

Temperature detection circuit 160 detects the temperature of the semiconductor switching-devices for Chiyotsupa, when the temperature has decreased to a high temperature above a predetermined value T _a is reduced according to the temperature of the current command value I _fm as shown in FIG. 14 Command value _If4 to be output.

The basic concept of power generation control will be described based on the embodiment described above.

In other words, the field winding current command value generation means A signal I corresponding to the voltage deviation epsilon ₂ of Batsuteri voltage and a predetermined set voltage
The field current command value epsilon ₁ occurs on the basis of the signal I _ff from _f0 and the field current signal generation means B, field winding from a field winding current supply means C based on the current command value epsilon ₁ A predetermined current is supplied to the line.

Which is configured this way, when the load connected to the Batsuteri is Batsuteri voltage is turned drops, it commensurate connexion current command value epsilon ₁ is increased, the field winding current iCH
Increase. As a result, the output voltage (current) of the generator increases and the battery is charged to a predetermined voltage.

In this state, if the temperature of the field winding rises and the resistance value increases due to the influence of the temperature, the field current stops flowing and the current decreases carelessly.

However, when the current decreases, the current command value increases and the supply amount automatically increases. Therefore, the output of the generator does not change even if the resistance value of the field winding increases, and the load (battery) does not change. Output) can be maintained.

Hereinafter, a specific circuit diagram shown in FIG. 15 will be described. The same reference numerals indicate corresponding parts throughout the drawings. 71 is a chopping circuit comprising switching elements such as power transistors and FETs for controlling the current flowing through the field winding 13; 170 is a constant voltage power supply for supplying the power supply voltage V _CC to each of the above control circuits; 180 is a DC load is there. Other configurations are first
It is the same as FIG. In the voltage-current command value conversion circuit 110, R ₀ and R ₁ are voltage dividing resistors that divide the output power supply voltage V _CC of the constant voltage power supply circuit 170 and output a set value V _BC of the battery charging pressure. R _2, R ₃ is fed back to Batsuteri voltage V _B at the input dividing resistor. A ₁ is an operational amplifier having an input resistor R ₄ to R ₆ and fed back resistor R _7, constitute a deviation amplifier. In the current control circuit 100, A ₂ is an operational amplifier having an input resistor R _8, R _9, R ₁₀ and fed back resistors R _11, 11
Command value from the current command I _f1 or auxiliary circuits from the voltage control circuit of 0 I _f2, I _f3, command values selected one of I _f4 I _f0
And a field amplifier for calculating a deviation between the current and the field current detection circuit _Iff . In the PWM control circuit 70, A ₃ is an operational amplifier, constitutes an integrator with the input resistors R ₁₂ , R ₁₃ , R ₁₄ and the feedback capacitor C ₁ , performs an integration operation on the input voltage, and sets the input resistor R ₁₃ addition and subtraction of the voltage e ₀ inputted through the input signal epsilon ₁ and another input resistor R ₁₂ inputted through. Subsequent A ₄ in an operational amplifier, an input resistor output e _I of the integrator
It receives an input via the R ₁₅ to the positive terminal, and fed back to the positive terminal similarly the output e ₀ via a feedback resistor R _16,
Construct a comparator with hysteresis. Operating level of this comparator A ₄ are dividing resistor power supply voltage V _CC
The voltage is divided by R ₁₇ and R ₁₈ and applied to the negative terminal via the input resistor R ₁₉ . A combination of the integrator and the comparator of the circuit configuration as described above, operates as a self-excited oscillator which outputs a square wave when fed back output e ₀ of the comparator to the integrator input. That is, in proportion to the input voltage epsilon ₁ functions as a PWM control circuit Deyutei changes.

Then 71 is Chiyotsupa, power transistors T ₁ and driver flange Star T ₂ and flywheel diode D ₁ of the switching-element, Chiyotsupa circuit is constituted by the current detecting shunt resistor 8 of the power transistors T ₁ and the like, the field winding the current i _f that flows through the 2 to switching-controlled by the output signal e ₀ of the PWM control circuit. Other elements for the above-mentioned chopper
It is a switching element such as an FET, and any means may be used.

Between the comparator A ₄ and Chiyotsupa 71 transflector Agate 143 is provided and is further connected to the output terminal of the transformer fir gate 144 on its output side. Both transfer gates are configured so that the ON / OFF state is switched between each other by the output of the state change detecting means of the external signal including the F / V converter 146a, the resistor 146b, the Zener diode 146c, and the comparator 146d. Accordingly, when the gate 143 is open, the gate 144 is closed, and a control signal is output from the PWM to the chopper. Conversely, when the gate 144 is open, the gate 143 is closed, and the chopper is controlled by an external signal.
The operation of the state change detecting means is as described with reference to FIGS.

90 is a current detection circuit. A ₅ represents an operational amplifier, an input resistor R ₂₀ to R _22, composed of a feedback resistor R _23. Reference numeral 91 denotes an analog switch, which is an output e of 70 PWM circuits through 92 buffers.
Driven at ₀ . C ₂ is the output voltage hold capacitor.

Next, the operation of each unit in the above configuration will be described. First, the operation of the field current detection circuit 90 will be described below. FIG. 16 is a configuration diagram of the current detection circuit 90, and FIG. 17 shows operation waveforms of each unit. Current detection by the current detection circuit detects the current i _CH of the power element which is a continuation current as of FIG. 17.

That is, amplified by the operational amplifier A ₅ detects the Chiyotsupa current i _CH in shunt resistor 8 and V _CH signal.

Detection signal V _CH of Chiyotsupa is converted into a sample and hold by the circuit of analog switch 91 and the hold capacitor C ₂ simulated field current signal V _ff.

In more detail, the output of the PWM control circuit 70 in synchronism with the PWM signal e ₀ OFF the analog switch 91, Chiyotsupa current i _CH in Chiyotsupa is OFF period this by holding the current value immediately before the Chiyotsupa OFF The detection signal at this time is a _Vf5 signal. Also, while the switch is ON, the analog switch
91 ON the Chiyotsupa current i _CH intact V _ff detection signal V _CH
Signal. Incidentally, ON the analog switch 91, the OFF operation is performed through the buffer 92 by the PWM control signal e ₀ as described above.

As shown in Figure 17 by the above operation, without the waveform of the simulated field current detection voltage V _ff obtained from Chiyotsupa current i _CH continued, the operation waveforms nearly field current i _f. As a result, the static characteristics of the field current detection circuit have good linearity as shown in FIG. 18, and can detect a wide range from a small field current to a large field current. Further, since an insulated detector is not required, the current detector can be configured at low cost.

Next, the current control operation will be described. Connexion back to Figure 15, the PWM control circuit 7 is for PWM controlling the Chiyotsupa 71, amplifier A _3, the integrating capacitor C _1, an integrator composed of an integrating resistor R _12, etc., of the amplifier A ₄ the output positive feedback is caused by the resistor R ₁₆ constituted by a comparator which has hysteresis. By feeding back the output e ₀ of the comparator A ₄ to the integral input resistance R ₁₂ , the PW capable of the duty control is obtained.
It becomes an M control circuit. The PWM control circuit has a proportionally controllable function energization of the output signal e ₀ Deyutei (conduction ratio) relative to the input signal (voltage) epsilon _1.

Then, the input signal epsilon ₁ of the PWM is given from 100 deviation amplifier. That is, the difference between the field current detected signal I _ff that the signal I _f0 from the voltage control circuit in deviation amplifier 100 gain-multiplied _{(G = R 11 / R 8} = R 10 / R 9) to the PWM control circuit 7
Is output as the input signal ε ₁ .

Therefore, the current control is 100 deviation amplifiers, 70 PWM
Control circuit, 90 field current detection circuit, 71 chopper circuit,
This is performed using a circuit composed of 13 field windings and the like.

Now, a deviation signal epsilon ₁ obtained from the fed back signal I _ff of the field current command I _f0 is given if the deviation amplifier 100 in the current occurs, giving the PWM signal circuit 70. PWM control circuit
The PWM signal e ₀ of the output at 70 is operated Chiyotsupa 71 field current i _f performs the fed back controlled so as to match the command value.

Therefore, the field current can be arbitrarily set by changing the current command value _If0 as shown in FIG.

The PWM circuit shown in the figure is configured as a variable frequency PWM circuit.

Such PWM control circuit in response to e ₀ indicating the duty ratio, where e ₀ is 50%, the frequency is maximized, e ₀ from the point is controlled so as the frequency becomes smaller small even in a large In addition, the pulsating rate of the field current can be suppressed within a certain narrow range.

Further, as shown in FIG. 20, the field electric current i _f even when is suddenly changed current command I _f0 becomes operation follows the command value.
As shown in FIG. 21, in the case of the conventional duty ratio control, the characteristic that the driving torque of the generator increases at low temperatures and decreases at high temperatures due to the temperature change of the field winding resistance. Becomes As a result, there was a problem that the capacity of the field winding of the generator and the elements of the chopper had to be designed to withstand the cold temperature, and there was a problem of oversizing.However, the current control of this embodiment is shown in FIG. As described above, even if there is a difference in the temperature of the field winding resistance, the target current can be controlled, so that the influence of the difference in the temperature does not appear. Further, there is no influence of a change in current due to a change in power supply voltage or the like. Therefore, the switching element such as the field winding of the alternator or the jumper does not need to be designed in an overspec manner, and the power can be increased. That is, if the maximum value of the operation in the normal state is increased up to the characteristics at the time of low temperature, the capacity is increased by that amount, and the output of the alternator can be increased. The up rate is several tens of percent, and the effect is great.

The operation of the voltage control circuit using the above-described current control circuit is as follows. Connexion back to Figure 15, the voltage control circuit 110 performs fed back control so that the actual Batsuteri voltage (generator output voltage) V _B matches the Batsuteri charging s pressure value V _BC. That is, outputs a deviation signal I _f0 (current command) set voltage V _BC of Batsuteri by the deviation amplifier A ₁ and Batsuteri voltage V _B, giving to the current control circuit 100. The output signal epsilon ₁ of the current control circuit 100 as described above occurs. PWM
The control circuit 70, ON in response to the output signal epsilon _1, PWM of OFF
Control is generated (pulse width control) pulse output e _0, the pulse voltage V _f intermittently to the field current 13 of the generator 1 is applied through the Chiyotsupa 71, controls the field current i _f. In the above control operation, the field current _if is detected by the shunt resistor 8 as described above, and the current control circuit 100
It is fed back to control the current. As a result, the output voltage of the armature winding of the generator 1 is controlled to charge the battery via the three-phase rectifier 12 or supply current to the load. Then, the output voltage V _B of the generator 1 is fed back to the voltage control circuit 110, the output voltage is so fed back controlled so as to match the Batsuteri set voltage V _BC.

Next, the peripheral technology of this embodiment will be described with reference to FIG.

1. Clock circuit This circuit generates a basic clock of 1 MHz and a clock signal obtained by dividing the basic clock.

CL ₁ drives the charge pump circuit with a ₁ MHz basic clock and charges a high voltage to the gate of FET 1.

CL ₂ -CL ₁₀ supplies a clock signal of the timer circuit in clock signal obtained by dividing the CL _1.

2. Rotation detection discrimination circuit This circuit detects the rotation speed of the generator and outputs a rotation speed signal for switching the circuit operation.

The number of circuits is detected by the frequency of the P terminal (one phase of the armature winding)
_P is (Where N is the number of revolutions of the generator (rpm); q is the number of poles of the generator; 2 is a constant during full-wave rectification).
_This is performed by comparing the frequency of _P with the clock pulses CL ₉ and CL ₁₀ .

The N1 output is “1” when the generator is 50 rpm or more, and is “0” when the generator is less than 50 rpm.

The N2 output is "1" when the generator is 1000 rpm or more, and is "0" when the generator is less than 1000 rpm.

The N3 output is “1” when the generator is at 2500 rpm or more, and is “0” when the generator is less than 2500 rpm.

3.Generation stop alarm circuit This circuit is used to prevent the battery from being charged and eventually stalling when the field winding and armature winding are disconnected or the FET1 is broken open. ,
When power generation is stopped (including when the engine is not running), a charge lamp is turned on to notify the user.

Its operation turns on the charge lamp when the generator is below 1000 rpm. When reaching 1000r.pm, the charge lamp is turned off. Engine speed drops again to 500r.pm
The charge lamp is turned on again when the following occurs.

Assuming that the engine idle speed is 700 rpm and the pulley ratio between the crank pulley and the generator pulley is 2, the generator speed at idle is 1400 rpm. Therefore, when the generator is normal, the charge lamp is turned off.

When power is not being generated, the number of revolutions is 0, and the charge lamp is turned on.

The important point is that there is a hysteresis between N1 and N2. This has the effect that the lamp does not blink at the time of cranking or the like and the driver does not feel uneasy (see FIGS. 28 and 29).

4. S terminal open alarm circuit The function of this circuit is S terminal (battery voltage detection terminal)
However, it prevents the generator from going out of control when it becomes open due to disconnection of wiring.

Flashes the charge lamp and alerts the driver.

Things.

In this operation, the voltage of the S terminal is normally compared with a reference voltage to perform voltage control. When the S terminal is opened, it reduces the Batsuteri voltage V _C, switches the I connexion terminal S · B terminal voltage switching circuit when the predetermined value or less (7V) to B from S.

At the same time, the charge lamp blinks. This blinking turns on and off the charge lamp at 1 second intervals (No.
See Figure 30).

5.B terminal open alarm circuit The function of this circuit is B terminal (output cable of generator)
However, it prevents the generator from going out of control when it becomes open due to disconnection of wiring.

Flashes the charge lamp to alert the driver.

On the point.

The function of this circuit is to give an alarm when voltage control becomes impossible for some reason.

Here, the case where the voltage control becomes impossible is considered when the FET1 is short-circuited and broken, and the B terminal and the F terminal are short-circuited externally (a metal piece is interposed between the terminals).

If operation is continued without voltage control, (i) the battery will be overcharged and hydrogen gas will
There is a risk of filling the room and exploding.

(Ii) Overvoltage occurs at high rotation speed, damaging on-vehicle electrical loads such as lamps and electronic devices.

However, this circuit prevents such problems from occurring.

When the operation is in the above mode, the field current command value is 0.
, And the gate voltage of the FET 1 continuously becomes 0 V. However, when the gate voltage becomes 0 V for a predetermined time (3 seconds), it is determined that the overvoltage mode is set, and the charge lamp blinks. The blinking cycle is 0.25 seconds on and 0.25 seconds off.
See Figure 2).

7. Gate circuit The function of this circuit is to blink the charge lamp when the S terminal is open, the B terminal is open, overvoltage, and when power generation is stopped, to give an alarm. The operation is performed by calculating the logical sum (OR) of the four signals and driving the gate of the FET2.

What is important here is that the blink cycle is set to an integral multiple of each event. By looking at the blinking pattern of the charge lamp, it is possible to diagnose what is wrong. Furthermore, priorities can be assigned to lamp displays in descending order of importance. For example, the frequency is lowered in the order of power generation stop, overvoltage, B terminal open, and S terminal open (see FIG. 33).

8. Overcurrent protection The role of this circuit is to prevent overcurrent from flowing into FET1 and destroy it when the field winding is short-circuited.

Its operation is e ₀ Nevertheless High, when remains low voltage of F terminal and lock the gate of FET1.

9.Initial excitation circuit The role of this circuit is that the rotation speed NG of the generator is, for example, the rotation speed.
N1 in such a low rotation (= 500 rpm) to detect a state that can not self-excitation power generation, and outputs the current command value I _f2 As the conduction ratio of Chiyotsupa is about 30%, based on it The target current command value _If0 is output from the switching circuit.

10.S / B terminal voltage switching circuit The role of this circuit is to always feed back the S terminal voltage (the voltage directly taken out from the battery terminal) through a filter circuit and to perform voltage control, and to remove the S terminal. The terminal B is supplied with a B terminal voltage (a voltage taken out from an intermediate wiring between the generator and the battery), and voltage control is continuously performed to prevent the generator from being in a non-charged state.

The operation always inputs the voltage of the B terminal and the voltage of the S terminal. When a signal from the S terminal open alarm circuit is generated, the detection terminal is switched from the S terminal to the B terminal. When a signal is generated from the B terminal open alarm circuit, the voltage signal is switched from the S terminal to the B terminal and the B terminal voltage is output to the filter circuit.

11. Filter circuit The role of this circuit is to smooth the rectified ripple voltage of the generator included in the SB terminal voltage and to stabilize the voltage feedback control.

In the operation, the ripple voltage is removed by using a low pass filter of the Miller integration type, the average voltage of the battery is output, and the battery voltage is fed back to the voltage-current command value conversion circuit. This can be detected well average of Yotsute Batsuteri voltage accuracy can be a control signal is the current command value I _f1 is not affected by the Ritsupuru.

12. Constant voltage circuit Converts the battery voltage into a constant voltage of a predetermined value, and then supplies it to each control circuit as a current.

13. Voltage-current command value conversion circuit The function of this circuit is to control the field current of the alternator I _f1 so that the battery terminal voltage becomes constant according to the battery voltage set value V _BC. Occurs.

The operation generates a current command value I _f1 to gain multiple amplifying taking a deviation between the output V _BC of the voltage command value V _BC 'and filter circuit from the setting value switching circuit.

14. Set value switching circuit role of this circuit is the internal reference value for setting the target voltage of Batsuteri, i.e., when the signal from the power generation Katsuhito control circuit setting value V _BC occurs, lower settings, power The point is to cut.

Its operation is usually voltage a voltage setting value V _BC as a voltage command value - it has been output to the current command value conversion circuit, the signal generator Katsuhito control circuit generates a voltage command value V _BC lower than normal power generation Don't do it.

15. Generating cut control circuit The function of this circuit is to reduce the driving torque of the generator (stop power generation) when the load increases, such as when the vehicle is accelerating, and to improve the acceleration.

More specifically, when the throttle opening detection switch SW1, which is inserted in series with the charge lamp, is open, for example, when the throttle is full or throttle, the power cut is performed until acceleration is completed (for example, over 10 seconds).

In this operation, the power generation cut detection uses the drain voltage of the lamp lighting FET 2 for the voltage detection terminal, so that the lamp lighting and the power generation cut detection are shared.

That is, in the power generation cut control circuit, the drain-source voltage V _DS of the FET ₂ and the current I _DS flowing through the detection resistor R _{g2 of the} FET ₂ are input. Now, SW1 is open and FET2 of V _DS
Is reduced and the current of FET2 is not flowing,
In order to cut off the power generation during the acceleration time of the vehicle (about 10 seconds), a set value switching signal is output to the set value switching circuit and a gate lock signal of the chopper is generated to the gate lock circuit.

16. Output current control circuit The function of this circuit is to control the maximum amount of power generated by the generator with a signal from an external controller and suppress the generated torque to improve vehicle acceleration, improve fuel efficiency, and prevent engine stall.

In the operation, a duty signal is input from an external controller to an output current control circuit via a terminal C, and the operation and stop of the PWM control circuit are controlled by an output signal from the control circuit.

As shown in FIG. 34, if the duty of the load signal input to the C terminal is linearly changed according to the external load (load of the vehicle), the output current of the generator is continuously reduced as shown in FIG. Voltage characteristics can be controlled.

FIG. 35 shows a typical example of a case where the duty is 100% and a case where the duty is 50%.

18. Load Response Control Circuit In this embodiment, a load response control function is provided to reduce fluctuations in the engine speed due to sudden changes in the electric load and vibrations caused thereby. 14 (a) and 14 (b) show the principle of operation.

When the load is turned on when there is no normal load response control, the control voltage (battery terminal voltage) drops, but the current command value responds stepwise by the feedback operation of the control system, and the battery is rapidly charged. At this time, since the generator acts as a load on the engine, the engine speed decreases (FIG. 23 (a)). This is a problem particularly in the vicinity of an idling operation at a low engine speed, and there is a danger that the engine may stall if the speed rapidly changes before the idle correction.

On the other hand, in the load response control, the generator is controlled so as not to easily become a load on the engine until the idle correction. Even if the control voltage drops due to the load application, if the control is performed so that the current command value slowly increases in a constant pattern, the recovery of the control voltage is delayed, but the fluctuation amount of the engine speed can be reduced ( FIG. 23 (b)). For this reason, a delay circuit having a constant time constant for changing the current command value output of the voltage control according to the rotation speed is provided in the control loop. The pattern of the current command value is shown in FIG. 24, which shows the change of the command value pattern depending on the presence or absence of the load response control.
The current command value that changes stepwise without control is
The controlled case is fixed is switched to the value of the reference value itself when the command value exceeds the reference value V ₁ given time. Then if the next command value to determine whether it exceeds the reference value V ₂ also should be switched in sequence to the next reference value, will the current command value Wayutsukuri and stepwise increased. If the current command value drops after the final reference value is fixed to the same value as when there is no control, the switching operation to the reference value is not performed, and the same value as without control is used.

Therefore, no matter what the current command value is before the load is applied, the command value is fixed only when the current value exceeds the reference value, so that overcharging and overdischarging can be prevented. Load response control shall be performed near idle speed, and alternator speed 2500
It operates at r / min or less. A circuit block for generating the actual command value pattern is shown in FIG. An analog switch is used for switching the command value, a comparator is used for comparing the reference voltage and the command value, and a digital logic circuit including a timer and a latch is used for controlling the control operation. Considering the incorporation of the IC, the number of comparison stages with the reference value is set to three so as not to increase the circuit scale.

A simulation was performed to verify the effects of the load response control described above. FIG. 26 shows a model of an external torque-engine speed characteristic in which a bypass air amount by idle control is used as a parameter. FIG. 27 shows a step response of the idle speed when an electric load (equivalent to 20 A) is applied using this model. By performing load response control, it was confirmed that the reduction of the number of rotations could be reduced from 100 r / min to 25 r / min or less.

Although the number of comparison stages is three in the present embodiment, the number of comparison stages is not particularly limited to this, and may be stepless.

Next, a control mode in the case where the control is performed by a microcomputer mounted on the vehicle will be described below.

 The principle will be described with reference to a functional block diagram shown in FIG.

The deviation of the actual value VS the set value V _BC of Batsuteri voltage is amplified by the voltage deviation amplifier output to Rimitsuta.

Rimitsuta outputs a current command value I _f0 in response to an input from the voltage deviation amplifier. The determination of the current command value I _f0 Atatsute inputs the load information or the environmental information on the size and the engine of the vehicle load current supplied to the electrical load to the microcomputer maximum time to time the optimum current command value The value _Ifmax is calculated, and the current command value _If0 is determined and output according to the voltage deviation within the range.

Next, a deviation between the current command value _If0 and the actual current value _If is detected, and the deviation is amplified by an amplifier to generate a pulse width modulation circuit (PW
M) drive signal is output.

The PWM drives the chopper of the field winding drive circuit with a duty according to the drive signal, and controls the field winding current _If .
As a result, the battery is appropriately charged by the output generated in the armature winding of the generator.

Next, the relationship with the control of the engine will be described with reference to the block circuit diagram shown in FIG. 37 and the control flow chart shown in FIG.

After the initialization of the register is completed in step 200, the microcomputer enters the step 201 through the A / D converter.
Engine speed, manifold intake pressure, knock signal,
An input signal such as a throttle opening signal and a battery load current is detected and input to a random access memory RAM.

The load current may be detected by detecting the load application state by turning the switch ON or OFF and capturing the load current via an input register.

In step 202, the control signal of the ignition system, the control signal of the fuel system, and the control signal of the exhaust system are calculated and output according to the calculation flow stored in the read only memory ROM based on the input signal.

The next step 203 is a step for detecting the magnitude of the engine load based on the intake pressure. When it is determined that the intake pressure is lower than a predetermined pressure Pa (negative pressure), the field current is reduced so that the generator does not become the engine load torque. The maximum value _Ifmax of the command value is set to 0 so that it becomes zero.

If it is determined that the intake pressure is higher than the predetermined value Pa, it is determined that the engine is operating under normal load, and the process proceeds to the next step.

In step 204, it is detected whether or not the throttle opening is fully opened, and when it is determined that the throttle is fully opened, it is determined that the throttle is in an acceleration state,
Also at this time, the maximum value _If0 of the current command value is set to 0 so that the generator does not become a load on the engine.

If the throttle is not fully open, it is determined that the vehicle is running normally, and the process proceeds to the next step.

Determines whether Hebinotsuku state from Notsuku signal in step 205, to avoid the generator to set the maximum value I _f0 of the current command value to zero load of the engine if it is determined that Hebinotsuku state.

 If not in the heavy knock state, proceed to the next step.

Step 206 determines whether Raitonotsuku state in the Notsuku signal, the generator to the engine by suppressing the maximum value generation capacity Set I _f0 to 2A of the current command value if it is determined that Raitonotsuku state rather low Reduce load torque.

If it is not a light knock, it is determined that there is no knock, and the process proceeds to the next step.

In step 207, it is determined whether or not the engine rotation speed is 1500 rpm or less.If it is determined that the rotation speed is not more than 1, the fluctuation amount of the electric load is calculated based on the load current or the number of load switch ONs, etc. Calculates and outputs the current command value _Ifmax .

If speed is 1500r.pm above, it sets the maximum value I _fmax of the current command value to the maximum allowable current value of 4.5A, and controls so that the maximum output is obtained.

The maximum value I _fmax of the current command value thus determined is D
It is input to the limiter of the generator control circuit of FIG. 36 via the -A converter.

It is also possible to output the maximum value DI _fmax of the field current command value as a duty signal from the output register of the microcomputer. In this case, the generator control circuit
The control can be performed by inputting the PWM output e ₀ and DI _fmax to the field winding driving circuit via an AND gate.

According to the present embodiment described above: 1. Since the field current is cut-controlled in accordance with the intake pressure of the engine, when a sudden load acts on the engine such as when climbing a hill, the generator is activated. Since the load on the engine can be prevented, engine stall and the like can be prevented.

Further, since the power generation cut control is performed even when the slot is fully opened, the output of the engine can be sufficiently used for acceleration during acceleration, and the acceleration performance can be improved.

In addition, since the power generation state of the generator is controlled according to the engine knock state, the drive torque for the generator is reduced when the ignition timing is delayed and the engine output is reduced, such as when knock occurs. Since this can be reduced, it is possible to prevent the engine stall due to the output reduction and the problem that the knock state is redundant.

Further, when the engine speed is low, optimal field current control can be performed according to the load current, that is, the state of the electric load, so that engine stall due to a drop in the engine speed at a low engine speed can be prevented.

According to the present embodiment, by controlling the field current of the charging generator for an automobile, it is possible to prevent the field current from fluctuating due to the cold temperature difference of the field winding resistance. Therefore, conventionally, the alternator (charging generator) was designed with a margin in view of the current fluctuation due to the cooling / heating difference. However, since there is no need to anticipate the fluctuation, the power up of the output is not possible when the alternator is the same size. I can do it. Alternatively, if the output is the same, the physique can be reduced in size. Further, it is possible to reduce the capacity of the semiconductor element of the field current control chopper. In addition, when the load suddenly changes, it is possible to prevent a sudden change in the load on the engine of the vehicle by controlling the rising operation of the field current by an external signal. That is, it is possible to continuously and arbitrarily vary the field current value from the minimum value to the maximum value in accordance with an external signal. Therefore, for example, reduction or stop of the power generation of the alternator from the engine control can be easily realized by an external request.

Furthermore, when the amount of power generation at the time of low-speed rotation of the alternator is small, the field current is minimized. In a so-called initial excitation state, it is possible to reduce the discharge amount of the battery and to suppress the field loss.

Further, if the current detection method of this embodiment is used, a continuous field current can be equivalently detected from the intermittent current flowing through the chopper element without directly detecting the field current. No need for an insulated current detector or the like.
Further, there is an effect that the field current can be continuously detected from the minimum value to the maximum value.

According to the present embodiment as described above, the command value of the current to be supplied to the field winding is obtained from the signal corresponding to the deviation voltage signal and the signal corresponding to the actual current flowing through the field winding, Since the current is supplied to the field winding based on this command value, the internal fluctuation of the field current is controlled while controlling the output of the generator to a wide range and the optimum output according to the load demand. It was possible to control the output optimally for the generator with large load fluctuation.

Further, in the invention relating to the detection of the field current, the necessity of using a current transformer is eliminated, so that it is possible to obtain a generator control device and a method which are inexpensive and suitable for IC.

Further, in the invention of the load response control, a control device and a control method which have a small torque fluctuation of the generator and do not adversely affect the rotation of the prime mover can be obtained by organically combining with the current feedback control.

〔The invention's effect〕

According to the present invention, the output of the charging generator does not become abnormal due to a failure occurring in the external control signal line of the charging generator. This has the effect of preventing the occurrence of malfunctions and improving the safety of the vehicle.

[Brief description of the drawings]

1 is a system connection diagram of an embodiment of the present invention, FIGS. 2 to 5 are circuit diagrams, FIG. 6 is an output characteristic diagram of the charging generator 1, FIG. 7 is a circuit diagram, and FIG. FIG. 9 is a timing chart showing the operation of the circuit shown in FIG. 7, FIG. 9 is a structural view showing the mounting of the charging generator 1, and FIG. 10 is a control of a vehicle charging generator using an intelligent IC regulator according to the present invention. FIG. 11 is a main block diagram showing an embodiment applied to the apparatus, FIG. 11 is a control block diagram of the entire system of the control device for the vehicle charging generator, and FIGS. 12 to 14 are examples of control operation of the present embodiment. FIG. 15 is a detailed circuit diagram of one embodiment shown in FIG. 1, FIG. 16 is a detailed diagram of a current detection circuit of this embodiment, FIG.
17 to 20 are operation and characteristic diagrams of each part of the present embodiment, and FIG.
FIG. 21 and FIG. 22 are characteristic diagrams for explaining the effect of this embodiment, and FIG.
(A) and (b) are principle diagrams for explaining the operation principle of the load response control circuit of the present embodiment, FIG. 24 is an explanatory diagram of the control operation, FIG. 25 is a specific circuit diagram of the circuit, FIG. 26 is a drawing showing the relationship between the alternator drive torque and the engine speed when the bypass air amount is used as a parameter, FIG. 27 is a drawing for explaining the effect of the load response control circuit, FIG. 28 and FIG. FIG. 29 is a drawing showing the relationship between the number of revolutions of the generator and the lighting state of the charge lamp, and FIG.
A diagram showing a terminal switching state and a blinking state of a charge lamp,
FIG. 31 is a drawing showing a terminal switching state, a gate lock state, a charging lamp blinking state with respect to the B terminal voltage, FIG. 32 is a drawing showing a charging lamp blinking state with respect to the gate voltage, and FIG. 33 is lighting and blinking of the charge lamp in each abnormal state. FIG. 34 is a diagram showing a signal input to the C input terminal as an external signal, FIG. 35 is a diagram showing a capacity control state of the generator, and FIG. 36 is a vehicle power generation using a micro computer. FIG. 37 is a block diagram of the control circuit of the apparatus, and FIG. 38 is a control flow chart of the control circuit. 1 ... Charging generator, 2 ... Battery, 13 ... Field coil, 40 ... Current command value generation circuit, 70 ... Current supply circuit (PWM control circuit), 90 ... Current detection circuit, A ... Field winding current command value generation means, B ... Field current signal generation means,
C: field winding current supply means, 146: external control signal determination circuit (state change detection circuit), 143, 144 ... transfer gate.

Continued on the front page (72) Inventor Katsuji Marumoto 4026 Kuji-cho, Hitachi City, Ibaraki Prefecture Inside Hitachi, Ltd.Hitachi Research Laboratories Co., Ltd. (72) Inventor Masakatsu Fujishita 2520 Oaza Takaba, Katsuta City, Ibaraki Prefecture Inside Sawa Plant, Hitachi, Ltd. (56) References JP-A-62-107642 (JP, A) JP-A-55-37881 (JP) , A) JP-A-60-144117 (JP, A) JP-A-57-192739 (JP, U) (58) Fields investigated (Int. Cl. ⁶ , DB name) H02J 7/14-7/24 H02P 9/00-9/48

Claims (15)

(57) [Claims] An output voltage of the charging generator is built in the charging generator, and a second output voltage of the charging generator depends on a first set value set in advance or a control signal supplied from outside the charging generator. In the control apparatus for a charging generator having means for controlling a current supplied to a field winding so as to approach a set value, a control signal supplied from outside the charging generator is set for a predetermined time. Wherein the field current is controlled based on the second set value when at least one change has occurred during the period. 2. An output of said charging generator according to claim 1, wherein said means for detecting a time change of a control signal supplied from outside of said charging generator and a detection value of said means for detecting said time change. A control device for a charging generator, comprising: means for switching a response speed of the field current according to a voltage. 3. A semiconductor power switch element for controlling a field current of the generator in a charging generator, a driving circuit for driving the power switching element, and the field winding according to a voltage of the charging generator. A charging voltage control circuit for controlling a current, and controlling the field winding current separately from a voltage of the charging generator according to an external signal based on an external factor such as an operation state of a prime mover that drives the generator. An auxiliary circuit, wherein the external signal is formed at least once within a predetermined period by a signal whose frequency or voltage state changes, and whether or not this external signal change occurs within a predetermined period. A fail safe means is provided for preventing the external signal from being transmitted to the semiconductor power switch element when the state change does not occur within a predetermined period. Electric machine control device. 4. The control device according to claim 3, wherein said fail-safe means is provided between said external signal input terminal and said semiconductor power switch element. 5. The semiconductor power switch element according to claim 3, wherein the control is performed by the fail-safe means so that the external signal is not transmitted to the semiconductor power switch element. A control device for a charging generator, comprising: 6. The generator control device according to claim 3, wherein said fail-safe means operates when the external signal does not change in a "High" level state. 7. A control device according to claim 3, wherein said fail-safe means operates when an external signal does not change in a "Low" level state. 8. A semiconductor power switch element for controlling a field current of the generator in a charging generator, a driving circuit for driving the power switching element, and the field winding according to a voltage of the charging generator. A charging voltage control circuit for controlling a current, and controlling the field winding current separately from a voltage of the charging generator according to an external signal based on an external factor such as an operation state of a prime mover that drives the generator. An auxiliary circuit, wherein the drive circuit is grounded to the body of the prime mover via a bracket of the generator, and when the potential of the ground becomes a predetermined value or more, the semiconductor by the auxiliary circuit A generator control device provided with fail-safe means for stopping control of a power switch element. 9. A charging generator which is driven by an engine of a vehicle and charges a battery of the vehicle with its output, and a power generator which controls a field current of the generator by a semiconductor power switch element to control a charging voltage of the battery. A quantity control circuit, signal generation means for detecting that an air conditioner mounted on the vehicle has been operated, and generating a pulse signal that continues at a predetermined cycle, and the field winding according to the pulse signal. An auxiliary power generation amount control means for controlling a current to be in a predetermined low current state, wherein the auxiliary power generation amount is detected by detecting that an operation signal of the air conditioner has not changed for a predetermined time. A control device for a generator, comprising a fail-safe means for invalidating control by the control means. 10. A power generator which is driven by an engine of a vehicle and charges a battery of the vehicle with its output, and a power generator which controls a field current of the generator by a semiconductor power switch element to control a charging voltage of the battery. A quantity control circuit, signal generation means for detecting that the vehicle has stopped supplying fuel to the fuel injection valve and then starting to supply fuel again, and generating a pulse signal that continues at a predetermined cycle, And a supplementary power generation amount control means for controlling the field winding current to be in a predetermined low current state by detecting that an output signal of the signal generation means has not changed for a predetermined time. And a fail-safe for invalidating the control by the auxiliary power generation amount control means. 11. A charging generator which is driven by an engine of a vehicle and charges a battery of the vehicle with its output, and a power generator which controls a field current of the generator by a semiconductor power switch element to control a charging voltage of the battery. A quantity control circuit, a signal generating means for generating a pulse signal that continues at a predetermined cycle during a time when the engine is in a starting state, and a method for setting the field winding current to a predetermined low current state according to the pulse signal. And a fail-safe means for detecting that the output signal of the signal generating means has not changed for a predetermined time and invalidating the control by the auxiliary power generation control means. A control device for a generator. 12. A power generator which is driven by an engine of a vehicle and charges a battery of the vehicle with its output, and a power generator which controls a field current of the generator by a semiconductor power switch element to control a charging voltage of the battery. A quantity control circuit, signal generation means for detecting that the vehicle is in an accelerating state and generating a pulse signal that continues at a predetermined cycle, and wherein the field winding current is set to a predetermined low current in accordance with the pulse signal. In a charging device comprising auxiliary power generation amount control means for controlling to be in a state, it is detected that an output signal of the signal generation means has not changed for a predetermined time, and the control by the auxiliary power generation amount control means is invalidated. A control device for a generator, wherein a fail-safe means is provided. 13. A charging generator which is driven by an engine of a vehicle and charges a battery of the vehicle with its output, and a power generator which controls a field current of the generator by a semiconductor power switch element to control a charging voltage of the battery. A quantity control circuit, signal generation means for detecting that the vehicle is in a decelerating state and generating a pulse signal that continues at a predetermined cycle, and wherein the field winding current is set to a predetermined high current in response to the pulse signal. In a charging device comprising auxiliary power generation amount control means for controlling to be in a state, an output signal of the signal generation means is detected to be in a non-change state for a predetermined time, and control by the auxiliary power generation amount control means is invalidated. A control device for a generator, wherein a fail-safe means is provided. 14. A charging generator which is driven by an engine of a vehicle and charges a battery of the vehicle with its output, and a power generator which controls a field current of the generator by a semiconductor power switch element to control a charging voltage of the battery. A quantity control circuit, signal generation means for detecting that the engine speed of the vehicle has become a predetermined low speed, and generating a pulse signal that continues at a predetermined cycle, and the field according to the pulse signal. In a charging apparatus comprising auxiliary power generation amount control means for controlling a magnetic winding current to be in a predetermined low current state, the auxiliary apparatus detects that an output signal of the signal generation means has not changed for a predetermined time, and A generator control device provided with fail-safe means for invalidating control by a power generation amount control means. 15. A charging generator driven by an engine of a vehicle and charging a battery of the vehicle with the output thereof, and a power generator controlling a field current of the generator by a semiconductor power switch element to control a charging voltage of the battery. A quantity control circuit, signal generation means for detecting that the vehicle has become in a steady state operation and charging of the battery is no longer necessary, and generating a pulse signal that continues at a predetermined cycle. A charging device comprising auxiliary power generation amount control means for controlling a winding current to be in a predetermined low current state, wherein the auxiliary power generation amount is detected by detecting that an output signal of the signal generation means has not changed for a predetermined time. A control device for a generator, comprising a fail-safe means for invalidating control by the control means.