JP2943512B2 - Adaptive receiver - Google Patents
Adaptive receiverInfo
- Publication number
- JP2943512B2 JP2943512B2 JP4204634A JP20463492A JP2943512B2 JP 2943512 B2 JP2943512 B2 JP 2943512B2 JP 4204634 A JP4204634 A JP 4204634A JP 20463492 A JP20463492 A JP 20463492A JP 2943512 B2 JP2943512 B2 JP 2943512B2
- Authority
- JP
- Japan
- Prior art keywords
- matched filter
- received signal
- output
- tap
- dfe
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Fee Related
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- Filters That Use Time-Delay Elements (AREA)
- Cable Transmission Systems, Equalization Of Radio And Reduction Of Echo (AREA)
Description
【発明の詳細な説明】DETAILED DESCRIPTION OF THE INVENTION
【０００１】[0001]
【産業上の利用分野】本発明は適応受信機に関し、特
に、マルチパスフェージング伝搬で生じた波形歪の除去
に適する適応受信機に関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an adaptive receiver, and more particularly, to an adaptive receiver suitable for removing waveform distortion caused by multipath fading propagation.
【０００２】[0002]
【従来の技術】図３の構成図を参照してマルチパスフェ
ージング回線で生じる波形歪を除去する従来のこの種の
適応受信機について説明する。この適応受信機は、入力
端子（ＩＮ）１１０から受信信号を受けるトランスバー
スルフィルタ型の整合フィルタ（ＭＦ）１０１と、出力
端子（ＯＵＴ）１２０に出力判定信号Ａｎを生じる判定
帰還型等化器（ＤＦＥ）１０２と、ｎ個の相関器１０３
とを含む。ＭＦ１０１は、タップ付き遅延素子を構成す
るｎ段のシフトレジスタ１０１ａと、ｎ個の乗算器１０
１ｂと、加算器１０１ｃとを含む。相関器１０３はＤＦ
Ｅ１０２の出力判定信号Ａｎとシフトレジスタ１０１ａ
の各タップ上の受信信号との相関を取ることにより、整
合フィルタ１０１のｎ個のタップ係数Ｗ（Ｗ０〜Ｗｎ−
１）を求める。これらのタップ係数Ｗは伝送系のインパ
ルス応答の時間反転で複素共役となっている。すなわち
シフトレジスタ１０１ａ上の受信信号は、乗算器１０１
ｂと加算器１０１ｃにより、上記ｎ個のタップ係数Ｗと
畳み込まれて整合フィルタリングが行われる。この整合
フィルタ１０２の出力がＤＦＥ１０２に通され、ＤＦＥ
１０２はこの出力について判定帰還等化を行い、受信信
号の符号間干渉除去が行われる。2. Description of the Related Art A conventional adaptive receiver of this type for removing a waveform distortion occurring in a multipath fading channel will be described with reference to a block diagram of FIG. This adaptive receiver includes a transversal filter type matched filter (MF) 101 that receives a received signal from an input terminal (IN) 110, and a decision feedback equalizer that produces an output decision signal An at an output terminal (OUT) 120. (DFE) 102 and n correlators 103
And The MF 101 includes an n-stage shift register 101 a constituting a delay element with a tap, and n multipliers 10
1b and an adder 101c. Correlator 103 is DF
E102 output determination signal An and shift register 101a
Of the taps of the matched filter 101 (W0-Wn−
Find 1). These tap coefficients W are complex conjugate by time inversion of the impulse response of the transmission system. That is, the received signal on the shift register 101a is
b and the adder 101c convolve with the n tap coefficients W to perform matched filtering. The output of the matched filter 102 is passed through the DFE 102,
Reference numeral 102 performs decision feedback equalization on the output to remove intersymbol interference of the received signal.
【０００３】図３の適応受信機は、文献（電子通信学
会，通信方式研究会資料，ＣＳ７８−２０３，１９７９
年２月，“マルチパス伝送路における適応受信方式”）
に提案されており、厳しいマルチパスフェージング回線
となる見通し外通信にすでに実用化されている。この方
式は、インパルス応答の前縁（ｐｒｅｃｕｒｓｏｒ）が
主応答に比べ大きくなるような、非最小位相推移フェー
ジングに対するＤＦＥ１０２の特性を改善する。ＭＦ１
０１による整合フィルタリングにより非対称なインパル
ス応答は対称化されるため、前縁の一部の電力はインパ
ルス応答の後縁（ｐｏｓｔｃｕｒｓｏｒ）に変換され
る。従って、ＤＦＥ１０２の線形等化部に対する負担は
減少し、このＤＦＥ１０２の等化特性が改善される。一
方、インパルス応答の後縁が支配的となる最小位相推移
フェージングでは、整合フィルタリングにより、上記後
縁の一部を前縁に変換するため、ＤＦＥ１０２は非線形
等化に加えて線形等化も行なうことになる。すなわちＭ
Ｆ１０１を用いないＤＦＥ１０２単体では、判定帰還に
よる等化だけが行なわれるのに対し、このＭＦ１０１お
よびＤＦＥ１０２を備える適応受信機の等化特性はＤＦ
Ｅ１０２単体の等化特性より劣化することになる。従っ
て図３の適応受信機を地上多値ＱＡＭマイクロ波伝送に
適用すると、多値レベルの増加に伴い、ＭＦ１０１の整
合フィルタリングにより生じる歪を無視できなくなる。[0003] The adaptive receiver shown in FIG. 3 is described in the literature (IEICE, Communication System Study Group, CS78-203, 1979).
February, "Adaptive receiving method in multipath transmission path")
And has already been put to practical use in line-of-sight communication, which is a severe multipath fading line. This scheme improves the performance of the DFE 102 against non-minimum phase transition fading, such that the leading edge of the impulse response is larger than the main response. MF1
Since the asymmetrical impulse response is symmetrical by the matching filtering by 01, a part of the power of the leading edge is converted to the trailing edge (postcursor) of the impulse response. Therefore, the burden on the linear equalizer of the DFE 102 is reduced, and the equalization characteristics of the DFE 102 are improved. On the other hand, in the minimum phase transition fading where the trailing edge of the impulse response becomes dominant, the DFE 102 performs linear equalization in addition to non-linear equalization because a part of the trailing edge is converted to the leading edge by matched filtering. become. That is, M
The DFE 102 alone without F101 performs only equalization by decision feedback, whereas the adaptive receiver including the MF101 and DFE 102 has an equalization characteristic of DF
It will be degraded from the equalization characteristics of E102 alone. Therefore, when the adaptive receiver shown in FIG. 3 is applied to terrestrial multilevel QAM microwave transmission, the distortion caused by the matched filtering of the MF 101 cannot be ignored as the multilevel increases.
【０００４】[0004]
【発明が解決しようとする課題】上述した従来のＭＦお
よびＤＦＥを備える適応受信機では、非最小位相推移フ
ェージングに対しては、ＤＦＥの等化特性を改善してい
るが、最小位相推移フェージングに対してはＤＦＥだけ
備える場合より等化特性が劣化するという問題がある。In the adaptive receiver having the conventional MF and DFE described above, the equalization characteristic of the DFE is improved for non-minimum phase transition fading. Only DFE
There is a problem that the equalization characteristic is deteriorated as compared with the case where it is provided .
【０００５】従って本発明の目的は、ＭＦおよびＤＦＥ
を用いても最小位相推移フェージングに対する特性劣化
を解消する適応受信機を提供することにある。Accordingly, an object of the present invention is to provide an MF and a DFE.
Is to provide an adaptive receiver that eliminates the characteristic deterioration due to the minimum phase shift fading even when the adaptive receiver is used.
【０００６】[0006]
【課題を解決するための手段】本発明の適応受信機は、
トランスバーサルフィルタで構成され，伝送系を通った
受信信号のインパルス応答を対称化する整合フィルタ
と、前記整合フィルタの出力から判定帰還等化により符
号間干渉を除去して出力判定信号を生じる判定帰還型等
化器と、前記出力判定信号と前記整合フィルタの対応す
る各タップ上の前記受信信号との相関を取ってそれらの
相関値を前記整合フィルタの対応する各タップ係数とす
る複数の相関器と、前記複数の相関器の出力する各相関
値のうち，主応答を前記整合フィルタの入力段のタップ
係数とし，最少位相推移された前記受信信号に対しては
前記複数の相関値のうち，主応答のみを前記整合フィル
タの入力段のタップ係数として与える制御手段とを備え
ている。SUMMARY OF THE INVENTION An adaptive receiver according to the present invention comprises:
Composed of a transversal filter and passed through the transmission system
A matched filter that makes the impulse response of the received signal symmetric, a decision feedback equalizer that removes intersymbol interference by decision feedback equalization from the output of the matched filter to generate an output decision signal, The corresponding filter
That those I preparative correlation between the received signal on each tap
Let the correlation values be the corresponding tap coefficients of the matched filter.
A plurality of correlators, and a main response of each of the correlation values output from the plurality of correlators is a tap of an input stage of the matched filter.
For the received signal that has undergone the minimum phase shift,
Control means for giving only a main response among the plurality of correlation values as a tap coefficient of an input stage of the matched filter.
【０００７】[0007]
【作用】本発明の適応受信機は、ＭＦとＤＦＥを用いる
適応受信機を比較的ＳＮ比の高いマルチパスフェージン
グ回線に適用する場合等には、インパルス応答の前縁が
増大した非最小位相推移フェージングの信号に対しては
整合フィルタリングを施し、インパルス応答の後縁が増
大した最小位相推移フェージングの信号に対しては整合
フィルタリングを施さない制御を行うことで、最小位相
推移フェージングを受けた受信信号に対する等化特性を
改善する。According to the adaptive receiver of the present invention, when the adaptive receiver using MF and DFE is applied to a multipath fading line having a relatively high S / N ratio, the non-minimum phase transition in which the leading edge of the impulse response is increased. A received signal that has undergone minimum phase shift fading by performing matched filtering on the fading signal and performing control without performing matched filtering on the minimum phase shift fading signal having an increased trailing edge of the impulse response. To improve the equalization characteristics for
【０００８】[0008]
【実施例】次に本発明について図面を参照して説明す
る。図１は本発明の一実施例の構成図である。また、図
２はこの実施例の動作と図３の従来例の動作とを比較す
るための説明図である。DESCRIPTION OF THE PREFERRED EMBODIMENTS Next, the present invention will be described with reference to the drawings. FIG. 1 is a configuration diagram of one embodiment of the present invention. FIG. 2 is an explanatory diagram for comparing the operation of this embodiment with the operation of the conventional example of FIG.
【０００９】図１の適応受信機は、図３の従来の適応受
信機と同様に、入力端子（ＩＮ）１１０から受信信号を
受けるトランスバースルフィルタ型の整合フィルタ（Ｍ
Ｆ）１０１と、出力端子（ＯＵＴ）１２０に出力判定信
号Ａｎを生じる判定帰還型等化器（ＤＦＥ）１０２と、
ｎ個の相関器１０３とを含む。ＭＦ１０１は、タップ付
き遅延素子を構成するｎ段のシフトレジスタ１０１ａ
と、ｎ個の乗算器１０１ｂと、加算器１０１ｃとを含
む。相関器１０３はＤＦＥ１０２の出力判定信号Ａｎと
シフトレジスタ１０１ａの各タップ上の受信信号との相
関を取ることにより、整合フィルタ１０１のｎ個のタッ
プ係数Ｗ０〜Ｗｎ−１を求める。The adaptive receiver shown in FIG. 1 is a transversal filter type matched filter (M) which receives a received signal from an input terminal (IN) 110, like the conventional adaptive receiver shown in FIG.
F) 101, a decision feedback equalizer (DFE) 102 that produces an output decision signal An at an output terminal (OUT) 120,
and n correlators 103. The MF 101 is an n-stage shift register 101a constituting a delay element with a tap.
And n multipliers 101b and an adder 101c. The correlator 103 obtains n tap coefficients W0 to Wn-1 of the matched filter 101 by correlating the output determination signal An of the DFE 102 with the received signal on each tap of the shift register 101a.
【００１０】この適応受信機は、さらに、本発明の特徴
である制御回路（ＣＯＮＴ）１０４とｎ個の切替スイッ
チ１０５とを備えている。[0010] The adaptive receiver further includes a control circuit (CONT) 104 and n changeover switches 105 which are features of the present invention.
【００１１】この適応受信機においては、ＭＦ１０１内
のシフトレジスタ１０１ａのタップ間隔（遅延時間）を
シンボル間隔Ｔあるいはその半分のＴ／２に設定する。
特にこの遅延時間をＴ／２に設定すると、ＭＦ１０１は
整合フィルタリングの他にタイミング制御機能も有する
ことになる。ここで、受信信号の送信シンボル列をａn
（ｎ＝−∞，…，＋∞）、受信信号がＭＦ１０１に入力
されるまでの伝送系のインパルス応答の離散値をｈn と
すると、受信信号の離散値ｒn は（１）式で示される。In this adaptive receiver, the tap interval (delay time) of the shift register 101a in the MF 101 is set to the symbol interval T or T / 2, which is a half thereof.
Particularly, when this delay time is set to T / 2, the MF 101 has a timing control function in addition to the matched filtering. Here, the transmission symbol sequence of the received signal is represented by a n
(N = -∞, ..., + ∞), the discrete values of the impulse response of the transmission system to the reception signal is input to the MF101 and h n, discrete value r n of the received signal represented by (1) It is.
【００１２】 [0012]
【００１３】シフトレジスタ１０１ａのタップ間隔がＴ
間隔の場合、シフトレジスタ１０１ａの各段（タップＷ
０，Ｗ１，Ｗ２，…，Ｗｎ−２，Ｗｎ−１）に上記受信
信号ｒn+1 ，ｒn+2 ，ｒn-3 ，…，ｒ1 ，ｒ0 がそれぞ
れ分布する。ＤＦＥ１０２の判定出力がＡｎの時、ＭＦ
１０１ａの各タップ上の受信信号は下記のように示され
る。When the tap interval of the shift register 101a is T
In the case of an interval, each stage of the shift register 101a (tap W
0, W1, W2, ..., Wn-2, Wn-1) the received signal to r n + 1, r n + 2, r n-3, ..., r 1, r 0 is distributed respectively. When the judgment output of the DFE 102 is An, the MF
The received signal on each tap of 101a is shown as follows.
【００１４】 [0014]
【００１５】従って、相関器１０３により、ＤＦＥ１０
２の判定出力Ａｎとシフトレジスタ１０１ａの各タップ
内容との相関を取る（タップ係数Ｗを得る）ことによ
り、インパルス応答離散値ｈi を得ることができる。こ
れらタップ係数Ｗは伝送系のインパルス応答と複素共役
および時間反転の関係になっている。相関器１０３出力
Ｗ（Ｗ０〜Ｗｎ−１）はＣＯＮＴ１０４で制御される切
替スイッチ１０５に入力される。ただし、ＭＦ１０１の
入力段のタップに対応するタップ係数Ｗ０については切
替スイッチ１０５によるＯＮ／ＯＦＦは行わないものと
する。この切替スイッチ１０５がすべてＯＮの場合、相
関器１０３の出力ＷはそれぞれＭＦ１０１のタップ係数
Ｗ０，Ｗ１，Ｗ２，…，Ｗｎ−２，Ｗｎ−１として乗算
器１０１ｂに供給され、ＭＦ１０１はこれらのタップ係
数Ｗを受信信号と畳み込むことにより整合フィルタリン
グを行なう。Therefore, the DFE 10
By correlating the respective taps the contents of the second decision output An and the shift register 101a (obtaining tap coefficients W), it is possible to obtain an impulse response discrete values h i. These tap coefficients W have a relationship of complex conjugate and time reversal with the impulse response of the transmission system. The output W (W0 to Wn-1) of the correlator 103 is input to the changeover switch 105 controlled by the CONT 104. However, it is assumed that ON / OFF of the tap coefficient W0 corresponding to the tap of the input stage of the MF 101 by the changeover switch 105 is not performed. When all the changeover switches 105 are ON, the output W of the correlator 103 is supplied to the multiplier 101b as tap coefficients W0, W1, W2,..., Wn-2, Wn-1 of the MF 101, respectively. Matching filtering is performed by convolving the coefficient W with the received signal.
【００１６】ＣＯＮＴ１０４は、電源投入時等のデータ
引き込み時には、入力段のタップＷ０のみをＯＮにし，
他の全ての切替スイッチ１０５をＯＦＦとする。ＣＯＮ
Ｔ１０４は、データを引き込んだ後、切替スイッチ１０
５を全てＯＮとし、Ｗ０以外のタップＷ１，Ｗ２，…，
Ｗｎ−２，Ｗｎ−１も接続する。これによりＭＦ１０１
の主応答，すなわち最も相関の高いタップがＷ０とな
る。即ち、これら切替スイッチ１０５のＯＮ／ＯＦＦ作
業は相関値の主応答をＭＦ１０１の入力段のタップＷ０
に固定する作業である。 The CONT 104 turns ON only the tap W0 of the input stage at the time of data pull-in such as when power is turned on.
All other switches 105 are turned off. CON
T104, after pulling in the data, the changeover switch 10
5 and all turned ON, tap other than W0 W1, W2, ...,
Wn-2 and Wn-1 are also connected. Thereby, MF101
, That is, the tap having the highest correlation is W0. That is, ON / OFF operation of these changeover switches 105
The main response of the correlation value is the tap W0 of the input stage of the MF101.
It is the work of fixing to.
【００１７】図２の（ａ）を参照して、伝送系に主波＋
進み波の非最小位相推移フェージングがあると、受信信
号は主波より前方に信号が存在するので、ＭＦ１０１は
Ｗ１等のタップに対しても応答がある。すなわち、図１
の適応受信機は、（ｃ）に示す従来の適応受信機と全く
同じ動作を行い、（ａ）のインパルス応答を（ｅ）のよ
うに対称化する。すなわち、ＭＦ１０１はインパルス応
答の前縁を等価的に減少させ、ＤＦＥ１０２の前縁に対
する等化能力を改善する。このように、伝送系に非最小
位相推移フェージングがあると、図１のＭＦ１０１はイ
ンパルス応答の前縁が増大した非最小位相推移フェージ
ングの受信信号に対して整合フィルタリングを施してい
る。 Referring to FIG. 2A, the main signal +
If there is proceed wave non-minimum phase shift fading, the received signal
Since the signal has a signal ahead of the main wave, the MF 101 also responds to taps such as W1. That is, FIG.
Performs the same operation as the conventional adaptive receiver shown in (c), and makes the impulse response in (a) symmetric as shown in (e). That is, the MF 101 equivalently reduces the leading edge of the impulse response and improves the equalization capability of the DFE 102 with respect to the leading edge. Thus, non-minimum transmission system
When there is phase transition fading, the MF 101 in FIG.
Non-minimum phase transition phasing with increased leading edge of impulse response
Matching filtering is applied to the
You.
【００１８】一方、図２の（ｂ）を参照すると、伝送系
に主波＋遅れ波の最小位相推移フェージングがあると、
受信信号は主波より前方に信号が存在しないので、ＭＦ
１０１は、切替スイッチ１０５が全てＯＮになっていて
もＷ１〜Ｗｎ−１のタップに対して応答はなく、Ｗ０の
みが動作する。従って、この状態では、ＭＦ１０１は
（ｂ）に示すようなインパルス応答に対しては整合フィ
ルタリングを行わず、ＤＦＥ１０２の入力端での受信信
号に対するインパルス応答状態は（ｆ）のようになって
いる。すなわち、マルチパス歪のほとんどはインパルス
応答の後縁によるもので、これらはすべてＤＦＥ１０２
の判定帰還による等化で除去される。On the other hand, referring to FIG. 2B, if the transmission system has the minimum phase transition fading of the main wave and the delayed wave,
Since the received signal has no signal ahead of the main wave, MF
101 indicates that all the changeover switches 105 are ON
Also does not respond to taps W1 to Wn-1, and only W0 operates. Therefore, in this state, the MF 101 does not perform matched filtering on the impulse response as shown in FIG. 2B, and the impulse response state with respect to the received signal at the input terminal of the DFE 102 is as shown in FIG. That is, most of the multipath distortion is due to the trailing edge of the impulse response, and these are all
And is removed by equalization by the decision feedback.
【００１９】なお図３に示した従来の適応受信機では図
２の（ｂ）に示すインパルス応答の受信信号に対しても
図２の（ｄ）のようにインパルス応答を対称化するた
め、ＤＦＥ１０２単体の特性より劣化するが、本発明の
適応受信機では最小位相推移フェージングに対しては整
合フィルタリングを施さないためＤＦＥ１０２単体によ
る高い等化能力を生かすことができている。In the conventional adaptive receiver shown in FIG. 3, since the impulse response is made symmetrical as shown in FIG. 2D with respect to the received signal having the impulse response shown in FIG. Although the characteristics are degraded from the characteristics of a single unit, the adaptive receiver of the present invention does not perform the matching filtering for the minimum phase transition fading, so that the high equalization capability of the DFE 102 alone can be utilized.
【００２０】[0020]
【発明の効果】以上説明したように本発明のＭＦおよび
ＤＦＥを用いる適応受信機は、相関器の出力する相関値
をＯＮ／ＯＦＦするための切替スイッチを設けて相関値
の主応答をＭＦ入力段のタップに固定することにより、
非最小位相推移フェージングを受けた受信信号に対して
は、整合フィルタリングを行わせることでＤＦＥ単体の
等化特性を改善し、最小位相推移フェージングを受けた
受信信号に対しては、整合フィルタリングを行なわせな
いことにより等化特性をＤＦＥ単体より劣化させない効
果がある。As described above, the adaptive receiver using the MF and DFE of the present invention is provided with a changeover switch for turning on / off the correlation value output from the correlator and providing the correlation value.
Is fixed to the tap of the MF input stage ,
For the received signal that has undergone non-minimum phase transition fading, the equalization characteristics of the DFE alone are improved by performing matched filtering, and for the received signal that has undergone minimum phase transition fading, matched filtering is performed. Not doing so has the effect of not deteriorating the equalization characteristics as compared to DFE alone.
【図面の簡単な説明】[Brief description of the drawings]
【図１】本発明の一実施例の構成図である。FIG. 1 is a configuration diagram of an embodiment of the present invention.
【図２】この実施例の動作と従来技術による適応受信機
の動作とを比較するための説明図である。FIG. 2 is an explanatory diagram for comparing the operation of this embodiment with the operation of an adaptive receiver according to the related art.
【図３】従来の適応受信機の構成図である。FIG. 3 is a configuration diagram of a conventional adaptive receiver.
１０１ 整合フィルタ（ＭＦ） １０１ａ ｎ段のシフトレジスタ １０１ｂ ｎ個の乗算器 １０１ｃ 加算器 １０２ 判定帰還型等化器（ＤＦＥ） １０３ ｎ個の相関器 １０４ 制御回路（ＣＯＮＴ） １０５ 切替スイッチ １１０ 入力端子（ＩＮ） １２０ 出力端子（ＯＵＴ） Reference Signs List 101 matched filter (MF) 101a n-stage shift register 101b n multipliers 101c adder 102 decision feedback equalizer (DFE) 103 n correlators 104 control circuit (CONT) 105 changeover switch 110 input terminal ( IN) 120 Output terminal (OUT)
フロントページの続き (58)調査した分野(Int.Cl.6，ＤＢ名) H04B 1/76 - 3/44 H04B 3/50 - 3/60 H04B 7/005 - 7/015 Continuation of the front page (58) Field surveyed (Int.Cl. 6 , DB name) H04B 1/76-3/44 H04B 3/50-3/60 H04B 7/005-7/015
Claims (1)
伝送系を通った受信信号のインパルス応答を対称化する
整合フィルタと、前記整合フィルタの出力から判定帰還
等化により符号間干渉を除去して出力判定信号を生じる
判定帰還型等化器と、前記出力判定信号と前記整合フィ
ルタの対応する各タップ上の前記受信信号との相関を取
ってそれらの相関値を前記整合フィルタの対応する各タ
ップ係数とする複数の相関器と、前記複数の相関器の出
力する各相関値のうち，主応答を前記整合フィルタの入
力段のタップ係数とし，最少位相推移された前記受信信
号に対しては前記複数の相関値のうち，主応答のみを前
記整合フィルタの入力段のタップ係数として与える制御
手段とを備えることを特徴とする適応受信機。1. A transversal filter, comprising:
A matched filter for symmetrical impulse response of a received signal passing through a transmission system, and a decision feedback type equalizer for removing an intersymbol interference from the output of the matched filter by decision feedback equalization to generate an output decision signal preparative and vessels, the correlation between the received signal on each tap corresponding of said output decision signal and the matched filter
Of the correlation values of the matched filter.
A plurality of correlators to-up coefficients, among the correlation values output from the plurality of correlators, enter the main response of the matched filter
The received signal that has undergone the minimum phase shift is the tap coefficient of the power stage.
Control means for giving only a main response of the plurality of correlation values as a tap coefficient of an input stage of the matched filter.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP4204634A JP2943512B2 (en) | 1992-07-31 | 1992-07-31 | Adaptive receiver |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP4204634A JP2943512B2 (en) | 1992-07-31 | 1992-07-31 | Adaptive receiver |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH0653780A JPH0653780A (en) | 1994-02-25 |
| JP2943512B2 true JP2943512B2 (en) | 1999-08-30 |
Family
ID=16493728
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP4204634A Expired - Fee Related JP2943512B2 (en) | 1992-07-31 | 1992-07-31 | Adaptive receiver |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP2943512B2 (en) |
Families Citing this family (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| TW538603B (en) * | 2001-12-28 | 2003-06-21 | Realtek Semi Conductor Corp | Receiver for block code in near-minimum phase channel |
| JP5681677B2 (en) * | 2011-07-27 | 2015-03-11 | ＡｖａｎＳｔｒａｔｅ株式会社 | Glass manufacturing method |
Family Cites Families (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS58161415A (en) * | 1982-03-18 | 1983-09-26 | Ricoh Co Ltd | Automatic equalizer |
| JPS59112714A (en) * | 1982-12-20 | 1984-06-29 | Nippon Telegr & Teleph Corp <Ntt> | Automatic waveform equalizer |
| JPS60206232A (en) * | 1984-03-30 | 1985-10-17 | Hitachi Denshi Ltd | Automatic equalization system |
| JPS62166626A (en) * | 1986-01-20 | 1987-07-23 | Nippon Telegr & Teleph Corp <Ntt> | Transversal type automatic equalizer |
| JPH01188037A (en) * | 1988-01-21 | 1989-07-27 | Matsushita Electric Ind Co Ltd | Equalizer with fraction number interval |
| JPH0831820B2 (en) * | 1989-11-17 | 1996-03-27 | 日本電気株式会社 | Decision feedback equalizer |
-
1992
- 1992-07-31 JP JP4204634A patent/JP2943512B2/en not_active Expired - Fee Related
Also Published As
| Publication number | Publication date |
|---|---|
| JPH0653780A (en) | 1994-02-25 |
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