JP2022080948A - Control device for ac rotary machine - Google Patents

Abstract

To provide a control device for an AC rotary machine capable of improving the accuracy of setting the timing at which synchronous rectification is performed on variation of in rotational speed or change in behavior of winding current when alternator power generation control is executed.SOLUTION: A control device for an AC rotary machine executes alternator power generation control for determining and switching a zero-on mode, a high-on mode, and a low-on mode for each phase when power generation is caused with an induced voltage for each set, and calculates a prediction value of winding current of each phase whose phase is advanced by γ in electric angle for each set based on a detection value of winding current of three phases of a first set and a second set, and determines switching of the zero-on mode, the high-on mode, and the low-on mode based on the prediction value of the winding current of each phase.SELECTED DRAWING: Figure 3

Description

The present application relates to a control device for an AC rotary machine.

The induced voltage generated in the armature winding of the stator improves power generation efficiency by turning on the switching element in which the diode through which the current flows is connected in anti-parallel when the AC rotating machine and the inverter generate rectified power. , A technique for controlling alternator power generation to reduce heat generation of an element is known.

In the technique of Patent Document 1, a control circuit detects a zero-crossing time point in which the winding current of each phase crosses 0A, and the switching element is turned on or off based on the zero-crossing time point.

In the technique of Patent Document 2, the time during which synchronous rectification is possible is obtained from the conduction time of the diode for each cycle of AC power, and the timing for turning on and off the switching element on the high potential side and the low potential side is determined.

Japanese Unexamined Patent Publication No. 2011-135695 Japanese Unexamined Patent Publication No. 2009-284564

However, in the technique of Patent Document 1, the control circuit continuously detects the zero crossing time point when the current crosses 0A, and the switching element is turned on or off based on the zero crossing time point. Therefore, the alternator is used for each control cycle. The effect of delay due to the control cycle that occurs in the control device that controls power generation is not taken into consideration. Further, in the technique of Patent Document 1, since the influence of the delay due to the control cycle is not considered, no consideration is given except for comparing the detected value of the winding current with 0A. Further, since it is necessary to mount a control circuit, it is difficult to miniaturize the vehicle generator because the mounting area increases as the number of phases of the armature winding increases.

In the technique of Patent Document 2, if the rotation speed is constant, it is possible to perform a desired operation at the timing of turning on and off the switching element determined for each cycle of AC power. However, when the rotation speed fluctuates, the switching element turns on and the current is disturbed in the section where diode rectification should be performed, or the switching element turns off and the calorific value increases in the section where synchronous rectification can be performed. .. Further, in a generator motor having a field winding in the rotor, the field magnetic flux changes due to a change in the field current. When the field magnetic flux changes, the induced voltage changes and the amplitude of the winding current changes. Therefore, it is difficult to respond to the change in the behavior of the winding current by the determination for each cycle of the alternating current.

Therefore, in the present application, when the alternator power generation control is executed, the control of the AC rotator that can improve the setting accuracy of the timing for performing the synchronous rectification with respect to the fluctuation of the rotation speed or the change of the behavior of the winding current. The purpose is to provide the device.

The control device for the AC rotary machine according to the present application is an AC rotary machine provided with a rotor and a stator having a first set of three-phase armature windings and a second set of three-phase armature windings. It is a control device for an AC rotary machine that is controlled via
In the inverter, for each phase of each set, a switching element on the high potential side connected to the high potential side of the DC power supply and a switching element on the low potential side connected to the low potential side of the DC power supply are connected in series. A series circuit is provided in which the connection point of the series connection is connected to the armature winding of the corresponding phase, and the switching element has the function of a diode connected in antiparallel.
The phase difference in the electrical angle of the second set of three-phase armature windings with respect to the first set of three-phase armature windings is −π / 6.
The control device for the AC rotary machine is
For each set, when the AC rotator is made to generate electricity by the induced voltage generated in the three-phase armature winding, the switching element on the high potential side and the low potential side is turned off for each phase. A mode, a high-on mode in which the switching element on the high potential side is turned on and the switching element on the low potential side is turned off, and a low mode in which the switching element on the high potential side is turned off and the switching element on the low potential side is turned on. Judges the switching between on mode and the alternate power generation control to switch,
For each set, the prediction of the current of the armature winding of each phase advanced by γ in the electric angle based on the detected value of the current of the armature winding of the three phases of the first set and the second set. A value is calculated, and switching between the zero-on mode, the high-on mode, and the low-on mode is determined based on the predicted value of the current of the armature winding of each phase.

The winding current of each phase of each set when the alternator power generation control is executed includes not only the electric angle primary component but also the electric angle fifth-order component. According to the control device for the AC rotary machine according to the present application, the phase difference between the first set of three-phase armature windings and the second set of three-phase armature windings is π / 6. For each set, not only the phase of the primary component of the electric angle but also the phase of the fifth component of the electric angle was advanced by γ based on the detected values of the winding currents of the three phases of the first set and the second set. The predicted value of the winding current of each phase can be calculated. Therefore, switching between the zero-on mode, the high-on mode, and the low-on mode is determined based on the predicted value of the winding current of each phase estimated accurately, so that the mode can be appropriately switched. Therefore, it is possible to improve the setting accuracy of the timing for performing each mode with respect to the fluctuation of the rotation speed or the behavior of the winding current.

It is a schematic block diagram of the AC rotary machine and the control device of the AC rotary machine which concerns on Embodiment 1. FIG. It is a figure explaining the phase of the armature winding which concerns on Embodiment 1. FIG. It is a schematic block diagram of the control device which concerns on Embodiment 1. FIG. It is a hardware block diagram of the control device which concerns on Embodiment 1. FIG. It is a time chart explaining the behavior of the winding current of each set at the time of execution of the alternator power generation control which concerns on Embodiment 1. FIG. It is a figure explaining the current behavior of the 1st set of inverters at the time t2a of FIG. 5 which concerns on Embodiment 1. FIG. It is a time chart explaining the control timing at the time of execution of the alternator power generation control which concerns on Embodiment 1. FIG. It is a flowchart explaining the mode switching determination process which concerns on Embodiment 1. It is a schematic diagram of the AC rotary machine which was made into the generator motor for the vehicle which concerns on Embodiment 1. FIG. It is a time chart explaining the on / off control behavior of the switching element of the converter which concerns on Embodiment 1. FIG.

1. 1. Embodiment 1
The control device 11 (hereinafter, simply referred to as the control device 11) of the AC rotary machine according to the first embodiment will be described with reference to the drawings. FIG. 1 is a schematic configuration diagram of an AC rotary machine 1, an inverter, and a control device 11 according to the present embodiment.

1-1. AC rotary machine 1
The AC rotating machine 1 includes a stator 18 and a rotor 14 arranged radially inside the stator 18. A first set of three-phase armature windings and a second set of three-phase armature windings are wound around the iron core of the stator 18. A field winding 4 is wound around the iron core of the rotor 14, and an electromagnet is provided. The stator 18 has a first set of three-phase armature windings Cu1, Cv1 and Cw1 of U1 phase, V1 phase and W1 phase, and a second set of three-phase armatures of U2 phase, V2 phase and W2 phase. Windings Cu2, Cv2, and Cw2 are provided. The three-phase armature windings of each set may be star-connected or delta-connected.

In this embodiment, as shown in the schematic diagram in FIG. 2, the second set of three-phase armature windings Cu2, Cv2, with respect to the positions of the first set of three-phase armature windings Cu1, Cv1 and Cw1. The phase difference Δθ at the electric angle of the position of Cw2 is set to Δθ = −π / 6 (−30 degrees). The electric angle is the mechanical angle of the rotor 14 multiplied by the number of pole pairs of the magnet.

The rotor 14 is provided with a rotation sensor 15 that detects the rotation angle (rotation angle) of the rotor 14. The output signal of the rotation sensor 15 is input to the control device 11. As the rotation sensor 15, various sensors such as a Hall element, a resolver, or an encoder are used. The rotation sensor 15 may not be provided, and may be configured to estimate the rotation angle (pole position) based on the current information obtained by superimposing the harmonic component on the current command value described later (so-called). Sensorless method).

1-2. DC power supply 2
The DC power supply 2 outputs a DC voltage Vdc to the first set of inverters 5a, the second set of inverters 5b, and the converter 9. As the DC power supply 2, any device that outputs a DC voltage, such as a battery, a DC-DC converter, a diode rectifier, and a PWM rectifier, is used. A smoothing capacitor 3 is connected in parallel to the DC power supply 2.

1-3. The inverter 5a of the first set of inverters performs power conversion between the DC power supply 2 and the three-phase armature windings of the first set. The second set of inverters 5b performs power conversion between the DC power supply 2 and the second set of three-phase armature windings.

In the first set of inverters 5a, a switching element SP1 on the high potential side connected to the high potential side of the DC power supply 2 and a switching element SN1 on the low potential side connected to the low potential side of the DC power supply 2 are connected in series. Three connected series circuits are provided corresponding to the armature windings of each of the three phases of the first set. The connection points of the two switching elements in each series circuit are connected to the first set of corresponding phase armature windings.

Specifically, in the first set of the U1 phase series circuit, the switching element SPu1 on the high potential side of the U1 phase and the switching element SNu1 on the low potential side of the U1 phase are connected in series, and the connection point of the two switching elements. Is connected to the first set of U1 phase armature windings Cu1. In the first set of V1 phase series circuit, the switching element SPv1 on the high potential side of the V1 phase and the switching element SNv1 on the low potential side of the V1 phase are connected in series, and the connection point of the two switching elements is the first set. It is connected to the V1 phase armature winding Cv1. In the first set of W1 phase series circuit, the switching element SPw1 on the high potential side of W and the switching element SNw1 on the low potential side of the W1 phase are connected in series, and the connection point of the two switching elements is the first set of W1. It is connected to the phase armature winding Cw1.

In the second set of inverters 5b, the switching element SP2 on the high potential side connected to the high potential side of the DC power supply 2 and the switching element SN2 on the low potential side connected to the low potential side of the DC power supply 2 are connected in series. Three connected series circuits are provided corresponding to the armature windings of the second set of three phases and each phase. The connection points of the two switching elements in each series circuit are connected to a second set of corresponding phase armature windings.

Specifically, in the second set of the U2 phase series circuit, the switching element SPu2 on the high potential side of the U2 phase and the switching element SNu2 on the low potential side of the U2 phase are connected in series, and the connection point of the two switching elements. Is connected to the second set of U2 phase armature windings Cu2. In the second set of V2 phase series circuit, the switching element SPv2 on the high potential side of the V2 phase and the switching element SNv2 on the low potential side of the V2 phase are connected in series, and the connection point of the two switching elements is the second set. It is connected to the V2 phase armature winding Cv2. In the second set of W2 phase series circuit, the switching element SPw2 on the high potential side of W and the switching element SNw2 on the low potential side of the W2 phase are connected in series, and the connection point of the two switching elements is the second set of W2. It is connected to the phase armature winding Cw2.

Each switching element of each set of inverters has the function of a diode connected in antiparallel. For example, each switching element has an IGBT (Insulated Gate Bipolar Transistor) in which diodes are connected in anti-parallel connection, a bipolar transistor in which diodes are connected in anti-parallel connection, and a MOSFET (Metal Oxide Semiconductor Field Effect Transistor) having a parasitic diode connected in anti-parallel connection. ) Etc. are used. The gate terminal of each switching element is connected to the control device 11 via a gate drive circuit or the like. Therefore, each switching element is turned on or off by the switching signal output from the control device 11.

The first set of armature current sensors 8a is a current detection circuit that detects the current flowing through the armature windings Cu1, Cv1, and Cw1 of each phase of the first set. The second set of armature current sensors 8b is a current detection circuit that detects the current flowing through the armature windings Cu2, Cv2, and Cw2 of each phase of the second set. In the present embodiment, the armature current sensors 8a and 8b of each set are provided on the electric wire connecting the series circuit of the switching element of each phase and the armature winding. The output signals of the armature current sensors 8a and 8b of each phase of each set are input to the control device 11. The armature current sensor is a current sensor for Hall elements, shunt resistors, and the like. The armature current sensor may be connected in series to the series circuit of the switching element of each phase of each set.

1-4. Converter 9
The converter 9 has a switching element and performs power conversion between the DC power supply 2 and the field winding 4. In the present embodiment, in the converter 9, the switching element SP on the high potential side connected to the high potential side of the DC power supply 2 and the switching element SN on the low potential side connected to the low potential side of the DC power supply 2 are connected in series. It is an H-bridge circuit provided with two sets of connected series circuits. The connection point between the switching element SP1 on the high potential side and the switching element SN1 on the low potential side in the series circuit 28 of the first set is connected to one end of the field winding 4, and the high potential in the series circuit 29 of the second set. The connection point between the switching element SP2 on the side and the switching element SN2 on the low potential side is connected to the other end of the field winding 4.

As the switching element of the converter 9, an IGBT in which diodes are connected in antiparallel, a bipolar transistor in which diodes are connected in antiparallel, a MOSFET, and the like are used. The gate terminal of each switching element is connected to the control device 11 via a gate drive circuit or the like. Therefore, each switching element is turned on or off by the switching signal output from the control device 11.

In addition, the converter 9 is replaced with a diode, the switching element SN1 on the low potential side of the series circuit 28 of the first set is replaced with a diode, the switching element SP2 on the high potential side of the series circuit 29 of the second set is replaced with a diode, and the like. It may be configured as.

The field current sensor 6 is a current detection circuit that detects the field current if, which is the current flowing through the field winding 4. In the present embodiment, the field current sensor 6 is provided on an electric wire connecting the field winding 4 and the converter 9. The field current sensor 6 may be provided at another location where the field current if can be detected. The output signal of the field current sensor 6 is input to the control device 11. The field current sensor 6 is a current sensor such as a Hall element and a shunt resistance.

1-5. Control device 11
The control device 11 controls the AC rotary machine 1 via the inverters 5a and 5b of the first set and the second set, and the converter 9. As shown in FIG. 3, the control device 11 includes functional units such as a rotation detection unit 31, an armature current detection unit 32, an inverter control unit 33, a field current detection unit 34, and a converter control unit 35. Each function of the control device 11 is realized by the processing circuit provided in the control device 11. Specifically, as shown in FIG. 4, the control device 11 has, as a processing circuit, an arithmetic processing unit 90 (computer) such as a CPU (Central Processing Unit), a storage device 91 for exchanging data with the arithmetic processing unit 90, and the like. The arithmetic processing unit 90 includes an input circuit 92 for inputting an external signal, an output circuit 93 for outputting a signal from the arithmetic processing unit 90 to the outside, a communication circuit 94 for data communication with the external device, and the like.

The arithmetic processing device 90 is provided with an ASIC (Application Specific Integrated Circuit), an IC (Integrated Circuit), a DSP (Digital Signal Processor), an FPGA (Field Programmable Gate Array), various logic circuits, various signal processing circuits, and the like. You may. Further, the arithmetic processing apparatus 90 may be provided with a plurality of the same type or different types, and each processing may be shared and executed. As the storage device 91, a RAM (Random Access Memory) configured to be able to read and write data from the arithmetic processing device 90, a ROM (Read Only Memory) configured to be able to read data from the arithmetic processing device 90, and the like are used. It is prepared. The input circuit 92 is connected to various sensors such as a rotation sensor 15, magnetic sensors 8a and 8b for each phase of each set, and a field current sensor 6, and inputs the output signals of these sensors to the arithmetic processing device 90. It is equipped with a D converter and the like. The output circuit 93 is connected to an electric load such as a gate drive circuit that drives the switching elements of the first and second sets of inverters 5a and 5b and the converter 9 on and off, and a control signal from the arithmetic processing device 90 is connected to these electric loads. It is equipped with a drive circuit that outputs. The communication circuit 94 communicates with an external device.

Then, in each function of the control units 31 to 35 included in the control device 11, the arithmetic processing device 90 executes software (program) stored in the storage device 91 such as a ROM, and the storage device 91 and the input circuit 92. , And by cooperating with other hardware of the control device 11 such as the output circuit 93. Various setting data used by the control units 31 to 35 and the like are stored in a storage device 91 such as a ROM as a part of software (program). Hereinafter, each function of the control device 11 will be described in detail.

The rotation detection unit 31 detects the rotor magnetic pole position θ (rotor rotation angle θ) and the rotation angular velocity ω at the electric angle. In the present embodiment, the rotation detection unit 31 detects the magnetic pole position θ (rotation angle θ) and the rotation angular velocity ω at the electric angle based on the output signal of the rotation sensor 15. The magnetic pole position is set in the direction of the north pole of the electromagnet provided in the rotor. In the present embodiment, the magnetic pole position θ (rotation angle θ) is the position (angle) of the magnetic pole (N pole) at the electric angle with respect to the armature winding of the U1 phase of the first set. From the phase difference π / 6 between the first set of armature windings and the second set of armature windings shown in FIG. 2, the electric angle is based on the second set of U2 phase armature windings. The position (angle) of the magnetic pole (N pole) of is θ−π / 6.

The rotation detection unit 31 is configured to estimate the rotation angle (pole position) based on the current information obtained by superimposing the harmonic component on the current command value without using the rotation sensor. It is also good (so-called sensorless method).

The armature current detection unit 32 detects the winding currents iu1s, iv1s, and iw1s flowing through the armature windings of the first set of three phases based on the output signal of the armature current sensor 8a of the first set. Here, iu1s is the detected value of the winding current iu1 of the U1 phase of the first set, iv1s is the detected value of the winding current iv1 of the V1 phase of the first set, and iw1s is the detected value of the winding current iv1 of the first set. It is a detected value of the winding current iw1 of the W1 phase. Further, the armature current detection unit 32 detects the winding currents iu2s, iv2s, and iw2s flowing through the armature windings of the second set of three phases based on the output signal of the second set of armature current sensors 8b. .. Here, iu2s is the detected value of the winding current iu2 of the U2 phase of the second set, iv2s is the detected value of the winding current iv2 of the V2 phase of the second set, and iw2s is the detected value of the winding current iv2 of the second set. It is a detected value of the winding current iw2 of the W2 phase. For each set, the armature current sensor is configured to detect the two-phase winding current, and the remaining one-phase winding current is calculated based on the detected value of the two-phase winding current. May be good. The winding current of each phase of each set is detected at the same timing for each control cycle Tc2 described later. When the deviation of the detection timing is sufficiently smaller than the control cycle Tc2, for example, less than Tc2 / 10, the same effect can be obtained.

1-5-1. Inverter control unit 33
<Power generation by induced voltage>
For each set, with all switching elements of the inverter turned off, when the induced voltage of the armature winding generated by the rotation of the rotor for each phase exceeds the voltage on the high potential side of the DC power supply, the armature winding A current flows from the wire to the high potential side of the DC power supply through the antiparallel diode of the switching element on the high potential side. On the other hand, when the induced voltage of the armature winding falls below the voltage on the low potential side of the DC power supply, a current flows from the low potential side of the DC power supply to the armature winding through the antiparallel diode of the switching element on the low potential side. Flows. In this way, when the induced voltage of the armature winding generated by rotation exceeds the voltage on the high potential side of the DC power supply and falls below the voltage on the low potential side of the DC power supply, the inverter functions as a rectifier and AC. The AC power generated by the rotating machine is rectified into DC power and supplied to the DC power supply. That is, the AC rotating machine generates electricity by the induced voltage generated in the three-phase armature winding. Such rectification by a diode is called diode rectification.

<Synchronous rectification>
When a current flows through a diode, the amount of heat generated increases because the power loss is large. Therefore, if the switching element of the diode is turned on when the current flows through the diode due to the induced voltage, the current flows through the switching element instead of the diode, so that the power loss can be reduced and the calorific value can be reduced. Rectification that turns on such a switching element is called synchronous rectification.

For example, FIG. 5 shows the winding currents iu1, iv1, iw1 of the first set of three phases and the winding currents iu2, iv2, iw2 of the second set of three phases at the time of power generation by the induced voltage. FIG. 5 shows the waveforms of the first-order and fifth-order electrical angles.

<Synchronous rectification according to winding current>
At time t2a, the current flows in the first set of inverters 5a as shown in FIG. At time t2a, the winding current of the U1 phase is positive, and when synchronous rectification is not performed, the current flows through the diode on the low potential side of the U1 phase, so the switching element SNu1 on the low potential side of the U1 phase should be turned on. Therefore, the calorific value can be reduced. Similarly, at time t2a, the current of the V1 phase is negative, and the current flows through the diode on the high potential side of the V1 phase. Therefore, by turning on the switching element SPv1 on the high potential side of the V1 phase, the calorific value is reduced. do. At time t2a, the current of the W1 phase is positive, and the current flows through the diode on the low potential side of the W1 phase. Therefore, the heat generation amount is reduced by turning on the switching element SNw1 on the low potential side of the W1 phase. Therefore, in synchronous rectification, when the winding current generated by the induced voltage is negative for each phase, the switching element SP on the high potential side is turned on, the switching element SN on the low potential side is turned off, and the winding current is changed. When positive, the switching element SP on the high potential side is turned off, and the switching element SN on the low potential side is turned on.

<Implementation of diode rectification near 0A>
On the other hand, at time t6a, the winding current iw1 of the W1 phase is a positive value, but is near 0A. Since the detection value iw1s of the winding current of the W1 phase includes a detection error, the detected value iw1s of the winding current may be a negative value even if the winding current iw1 is a positive value. If the switching element on the opposite side where the diode is not energized is erroneously turned on, a current flows through the switching element on the opposite side which is erroneously turned on, and the power generation efficiency is lowered. Further, in the vicinity of 0A, the calorific value does not increase even if a current flows through the diode. Therefore, in consideration of the current detection error, in the vicinity of 0A, both the switching element on the high potential side and the switching element on the low potential side are turned off to perform diode rectification so that the switching element on the opposite side is not accidentally turned on. Is possible.

Further, in Patent Document 1, since the zero crossing time point at which the current crosses 0A is continuously detected and the switching element is turned on or off based on the zero crossing time point, the influence of the delay due to the control cycle is not taken into consideration. .. However, in the present embodiment, as will be described later, since the current is detected for each control cycle Tc2 and the switching element is turned on or off, it is necessary to consider the influence of the delay due to the control cycle.

<Alter power generation control>
Therefore, when the inverter control unit 33 causes the AC rotary machine to generate electric power by the induced voltage generated in the three-phase armature windings for each set, the zero-on mode, the high-on mode, and the low-on mode are used for each phase. Judges the switching with and executes the switching alternator power generation control. The zero-on mode is a mode in which the switching element on the high potential side and the switching element on the low potential side are turned off. The hion mode is a mode in which the switching element on the high potential side is turned on and the switching element on the low potential side is turned off. The low-on mode is a mode in which the switching element on the high potential side is turned off and the switching element on the low potential side is turned on. In the present embodiment, the mode switching determination and switching are executed every control cycle Tc2.

According to this configuration, since both the high-potential side and low-potential side switching elements are switched to the zero-on mode, even if a current detection error and a delay due to the control cycle occur, an error occurs near 0A. Therefore, it is possible to suppress the switching element on the opposite side where the diode is not energized from being turned on, and to suppress the decrease in power generation efficiency.

<Control timing>
FIG. 7 shows the control behavior of the first set. When the alternator power generation control is executed, the winding currents iu1s, iv1s, and iw1s of the first set of three phases are detected at the peak of the carrier signal C2 of the triangular wave oscillating in the control cycle Tc2. After the winding current is detected, switching determination processing of zero-on mode, high-on mode, and low-on mode is performed based on the detected value of the winding current of each phase, and switching is performed at the peak of the valley of the next carrier signal C2. Based on the determination result of, the on / off setting of the switching signal of each switching element of the first set of inverters 5a is updated, and the updated on / off setting is set in the valley of the next next carrier signal C2. It is retained up to the apex. The same applies to the second group.

1-5-1-1. Switching determination The inverter control unit 33 determines switching between zero-on mode, high-on mode, and low-on mode for each set based on the predicted value of the winding current of each phase whose phase is advanced by γ at the electric angle. .. The method of calculating the predicted value of the winding current will be described later.

In the present embodiment, the switching determination described below is executed for each set. The inverter control unit 33 is currently in the low-on mode for each phase, and when the predicted value of the winding current in which the phase is advanced by γ at the electric angle becomes smaller than the low-zero determination value IsL0, the inverter control unit 33 switches to the zero-on mode. Switch. Further, the inverter control unit 33 is currently in the high-on mode for each phase, and when the predicted value of the winding current whose phase is advanced by γ at the electric angle becomes larger than the high-zero determination value IsH0, the zero-on mode Switch to. Here, γ is set to the phase corresponding to the predicted time Te of the next on / off time Tnxt. In this way, in the current high-on mode or low-on mode, the predicted time Te corresponding to γ is changed from the current current detection time point to the winding current detection value detected at the next current detection time point. The next on / off time Tnxt, which is the period until the time when the switching element is turned on / off based on the switching determination result determined based on the above, is set.

The low-zero determination value IsL0 is set to a positive value of the offset value αL0 preset in consideration of the current detection error and the prediction error, and the high-zero determination value IsH0 is preset in consideration of the current detection error and the prediction error. The offset value αH0 may be set to a negative value.

In the case of switching from low-on mode or high-on mode to zero-on mode, in the period from the on-off time based on the current winding current detection value and predicted value to the on-off time based on the next winding current detection value and predicted value. If there is a possibility of straddling 0A, switch to zero-on mode to prevent the switching element on the opposite side where the diode is not energized from being accidentally turned on near 0A, and the power generation efficiency will decrease. I want to suppress. According to the above configuration, switching from the low-on mode or the high-on mode to the zero-on mode is determined based on the predicted value of the winding current at the next on-off time Tnxt destination, so that the next on-off time Tnxt destination is reached. In the period until the on / off time based on the detected value and predicted value of the next winding current, it is determined whether or not the winding current straddles 0A, and if it straddles 0A, it can be switched to the zero-on mode, near 0A. Therefore, it is possible to prevent the switching element on the opposite side from which the diode is not energized from being turned on by mistake, and to prevent the power generation efficiency from decreasing.

The inverter control unit 33 is currently in the zero-on mode for each phase, and the predicted value of the winding current whose phase is advanced by γ at the electric angle is set to a value larger than 0, which is a zero-low determination value Is 0L or more. If it becomes, switch to low-on mode. Further, the inverter control unit 33 is currently in the zero-on mode for each phase, and the predicted value of the winding current whose phase is advanced by γ at the electric angle is set to a value smaller than 0, which is a zero-high determination value Is0H. Switch to high-on mode when: Here, γ is set to the phase corresponding to the predicted time Te of the on / off delay time Tdly. In this way, in the case of the zero-on mode at present, the predicted time Te corresponding to γ is determined based on the detection value of the winding current detected at the time of the current current detection from the time of the current current detection. The on / off delay time Tdry, which is the period until the time when the switching element is turned on / off, is set according to the switching determination result.

The zero-low judgment value Is0L is set to a positive value of the offset value α0L preset in consideration of the current detection error and the prediction error, and the zero-high judgment value Is0H is preset in consideration of the current detection error and the prediction error. It may be set to a negative value of the offset value α0H.

In the case of switching from zero-on mode to low-on mode or high-on mode, in the period from the on-off time based on the current winding current detection value and predicted value to the on-off time based on the next winding current detection value and predicted value. If there is no possibility of straddling 0A, it is desirable to set a low-on mode or a high-on mode to improve power generation efficiency. According to the above configuration, switching from the zero-on mode to the low-on mode or the high-on mode is determined based on the predicted value of the winding current of the on-off delay time Tdly destination, so that the on-off delay time Tdly destination is set this time. At the time of turning on / off based on the detected value and predicted value of the winding current of In the period from the time point to the on / off time point based on the detected value and predicted value of the next winding current, it is possible to switch to the low-on mode or the high-on mode at an early stage, increase the period of synchronous rectification, and improve the power generation efficiency. can.

<Flow chart>
The switching determination process of each set can be configured as shown in the flowchart shown in FIG. The determination process of FIG. 8 is executed for each phase after the winding currents of the three phases are detected for each set. In step S150, the inverter control unit 33 determines whether or not the mode is currently in the low-on mode, and if the mode is in the low-on mode, the process proceeds to step S151, and if the mode is not in the low-on mode, the process proceeds to step S154. In step S151, the inverter control unit 33 advances the phase by γ by the electric angle based on the detected values of the winding currents of the three phases of the first set and the second set by the method described later, and predicts the winding current. Is calculated. Here, γ is set to the phase corresponding to the next on / off time Tnxt. The inverter control unit 33 determines whether or not the predicted value of the winding current is smaller than the low-zero determination value IsL0, and if it is less than the low-zero determination value IsL0, proceeds to step S152 and determines that the mode is switched to the zero-on mode. If it is not less than the low-zero determination value IsL0, the process proceeds to step S153, and it is determined that the low-on mode is maintained.

On the other hand, in step S154, the inverter control unit 33 determines whether or not it is currently in the high-on mode, and if it is in the high-on mode, it proceeds to step S155, and if it is not in the high-on mode, it proceeds to step S158. In step S155, the inverter control unit 33 advances the phase by γ by the electric angle based on the detected values of the winding currents of the three phases of the first set and the second set by the method described later, and predicts the winding current. Is calculated. Here, γ is set to the phase corresponding to the next on / off time Tnxt. The inverter control unit 33 determines whether or not the predicted value of the winding current is larger than the high-zero determination value IsH0, and if it is larger than the high-zero determination value IsH0, proceeds to step S156 and determines that the mode is switched to the zero-on mode. If it is not larger than the high-zero determination value IsH0, the process proceeds to step S157, and it is determined that the high-on mode is maintained.

On the other hand, since the zero-on mode is currently set in step S158, the inverter control unit 33 phase with the electric angle based on the detected values of the winding currents of the three phases of the first set and the second set by the method described later. Calculate the predicted value of the winding current advanced by γ. Here, γ is set to the phase corresponding to the on / off delay time Tdry. The inverter control unit 33 determines whether or not the predicted value of the winding current is the zero-low determination value Is0L or more, and if it is the zero-low determination value Is0L or more, proceeds to step S159 and determines that the mode is switched to the low-on mode. If it is not equal to or greater than the zero-low determination value Is0L, the process proceeds to step S160. In step S160, the inverter control unit 33 determines whether or not the predicted value of the winding current is equal to or less than the zero-high determination value Is0H, and if it is equal to or less than the zero-high determination value Is0H, the process proceeds to step S161 to enter the high-on mode. It is determined to switch, and if it is not equal to or less than the zero-high determination value Is0H, the process proceeds to step S162, and it is determined to maintain the zero-on mode. The determination result of each phase is reflected in the setting of the switching signal at the apex of the valley of the next carrier signal C2.

<Simplification of prediction processing>
If both the predicted value of the winding current of the next on / off time Tnxt destination and the predicted value of the winding current of the on / off delay time Tdly destination are calculated, the processing load will increase. The processing load is reduced by making a judgment using the detected value of the winding current instead of the value.

That is, the inverter control unit 33 is currently in the zero-on mode for each phase, and when the detected value of the armature winding current becomes the zero-low determination value Is0L or more set to a value larger than 0. , You may switch to low-on mode. The inverter control unit 33 is currently in the zero-on mode for each phase, and high-on when the detected value of the armature winding current becomes equal to or less than the zero-high determination value Is0H set to a value smaller than 0. You may switch to the mode.

According to this configuration, the period set to the second control cycle Tc2 minutes, the low-on mode or the high-on mode may be shorter than the case where the predicted value of the winding current of the on / off delay time Tdry destination is used. However, at the time of detecting the current, it is determined whether or not the current has already straddled 0A, and if the current has been straddled, the mode can be switched to the low-on mode or the high-on mode, so that there is a possibility of straddling 0A. In some cases, it is possible to prevent the user from being mistakenly switched to the low-on mode or the high-on mode, and to prevent the power generation efficiency from being lowered.

<Alternative to dead time with zero-on mode>
Here, in each phase, when switching from the low-on mode to the high-on mode and when switching from the high-on mode to the low-on mode, the switching element on the high potential side and the switching element on the low potential side should not be turned on at the same time. It is necessary to consider providing a dead time for turning off both the switching element on the high potential side and the switching element on the low potential side. This dead time is the same as the zero-on mode. According to the switching determination process based on the detection value of the winding current described above, the zero-on mode is switched between the high-on mode and the low-on mode, which is a substitute for the dead time.

The inverter control unit 33 switches from the zero-on mode to the high-on mode or the low-on mode, and switches from the high-on mode or the low-on mode to the zero-on mode, but switches from the high-on mode to the low-on mode and the low-on. It is configured not to switch from mode to high-on mode.

<Setting of control cycle Tc2>
The control cycle Tc2 is set to a cycle shorter than one electrical angle cycle. For example, the control cycle Tc2 may be set to at least 1/4 or less of the electric angle 1 cycle at the maximum rotation speed of the AC rotating machine. The zero-on mode, the high-on mode, and the low-on mode can be appropriately switched during one cycle of the electric angle.

1-5-1-2. Method of calculating predicted value of winding current The method of calculating the predicted value of winding current with the phase advanced by γ at the electrical angle will be described below.
In many cases, the winding current of each phase of each set during induced power generation includes not only the first-order electric angle component but also the fifth-order electric angle component, and thus can be approximately expressed by the following equation.

Here, ω is the rotation angle velocity at the electric angle, I1 is the current amplitude of the electric angle primary component of each set, δ1 is the phase of the electric angle primary component of each set, and I5 is. , Is the current amplitude of the 5th order component of the electric angle of each set, and δ5 is the phase of the 5th order component of the electric angle of each set. From the phase difference π / 6 between the first set of armature windings and the second set of armature windings shown in FIG. 2, the winding current of the second set of three phases is that of the first set of three phases. It lags behind the winding current by a phase difference of π / 6.

<Calculation of predicted values of primary and fifth electrical angles>
When the predicted value iu1e of the winding current of the U1 phase whose phase is advanced by γ is calculated by, for example, the equation (2) using the current and past current detection values iu1s and iu1s_old of the U1 phase, the electric angle Although the first-order component has an approximation error, it can be estimated, but the phase of the fifth-order electric angle component cannot be advanced correctly.

Therefore, in the present embodiment, since the phase difference between the first set of three-phase armature windings and the second set of three-phase armature windings is π / 6, each phase of each set. Not only the phase of the primary component of the electric angle is advanced by γ, but also the phase of the fifth component of the electric angle is advanced by 5γ by using the current detection value of. As shown in the formula (1), the U1 phase is for the W1 phase, the V1 phase is for the U1 phase, the W1 phase is for the V1 phase, the U2 phase is for the W2 phase, and the V2 phase is for U2. In the W2 phase, the phase of the first-order electric angle component is delayed by 2 / 3π and the phase of the fifth-order electric angle component is advanced by 2 / 3π with respect to the V2 phase. Further, the phase of the primary component of the electric angle is delayed by π / 2 with respect to the W2 phase of the U1 phase, the phase of the V1 phase with respect to the U2 phase, and the phase of the W1 phase with respect to the V2 phase. Is delayed by π / 2. Therefore, the inverter control unit 33 has the U1 phase electric angle primary component iu1_1f, the V1 phase electric angle primary component iv1_1f, the W1 phase electric angle primary component iw1_1f, the U2 phase electric angle primary component iu2-1f, and the V1 phase. The electric angle primary component iv2_1f and the electric angle primary component iw2_1f of the W2 phase can be calculated using the equation (3) based on the current detection values of each phase of each set.

Further, the inverter control unit 33 has a U1 phase electric angle fifth-order component iu1_5f, a V1 phase electric angle fifth-order component iv1_5f, a W1 phase electric angle fifth-order component iw1_5f, a U2 phase electric angle fifth-order component iu2_5f, and a V1 phase. The electric angle fifth-order component iv2_5f and the W2 phase electric angle fifth-order component iw2_5f can be calculated using the equation (4) based on the current detection values of each phase of each set.

Therefore, the current of the U1 phase whose phase is advanced by γ is the electric angle 1 of the W2 phase whose phase is π / 2 different from that of the U1 phase with the electric angle primary component and the fifth order component of the U1 phase as shown in equation (5). It can be calculated based on the following component and the fifth component.

Since the same can be considered for other phases, the inverter control unit 33 uses Eq. (6) to determine the predicted value of the winding current of each phase of each set whose phase is advanced by γ by the electric angle, and for each of the sets. It can be calculated based on the primary component and the fifth component of the electric angle of the phase.

As shown in the equation (6), the inverter control unit 33 multiplies the electrical angle primary component of each phase of each set by sin (γ) or cos (γ), and each phase of each set. Prediction of winding current of each phase of each set whose phase is advanced by γ by electric angle based on the value obtained by multiplying the fifth-order electric angle component by sin (5 × γ) or cos (5 × γ). The value can be calculated.

Specifically, the predicted value iu1e of the winding current of the U1 phase has a phase of π / 2 with the armature winding of the U1 phase, the electric angle primary component iu1_1f and the electric angle fifth component iu1_5f, and the armature winding of the U1 phase. It is calculated based on the electric angle primary component iw2_1f and the electric angle fifth order component iw2_5f of different W2 phases (see FIG. 2). Further, the primary component of the electrical angle of the W1 phase (see FIG. 2) whose phase differs by π / 2 from the armature winding of the V2 phase, the primary component of the electrical angle iv2_1f and the fifth component of the electrical angle iv2_1f, and the armature winding of the V2 phase. It is calculated based on iw1_1f and the fifth-order electric angle component iw1_5f. As described above, the inverter control unit 33 sets the predicted value of the winding current of the m-phase of one of the first set and the second set to the electric angle primary component and the electric angle fifth component of the m-phase. It can be calculated based on the primary component of the electric angle and the fifth-order component of the electric angle of the other set of the other set whose phases differ by π / 2 from the armature winding of the m-phase and the electric angle.

When γ is minute, it can be approximated to cosγ = 1 and cos5γ = 1 in Eq. (6), so the predicted value of the winding current of each phase of each set whose phase is advanced by γ by the electric angle is given by Eq. It may be calculated using (7).

When γ is minute, it can be approximated to sinγ = γ and sin5γ = 5γ in the equation (7), so that the predicted value of the winding current of each phase of each set whose phase is advanced by γ by the electric angle is , Equation (7) may be used for calculation.

Utilizing the fact that the sum of the predicted values of the winding currents of the three phases becomes 0 for each set, the predicted values of the winding currents of any two phases are calculated for each set, and the calculated two-phase winding is performed. The predicted value of the winding current of the remaining one phase may be calculated based on the predicted value of the line current. For example, as shown in the equation (9), the predicted value of the winding current of the W1 phase and the V2 phase may be calculated based on the predicted value of the winding current of the other two phases.

If the arithmetic processing load can be reduced, the control cycle Tc2 can be shortened, and the period during which synchronous rectification is executed can be increased. Therefore, by substituting the equations (3) and (4) into the equation (6) and rearranging them using the equation (10), the equation (11) is obtained. Since the predicted value of the winding current can be calculated without calculating the electric angle primary component and the fifth-order component of the equations (3) and (4), the arithmetic processing load can be reduced. The predicted value of the winding current of each phase of each set whose phase is advanced by γ by the electric angle may be calculated by using the equation (11). In particular, when the control cycle Tc2 is constant, it is advisable to prepare in advance a conversion coefficient to be multiplied by each current detection value.

As shown in the equation (11), the inverter control unit 33 detects the winding current of two phases in the first set of three phases and the winding current of two phases in the second set of three phases. The predicted value of the winding current of each phase of each set can be calculated by multiplying each of the values by an individual conversion coefficient. The inverter control unit 33 calculates individual conversion coefficients using sin (γ), cos (γ), sin (5 × γ), and cos (5 × γ).

なお、各判定値は、検出誤差、演算時の近似誤差、および電気角１次および５次以外の例えば７次、１１次、１３次などの高調波成分による予測誤差を鑑みて、決定すればよい。 Here, when γ is minute, it may be simplified by an approximate expression such as Eq. (12).

It should be noted that each determination value is determined in consideration of the detection error, the approximation error at the time of calculation, and the prediction error due to the harmonic components such as the 7th, 11th, and 13th orders other than the 1st and 5th electric angles. good.

<Gamma setting>
As shown in the equation (13), the inverter control unit 33 sets a value obtained by multiplying the predicted time Te by the rotation angular velocity ω at the electric angle as γ for each phase of each set.

As described above, the inverter control unit 33 sets the predicted time Te for each phase of each set in the high-on mode or the low-on mode from the current current detection time point to the next current detection time point. The next on / off time Tnxt, which is the period until the time when the switching element is turned on / off based on the switching determination result determined based on the detected value of, is set.

As described above, the inverter control unit 33 detects the predicted time Te for each phase of each set from the current current detection time point to the current current detection time point when the zero-on mode is currently set. The on / off delay time Tdry, which is the period until the switching element is turned on / off based on the switching determination result determined based on the detection value of the winding current, is set.

<When used as a generator motor for vehicles>
When the control device for the AC rotary machine of the present embodiment is used for a generator motor for a vehicle, the configuration is as shown in FIG. The rotary shaft of the rotor of the AC rotary machine 1 is connected to the crank shaft of the internal combustion engine 100 via a pulley and a belt mechanism 101. The rotating shaft of the AC rotating machine 1 is connected to the wheel 103 via the internal combustion engine 100 and the transmission 102. The AC rotary machine 1 functions as an electric motor, serves as a driving force source for the wheels 103 as an auxiliary machine of the internal combustion engine 100, and also functions as a generator, and generates electricity by utilizing the rotation of the internal combustion engine 100. Since the AC rotary machine 1 is connected to the internal combustion engine 100, the rotation fluctuation becomes gradual due to the inertia of the internal combustion engine 100. Therefore, when the alternator power generation control is performed in the second control cycle Tc2, the rotation fluctuation changes. The influence can be reduced, and the prediction accuracy of the predicted value of the winding current can be improved. Further, it is possible to obtain the same effect even with a generator for a vehicle.

1-5-2. Converter control unit 35
The field current detection unit 34 detects the field current ifs, which is the current flowing through the field winding 4, based on the output signal of the field current sensor 6. Here, ifs is a detected value of the field current if.

The converter control unit 35 performs proportional integral control with respect to the deviation Δif between the field current command value ifo and the field current detection value ifs so that the field current detection value ifs approaches the field current command value ifo. The field voltage command value Vf is calculated, and a current is applied to the field winding 4 based on the field voltage command value Vf.

In the present embodiment, as shown in FIG. 3, the converter control unit 35 includes a current command value calculation unit 351, a voltage command value calculation unit 352, and a PWM control unit 353.

The current command value calculation unit 351 sets the field current command value ifo. For example, when the inverter control is executed, the current command value calculation unit 351 sets the field current command value ifo based on the torque command value To or the like. When the alternator power generation control is executed, the current command value calculation unit 351 changes the field current command value ifo so that the DC voltage Vdc approaches the target voltage.

Then, the voltage command value calculation unit 352 performs proportional integral control with respect to the deviation between the field current command value ifo and the field current detection value ifs, and calculates the field voltage command value Vf.

The PWM control unit 353 controls on / off of a plurality of switching elements of the converter 9 by PWM control based on the field voltage command value Vf.

For example, as shown in FIG. 10, the PWM control unit 353 controls a plurality of switching elements on and off by comparing the field voltage command value Vf with the field carrier signal Cf vibrating in the field control cycle Tsf. The field carrier signal Cf is a triangular wave that oscillates between -1 × DC voltage Vdc and DC voltage Vdc in the field control period Tsf. The DC voltage Vdc may be detected by a voltage sensor.

When the field carrier signal Cf falls below the field voltage command value Vf, the PWM control unit 353 turns on the switching signal QP1 of the switching element SP1 on the high potential side of the first set (1 in this example). The switching signal QN1 of the switching element SN1 on the low potential side of the first set is turned off (0 in this example), the switching signal QP2 of the switching element SP2 on the high potential side of the second set is turned off (0), and the second set. The switching signal QN2 of the switching element SN2 on the low potential side of the set is turned on (1).

On the other hand, when the field carrier signal Cf exceeds the field voltage command value Vf, the PWM control unit 353 turns off (0) the switching signal QP1 on the high potential side of the first set, and the low potential of the first set. The switching signal QN1 on the side is turned on (1), the switching signal QP2 on the high potential side of the second set is turned on (1), and the switching signal QN2 on the low potential side of the second set is turned off (0). For each set, between the on-period of the switching element on the high-potential side and the on-period of the switching element on the low-potential side, a short-circuit prevention period in which both the switching element on the positive electrode side and the switching element on the low-potential side are turned off ( A dead time) may be provided.

If it is not necessary to change the current direction of the field winding, the switching signal QP2 on the high potential side of the second set may be turned off at all times, and the switching signal QN1 on the low potential side of the first set may be constantly turned off. You may turn it off. Since the inductance of the field winding is larger than the inductance of the armature winding in many cases, the fluctuation of the field current during the second control cycle Tc2 during alternator power generation control is small, and the field magnetic flux is directly changed. It is suitable for alternator power generation control because it can be used.

<Example of diversion>
(1) In the first embodiment described above, the case where the AC rotary machine is a generator motor for a vehicle has been described as an example. However, the AC rotary electric machine may be used as a driving force source for various devices other than the vehicle.

(2) In the first embodiment described above, a field winding type AC rotary machine has been described as an example. However, the AC rotating machine may be a permanent magnet type AC rotating machine.

(3) In the first embodiment described above, the case where the inverter control unit 33 executes the alternator power generation control has been described as an example. However, the inverter control unit 33 may switch between the alternator power generation control and other controls for execution. For example, as another control, an inverter control for turning on / off the switching element of the inverter by PWM control is executed based on the voltage command values of the three phases for each set. In the inverter control, a known vector control for controlling the current on the d-axis and q-axis rotating coordinate systems is used.

(4) When the predicted value of the winding current obtained by advancing the phase by γ in the electric angle for each phase of each set is the low-on determination value IsL set to a value larger than 0 in the inverter control unit 33. Judges to switch to the low-on mode, and switches to the high-on mode when the predicted value of the winding current whose phase is advanced by γ by the electric angle is equal to or less than the high-on judgment value set to a value smaller than 0. Even if it is configured to switch to the zero-on mode when the predicted value of the winding current whose phase is advanced by γ by the electric angle is smaller than the low-on judgment value and larger than the high-on judgment value. good. γ is set to the phase corresponding to the next on / off time Tnxt.

Although the present application describes various exemplary embodiments and examples, the various features, embodiments, and functions described in one or more embodiments are applications of a particular embodiment. It is not limited to, but can be applied to embodiments alone or in various combinations. Therefore, innumerable variations not exemplified are envisioned within the scope of the techniques disclosed herein. For example, it is assumed that at least one component is modified, added or omitted, and further, at least one component is extracted and combined with the components of other embodiments.

1 AC rotating machine, 2 DC power supply, 4 field winding, 11 AC rotating machine control device, 14 rotor, 18 stator, Tnxt next on / off time, Tdry on / off delay time

Claims (16)

A control device for an AC rotating machine that controls an AC rotating machine provided with a rotor and a stator having a first set of three-phase armature windings and a second set of three-phase armature windings via an inverter. And,
In the inverter, for each phase of each set, a switching element on the high potential side connected to the high potential side of the DC power supply and a switching element on the low potential side connected to the low potential side of the DC power supply are connected in series. A series circuit is provided in which the connection point of the series connection is connected to the armature winding of the corresponding phase, and the switching element has the function of a diode connected in antiparallel.
The phase difference in the electrical angle of the second set of three-phase armature windings with respect to the first set of three-phase armature windings is −π / 6.
The control device for the AC rotary machine is
For each set, when the AC rotator is made to generate electricity by the induced voltage generated in the three-phase armature winding, the switching element on the high potential side and the low potential side is turned off for each phase. A mode, a high-on mode in which the switching element on the high potential side is turned on and the switching element on the low potential side is turned off, and a low mode in which the switching element on the high potential side is turned off and the switching element on the low potential side is turned on. Judges the switching between on mode and the alternate power generation control to switch,
For each set, prediction of the current of the armature winding of each phase advanced by γ in phase with the electric angle based on the detected value of the current of the armature winding of the three phases of the first set and the second set. A control device for an AC rotating machine that calculates a value and determines switching between the zero-on mode, the high-on mode, and the low-on mode based on the predicted value of the current of the armature winding of each phase. For each set, based on the current detection values of the armature windings of the three phases of the first set and the second set, the electric angle primary component and the electric angle included in the current of the armature winding of each phase. Calculate the 5th order component and
A value obtained by multiplying the first-order electric angle component of each phase of each set by sin (γ) or cos (γ), and a sin for the fifth-order electric angle component of each phase of each set. The control of the AC rotating machine according to claim 1, wherein the predicted value of the current of the armature winding of each phase of each set is calculated based on the value multiplied by (5 × γ) or cos (5 × γ). Device. For each set, based on the current detection values of the armature windings of the three phases of the first set and the second set, the electric angle primary component and the electric angle included in the current of the armature winding of each phase. Calculate the 5th order component and
The predicted value of the current of the armature winding of the m-phase of one of the first set and the second set is the component of the first-order electric angle included in the current of the armature winding of the m-phase. And the electricity contained in the current of the fifth-order component of the electric angle and the current of the armature winding of the nth phase of the other set whose phase is π / 2 different from that of the armature winding of the mth phase. The control device for an AC rotary machine according to claim 1 or 2, which is calculated based on a component having a first-order angle and a component having a fifth-order electric angle. The predicted values of the currents of the armature windings of the first phase, the second phase, and the third phase of the first set are set to iu1e, iv1e, and iw1e, respectively.
The predicted values of the currents of the armature windings of the first phase, the second phase, and the third phase of the second set are set to iu2e, iv2e, and iw2e, respectively.
The components of the first-order electric angle and the fifth-order electric angle included in the current of the armature winding of the first phase of the first set are defined as iu1-1_1f and iu1_5f, respectively.
The first-order electric angle component and the fifth-order electric angle component included in the current of the armature winding of the second phase of the first set are defined as iv1_1f and iv1_5f, respectively.
The components of the first-order electric angle and the fifth-order electric angle included in the current of the armature winding of the third phase of the first set are defined as iw1_1f and iw1_5f, respectively.
The components of the first-order electric angle and the fifth-order electric angle included in the current of the armature winding of the first phase of the second set are defined as iu2_1f and iu2_5f, respectively.
The components of the first-order electric angle and the fifth-order electric angle included in the current of the armature winding of the second phase of the second set are defined as iv2_1f and iv2_5f, respectively.
The components of the first-order electric angle and the fifth-order electric angle included in the current of the armature winding of the third phase of the second set are defined as iw2_1f and iw2_5f, respectively.

The control device for an AC rotary machine according to claim 3, wherein the predicted value of the current of the armature winding of each phase of each set is calculated by the calculation formula of. The current detection values of the armature windings of the first phase, the second phase, and the third phase of the first set are set to iu1s, iv1s, and iw1s, respectively.
The current detection values of the armature windings of the first phase, the second phase, and the third phase of the second set are set to iu2s, iv2s, and iw2s, respectively.

The control device for an AC rotary machine according to claim 4, wherein the component of the primary electric angle included in the current of the armature winding of each phase of each set is calculated by the calculation formula of. The current detection values of the armature windings of the first phase, the second phase, and the third phase of the first set are set to iu1s, iv1s, and iw1s, respectively.
The current detection values of the armature windings of the first phase, the second phase, and the third phase of the second set are set to iu2s, iv2s, and iw2s, respectively.

The control device for an AC rotary machine according to claim 4 or 5, wherein the component of the fifth order of the electric angle included in the current of the armature winding of each phase of each set is calculated by the calculation formula of. Individual conversion to the current detection value of the armature winding of two of the three phases of the first set and the current detection value of the armature winding of two phases of the three phases of the second set. The predicted value of the current of the armature winding of each phase of each set is calculated by the sum of the values multiplied by the coefficients.
The control device for an AC rotary machine according to claim 1, wherein the individual conversion coefficients are calculated using sin (γ), cos (γ), sin (5 × γ), and cos (5 × γ). The predicted values of the currents of the armature windings of the first phase, the second phase, and the third phase of the first set are set to iu1e, iv1e, and iw1e, respectively.
The predicted values of the currents of the armature windings of the first phase, the second phase, and the third phase of the second set are set to iu2e, iv2e, and iw2e, respectively.
The current detection values of the armature windings of the first phase, the second phase, and the third phase of the first set are set to iu1s, iv1s, and iw1s, respectively.
The current detection values of the armature windings of the first phase, the second phase, and the third phase of the second set are set to iu2s, iv2s, and iw2s, respectively.

The control device for an AC rotary machine according to claim 7, wherein the predicted value of the current of the armature winding of each phase of each set is calculated by the calculation formula of. The control device for an AC rotary machine according to any one of claims 1 to 8, which switches between the zero-on mode, the high-on mode, and the low-on mode in a control cycle shorter than one electrical angle cycle. For each phase of each set, the value obtained by multiplying the predicted time by the rotation angular velocity at the electric angle of the rotor is set as γ.
When each phase of each set is currently in the high-on mode or the low-on mode, the predicted time is switched from the current current detection time point to the next current detection time point based on the current detection value. The control device for an AC rotating machine according to any one of claims 1 to 9, which is set in a period until a time point in which the switching element is turned on and off based on a determination result. Any of claims 1 to 10 which is currently in the high-on mode for each phase of each set and switches to the zero-on mode when the predicted value of the current of the armature winding becomes larger than the high-zero determination value. The control device for the AC rotary machine described in item 1. 13. The control device for the AC rotating machine according to any one of the items. For each phase of each set, the value obtained by multiplying the predicted time by the rotation angular velocity at the electric angle of the rotor is set as γ.
For each phase of each set, in the case of the zero-on mode, the predicted time is determined based on the switching determination result determined based on the current detection value at the current current detection time from the current current detection time. The control device for an AC rotary machine according to any one of claims 1 to 12, which is set in a period until the switching element is turned on and off. Each phase of each set is currently in the zero-on mode, and when the predicted value of the current of the armature winding becomes equal to or less than the zero-high determination value, the mode is switched to the high-on mode.
13. Control device for AC rotating machine. Each phase of each set is currently in the zero-on mode, and when the current detection value of the armature winding becomes equal to or less than the zero-high determination value, the mode is switched to the high-on mode.
The alternating current according to any one of claims 1 to 12, which is currently in the zero-on mode and switches to the low-on mode when the current detection value of the armature winding becomes equal to or higher than the zero-low determination value. Rotating machine control device. The control device for an AC rotator according to any one of claims 1 to 15, wherein the AC rotator is a generator for a vehicle or a generator motor.

Images