JP2021180596A - Rotary electric machine - Google Patents

Abstract

To provide a rotary electric machine that can improve the space factor.SOLUTION: A rotary electric machine 10 includes a stator 30 including a multi-phase stator winding 32 and a stator core 31 having teeth T1 to T18 that are provided in the circumferential direction and around which stator windings 32 are wound. The teeth T1 to T18 include a plurality of first teeth in each of which the stator winding 32 is wound a predetermined number of times, and a plurality of second teeth in which the stator winding 32 is wound the number of times less than the first teeth. Two or more second teeth are continuously provided in the circumferential direction, and a first distance θ1 between the first teeth and the second teeth in the circumferential direction is wider than a second distance θ2 between the second teeth in the circumferential direction.SELECTED DRAWING: Figure 11

Description

The present invention relates to a rotary electric machine.

Conventionally, a rotary electric machine having an armature winding having a plurality of coil portions wound around teeth provided at predetermined intervals in the circumferential direction is known. In some such rotary electric machines, the multi-winding coil portion having a large number of turns of the conducting wire and the adjacent coil portion have the same phase, and heat generation is locally concentrated. Therefore, in the rotary electric machine described in Patent Document 1, the increase in local heat generation in a specific coil portion is suppressed by appropriately changing the number of turns or the alignment of the conducting wire of some coil portions.

International Publication No. 2017/073092

However, in such a rotary electric machine, the space factor of the conductors in each slot varies because the number of turns or the alignment of the conductors of some of the coil portions is different. For this reason, the armature as a whole has a problem that a wasteful space is generated in the slot and the space factor is lowered. That is, there is a problem that the motor efficiency is lowered.

The present invention has been made in view of the above circumstances, and an object of the present invention is to provide a rotary electric machine capable of improving the space factor.

The means for solving the above problems are a field portion having a plurality of magnetic poles having alternating polarities in the circumferential direction, a multi-phase armature winding, and a plurality of armature windings provided in the circumferential direction. An armature having an armature to be wound In a rotary electric machine including an armature having an iron core, the armature is compared with a first tooth in which the armature winding is wound a predetermined number of times and the first tooth. A plurality of second teeth, each of which has a small number of turns of the armature winding, are provided, and at least two or more of the second teeth are continuously provided in the circumferential direction. The first distance between the first teeth and the second teeth in the circumferential direction is wider than the second distance between the second teeth in the circumferential direction.

According to this means, the first distance between the first teeth and the second teeth in the circumferential direction is set to be wider than the second distance between the second teeth in the circumferential direction. .. As a result, it is possible to improve the space factor in the slot between the first teeth and the second teeth while improving the space rate in the slot between the second teeth. This makes it possible to improve the overall space factor in the armature.

A vertical sectional view showing a motor. Cross-sectional view showing a motor. The figure which shows the electrical composition of a control device. The figure which shows the arrangement of a partial winding. The figure which shows the stator winding. The figure which shows the arrangement of a leader line. The figure which shows the harmonic component of torque. A vector diagram showing the sum of the magnetomotive forces. The figure which shows the fluctuation of the electromagnetic force. The cross-sectional view which shows the motor in the comparative example. The cross-sectional view which shows the motor in this embodiment. An enlarged cross-sectional view showing a motor in a comparative example. An enlarged cross-sectional view showing a motor in this embodiment. The figure which shows the cogging torque. The figure which shows the arrangement of the partial winding in 2nd Embodiment. Cross-sectional view showing a motor. The vector figure which shows the sum of the magnetomotive force of 2nd Embodiment. The figure which shows the arrangement of the partial winding in 3rd Embodiment. The figure which shows the arrangement of the partial winding in 4th Embodiment. The figure which shows the arrangement of the partial winding in another example. The figure which shows the arrangement of the partial winding in another example. The figure which shows the arrangement of the partial winding in another example.

(First Embodiment)
Hereinafter, each embodiment will be described with reference to the drawings. In each of the following embodiments, the parts that are the same or equal to each other are designated by the same reference numerals, and the description thereof will be used for the parts having the same reference numerals. In the first embodiment, the motor 10 as a rotary electric machine will be illustrated and described.

The motor 10 shown in FIG. 1 is of the permanent magnet field type, and specifically, is a permanent magnet field type synchronous machine having a three-phase winding. That is, the motor 10 is a brushless motor. This three-phase winding may have two systems. The motor 10 includes a housing 20, a stator 30 fixed to the housing 20, a rotor 40 that rotates with respect to the stator 30, and a rotating shaft 11 to which the rotor 40 is fixed. Hereinafter, in the present embodiment, the axial direction means the axial direction of the rotating shaft 11 (indicated by an arrow Y1 in the figure). The radial direction indicates the radial direction of the rotating shaft 11 (indicated by an arrow Y2 in the figure). The circumferential direction indicates the circumferential direction of the rotating shaft 11 (indicated by an arrow Y3 in the figure).

The housing 20 is formed in a cylindrical shape, and the stator 30, the rotor 40, and the like are housed in the housing 20. Bearings 23 and 24 are provided in the housing 20, and the rotating shaft 11 is rotatably supported by the bearings 23 and 24. The axis of the inner peripheral surface of the housing 20 is coaxial with the rotating shaft 11. An angle sensor 12 is provided on the tip end side of the rotating shaft 11. The angle sensor 12 may be a magnetic sensor or a resolver.

The stator 30 is provided in a cylindrical shape along the inner circumference of the housing 20 at substantially the center of the housing 20 in the axial direction. The stator 30 is fixed to the inner peripheral surface of the housing 20 with the axis O of the rotating shaft 11 as the center. The stator 30 constitutes a part of a magnetic circuit, and has an annular shape, and the stator core 31 (armature core, armature core, etc.) arranged so as to face each other in the radial direction on the outer peripheral side of the rotor 40. It has a stator core) and a stator winding 32 (armature winding, armature coil) wound around a stator core 31.

As shown in FIG. 2, the stator core 31 includes an annular back yoke 33 and a plurality of teeth T1 to T18 protruding from the back yoke 33 in the radial direction toward the rotation axis 11 and arranged side by side in the circumferential direction. A slot 35 (status lot) is formed between the adjacent teeth T1 to T18. Further, the radial tips of the teeth T1 to T18 are wider than the circumferential width dimensions of the teeth T1 to T18, respectively, and have a flange portion 70 as an opposing portion facing the rotor 40.

In the stator core 31, the slots 35 are provided side by side in the circumferential direction, and the stator winding 32 is wound around the slot 35. In the present embodiment, the number of teeth T1 to T18 is "18", and the number of slots 35 is "18". For convenience of explanation, each of the teeth T1 to T18 is designated by the reference numerals T1 to 18 in a counterclockwise arrangement order in the circumferential direction. The stator winding 32 is housed and held in the slot 35. Then, the stator winding 32 generates a magnetic flux by being supplied with electric power (alternating current power).

The stator core 31 is an integral type formed by laminating a plurality of thin plate-shaped magnetic steel plates (core sheets) forming an annular shape in the axial direction of the stator core 31. The steel plate is formed by pressing and punching a strip-shaped electromagnetic steel plate material.

The rotor 40 constitutes a part of the magnetic circuit, has one or a plurality of pairs of magnetic poles in the circumferential direction, and is arranged so as to face the stator 30 in the radial direction. In the present embodiment, the rotor 40 corresponds to a field portion having 14 (that is, 7 magnetic pole pairs) magnetic poles. The rotor 40 includes a rotor core 41 made of a magnetic material and a permanent magnet 42 fixed to the rotor core 41. Specifically, as shown in FIG. 2, the rotor 40 is provided with 14 permanent magnets 42 as magnet portions so that the polarities alternate in the circumferential direction, and the rotor 40 is provided along the axial direction with the rotor core 41. A permanent magnet 42 is embedded in the accommodating hole provided therein.

The rotor 40 may have a well-known configuration, and may be, for example, an IPM type (Interior Permanent Magnet) rotor or an SPM type (Surface Permanent Magnet: surface magnet side) rotor. good. Further, as the rotor 40, a rotor on the field winding side may be adopted. In this embodiment, an IPM type rotor is adopted. A rotary shaft 11 is inserted through the rotor 40 and is fixed to the rotary shaft 11 so as to rotate integrally with the rotary shaft 11 around the rotary shaft 11.

A control device 50 is connected to the motor 10. The control device 50 is mainly composed of a microcomputer equipped with a CPU, ROM, RAM, I / O, etc., and the CPU realizes various functions by executing a program stored in the ROM. The various functions may be realized by electronic circuits that are hardware, or at least a part of them may be realized by software, that is, processing executed on a computer.

As a function of the control device 50, for example, it has a function of converting electric power from an outside (for example, a battery) and supplying it to a motor 10 to generate a driving force. Further, for example, the control device 50 has a function of controlling the motor 10 (current control, etc.) by using the information regarding the rotation angle input from the angle sensor 12.

Further, as shown in FIG. 3, the control device 50 is provided with a first inverter circuit 51 and a second inverter circuit 52. The first inverter circuit 51 is composed of a full bridge circuit having the same number of upper and lower arms as the number of phases of each of the three phases. The control device 50 controls the current in each phase by turning on / off the switching element provided in each arm.

More specifically, as shown in FIG. 3, in the first inverter circuit 51, the upper arm switch Sp and the lower arm switch Sn as switching elements are connected in series in three phases including U phase, V phase and W phase. Each has a body. In the present embodiment, a voltage-controlled semiconductor switching element is used as the upper arm switch Sp and the lower arm switch Sn in each phase, and specifically, an IGBT is used. In addition, MOSFET may be used. Freewheel diodes (reflux diodes) Dp and Dn are connected in antiparallel to the upper arm switch Sp and the lower arm switch Sn in each phase, respectively.

The high potential side terminal (collector) of the upper arm switch Sp of each phase is connected to the positive electrode terminal of the battery. Further, the low potential side terminal (emitter) of the lower arm switch Sn of each phase is connected to the negative electrode terminal (ground) of the battery. The intermediate connection points between the upper arm switch Sp and the lower arm switch Sn of each phase are connected to one end (leader wires A1, B1, C1) of the stator winding 32, respectively. Since the second inverter circuit 52 is the same as the first inverter circuit 51, detailed description thereof will be omitted.

Next, the winding method of the stator winding 32 will be described in detail. The stator winding 32 is classified into U-phase, V-phase, and W-phase stator windings 32 that represent each of the three phases. As shown in FIGS. 4 and 5, the U-phase stator winding 32 is composed of eight partial windings + U11, + U12, −U13, −U14, −U21, + U22, + U23, −U24. .. The V-phase stator winding 32 is composed of eight partial windings −V11, + V12, + V13, −V14, + V21, −V22, −V23, + V24. The U-phase stator winding 32 is composed of eight partial windings + W11, −W12, −W13, + W14, + W21, −W22, −W23, + W24.

Further, as shown in FIGS. 2 and 4, the 24 partial windings correspond to + U11, + V21, + W11 / -V22, -W12, -U21, -V11 / + U22, respectively, corresponding to the teeth T1 to T18. It is arranged in the order of + V12, + W21, + U12 / -W22, -U13, -V23, -W13 / + V24, + W14, + U23, + V13 / -U24, -V14, -W23, -U14 / + W24.

The symbols "+" and "-" indicate the direction of the current, that is, the polarity of the field generated by the partial winding. For example, in FIG. 2 of the present embodiment, when the current flow from the front side to the back side of the paper is "+", the current flow from the back side to the front side is "-". That is, when a current flows through the stator winding 32, it means that a “+” partial winding and a “−” partial winding generate magnetomotive forces that are opposite in the radial direction. It can be said that the "+" partial winding and the "-" partial winding have a phase difference of the magnetomotive force of 180 degrees in the electric angle. The "+" partial winding and the "-" partial winding can be realized by reversing the winding method. The same applies to the coil body described later.

Further, "/" indicates that the two partial windings are arranged at different radial positions with respect to the same teeth T1 to T18. That is, two partial windings are arranged for the teeth T3, T6, T9, T12, T15, and T18. Then, one partial winding is arranged for the other teeth T1, T2, T4, T5, T7, T8, T10, T11, T13, T14, T16, T17. In the teeth T3, T6, T9, T12, T15, and T18, the radial positions of the partial windings may be exchanged.

Next, the wiring of the stator winding 32 will be described with reference to FIG. In the present embodiment, the Y connection (star connection) is used, but a delta connection may be used.

As shown in FIG. 5, the stator winding 32 is composed of a first stator winding 32a and a second stator winding 32b. In the first stator winding 32a, the U-phase partial windings + U11, + U12, -U13, and -U14 are connected in series, and the V-phase partial windings -V11, + V12, + V13, and -V14 are connected in series. The W phase partial winding + W11, −W12, −W13, + W14 are connected in series. One end of these series connectors is connected to the neutral point Q, and the other end is connected to leader lines A1, B1, and C1 connected to the first inverter circuit 51. A U-phase partial winding is connected to the leader wire A1, a V-phase partial winding is connected to the leader wire B1, and a W-phase partial winding is connected to the leader wire C1. ..

Similarly, in the second stator winding 32b, the U-phase partial windings −U21, + U22, + U23, −U24 are connected in series, and the V-phase partial windings + V21, −V22, −V23, + V24 are connected in series. The W phase partial winding + W21, −W22, −W23, + W24 are connected in series. One end of these series connectors is connected to the neutral point Q, and the other end is connected to leader lines A2, B2, and C2 connected to the second inverter circuit 52. The U-phase partial winding is connected to the leader wire A2, the V-phase partial winding is connected to the leader wire B2, and the W-phase partial winding is connected to the leader wire C2. ..

As shown in FIG. 6, the leader lines A1, B1, C1, A2, B2, and C2 are arranged so as to be point-symmetrical about the axis O of the rotation axis 11. That is, the leader lines A1 and A2 are arranged at 180 degree intervals, the leader lines B1 and B2 are arranged at 180 degree intervals, and the leader lines C1 and C2 are arranged at 180 degree intervals. The leader lines A1, B1, C1, A2, B2, and C2 are provided linearly along the axial direction.

Here, by winding (winding) only the first stator winding 32a around the teeth T1, T4, T7, T10, T13, and T16, two coils for each phase are provided. ing. These U-phase coil bodies are referred to as coil bodies Ua, V-phase coil bodies are referred to as coil body Va, and W-phase coil bodies are referred to as coil body Wa. In the following, a tooth in which only the first stator winding 32a is wound may be referred to as a second A tooth. In the first embodiment, the teeth T1, T4, T7, T10, T13, T16 correspond to the second teeth and correspond to the second A teeth.

Further, by winding only the second stator winding 32b around the teeth T2, T5, T8, T11, T14, and T17, two coils of each phase are provided. These U-phase coil bodies are referred to as coil bodies Ub, V-phase coil bodies are referred to as coil bodies Vb, and W-phase coil bodies are referred to as coil body Wb. In the following, a tooth in which only the second stator winding 32b is wound may be referred to as a second B tooth. In the first embodiment, the teeth T2, T5, T8, T11, T14, T17 correspond to the second teeth and correspond to the second teeth.

Then, the first stator winding 32a and the second stator winding 32b are wound around the teeth T3, T6, T9, T12, T15, and T18, so that the coil bodies of each phase are respectively wound. There are two each. These U-phase coil bodies are referred to as coil bodies Uc, V-phase coil bodies are referred to as coil bodies Vc, and W-phase coil bodies are referred to as coil bodies Wc. In the following, the teeth around which the first stator winding 32a and the second stator winding 32b are wound may be referred to as the first teeth. In the first embodiment, the teeth T3, T6, T9, T12, T15, T18 correspond to the first teeth.

As shown in FIG. 2, the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc of each phase are arranged twice rotationally symmetrically with respect to the axis of the rotation axis 11. .. That is, the arrangement order of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc is the same even if the coil bodies are rotated by 180 degrees around the axis.

Here, the magnetomotive force Fu1a of the partial winding + U11, + U12, the magnetomotive force Fu1b of the partial winding-U13, -U14, the magnetomotive force Fu2a of the partial winding + U22, + U23, and the magnetomotive force Fu2b of the partial winding-U21, -U24. Can be expressed by mathematical formulas (1) to (4). Note that "θ" is the phase of the current flowing through the stator winding 32 (based on the phase of the U-phase current supplied from the first inverter circuit 51). “Β” is a phase difference between the current supplied from the first inverter circuit 51 and the current supplied from the second inverter circuit 52 (hereinafter, may be referred to as a current phase difference). Further, "N" is the number of turns of each partial winding.

Similarly, the magnetomotive force Fv1a of the partial winding + V12, + V13, the magnetomotive force Fv1b of the partial winding-V11, -V14, the magnetomotive force Fv2a of the partial winding + V21, + V24, and the magnetomotive force Fv2b of the partial winding-V22, -V23. Can be expressed by mathematical formulas (5) to (8).

Similarly, the magnetomotive force Fw1a of the partial winding + W11, + W14, the magnetomotive force Fw1b of the partial winding-W12, -W13, the magnetomotive force Fw2a of the partial winding + W21, + W24, and the magnetomotive force Fw2b of the partial winding-W22, -W23. Can be expressed by mathematical formulas (9) to (12).

By the way, the sixth harmonic component "Tr6" of the torque in each phase can be expressed by the mathematical formula (13). Further, the 12th harmonic component "Tr12" of the torque in each phase can be expressed by the mathematical formula (14).

In the mathematical formulas (13) and (14), α is a constant and depends on noise and the like. Further, in the first embodiment, the first term of the mathematical formulas (13) and (14) corresponds to the components based on the coil bodies Ua, Va, Wa, and the second term is based on the coil bodies Ub, Vb, Wb. Corresponding to the components, the third term corresponds to the components based on the coil bodies Uc, Vc, Wc.

Further, “λ1” indicates the phase difference of the magnetomotive force of the coil body Ub with respect to the magnetomotive force of the coil body Ua in the U phase. That is, the phase delay of the magnetomotive force of the coil body Ub is shown with reference to the magnetomotive force of the coil body Ua. Similarly, “λ1” indicates the phase difference of the magnetomotive force of the coil body Vb with respect to the magnetomotive force of the coil body Va in the V phase, and in the W phase, the magnetomotive force of the coil body Wb with respect to the magnetomotive force of the coil body Wa. Shows the phase difference of. Similarly, “λ2” indicates the phase difference of the magnetomotive force of the coil body Uc with respect to the magnetomotive force of the coil body Ua in the U phase, and in the V phase, the magnetomotive force of the coil body Vc with respect to the magnetomotive force of the coil body Va. In the W phase, the phase difference of the magnetomotive force of the coil body Wc with respect to the magnetomotive force of the coil body Wa is shown. Further, in the mathematical formulas (13) and (14), "Ta" is a constant proportional to the number of turns of the coil bodies Ua, Va, and Wa and the amplitude of the current. Further, "Tb" is a constant proportional to the number of turns of the coil bodies Ub, Vb, and Wb and the amplitude of the current. Further, "Tc" is a constant proportional to the number of turns of the coil bodies Uc, Vc, and Wc and the amplitude of the current.

Here, when "γ1" and "γ2" are "20 degrees" and "40 degrees" in electrical angle, respectively, and "Ta", "Tb", and "Tc" are the same, the mathematical formula ( As shown in 15), (16) and FIG. 7, it can be seen that each harmonic component of the torque is canceled.

In the present embodiment, the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to 20 degrees in terms of electrical angle. That is, the phase difference between the magnetomotive force of the coil bodies Ua, Va, and Wa and the magnetomotive force of the coil bodies Ub, Vb, and Wb is 20 degrees, and "λ1" is 20 degrees. Therefore, it can be said that torque ripple can be suppressed by setting the phase difference between the magnetomotive forces of the coil bodies Ua, Va, and Wa to the magnetomotive forces of the coil bodies Uc, Vc, and Wc to be 40 degrees.

That is, the phase difference between the magnetomotive forces of the coils Ua, Va, and Wa and the magnetomotive forces of the coils Ub, Vb, and Wb, and the magnetomotive forces of the coils Uc, Vc, and Wc with respect to the magnetomotive forces of the coils Ub, Vb, and Wb. The phase difference of each of the above may be set to 20 degrees. The phase difference is preferably 20 degrees, but may be a predetermined phase range including 20 degrees (for example, a range of 15 to 25 degrees), and even in this case, the effect of suppressing torque ripple can be obtained.

Therefore, in the present embodiment, the phase difference between the magnetomotive forces of the coils Uc, Vc, and Wc with respect to the magnetomotive forces of the coils Ua, Va, and Wa is 40 degrees (with respect to the magnetomotive forces of the coils Ub, Vb, and Wb). The magnetomotive force generated by the partial winding of the first stator winding 32a wound around each first tooth (so that the phase difference between the magnetomotive forces of the coils Uc, Vc, and Wc is 20 degrees) The phase difference from the magnetomotive force generated by the partial winding of the second stator winding 32b is set to be within the range of 72 to 88 degrees in terms of electric angle. In the following, the phase difference of the magnetomotive force of the partial winding of the second stator winding 32b is set with respect to the partial winding of the first stator winding 32a wound around each first tooth. , May be indicated as a total phase difference.

The total phase difference is in the range of 72 to 88 degrees in terms of electrical angle, but it is desirable to set it to 80 degrees. In this embodiment, the total phase difference is set to be 80 degrees.

The total of the magnetomotive forces will be described in detail by exemplifying the coil body Uc provided in the teeth T9, which is the first teeth. As shown in FIGS. 2 and 4, the coil body Uc provided in the teeth T9 is composed of a partial winding + U12 / −W22. The magnetomotive force Fu1a of the partial winding + U12 and the magnetomotive force Fw2b of the partial winding −W22 are as shown in the equations (1) and (12). When these magnetomotive forces are represented by a vector diagram, it is as shown in FIG. Then, when the magnetomotive force Fu1a of the partial winding + U12 and the magnetomotive force Fw2b of the partial winding −W22 are added together, the formula (17) is obtained.

In the formula (17), the number of turns of the partial winding + U12 and the number of turns of the partial winding −W22 are both set to N. As shown in the formula (17), by winding the partial winding + U12 and the partial winding-W22 around the teeth T9, the coil body Ua, Va, Wa has a phase difference of 40 degrees with respect to the magnetomotive force. The magnetomotive forces of the bodies Uc, Vc, and Wc can be realized.

By the way, as shown in the formula (17), the magnetomotive force is proportional to the number of turns of the partial winding. Therefore, if the number of turns of each partial winding is not set appropriately, the amplitudes of the magnetomotive forces will not be uniform between the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc. .. That is, in the mathematical formulas (13) and (14), the constants "Ta", "Tb", and "Tc" vary. If the amplitudes of the magnetomotive forces are not uniform, the canceling effect of torque ripple is reduced. Therefore, it is desirable to set the number of turns so that the amplitude of the magnetomotive force of each coil body Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, Wc is within a predetermined amplitude range.

Therefore, in the present embodiment, in order to align the magnetomotive force of the coil bodies Ua, Va, Wa with the magnetomotive force of the coil bodies Ub, Vb, Wb, the coil bodies Ua, Va, Wa and the coil bodies Ub, Vb, Wb The number of turns is the same as the number of turns "Na".

Further, the first stator wound around each first tooth so that the magnetomotive forces of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc of each phase are about the same. The number of turns of the winding 32a and the number of turns of the second stator winding 32b are set.

Specifically, when the number of turns of the first stator winding 32a wound around the first tooth and the number of turns of the second stator winding 32b are set to "Nb", 1.4. The number of turns "Na" and "Nb" are set so as to satisfy the relationship of ≤Na / Nb≤1.6. It is preferable that the value of Na / Nb approaches 1.53, and in this embodiment, the number of turns is set so that the ratio of Na: Nb is 3: 2 (Na / Nb is 1.5). ing.

By the way, when the number of turns is set in this way, the number of turns of the stator winding 32 wound around the first tooth is wound around the second tooth (the second A tooth or the second B tooth). This is larger than the number of turns of the stator winding 32. Specifically, the number of turns increases at a ratio of 4: 3.

Further, as shown in FIG. 2 and the like, at least two second teeth are continuously provided in the circumferential direction, and two first teeth are provided at equal intervals in the circumferential direction. .. That is, in the circumferential direction, the second teeth are arranged on both sides of the first teeth. The second A teeth are arranged between the first teeth and the second B teeth, and the second B teeth are arranged between the first teeth and the second A teeth.

Therefore, as shown in the comparative example of FIG. 10, when all the teeth have the same circumferential spacing (pitch) (that is, all the circumferential spacing θ0) and the sizes (and spacings) of all the slots are equalized. , The following problems occur. That is, it is formed between the slot S1 formed between the first teeth having a large number of turns and the second teeth having a small number of turns of the stator winding 32, and the second teeth having a small number of turns. The space factor is different from that of the slot S2. That is, even when the stator windings 32 are arranged in the slot S1 by the number that can be arranged (when the stator windings 32 are arranged so that the gap becomes as small as possible), a gap is formed in the slot S2. Therefore, the space factor is lower than that of slot S1. As a result, the stator 30 as a whole has a large gap in the slot 35, and the space factor is lowered.

Here, the space factor is the ratio of the area of the conducting wire (however, the portion of the conductive material excluding the insulating material including the insulating film) to the area of the slot 35. The area of the slot 35 is the area of a portion that can accommodate the lead wire. For example, as shown in FIG. 13, in the radial direction, the collar provided from the back yoke 33 to the tips of the teeth T1 to T18. It is a portion L10 up to the radial inner portion of the portion 70, and is a portion L20 between adjacent teeth T1 to T18 in the circumferential direction.

Therefore, in the present embodiment, as shown in FIG. 11, the first distance θ1 between the first teeth and the second teeth in the circumferential direction is set to the second distance θ2 between the second teeth in the circumferential direction. Compared to it, it is wider. In the present embodiment, the first spacing θ1 and the second spacing θ2 are set so that the space factors in each slot 35 approach evenly as compared with the comparative example shown in FIG.

Further, as described above, when the first interval θ1 and the second interval θ2 are set differently, usually, as in the comparative example shown in FIG. 12, between the flange portions 70 adjacent to each other in the circumferential direction. The intervals are also non-uniform. That is, the third distance θ30 in the circumferential direction between the flange portion 70a provided on the first tooth and the flange portion 70b provided on the second tooth is set between the flange portions 70b provided on the second tooth. It tends to be larger than the fourth interval θ40 in the circumferential direction. Alternatively, although not shown, the width dimension (L30) of the flange portion 70 in the circumferential direction may be non-uniform. In this case, as shown in FIG. 14, the cogging torque will increase. In FIG. 14, the cogging torque in the comparative example of FIG. 12 is shown by the broken line f1.

Therefore, in the present embodiment, as shown in FIG. 13, which is a partially enlarged view of FIG. 11, the flange portion 70a provided in the first tooth is provided in the circumferential width dimension L11 and the second tooth. The ratio of the flange portion 70b to the circumferential width dimension L12 is set to be closer to 1 than the ratio of the first spacing θ1 and the second spacing θ2. More specifically, the circumferential width dimension L11 of the flange portion 70a and the circumferential width dimension L12 of the flange portion 70b are set to be the same.

Further, as shown in FIG. 13, a third distance θ3 in the circumferential direction between the flange portion 70a provided on the first tooth and the flange portion 70b provided on the second tooth, and the second tooth are provided. The ratio of the flange portion 70b to the fourth spacing θ4 in the circumferential direction is set closer to 1 than the ratio of the first spacing θ1 to the second spacing θ2. More specifically, the third interval θ3 and the fourth interval θ4 are set to be the same. By configuring as in the present embodiment, the cogging torque can be suppressed as shown by the solid line f2 in FIG.

As described above, according to the configuration of the first embodiment, it has the following effects.

The first distance θ1 between the first teeth and the second teeth in the circumferential direction is set to be wider than the second distance θ2 between the second teeth in the circumferential direction. As a result, the space factor in the slot 35 between the first teeth and the second teeth can be improved, and the space ratio in the slot 35 between the second teeth can be improved. Thereby, the total space factor in the stator 30 can be improved.

Further, the ratio of the circumferential width dimension L11 of the flange portion 70a to the circumferential width dimension L12 of the flange portion 70b is closer to 1 than the ratio of the first spacing θ1 and the second spacing θ2. Was set. More specifically, the circumferential width dimension L11 of the flange portion 70a and the circumferential width dimension L12 of the flange portion 70b are set to be the same.

Further, the ratio of the third interval θ3 and the fourth interval θ4 is set to be closer to 1 than the ratio of the first interval θ1 and the second interval θ2. More specifically, the third interval θ3 and the fourth interval θ4 are set to be the same. As a result, as shown in FIG. 14, the cogging torque can be suppressed.

Phase difference of the magnetomotive force of the coil bodies Ub, Vb, Wb with respect to the magnetomotive force of the coil bodies Ua, Va, Wa, and each phase difference of the magnetomotive force of the coil bodies Uc, Vc, Wc with respect to the magnetomotive force of the coil bodies Ub, Vb, Wb. Was within a predetermined phase range including 20 degrees. Specifically, the second fixation wound around the first tooth with respect to the magnetomotive force generated by the partial winding of the first stator winding 32a wound around each first tooth. The phase difference (total phase difference) of the magnetomotive force generated by the partial winding of the child winding 32b was set to be in the range of 72 to 88 degrees in terms of electric angle. In this embodiment, the total phase difference is set to 80 degrees. As a result, as shown in the formulas (15) to (17), it is possible to cancel the 6th or 12th harmonic component of the torque and suppress the torque ripple.

The number of turns of each partial winding is set so that the magnetomotive force of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc is within a predetermined amplitude range (similar in this embodiment). bottom. Specifically, when the number of turns of the first stator winding 32a wound around the second A tooth is set to the number of turns "Na", the second stator winding wound around the second B tooth The number of turns of the wire 32b is defined as "Na". When the number of turns of the first stator winding 32a wound around the first tooth and the number of turns of the second stator winding 32b are set to "Nb", 1.4 ≦ Na. The number of turns was set so as to satisfy the relationship of / Nb ≦ 1.6. In this embodiment, the number of turns is set so that Na: Nb has a ratio of 3: 2 (Na / Nb is 1.5). As a result, the amplitude of the magnetomotive force of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc can be made to the same level, and torque ripple can be suppressed.

In the motor 10, the number of magnetic poles is "14" and the number of slots 35 is "18". That is, the number of magnetic poles was (18 ± 4) × m (m is an integer of 1 or more), and the number of slots was 18 × m. As a result, the electromagnetic force can be balanced around the axis.

This will be described in detail with reference to FIG. FIG. 9A is a diagram showing the relationship between the electromagnetic force generated by each of the teeth T1 to T18 and the mechanical angle of the motor 10. FIG. 9B shows the fluctuation of the electromagnetic force shown in FIG. 9A along the circumferential direction when the rotation axis 11 is centered.

As shown in FIG. 4, U-phase coil bodies Ua, Ub, and Uc are arranged at intervals of about 90 degrees. The same applies to the V-phase coil bodies Va, Vb, Vc and the W-phase coil bodies Wa, Wb, Wc. Therefore, as shown in FIG. 9, the balance of the electromagnetic force is improved. Therefore, the electromagnetic force is not biased somewhere, torque fluctuation can be suppressed, and vibration and noise can be suppressed.

The number of magnetic poles is "14", the number of slots is "18", and the magnetomotive force generated by the partial winding of the first stator winding 32a wound around the first tooth and the first one. The total phase difference with the magnetomotive force generated by the partial winding of the second stator winding 32b wound around the teeth was set to 80 degrees in terms of electrical angle. As a result, the partial windings are arranged as shown in FIGS. 2 and 4. As shown in FIGS. 2 and 4, the first stator winding 32a wound around the first teeth is wound around one of the teeth T1 to T18 adjacent to each other in the circumferential direction. It becomes possible to connect with the child winding 32a. For example, the partial winding-U14 of the first stator winding 32a wound around the first teeth T18 is wound around the second A teeth T1 adjacent in the circumferential direction. It becomes possible to connect with the partial winding + U11 of the stator winding 32a of 1.

Similarly, the second stator winding 32b wound around the first tooth is connected to the second stator winding 32b wound around the other of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible. For example, the partial winding + W24 of the second stator winding 32b wound around the first teeth T18 is wound around the second teeth T17 adjacent to the circumferential direction. It becomes possible to connect to the partial winding-W23 of the stator winding 32b of. As a result, at the coil end, the crossover for connecting the slots 35 can be shortened, the connection can be facilitated, and the size can be reduced.

As shown in FIG. 6, the leader lines A1, B1, C1, A2, B2, and C2 are arranged so that their phases are symmetrical with respect to the axis of the rotating shaft 11. As a result, the leakage flux generated from the leader lines A1, B1, C1, A2, B2, and C2 can be balanced and canceled, so that the detection error of the angle sensor 12 can be suppressed.

(Second Embodiment)
In the first embodiment, the total phase difference is 80 degrees, but in the second embodiment, the total phase difference is 40 degrees. That is, in the second embodiment, the coil body Ua, Va, and Wa are wound around each first tooth so that the phase difference between the magnetomotive forces of the coil bodies Uc, Vc, and Wc is 40 degrees. The total phase difference of the magnetomotive force generated by the partial winding of the second stator winding 32b is 40 degrees with respect to the magnetomotive force generated by the partial winding of the first stator winding 32a. It is set. It is preferably 40 degrees, but it may be changed within the range of 32 to 48 degrees.

In this case, the arrangement of the partial windings of each phase will be as shown in FIGS. 15 and 16. Here, the coil body Uc provided in the teeth T9 will be illustrated to explain that the total phase difference is 40 degrees.

As shown in FIG. 15, the coil body Uc provided in the teeth T9 is composed of a partial winding −W12 / + U22. The magnetomotive force Fw1b of the partial winding −W12 and the magnetomotive force Fu2a of the partial winding + U22 are as shown in the equations (10) and (3). When these are represented by a vector diagram, it is as shown in FIG. Then, the sum of the magnetomotive force Fw1b of the partial winding −W12 and the magnetomotive force Fu2a of the partial winding + U22 is shown in the equation (18).

In the formula (18), the number of turns of the partial winding −W12 and the number of turns of the partial winding + U22 are both set to N. As shown in the formula (18), by winding the partial winding −W12 and the partial winding + U22 around the teeth T9, the phase difference (total phase difference) with respect to the magnetomotive force of the coil bodies Ua, Va, and Wa is increased. It is possible to realize the magnetomotive force of the coil bodies Uc, Vc, and Wc which are 40 degrees.

By the way, as shown in the equation (18), the magnetomotive force is proportional to the number of turns of the partial winding. Therefore, if the number of turns of each partial winding is not set appropriately, the amplitudes of the magnetomotive forces will not be uniform between the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc. ..

Therefore, in the second embodiment, the number of turns of the coil bodies Ua, Va, Wa and the coil bodies Ub, Vb, Wb are both set to the same number of turns "Na", and the first stator wound around the first tooth. When the number of turns of the winding 32a and the number of turns of the second stator winding 32b are "Nb", the number of turns "Na" so as to satisfy the relationship of 1.8 ≤ Na / Nb ≤ 2.0. And "Nb" are set. It is preferable that the value of Na / Nb approaches 1.88, and in this embodiment, the number of turns is set so that the ratio of Na: Nb is 19:10 (Na / Nb is 1.9). ing.

Further, in this case as well, it is desirable that the first interval θ1 is wider than the second interval θ2, as in the first embodiment. That is, it is desirable to set the first spacing θ1 and the second spacing θ2 so that the space factors in each slot 35 approach evenly. Thereby, the space factor can be improved.

Further, as in the first embodiment, the ratio of the circumferential width dimension L11 of the flange portion 70a to the circumferential width dimension L12 of the flange portion 70b is the ratio of the first spacing θ1 and the second spacing θ2. It is desirable to set it so that it is close to 1 in comparison. More specifically, it is desirable to set the peripheral width dimension L11 of the flange portion 70a and the circumferential width dimension L12 of the flange portion 70b to be the same.

Similarly, the ratio of the third interval θ3 and the fourth interval θ4 may be set to be closer to 1 than the ratio of the first interval θ1 and the second interval θ2. desirable. More specifically, it is desirable to set the third interval θ3 and the fourth interval θ4 to be the same. Thereby, the cogging torque can be suppressed.

As described above, according to the configuration of the second embodiment, it has the following effects.

Phase difference of the magnetomotive force of the coil bodies Ub, Vb, Wb with respect to the magnetomotive force of the coil bodies Ua, Va, Wa, and each phase difference of the magnetomotive force of the coil bodies Uc, Vc, Wc with respect to the magnetomotive force of the coil bodies Ub, Vb, Wb. Was within a predetermined phase range including 20 degrees. Specifically, the second stator wound around the first tooth with respect to the magnetomotive force generated by the partial winding of the first stator winding 32a wound around the first tooth. The total phase difference of the magnetomotive force generated by the partial winding of the winding 32b was set to be 40 degrees. That is, the total phase difference was set to be 40 degrees. As a result, as shown in the mathematical formulas (15), (16) and (18), it is possible to cancel the 6th or 12th harmonic component of the torque and suppress the torque ripple.

Further, the number of turns was set so as to satisfy the relationship of 1.8 ≦ Na / Nb ≦ 2.0. In this embodiment, the number of turns is set so that the ratio of Na: Nb is 19:10 (Na / Nb is 1.9). As a result, the amplitude of the magnetomotive force of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc can be made to the same level, and torque ripple can be suppressed.

In the motor 10, the number of magnetic poles is "14" and the number of slots 35 is "18". That is, the number of magnetic poles was (18 ± 4) × m (m is an integer of 1 or more), and the number of slots was 18 × m. As a result, the electromagnetic force can be balanced around the axis as in the first embodiment.

(Third Embodiment)
In the first embodiment, the current phase difference “β” between the first inverter circuit 51 and the second inverter circuit 52 is set to 20 degrees in terms of electrical angle, but in the third embodiment, it is set to 40 degrees. That is, the phase difference between the magnetomotive force of the coil bodies Ua, Va, and Wa and the magnetomotive force of the coil bodies Ub, Vb, and Wb is 40 degrees.

Therefore, in the third embodiment, in the mathematical formulas (13) and (14), the first term corresponds to the components based on the coil bodies Ua, Va, Wa, and the second term corresponds to the coil bodies Uc, Vc, Wc. Corresponds to the component based on, and corresponds to the component based on the coil bodies Ub, Vb, Wb.

Then, in the third embodiment, "λ1" indicates the phase difference of the magnetomotive force of the coil body Uc with respect to the magnetomotive force of the coil body Ua in the U phase, and the coil with respect to the magnetomotive force of the coil body Va in the V phase. The phase difference of the magnetomotive force of the body Vc is shown, and in the W phase, the phase difference of the magnetomotive force of the coil body Wc with respect to the magnetomotive force of the coil body Wa is shown. Similarly, “λ2” indicates the phase difference of the magnetomotive force of the coil body Ub with respect to the magnetomotive force of the coil body Ua in the U phase, and in the V phase, the magnetomotive force of the coil body Vb with respect to the magnetomotive force of the coil body Va. In the W phase, the phase difference of the magnetomotive force of the coil body Wb with respect to the magnetomotive force of the coil body Wa is shown. Further, in the mathematical formulas (13) and (14), "Ta" is a constant proportional to the number of turns of the coil bodies Ua, Va, and Wa and the amplitude of the current. “Tb” is a constant proportional to the number of turns of the coil bodies Uc, Vc, and Wc and the amplitude of the current. “Tc” is a constant proportional to the number of turns of the coil bodies Ub, Vb, and Wb and the amplitude of the current.

Therefore, if the phase difference between the magnetomotive forces of the coil bodies Ua, Va, and Wa and the magnetomotive forces of the coil bodies Uc, Vc, and Wc is set to 20 degrees, the torque ripple is suppressed by the mathematical formulas (15) and (16). It can be said that it can be done.

That is, the phase difference between the magnetomotive forces of the coils Ua, Va, and Wa and the magnetomotive forces of the coils Uc, Vc, and Wc, and the magnetomotive forces of the coils Ub, Vb, and Wb with respect to the magnetomotive forces of the coils Uc, Vc, and Wc. The phase difference of each of the above may be set to 20 degrees. The phase difference is preferably 20 degrees, but may be a predetermined phase range including 20 degrees (for example, a range of 15 to 25 degrees), and even in this case, the effect of suppressing torque ripple can be obtained.

Therefore, in the third embodiment, the magnetomotive force generated by the partial winding of the first stator winding 32a wound around each first tooth and the partial winding of the second stator winding 32b generate. The phase difference from the magnetomotive force is set to be in the range of 72 to 88 degrees in terms of electrical angle. That is, the total phase difference is set to be in the range of 72 to 88 degrees in electrical angle. In the third embodiment as well, it is desirable that the total phase difference is 80 degrees as in the first embodiment.

Specifically, as shown in FIG. 18, partial windings are arranged in each of the teeth T1 to T18. With this configuration, the phase difference between the magnetomotive forces of the coil bodies Ua, Va, and Wa and the magnetomotive forces of the coil bodies Uc, Vc, and Wc, and the coil body Ub with respect to the magnetomotive forces of the coil bodies Uc, Vc, and Wc, The phase difference between the magnetomotive forces of Vb and Wb can be set to 20 degrees, respectively. Further, as in the first embodiment, in order to align the magnetomotive forces of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc, the ratio of Na: Nb is 3: 2 (Na / Nb). The number of turns is set so that is 1.5).

Further, in this case as well, it is desirable to set the first interval θ1 and the second interval θ2, respectively, as in the first embodiment. Thereby, the space factor can be improved. Further, it is desirable to set the circumferential width dimension L11 of the flange portion 70a, the circumferential width dimension L12 of the flange portion 70b, the third spacing θ3, and the fourth spacing θ4, as in the first embodiment. Thereby, the cogging torque can be suppressed.

With the above configuration, the third embodiment can obtain the same effect as the first embodiment.

(Fourth Embodiment)
In the fourth embodiment, the current phase difference "β" of the inverter circuits 51 and 52 is set to 40 degrees, and the total phase difference is set to 40 degrees unlike the third embodiment. That is, the magnetomotive force generated by the partial winding of the first stator winding 32a wound around each first tooth and the magnetomotive force generated by the partial winding of the second stator winding 32b. The phase difference is set to be 40 degrees. As in the second embodiment, it is preferably 40 degrees, but it may be changed within the range of 32 to 48 degrees.

Specifically, as shown in FIG. 19, partial windings are arranged in each of the teeth T1 to T18. With this configuration, the phase difference between the magnetomotive forces of the coil bodies Ua, Va, and Wa and the magnetomotive forces of the coil bodies Uc, Vc, and Wc, and the coil body Ub with respect to the magnetomotive forces of the coil bodies Uc, Vc, and Wc, The phase difference between the magnetomotive forces of Vb and Wb can be set to 20 degrees, respectively. Further, for the same reason as in the second embodiment, in order to align the magnetomotive forces of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc, the ratio of Na: Nb is 19:10 (Na). The number of turns is set so that / Nb is 1.9).

Further, in this case as well, it is desirable to set the first interval θ1 and the second interval θ2, respectively, as in the first embodiment. Thereby, the space factor can be improved. Further, it is desirable to set the circumferential width dimension L11 of the flange portion 70a, the circumferential width dimension L12 of the flange portion 70b, the third spacing θ3, and the fourth spacing θ4, as in the first embodiment. Thereby, the cogging torque can be suppressed.

As described above, the fourth embodiment can obtain the same effect as the second embodiment.

(Other embodiments)
Each of the above embodiments may be changed as follows.

In the above embodiment, the number of magnetic poles is set to "22", the number of slots is set to "18", and the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to "20 degrees". , And the total phase difference may be set to "80 degrees". FIG. 20 shows an example of the arrangement of the partial windings in this case.

In this case, as shown in FIG. 20, the first stator winding 32a wound around the first teeth is wound around one of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible to connect with the child winding 32a. For example, the partial winding-U12 of the first stator winding 32a wound around the first teeth T2 in this example is wound around the second A teeth T1 adjacent in the circumferential direction. It becomes possible to connect with the partial winding + U11 of the first stator winding 32a to be formed.

Similarly, the second stator winding 32b wound around the first tooth is connected to the second stator winding 32b wound around the other of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible. For example, the partial winding + W21 of the second stator winding 32b wound around the first teeth T2 in this example is wound around the second B teeth T3 adjacent in the circumferential direction. It becomes possible to connect to the partial winding-W22 of the second stator winding 32b. As a result, at the coil end, the crossover for connecting the slots 35 can be shortened, the connection can be facilitated, and the size can be reduced.

In the above embodiment, the number of magnetic poles is set to "22", the number of slots is set to "18", and the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to "20 degrees". , And the total phase difference may be set to "40 degrees". FIG. 20 shows an example of the arrangement of the partial windings in this case.

In the above embodiment, the number of magnetic poles is set to "22", the number of slots is set to "18", and the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to "40 degrees". , And the total phase difference may be set to "80 degrees". FIG. 20 shows an example of the arrangement of the partial windings in this case.

In this case, as shown in FIG. 20, the first stator winding 32a wound around the first teeth is wound around one of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible to connect with the child winding 32a. For example, the partial winding + V11 of the first stator winding 32a wound around the first teeth T3 in this example is wound around the second A teeth T4 adjacent in the circumferential direction. It becomes possible to connect to the partial winding-V12 of the first stator winding 32a.

Similarly, the second stator winding 32b wound around the first tooth is connected to the second stator winding 32b wound around the other of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible. For example, the partial winding + U22 of the second stator winding 32b wound around the first teeth T3 in this example is wound around the second B teeth T2 adjacent in the circumferential direction. It becomes possible to connect to the partial winding-U21 of the second stator winding 32b. As a result, at the coil end, the crossover for connecting the slots 35 can be shortened, the connection can be facilitated, and the size can be reduced.

In the above embodiment, the number of magnetic poles is set to "22", the number of slots is set to "18", and the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to "40 degrees". , And the total phase difference may be set to "40 degrees". FIG. 20 shows an example of the arrangement of the partial windings in this case.

In the above embodiment, the number of magnetic poles is set to "16", the number of slots is set to "18", and the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to "20 degrees". , And the total phase difference may be set to "80 degrees". FIG. 21 shows an example of the arrangement of the partial windings in this case.

In this case, as shown in FIG. 21, the first stator winding 32a wound around the first teeth is wound around the two adjacent teeth T1 to T18 in the circumferential direction. It becomes possible to connect with the winding 32a. For example, the partial winding + V11 of the first stator winding 32a wound around the first teeth T2 in this example is wound around the second A teeth T4 adjacent to each other in the circumferential direction. It becomes possible to connect to the partial winding + V12 of the first stator winding 32a to be turned.

Similarly, connecting the second stator winding 32b wound around the first tooth to the second stator winding 32b wound around two adjacent teeth T1 to T18 in the circumferential direction. Is possible. For example, the partial winding-U21 of the second stator winding 32b wound around the first teeth T2 in this example is placed on the second B teeth T18 adjacent to each other in the circumferential direction. It becomes possible to connect to the partial winding-U24 of the second stator winding 32b to be wound. As a result, at the coil end, the crossover for connecting the slots 35 can be shortened, the connection can be facilitated, and the size can be reduced.

In the above embodiment, the number of magnetic poles is set to "16", the number of slots is set to "18", and the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to "20 degrees". , And the total phase difference may be set to "40 degrees". FIG. 21 shows an example of the arrangement of the partial windings in this case.

In this case, as shown in FIG. 21, the first stator winding 32a wound around the first teeth is wound around one of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible to connect with the child winding 32a. For example, the partial winding-U12 of the first stator winding 32a wound around the first teeth T2 in this example is wound around the second A teeth T1 adjacent in the circumferential direction. It becomes possible to connect with the partial winding + U11 of the first stator winding 32a to be formed.

Similarly, the second stator winding 32b wound around the first tooth is connected to the second stator winding 32b wound around the other of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible. For example, the partial winding + V21 of the second stator winding 32b wound around the first teeth T2 in this example is wound around the second B teeth T3 adjacent in the circumferential direction. It becomes possible to connect to the partial winding-V22 of the second stator winding 32b. As a result, at the coil end, the crossover for connecting the slots 35 can be shortened, the connection can be facilitated, and the size can be reduced.

In the above embodiment, the number of magnetic poles is set to "16", the number of slots is set to "18", and the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to "40 degrees". , And the total phase difference may be set to "80 degrees". FIG. 21 shows an example of the arrangement of the partial windings in this case.

In this case, as shown in FIG. 21, the first stator winding 32a wound around the first teeth is wound around the two adjacent teeth T1 to T18 in the circumferential direction. It becomes possible to connect with the winding 32a. For example, the partial winding + U12 of the first stator winding 32a wound around the first teeth T3 in this example is wound around the second A teeth T1 adjacent to each other in the circumferential direction. It becomes possible to connect with the partial winding + U11 of the first stator winding 32a to be turned.

Similarly, connecting the second stator winding 32b wound around the first tooth to the second stator winding 32b wound around two adjacent teeth T1 to T18 in the circumferential direction. Is possible. For example, the partial winding + W21 of the second stator winding 32b wound around the first teeth T3 in this example is wound around the second B teeth T5 adjacent to each other in the circumferential direction. It becomes possible to connect to the partial winding + W22 of the second stator winding 32b to be turned. As a result, at the coil end, the crossover for connecting the slots 35 can be shortened, the connection can be facilitated, and the size can be reduced.

In the above embodiment, the number of magnetic poles is set to "16", the number of slots is set to "18", and the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to "40 degrees". , And the total phase difference may be set to "40 degrees". FIG. 21 shows an example of the arrangement of the partial windings in this case.

In this case, as shown in FIG. 21, the first stator winding 32a wound around the first teeth is wound around one of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible to connect with the child winding 32a. For example, the partial winding-V11 of the first stator winding 32a wound around the first teeth T3 in this example is wound around the second A teeth T4 adjacent in the circumferential direction. It becomes possible to connect with the partial winding + V12 of the first stator winding 32a to be formed.

Similarly, the second stator winding 32b wound around the first tooth is connected to the second stator winding 32b wound around the other of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible. For example, the partial winding-V22 of the second stator winding 32b wound around the first teeth T3 in this example is wound around the second B teeth T2 adjacent in the circumferential direction. It becomes possible to connect with the partial winding + V21 of the second stator winding 32b. As a result, at the coil end, the crossover for connecting the slots 35 can be shortened, the connection can be facilitated, and the size can be reduced.

In the above embodiment, the number of magnetic poles is set to "20", the number of slots is set to "18", and the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to "20 degrees". , And the total phase difference may be set to "80 degrees". FIG. 22 shows an example of the arrangement of the partial windings in this case.

In this case, as shown in FIG. 22, the first stator winding 32a wound around the first teeth is wound around the two adjacent teeth T1 to T18 in the circumferential direction. It becomes possible to connect with the winding 32a. For example, the partial winding + U12 of the first stator winding 32a wound around the first teeth T3 in this example is wound around the second A teeth T1 adjacent to each other in the circumferential direction. It becomes possible to connect with the partial winding + U11 of the first stator winding 32a to be turned.

Similarly, connecting the second stator winding 32b wound around the first tooth to the second stator winding 32b wound around two adjacent teeth T1 to T18 in the circumferential direction. Is possible. For example, the partial winding-W21 of the second stator winding 32b wound around the first teeth T3 in this example is placed on the second B teeth T5 adjacent to each other in the circumferential direction. It becomes possible to connect to the partial winding-W22 of the second stator winding 32b to be wound. As a result, at the coil end, the crossover for connecting the slots 35 can be shortened, the connection can be facilitated, and the size can be reduced.

In the above embodiment, the number of magnetic poles is set to "20", the number of slots is set to "18", and the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to "20 degrees". , And the total phase difference may be set to "40 degrees". FIG. 22 shows an example of the arrangement of the partial windings in this case.

In this case, as shown in FIG. 22, the first stator winding 32a wound around the first teeth is wound around one of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible to connect with the child winding 32a. For example, the partial winding-W11 of the first stator winding 32a wound around the first teeth T3 in this example is wound around the second A teeth T4 adjacent in the circumferential direction. It becomes possible to connect with the partial winding + W12 of the first stator winding 32a to be formed.

Similarly, the second stator winding 32b wound around the first tooth is connected to the second stator winding 32b wound around the other of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible. For example, the partial winding + U22 of the second stator winding 32b wound around the first teeth T3 in this example is wound around the second B teeth T2 adjacent in the circumferential direction. It becomes possible to connect to the partial winding-U21 of the second stator winding 32b. As a result, at the coil end, the crossover for connecting the slots 35 can be shortened, the connection can be facilitated, and the size can be reduced.

In the above embodiment, the number of magnetic poles is set to "20", the number of slots is set to "18", and the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to "40 degrees". , And the total phase difference may be set to "80 degrees". FIG. 22 shows an example of the arrangement of the partial windings in this case.

In this case, as shown in FIG. 22, the first stator winding 32a wound around the first teeth is wound around the two adjacent teeth T1 to T18 in the circumferential direction. It becomes possible to connect with the winding 32a. For example, the partial winding + W11 of the first stator winding 32a wound around the first teeth T2 in this example is wound around the second A teeth T4 adjacent to each other in the circumferential direction. It becomes possible to connect to the partial winding + W12 of the first stator winding 32a to be turned.

Similarly, connecting the second stator winding 32b wound around the first tooth to the second stator winding 32b wound around two adjacent teeth T1 to T18 in the circumferential direction. Is possible. For example, the partial winding + V21 of the second stator winding 32b wound around the first teeth T2 in this example is wound around the second B teeth T18 adjacent to each other in the circumferential direction. It becomes possible to connect to the partial winding + V24 of the second stator winding 32b to be turned. As a result, at the coil end, the crossover for connecting the slots 35 can be shortened, the connection can be facilitated, and the size can be reduced.

In the above embodiment, the number of magnetic poles is set to "20", the number of slots is set to "18", and the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to "40 degrees". , And the total phase difference may be set to "40 degrees". FIG. 22 shows an example of the arrangement of the partial windings in this case.

In this case, as shown in FIG. 22, the first stator winding 32a wound around the first teeth is wound around one of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible to connect with the child winding 32a. For example, the partial winding-U12 of the first stator winding 32a wound around the first teeth T2 in this example is wound around the second A teeth T1 adjacent in the circumferential direction. It becomes possible to connect with the partial winding + U11 of the first stator winding 32a to be formed.

Similarly, the second stator winding 32b wound around the first tooth is connected to the second stator winding 32b wound around the other of the teeth T1 to T18 adjacent in the circumferential direction. It becomes possible. For example, the partial winding-U21 of the second stator winding 32b wound around the first teeth T2 in this example is wound around the second B teeth T3 adjacent in the circumferential direction. It becomes possible to connect with the partial winding + U22 of the second stator winding 32b. As a result, at the coil end, the crossover for connecting the slots 35 can be shortened, the connection can be facilitated, and the size can be reduced.

In the above embodiment, the number of magnetic poles may be (18 ± 4) × m (m is an integer of 1 or more), and the number of slots may be 18 × m. Further, the number of magnetic poles may be (18 ± 2) × n (n is an integer of 1 or more), and the number of slots may be 18 × n. When the number of magnetic poles is (18 ± 4) × m (m is an integer of 1 or more) and the number of slots is 18 × m, as described above in FIG. 9, the electromagnetic force is applied at 90 degree intervals. Can be balanced and noise and vibration can be suppressed.

In the above embodiment, the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is preferably "20 degrees" or "40 degrees", but each is 15 to 25 degrees. And may be changed within the range of 35 to 45 degrees.

In the above embodiment, the total phase difference between the first stator winding 32a wound around the first tooth and the second stator winding 32b is "40 degrees" or "80 degrees". It is preferable, but it may be changed within the range of 32 to 48 degrees and the range of 72 to 88 degrees, respectively.

-In the above embodiment, the motor 10 is not limited to the radial gap motor, and may be, for example, an axial gap motor. Further, the motor 10 may be a reluctance motor or an induction motor.

In the above embodiment and the above modification, the magnetomotive force generated by the partial winding of the first stator winding 32a wound around the first tooth and the second winding around the first tooth. Torque ripple was suppressed by setting the total phase difference (total phase difference of the magnetomotive force) from the magnetomotive force generated by the partial winding of the stator winding 32b to be within a predetermined range. Instead of this magnetomotive force summed phase difference, the current flowing through the partial winding of the first stator winding 32a wound around the first tooth and the second stator wound around the first tooth. The total phase difference (current total phase difference) with the current flowing in the partial winding of the winding 32b may be used.

It should be noted that the phase of the current flowing through the partial winding is 180 degrees out of phase depending on the winding direction of the partial winding. That is, even in the same U-phase partial winding, the current flowing in the "+" partial winding and the current flowing in the "-" partial winding are shifted by 180 degrees and the sum of the currents. It is necessary to consider the phase difference.

For example, when the current phase difference "β" of the inverter is 20 degrees, it is a U-phase partial winding, and the phase of the current flowing through the "+" partial winding is the reference phase "θ". , The phase of the current flowing in the "-" partial winding of the V-phase partial winding is "θ-120 (phase shift due to V phase) -20 (shift based on current phase difference β) -180. (Phase shift due to winding direction) ”=“ θ-320 ”.

θ1 ... 1st interval, θ2 ... 2nd interval, 10 ... motor, 30 ... stator, 32 ... stator winding, 40 ... rotor, T1 to T18 ... teeth.

Claims (19)

A field portion (40) having a plurality of magnetic poles having alternating polarities in the circumferential direction, a multi-phase armature winding (32), and a plurality of armature windings (32) provided in the circumferential direction are wound. In an armature having an armature (T1 to T18) to be turned, in a rotating electric machine (10) having an armature (30) having an iron core.
The tees include a first tee in which the armature winding is wound a predetermined number of times, and a second tee in which the number of turns of the armature winding is smaller than that of the first tee. There are multiple,
Two or more of the second teeth are continuously provided in at least the circumferential direction.
The first distance (θ1) between the first teeth and the second teeth in the circumferential direction is wider than the second distance (θ2) between the second teeth in the circumferential direction. .. Each radial tip of the tooth has a facing portion (70, 70a, 70b) facing the field portion, which is wider than the circumferential width dimension of the tooth.
The circumferential width dimension (L11) of the facing portion (70a) provided on the first tooth and the circumferential width dimension (L12) of the facing portion (70b) provided on the second tooth. The ratio is set closer to 1 as compared with the ratio between the first interval and the second interval.
Further, a third distance (θ3) in the circumferential direction between the facing portion provided on the first tooth and the facing portion provided on the second tooth, and the second tooth are provided. According to claim 1, the ratio of the facing portions to the fourth interval (θ4) in the circumferential direction is set closer to 1 than the ratio of the first interval to the second interval. The rotary electric machine described. Each radial tip of the tooth has a facing portion that is wider than the circumferential width dimension of the tooth and faces the field portion.
The rotary electric machine according to claim 1 or 2, wherein the circumferential width dimensions of the facing portions are all the same, and the spacing between the facing portions adjacent to each other in the circumferential direction is the same. The armature winding is supplied with a first armature winding (32a) to which a three-phase current is supplied from the first inverter (51) and a three-phase current supplied from the second inverter (52). There is a second armature winding (32b), which is
The first armature winding and the second armature winding are both wound around the first tooth.
Only either the first armature winding or the second armature winding is wound around the second armature.
In the circumferential direction, the second teeth are arranged on both sides of the first teeth.
The three-phase current supplied from the first inverter and the three-phase current supplied from the second inverter are any of claims 1 to 3 having a predetermined current phase difference (β). The rotary electric machine according to item 1. The rotary electric machine according to claim 4, wherein the predetermined current phase difference (β) is set in the range of 15 to 25 degrees or the range of 35 to 45 degrees. The first armature winding and the second armature winding wound around the first tee are either of the second tees arranged on both sides of the first tee in the circumferential direction. The rotary electric machine according to claim 4 or 5, which is connected to the armature winding wound around the armature, respectively. The armature winding is supplied with a first armature winding (32a) to which a three-phase current is supplied from the first inverter (51) and a three-phase current supplied from the second inverter (52). There is a second armature winding (32b), which is
The three-phase current supplied from the first inverter and the three-phase current supplied from the second inverter each have a predetermined current phase difference (β).
A U-phase coil body Ua formed by winding the first armature winding of the U-phase of the three-phase around the second A of the second teeth.
A V-phase coil body Va formed by winding the first armature winding of the V-phase among the three phases around the second A teeth.
A W-phase coil body Wa formed by winding the first armature winding of the W phase of the three phases around the second A teeth.
A U-phase coil body Ub formed by winding the second armature winding of the U-phase around the second B of the second teeth,
A V-phase coil body Vb formed by winding the second armature winding of the V-phase around the second B teeth,
A W-phase coil body Wb formed by winding the second armature winding of the W-phase around the second B teeth,
The first armature winding of any one of the three phases and the second armature winding of any one of the three phases are wound around the first tooth. The U-phase coil body Uc formed by
The first armature winding of any one of the three phases and the second armature winding of any one of the three phases are wound around the first tooth. V-phase coil body Vc formed by
The first armature winding of any one of the three phases and the second armature winding of any one of the three phases are wound around the first tooth. With a W-phase coil body Wc formed by
The phase difference between the magnetomotive forces of the coils Uc, Vc, and Wc of each phase with respect to the magnetomotive forces of the coils Ua, Va, and Wa of each phase, and the coils of each phase with respect to the magnetomotive forces of the coils Uc, Vc, and Wc of each phase. The phase difference between the magnetomotive forces of the bodies Ub, Vb, and Wb is within a predetermined phase range including 20 degrees in electrical angle.
Alternatively, the phase difference between the electromotive force of the coil bodies Ub, Vb, Wb of each phase with respect to the electromotive force of the coil bodies Ua, Va, Wa of each phase and each phase with respect to the electromotive force of the coil bodies Ub, Vb, Wb of each phase. The first armature wound around the first tooth so that the phase difference between the electromotive forces of the coil bodies Uc, Vc, and Wc of the coil body Uc, Vc, and Wc is within a predetermined phase range including 20 degrees in electric angle. The total phase difference between the electromotive force generated by the partial winding of the winding and the electromotive force generated by the partial winding of the second armature winding wound around the first tooth, or the first. The current flowing through the partial winding of the first armature winding wound around the tooth and the current flowing through the partial winding of the second armature winding wound around the first tooth. The rotary electric machine according to any one of claims 1 to 6, wherein a total phase difference is set. The first coil wound around the second A teeth so that the magnetomotive forces of the coils Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc of each phase are within a predetermined amplitude range. The first armature wound around the first tooth with respect to the number of turns of the armature winding or the number of turns of the second armature winding wound around the second B tooth. The rotary electric machine according to claim 7, wherein the number of turns of the winding and the number of turns of the second armature winding are different. The rotary electric machine according to claim 7 or 8, wherein the total phase difference is set in the range of 72 to 88 degrees in electric angle. The rotary electric machine according to claim 9, wherein the number of magnetic poles in the field portion is (18 ± 4) × m (m is an integer of 1 or more), and the number of slots between the teeth is 18 × m. The rotary electric machine according to claim 9, wherein the number of magnetic poles in the field portion is (18 ± 2) × n (n is an integer of 1 or more), and the number of slots between the teeth is 18 × n. Claim 7 or 8 in which the number of magnetic poles of the field portion is "14" or "22", the number of slots between the teeth is "18", and the total phase difference is 80 degrees in electrical angle. The rotary electric machine described. Claim 7 or 8 in which the number of magnetic poles of the field portion is "16" or "20", the number of slots between the teeth is "18", and the total phase difference is 80 degrees in electrical angle. The rotary electric machine described in the section. The number of turns of the first armature winding wound around the second A tooth and the number of turns of the second armature winding wound around the second B tooth are set to "Na", respectively, and the first When the number of turns of the first armature winding wound around the first tooth and the number of turns of the second armature winding wound around the first tooth are "Nb", respectively, 1 .4 The rotary armature according to any one of claims 9 to 13, wherein the number of turns is set so as to satisfy the relationship of ≤Na / Nb≤1.6. The rotary electric machine according to claim 7 or 8, wherein the total phase difference is set in the range of 32 to 48 degrees in the electric angle. The rotary electric machine according to claim 15, wherein the number of magnetic poles in the field portion is (18 ± 4) × m (m is an integer of 1 or more), and the number of slots between the teeth is 18 × m. The rotary electric machine according to claim 15, wherein the number of magnetic poles in the field portion is (18 ± 2) × n (n is an integer of 1 or more), and the number of slots between the teeth is 18 × n. Claim 7 or 8 in which the number of magnetic poles of the field portion is "16" or "20", the number of slots between the teeth is "18", and the total phase difference is 40 degrees in electrical angle. The rotary electric machine described in the section. The number of turns of the first armature winding wound around the second A tooth and the number of turns of the second armature winding wound around the second B tooth are set to "Na", respectively, and the first When the number of turns of the first armature winding wound around the first tooth and the number of turns of the second armature winding wound around the first tooth are "Nb", respectively, 1 8. The rotary armature according to any one of claims 15 to 18, wherein the number of turns is set so as to satisfy the relationship of 8 ≦ Na / Nb ≦ 2.0.

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