JP2019062640A - Power supply device - Google Patents

Power supply device Download PDF

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JP2019062640A
JP2019062640A JP2017185140A JP2017185140A JP2019062640A JP 2019062640 A JP2019062640 A JP 2019062640A JP 2017185140 A JP2017185140 A JP 2017185140A JP 2017185140 A JP2017185140 A JP 2017185140A JP 2019062640 A JP2019062640 A JP 2019062640A
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Prior art keywords
power supply
capacitor
conversion unit
discharge resistor
supply device
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JP6340463B1 (en
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隆彦 金井
Takahiko Kanai
隆彦 金井
春樹 吉田
Haruki Yoshida
春樹 吉田
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Neturen Co Ltd
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Neturen Co Ltd
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Priority to JP2017185140A priority Critical patent/JP6340463B1/en
Priority to TW106143571A priority patent/TWI644506B/en
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Priority to CN201880026156.3A priority patent/CN110521076B/en
Priority to PCT/JP2018/034913 priority patent/WO2019065472A1/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M5/4585—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
    • H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
    • H02H7/10—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers
    • H02H7/12—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers
    • H02H7/1216—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers for AC-AC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H02M1/322—Means for rapidly discharging a capacitor of the converter for protecting electrical components or for preventing electrical shock
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B6/00—Heating by electric, magnetic or electromagnetic fields
    • H05B6/02—Induction heating

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

To provide a power supply device that makes a capacitor included in a smoothing unit quickly discharge at a time of abnormality and can reduce loss at a normal time.SOLUTION: A power supply device includes: a forward converter 3; a smoothing unit 4; an inverter 5; a housing 7 for accommodating the above; and an abnormality detector for detecting at least one of the forward converter 3, the inverter 5, and the housing 7. The smoothing unit 4 includes: a capacitor 10 connected in parallel to an output of the forward converter 3; a first discharge resistor 12 for discharging the capacitor 10; and a switching element 14 connected in series with the first discharge resistor 12. When abnormality is detected by the abnormality detector, the switching element 14 is closed by the abnormality detector. When the switching element 14 is closed, the capacitor 10 is discharged by the first discharge resistor 12.SELECTED DRAWING: Figure 2

Description

本発明は、電源装置に関する。   The present invention relates to a power supply device.

特許文献１に記載されたインバータ装置は、交流電源から直流電源を生成し、リアクタ及び平滑コンデンサからなる平滑回路を介して出力される直流出力から、インバータ回路のスイッチング素子をオンオフ制御して交流出力を得て、誘導加熱用の加熱コイルに高周波の交流電力を供給する。このインバータ装置では、平滑コンデンサを所定の放電時定数で放電する放電用抵抗が、平滑コンデンサに並列に接続されている。   The inverter device described in Patent Document 1 generates a DC power source from an AC power source, and controls the switching elements of the inverter circuit on / off from a DC output output via a smoothing circuit including a reactor and a smoothing capacitor to perform AC output. And supply high frequency AC power to the heating coil for induction heating. In this inverter device, a discharge resistor that discharges the smoothing capacitor with a predetermined discharge time constant is connected in parallel to the smoothing capacitor.

特許第３４１９６４１号公報Patent No. 3419641

特許文献１に記載されたインバータ装置のように、放電用抵抗が平滑コンデンサに並列に接続されていると、電力が放電用抵抗によって常に消費されてしまう。放電用抵抗によって消費される電力を低減するために放電用抵抗の抵抗値を大きくすると、放電時定数が大きくなり、平滑コンデンサの放電に要する時間が長くなる。平滑コンデンサに電荷が残っていると回路の点検及び修理の妨げとなることから、装置に異常が発生した際には、平滑コンデンサは速やかに（例えば１０秒以内に）放電されることが要請される。   If the discharging resistor is connected in parallel to the smoothing capacitor as in the inverter device described in Patent Document 1, power is always consumed by the discharging resistor. When the resistance value of the discharge resistor is increased to reduce the power consumed by the discharge resistor, the discharge time constant is increased, and the time required to discharge the smoothing capacitor is increased. Since the remaining charge in the smoothing capacitor interferes with the inspection and repair of the circuit, the smoothing capacitor is required to be discharged quickly (for example, within 10 seconds) when an abnormality occurs in the device. Ru.

特許文献１に記載されたインバータ装置は、鍋等の調理器具の誘導加熱に用いられ、その出力は比較的小さく、平滑コンデンサの静電容量もまた比較的小さい。このため、放電用抵抗の抵抗値を大きくすることによって放電時定数が大きくなるとしても、その影響は軽微である。特許文献１に一例として記載された、平滑コンデンサの静電容量が９μＦ、放電用抵抗の抵抗値が２４０ＫΩである場合に、放電時定数は２秒程である。   The inverter device described in Patent Document 1 is used for induction heating of cooking utensils such as pans, the output of which is relatively small, and the capacitance of the smoothing capacitor is also relatively small. For this reason, even if the discharge time constant is increased by increasing the resistance value of the discharge resistor, the influence is minor. When the capacitance of the smoothing capacitor is 9 μF and the resistance value of the discharging resistor is 240 KΩ, which is described as an example in Patent Document 1, the discharging time constant is about 2 seconds.

しかし、鋼材の熱処理、電縫管の溶接等に用いられるような、出力が比較的大きい電源装置では、平滑コンデンサの静電容量もまた大きい。特に、電縫管の溶接に用いられる電源装置は低リップルであることが要請され、この種の電源装置に用いられる平滑コンデンサの静電容量は、数万μＦと極めて大きい。平滑コンデンサの静電容量がこれほどまでに大きいと、放電用抵抗の抵抗値の増大は、放電時定数の著しい増大をもたらす。一方で、放電用抵抗の抵抗値を小さくすると、放電用抵抗によって消費される電力量が増加し、また、消費電力と抵抗器の定格との関係で多数の抵抗器が必要となり、電源装置の製造コスト及び運転コストの上昇、並びに電源装置の大型化が懸念される。   However, in a power supply having a relatively large output such as used for heat treatment of steel materials, welding of welded tubes, etc., the capacitance of the smoothing capacitor is also large. In particular, it is required that a power supply used for welding of a welded tube have a low ripple, and the capacitance of the smoothing capacitor used in this kind of power supply is extremely large, such as several tens of thousands of μF. If the capacitance of the smoothing capacitor is so high, an increase in the resistance of the discharge resistor leads to a significant increase in the discharge time constant. On the other hand, when the resistance value of the discharge resistor is reduced, the amount of power consumed by the discharge resistor increases, and a large number of resistors are required due to the relationship between the power consumption and the rating of the resistor. There are concerns about the increase in manufacturing costs and operating costs, as well as the increase in size of the power supply.

本発明は、上述した事情に鑑みなされたものであり、異常時には平滑部に含まれるコンデンサを速やかに放電させ、且つ平時における損失を低減可能な電源装置を提供することを目的とする。   The present invention has been made in view of the above-described circumstances, and has an object to provide a power supply device capable of rapidly discharging a capacitor included in a smoothing unit at the time of abnormality and reducing loss in normal time.

本発明の一態様の電源装置は、交流電源から供給される交流電力を直流電力に変換する順変換部と、前記順変換部から出力されるリップルを含んだ直流電力を平滑する平滑部と、前記平滑部によって平滑された直流電力を交流電力に変換する逆変換部と、前記順変換部、前記平滑部、及び前記逆変換部を収納している筐体と、前記順変換部、前記逆変換部、及び前記筐体の少なくとも一つの異常を検出する異常検出部と、を備え、前記平滑部は、前記順変換部の出力に並列に接続されている少なくとも一つのコンデンサと、前記コンデンサを放電する第１放電抵抗と、前記第１放電抵抗と直列に接続されている開閉素子と、を含み、前記異常検出部によって異常が検出された場合に、前記開閉素子は前記異常検出部によって閉じられ、前記開閉素子が閉じられている場合に、前記コンデンサは前記第１放電抵抗によって放電される。   A power supply device according to one aspect of the present invention includes: a forward conversion unit that converts alternating current power supplied from an alternating current power supply into direct current power; and a smoothing unit that smoothes direct current power including ripples output from the forward conversion unit. An inverse conversion unit that converts direct current power smoothed by the smoothing unit into alternating current power, a housing that houses the forward conversion unit, the smoothing unit, and the reverse conversion unit, the forward conversion unit, and the reverse conversion unit A conversion unit, and an abnormality detection unit for detecting at least one abnormality of the housing, wherein the smoothing unit includes at least one capacitor connected in parallel with the output of the forward conversion unit; The switching device is closed by the abnormality detecting unit when the abnormality detecting unit includes a first discharging resistor to be discharged and a switching device connected in series with the first discharging resistor, and the abnormality detecting unit detects an abnormality. And said open When the device is closed, the capacitor is discharged by said first discharge resistor.

本発明によれば、異常時には平滑部に含まれるコンデンサを速やかに放電させ、且つ平時における損失を低減可能な電源装置を提供することができる。   According to the present invention, it is possible to provide a power supply device capable of quickly discharging a capacitor included in a smoothing unit at the time of abnormality and reducing loss in normal time.

本発明の実施形態を説明するための、電源装置の一例のブロック図である。It is a block diagram of an example of a power supply device for describing an embodiment of the present invention. 図１の電源装置の平滑部の回路図である。It is a circuit diagram of the smoothing part of the power supply device of FIG. 図１の電源装置の平滑部の変形例の回路図である。It is a circuit diagram of the modification of the smooth part of the power supply device of FIG. 本発明の実施形態を説明するための、電源装置の他の例のブロック図である。It is a block diagram of the other example of a power supply device for describing the embodiment of the present invention. 図４の電源装置の制御部の回路図である。It is a circuit diagram of the control part of the power supply device of FIG. 図４の電源装置の制御部の回路図である。It is a circuit diagram of the control part of the power supply device of FIG.

図１は、本発明の実施形態を説明するための、電源装置の一例を示し、図２は、平滑部の一例を示す。   FIG. 1 shows an example of a power supply device for describing an embodiment of the present invention, and FIG. 2 shows an example of a smoothing unit.

電源装置１は、交流電源２から供給される交流電力を直流電力に変換する順変換部３と、順変換部３から出力されるリップルを含んだ直流電力を平滑する平滑部４と、平滑部４によって平滑された直流電力を交流電力に変換する逆変換部５と、を備える。本例では、電源装置１は、交流電源２から順変換部３に過電流が流れた場合に順変換部３に対する電力供給を遮断するブレーカ６をさらに備え、順変換部３、平滑部４、逆変換部５、及びブレーカ６は、筐体７に収納されている。   The power supply device 1 includes a forward conversion unit 3 that converts alternating current power supplied from an alternating current power supply 2 into direct current power, a smoothing unit 4 that smoothes direct current power including ripples output from the forward conversion unit 3, and a smoothing unit And a reverse conversion unit 5 for converting the DC power smoothed by step 4 into AC power. In this example, the power supply device 1 further includes a breaker 6 that shuts off the power supply to the forward conversion unit 3 when an overcurrent flows from the AC power supply 2 to the forward conversion unit 3, and the forward conversion unit 3, the smoothing unit 4, The reverse conversion unit 5 and the breaker 6 are housed in a housing 7.

順変換部３は、例えばダイオードブリッジを用いて整流するものであってもよいし、外部信号に基づいて導通の制御が可能なサイリスタ等の半導体素子を用いて平滑後の直流電圧を可変に整流するものであってもよい。半導体素子が用いられる場合に、半導体素子の導通は、制御部８によって制御される。   The forward conversion unit 3 may rectify using, for example, a diode bridge, or may rectify the smoothed DC voltage variably using a semiconductor element such as a thyristor capable of controlling conduction based on an external signal. It may be When the semiconductor device is used, the conduction of the semiconductor device is controlled by the control unit 8.

逆変換部５は、例えばスイッチング動作可能な４つのパワー半導体素子を主体とするフルブリッジ回路によって構成され、４つのパワー半導体素子の所定のスイッチング動作によって高周波の交流電力が生成される。また、高周波の出力は、６つのパワー半導体素子を使用して、三相出力とされてもよい。パワー半導体素子のスイッチング動作は、制御部８によって制御される。   The reverse conversion unit 5 is formed of, for example, a full bridge circuit mainly composed of four power semiconductor elements capable of switching operation, and high frequency AC power is generated by a predetermined switching operation of the four power semiconductor elements. Also, the high frequency output may be a three phase output using six power semiconductor devices. The switching operation of the power semiconductor device is controlled by the controller 8.

パワー半導体素子としては、例えばＩＧＢＴ（Insulated Gate Bipolar Transistor、絶縁ゲートバイポーラトランジスタ）や、ＭＯＳＦＥＴ（Metal-Oxide-Semiconductor Field-Effect Transistor、金属酸化物半導体電界効果トランジスタ）といったスイッチング動作可能な各種のパワー半導体素子が使用可能であり、半導体材料として、例えばＳｉ（シリコン）を用いたものや、ＳｉＣ（シリコンカーバイト）を用いたものがある。   Various power semiconductors capable of switching operation such as IGBTs (Insulated Gate Bipolar Transistors, Insulated Gate Bipolar Transistors) and MOSFETs (Metal-Oxide-Semiconductor Field-Effect Transistors, Metal Oxide Semiconductor Field Effect Transistors) as the power semiconductor element A device can be used, and as a semiconductor material, for example, one using Si (silicon) or one using SiC (silicon carbide) is known.

逆変換部５の出力には、加熱コイルを含む負荷９が接続され、逆変換部５によって生成された高周波の交流電力が加熱コイルに供給される。そして、加熱コイルによって加熱対象物が誘導加熱される。加熱対象物及び加熱目的は、特に限定されないが、鋼材の熱処理（焼入れ等）、電縫管の溶接等を例示することができる。   A load 9 including a heating coil is connected to the output of the inverse conversion unit 5, and high frequency AC power generated by the inverse conversion unit 5 is supplied to the heating coil. Then, the object to be heated is inductively heated by the heating coil. The object to be heated and the purpose of the heating are not particularly limited, but can be exemplified by heat treatment (quenching etc.) of steel materials, welding of a welded tube etc.

平滑部４は、図２に示す例では、コンデンサ１０と、リアクトル１１と、第１放電抵抗１２と、第２放電抵抗１３と、開閉素子１４とを含む。   Smoothing unit 4 includes, in the example shown in FIG. 2, capacitor 10, reactor 11, first discharge resistor 12, second discharge resistor 13, and switching element 14.

コンデンサ１０は、順変換部３の出力に並列に接続されており、順変換部３の直流出力に含まれるリップルを除去ないし軽減する。コンデンサ１０の静電容量は、電源装置１の出力に応じて適宜設定され、例えば電源装置１の出力が３００ｋＷ程度であるものとして、コンデンサ１０の静電容量は２００００μＦ程度とすることができる（ただし、この静電容量は、かなりの低リップルの電源装置での値である）。コンデンサ１０としては、例えば大容量化が容易な電解コンデンサが用いられるが、電解コンデンサに限定されるものではない。   The capacitor 10 is connected in parallel to the output of the forward conversion unit 3 and removes or reduces the ripple contained in the DC output of the forward conversion unit 3. The capacitance of the capacitor 10 is appropriately set according to the output of the power supply device 1. For example, assuming that the output of the power supply device 1 is about 300 kW, the capacitance of the capacitor 10 can be about 20000 μF (however, , This capacitance is the value at a fairly low ripple power supply). As the capacitor 10, for example, an electrolytic capacitor whose capacity can be easily increased is used, but it is not limited to the electrolytic capacitor.

さらに本例では、リアクトル１１が、順変換部３の出力の正極と、この正極側に接続されているコンデンサ１０の端子との間に介在している。リアクトル１１は、コンデンサ１０と協働してローパスフィルタを形成し、リップルの除去能を高めている。   Furthermore, in the present example, the reactor 11 is interposed between the positive electrode of the output of the forward conversion unit 3 and the terminal of the capacitor 10 connected to the positive electrode side. The reactor 11 cooperates with the capacitor 10 to form a low pass filter to enhance the ability to remove ripples.

第１放電抵抗１２と開閉素子１４とは直列に接続されており、直列に接続された第１放電抵抗１２及び開閉素子１４は、順変換部３の出力に並列に接続されている。開閉素子１４は、外部信号に基づいて開閉可能であり、制御部８によって開閉される。そして、開閉素子１４が閉じられている（導通されている）場合に、コンデンサ１０は第１放電抵抗１２及び開閉素子１４を通して放電される。   The first discharge resistor 12 and the switching element 14 are connected in series, and the first discharge resistor 12 and the switching element 14 connected in series are connected in parallel to the output of the forward conversion unit 3. The switching element 14 can be opened and closed based on an external signal, and is opened and closed by the control unit 8. Then, when the switching element 14 is closed (conductive), the capacitor 10 is discharged through the first discharge resistor 12 and the switching element 14.

開閉素子１４としては、例えば電磁石による可動鉄片の吸引を利用して開閉されるマグネットスイッチ等の機械的接点を有する素子、又はサイリスタ等の半導体素子を用いることができるが、機械的接点を有する素子に比べて素子の寿命が長い半導体素子が好適に用いられる。   For example, an element having a mechanical contact such as a magnet switch or a semiconductor element such as a thyristor can be used as the opening / closing element 14, but an element having a mechanical contact can be used. A semiconductor device having a longer device life than that of the semiconductor device is preferably used.

第２放電抵抗１３は、第１放電抵抗１２と並列に接続されており、コンデンサ１０は第２放電抵抗１３を通して常に放電される。第２放電抵抗１３の抵抗値は、第１放電抵抗１２の抵抗値よりも大きく、例えば第１放電抵抗１２の抵抗値は数百Ωであり、第２放電抵抗１３の抵抗値は数十ｋΩ〜数百ｋΩである。   The second discharge resistor 13 is connected in parallel to the first discharge resistor 12, and the capacitor 10 is always discharged through the second discharge resistor 13. The resistance value of the second discharge resistor 13 is larger than the resistance value of the first discharge resistor 12. For example, the resistance value of the first discharge resistor 12 is several hundreds Ω, and the resistance value of the second discharge resistor 13 is several tens kΩ It is several hundred kΩ.

ブレーカ６は、交流電源２から順変換部３に過電流が流れた場合に順変換部３に対する電力供給を遮断し、順変換部３に対する電力供給を遮断した際に、順変換部３の異常を示す異常信号を制御部８に送出する。   The breaker 6 cuts off the power supply to the forward conversion unit 3 when an overcurrent flows from the AC power supply 2 to the forward conversion unit 3, and cuts off the power supply to the forward conversion unit 3. And sends an abnormality signal indicating the signal to the control unit 8.

制御部８は、例えばプロセッサを主体として構成され、逆変換部５のパワー半導体素子のスイッチング動作を制御し、また、順変換部３にサイリスタ等の半導体素子が用いられる場合には半導体素子の導通を制御する。また、制御部８は、異常信号がブレーカ６から入力された際に開閉素子１４を閉じる。   The control unit 8 mainly includes, for example, a processor, controls the switching operation of the power semiconductor element of the inverse conversion unit 5, and when the forward conversion unit 3 uses a semiconductor element such as a thyristor, conduction of the semiconductor element is performed. Control. Further, the control unit 8 closes the open / close element 14 when an abnormality signal is input from the breaker 6.

開閉素子１４が閉じられることにより、コンデンサ１０は、第２放電抵抗１３に加え、第１放電抵抗１２を通して放電される。第１放電抵抗１２の抵抗値（例えば数百Ω）は、第２放電抵抗１３の抵抗値（例えば数十ｋΩ〜数百ｋΩ）よりも小さく、コンデンサ１０に蓄積された電荷の殆どは第１放電抵抗１２に流れる。コンデンサ１０の端子間電圧に対して放電抵抗の抵抗値が小さいほど放電抵抗に流れる電流は大きくなり、ブレーカ６及び制御部８によって順変換部３の異常が検出された際に、抵抗値が小さい第１放電抵抗１２によってコンデンサ１０を速やかに放電することができる。例えばコンデンサ１０の静電容量が２００００μＦであり、第１放電抵抗１２の抵抗値が３００Ωである場合に、放電時定数は６秒程である。   When the switching element 14 is closed, the capacitor 10 is discharged through the first discharge resistor 12 in addition to the second discharge resistor 13. The resistance value (for example, several hundred Ω) of the first discharge resistor 12 is smaller than the resistance value (for example, several tens kΩ to several hundreds kΩ) of the second discharge resistor 13 and most of the charge stored in the capacitor 10 is the first It flows to the discharge resistance 12. The smaller the resistance value of the discharge resistor with respect to the voltage across the capacitor 10, the larger the current flowing through the discharge resistor, and the smaller the resistance value when the breaker 6 and the controller 8 detect an abnormality in the forward converter 3 The capacitor 10 can be discharged quickly by the first discharge resistor 12. For example, when the capacitance of the capacitor 10 is 20000 μF and the resistance value of the first discharge resistor 12 is 300 Ω, the discharge time constant is about 6 seconds.

また、常時通電される抵抗器は、発熱に対する安全性の観点から、一般に定格電力の１／４程度で運用されるが、第１放電抵抗１２には、異常時において開閉素子１４が閉じられた時点でコンデンサ１０に蓄積されている電荷が流れるだけであり、第１放電抵抗１２の通電に伴う発熱は一時的であるため、第１放電抵抗１２は、定格電力の上限又は上限近傍で運用可能である。これにより、第１放電抵抗１２を構成する抵抗器の本数を削減することができ、電源装置１の製造コストの削減及び電源装置１の小型化が可能である。例えば、交流電源２の出力電圧が４４０Ｖであり、順変換部３がダイオードブリッジを用いて整流するものである場合に、順変換部３の出力電圧は約６００Ｖとなる。そして、第１放電抵抗１２の抵抗値が３００Ωである場合に、第１放電抵抗１２に流れる電流は最大で２Ａとなり、第１放電抵抗１２の消費電力は最大で１２００Ｗとなる。この場合に、例えばホーロー抵抗器等の定格電力が比較的大きい抵抗器を用いれば、第１放電抵抗１２を一本の抵抗器によって構成することができる。なぜなら、第１放電抵抗１２は、放電時に使用されるのみであり、非常に使用率の低い方法で使用されるからである。   Moreover, although the resistor which is always energized is generally operated at about 1⁄4 of the rated power from the viewpoint of safety against heat generation, the switching element 14 is closed to the first discharge resistor 12 at the abnormal time. At this time, only the charge accumulated in the capacitor 10 flows, and the heat generation accompanying the energization of the first discharge resistor 12 is temporary, so the first discharge resistor 12 can be operated at the upper limit or near the upper limit of the rated power. It is. Thereby, the number of resistors constituting the first discharge resistor 12 can be reduced, and the manufacturing cost of the power supply device 1 can be reduced and the power supply device 1 can be miniaturized. For example, when the output voltage of the AC power supply 2 is 440 V and the forward converter 3 rectifies using the diode bridge, the output voltage of the forward converter 3 is about 600 V. When the resistance value of the first discharge resistor 12 is 300Ω, the current flowing through the first discharge resistor 12 is 2 A at the maximum, and the power consumption of the first discharge resistor 12 is 1200 W at the maximum. In this case, if, for example, a resistor having a relatively large rated power, such as a hollow resistor, is used, the first discharge resistor 12 can be configured by a single resistor. The reason is that the first discharge resistor 12 is used only at the time of discharge and is used in a very low usage rate method.

そして、平時、すなわち異常が検出されずに電源装置１が正常に動作及び停止している際には、第１放電抵抗１２は通電されず、第１放電抵抗１２によって電力が消費されることもない。これにより、電源装置１の運転コストの削減が可能である。   In normal operation, that is, when the power supply apparatus 1 is normally operated and stopped without detecting any abnormality, the first discharge resistor 12 is not energized and power may be consumed by the first discharge resistor 12. Absent. Thereby, the operating cost of the power supply device 1 can be reduced.

なお、異常時にコンデンサ１０を速やかに放電する観点では、第２放電抵抗１３は省略されてもよいが、好ましくは、第２放電抵抗１３が設けられ、電源装置１が正常に動作及び停止している際に、コンデンサ１０は第２放電抵抗１３を通して常に放電される。例えばコンデンサ１０の充電が開始された際などの過渡状態においてコンデンサ１０の端子間電圧が一時的に高くなる場合があるが、コンデンサ１０が第２放電抵抗１３を通して放電されることにより、逆変換部５に過大な電圧が印加されることを抑制でき、逆変換部５のパワー半導体素子を保護することができる。   Although the second discharge resistor 13 may be omitted from the viewpoint of rapidly discharging the capacitor 10 at the time of abnormality, preferably, the second discharge resistor 13 is provided, and the power supply device 1 operates and stops normally. At the same time, the capacitor 10 is always discharged through the second discharge resistor 13. For example, the voltage across the terminals of the capacitor 10 may temporarily increase in a transient state such as when charging of the capacitor 10 is started, but the capacitor 10 is discharged through the second discharge resistor 13 to cause an inverse conversion unit The application of an excessive voltage to 5 can be suppressed, and the power semiconductor element of the inverse conversion unit 5 can be protected.

そして、第２放電抵抗１３の抵抗値は、第１放電抵抗１２の抵抗値よりも十分に大きく、例えば数十ｋΩ〜数百ｋΩであるので、第２放電抵抗１３に流れる電流は極めて小さく、例えば数ｍＡ〜数十ｍＡとなるので、第２放電抵抗１３によって常に電力が消費されるとしても、消費される電力量は僅かである。   And since the resistance value of the second discharge resistor 13 is sufficiently larger than the resistance value of the first discharge resistor 12, for example, several tens kΩ to several hundreds kΩ, the current flowing through the second discharge resistor 13 is extremely small, For example, since several mA to several tens of mA, even if power is always consumed by the second discharge resistor 13, the amount of power consumed is small.

図３は、平滑部４の変形例を示す。   FIG. 3 shows a modification of the smoothing unit 4.

図３に示す例では、平滑部４は、順変換部３の出力に並列に接続されるコンデンサとして、ダイオード２０を介して接続されている第１コンデンサ２１と、直接接続されている第２コンデンサ２２とを含み、さらに、第１放電抵抗２３と、第２放電抵抗２４と、第３放電抵抗２５と、開閉素子２６とを含む。   In the example illustrated in FIG. 3, the smoothing unit 4 is a capacitor connected in parallel to the output of the forward conversion unit 3, and a second capacitor connected directly to the first capacitor 21 connected via the diode 20. 22 and further includes a first discharge resistor 23, a second discharge resistor 24, a third discharge resistor 25, and an open / close element 26.

第１放電抵抗２３と開閉素子２６とは直列に接続されており、直列に接続された第１放電抵抗２３及び開閉素子２６は、第１コンデンサ２１と並列に接続されている。開閉素子２６は、外部信号に基づいて開閉可能であり、制御部８によって開閉される。   The first discharge resistor 23 and the switching element 26 are connected in series, and the first discharge resistor 23 and the switching element 26 connected in series are connected in parallel to the first capacitor 21. The switching element 26 can be opened and closed based on an external signal, and is opened and closed by the control unit 8.

第２放電抵抗２４は、第１放電抵抗２３と並列に接続されており、第１コンデンサ２１は第２放電抵抗２４を通して常に放電される。第２放電抵抗２４によって消費される電力量を削減する観点から、第２放電抵抗２４の抵抗値は第１放電抵抗２３の抵抗値よりも大きく、例えば第１放電抵抗２３の抵抗値は数百Ωであり、第２放電抵抗２４の抵抗値は数十ｋΩ〜数百ｋΩである。   The second discharge resistor 24 is connected in parallel to the first discharge resistor 23, and the first capacitor 21 is always discharged through the second discharge resistor 24. From the viewpoint of reducing the amount of power consumed by the second discharge resistor 24, the resistance value of the second discharge resistor 24 is larger than the resistance value of the first discharge resistor 23. For example, the resistance value of the first discharge resistor 23 is several hundred. The resistance value of the second discharge resistor 24 is several tens kΩ to several hundreds kΩ.

第３放電抵抗２５は、第２コンデンサ２２と並列に接続されており、第２コンデンサ２２は第３放電抵抗２５を通して常に放電される。第３放電抵抗２５によって消費される電力量を削減する観点から、第３放電抵抗２５の抵抗値は第１放電抵抗２３の抵抗値よりも大きく、例えば第１放電抵抗２３の抵抗値は数百Ωであり、第３放電抵抗２５の抵抗値は数十ｋΩ〜数百ｋΩである。   The third discharge resistor 25 is connected in parallel to the second capacitor 22, and the second capacitor 22 is always discharged through the third discharge resistor 25. From the viewpoint of reducing the amount of power consumed by the third discharge resistor 25, the resistance value of the third discharge resistor 25 is larger than the resistance value of the first discharge resistor 23. For example, the resistance value of the first discharge resistor 23 is several hundred. The resistance value of the third discharge resistor 25 is several tens kΩ to several hundreds kΩ.

ダイオード２０を介して順変換部３の出力に並列に接続されている第１コンデンサ２１は、第１コンデンサ２１の端子間電圧が第２コンデンサ２２の端子間電圧よりも低い場合に充電される。したがって、順変換部３の出力に含まれるリップルは、基本的には第２コンデンサ２２によって除去ないし軽減される。図２に示した平滑部４のコンデンサ１０と同様に、第２コンデンサ２２が第３放電抵抗２５を通して常に放電されることにより、過渡状態における第２コンデンサ２２の端子間電圧の上昇が抑制され、逆変換部５のパワー半導体素子が保護される。第１コンデンサ２１は、ダイオード２０と、第２放電抵抗２４と協働して過渡電圧抑制回路を形成し、過渡状態における第２コンデンサ２２の端子間電圧の上昇をさらに抑制する。なお、過渡状態における第２コンデンサ２２の端子間電圧の上昇は、上記過渡電圧抑制回路によって抑制されるので、第３放電抵抗２５は省略されてもよい。   The first capacitor 21 connected in parallel to the output of the forward conversion unit 3 via the diode 20 is charged when the voltage across the terminals of the first capacitor 21 is lower than the voltage across the terminals of the second capacitor 22. Therefore, the ripple contained in the output of the forward converter 3 is basically eliminated or reduced by the second capacitor 22. Similarly to the capacitor 10 of the smoothing unit 4 shown in FIG. 2, the second capacitor 22 is always discharged through the third discharge resistor 25 to suppress an increase in the voltage across the terminals of the second capacitor 22 in a transient state, The power semiconductor element of the inverse conversion unit 5 is protected. The first capacitor 21 cooperates with the diode 20 and the second discharge resistor 24 to form a transient voltage suppression circuit to further suppress an increase in the voltage across the terminals of the second capacitor 22 in the transient state. Since the rise of the voltage across the terminals of the second capacitor 22 in the transient state is suppressed by the transient voltage suppression circuit, the third discharge resistor 25 may be omitted.

好ましくは、第１コンデンサ２１の静電容量は、第２コンデンサ２２の静電容量よりも小さく、静電容量が相対的に小さい第１コンデンサ２１としては、例えば電解コンデンサに比べて長寿命なフィルムコンデンサが好適である。   Preferably, the electrostatic capacitance of the first capacitor 21 is smaller than the electrostatic capacitance of the second capacitor 22, and as the first capacitor 21 having a relatively small electrostatic capacitance, for example, a film having a longer life than an electrolytic capacitor. A capacitor is preferred.

図３に示す例においても、交流電源２から順変換部３に過電流が流れた場合に、順変換部３に対する電力供給がブレーカ６によって遮断され、異常信号がブレーカ６から制御部８に送出され、開閉素子２６が制御部８によって閉じられる。開閉素子２６が閉じられることにより、まず、第１コンデンサ２１が、第２放電抵抗２４に加え、第１放電抵抗２３を通して放電される。第１放電抵抗２３の抵抗値（例えば数百Ω）は、第２放電抵抗２４の抵抗値（例えば数十ｋΩ〜数百ｋΩ）よりも小さく、第１コンデンサ２１に蓄積された電荷の殆どは第１放電抵抗２３に流れ、第１コンデンサ２１は第１放電抵抗２３を通して速やかに放電される。そして、第１コンデンサ２１が放電されて第１コンデンサ２１の端子間電圧が第２コンデンサ２２の端子間電圧よりも低くなることにより、第２コンデンサ２２もまた、第１放電抵抗２３を通して速やかに放電される。例えば第１コンデンサ２１の静電容量が７０００μＦであり、第２コンデンサ２２の静電容量が２００００μＦであり、第１放電抵抗２３の抵抗値が３００Ωである場合に、放電時定数は８秒程である。   Also in the example shown in FIG. 3, when an overcurrent flows from the AC power supply 2 to the forward conversion unit 3, the power supply to the forward conversion unit 3 is interrupted by the breaker 6, and an abnormal signal is sent from the breaker 6 to the control unit 8. And the switching element 26 is closed by the control unit 8. When the switching element 26 is closed, the first capacitor 21 is firstly discharged through the first discharge resistor 23 in addition to the second discharge resistor 24. The resistance value (for example, several hundred Ω) of the first discharge resistor 23 is smaller than the resistance value (for example, several tens kΩ to several hundreds kΩ) of the second discharge resistor 24, and most of the charge stored in the first capacitor 21 is The current flows to the first discharge resistor 23, and the first capacitor 21 is quickly discharged through the first discharge resistor 23. Then, the first capacitor 21 is discharged, and the voltage across the terminals of the first capacitor 21 becomes lower than the voltage across the terminals of the second capacitor 22, so that the second capacitor 22 is also discharged quickly through the first discharge resistor 23. Be done. For example, when the capacitance of the first capacitor 21 is 7000 μF, the capacitance of the second capacitor 22 is 20000 μF, and the resistance value of the first discharge resistor 23 is 300 Ω, the discharge time constant is about 8 seconds. is there.

ここまで、電源装置１の異常として、交流電源２から順変換部３に過電流が流れる場合を例にし、この順変換部３の異常がブレーカ６と制御部８とによって検出されるものとして説明したが、電源装置１の異常として、筐体７の開扉が検出されてもよい。例えば適宜なスイッチ又はセンサからなる開扉検出部が筐体７の扉又は扉枠に設けられ、筐体７の開扉に応じて開扉検出部がＯＮ又はＯＦＦされ、開扉検出部のＯＮ状態及びＯＦＦ状態に基づき、筐体７の開扉が制御部８によって検出される。筐体７の開扉が検出された場合に、図２に示した平滑部４では、開閉素子１４が制御部８によって閉じられ、コンデンサ１０が第１放電抵抗１２を通して速やかに放電され、また図３に示した平滑部４では、開閉素子２６が制御部８によって閉じられ、第１コンデンサ２１及び第２コンデンサ２２が第１放電抵抗２３を通して速やかに放電される。   Up to here, the case where an overcurrent flows from the AC power supply 2 to the forward conversion unit 3 as an abnormality of the power supply device 1 is described as an example where the failure of the forward conversion unit 3 is detected by the breaker 6 and the control unit 8 However, the door opening of the housing 7 may be detected as an abnormality of the power supply device 1. For example, an open detection unit including an appropriate switch or sensor is provided on the door or door frame of the housing 7, and the open detection unit is turned on or off according to the opening of the housing 7, and the open detection unit is turned on. The controller 8 detects the opening of the housing 7 based on the state and the OFF state. When the door opening of the housing 7 is detected, the switching element 14 is closed by the control unit 8 in the smoothing unit 4 shown in FIG. 2, and the capacitor 10 is discharged quickly through the first discharge resistor 12. In the smoothing unit 4 shown in FIG. 3, the switching element 26 is closed by the control unit 8, and the first capacitor 21 and the second capacitor 22 are rapidly discharged through the first discharge resistor 23.

また、電源装置１の異常として、逆変換部５の異常が検出されてもよく、図４から図６を参照して、逆変換部５の異常と、その検出方法の一例を説明する。なお、上述した電源装置１と共通する要素には共通の符号を付し、説明を省略又は簡略する。   In addition, an abnormality of the inverse conversion unit 5 may be detected as an abnormality of the power supply device 1. An abnormality of the inverse conversion unit 5 and an example of a detection method thereof will be described with reference to FIGS. 4 to 6. In addition, the same code | symbol is attached | subjected to the element which is common in the power supply device 1 mentioned above, and description is abbreviate | omitted or simplified.

制御部８は、逆変換部５から出力される交流電力の周波数を、逆変換部５に接続される負荷９の共振周波数となるように制御する位相同期ループ回路（以下、「ＰＬＬ回路」と略す。）３０と、異常検出回路３１とを有する。また、逆変換部５には、負荷９に供給される電流Ｉ１を検出する変流器３２と、負荷９に印加される電圧Ｖ１を検出する変圧器３３が設けられている。   The control unit 8 controls the frequency of the AC power output from the inverse conversion unit 5 to be the resonance frequency of the load 9 connected to the inverse conversion unit 5 (hereinafter referred to as “PLL circuit”). (Abbreviated) 30 and an abnormality detection circuit 31. Further, in the reverse conversion unit 5, a current transformer 32 that detects the current I 1 supplied to the load 9 and a transformer 33 that detects the voltage V 1 applied to the load 9 are provided.

図５に示すように、ＰＬＬ回路３０には、変流器３２によって検出される電流Ｉ１と、変圧器３３によって検出される電圧Ｖ１の位相を検出する位相比較回路４０と、位相比較回路４０によって検出される位相に応じて、予め設定された周波数設定値を加減するアナログ加減算器４１と、このアナログ加減算器４１から出力される電圧に応じた周波数の信号を出力する電圧制御発振器４２と、電圧制御発振器４２から出力される信号の周波数に応じて、逆変換部５のパワー半導体素子Ｍ１〜Ｍ４の制御端子ｇ１〜ｇ４に制御信号を送出する制御信号回路４３とが設けられている。   As shown in FIG. 5, the PLL circuit 30 includes a phase comparison circuit 40 that detects the phase of the current I1 detected by the current transformer 32 and the voltage V1 detected by the transformer 33, and the phase comparison circuit 40. An analog adder / subtractor 41 for adding or subtracting a preset frequency set value according to a phase to be detected, a voltage control oscillator 42 for outputting a signal of a frequency corresponding to the voltage output from the analog adder / subtractor 41, a voltage A control signal circuit 43 for transmitting a control signal to control terminals g1 to g4 of the power semiconductor elements M1 to M4 of the inverse conversion unit 5 is provided according to the frequency of the signal output from the control oscillator 42.

ＰＬＬ回路３０によって、負荷９に供給される電流Ｉ１及び負荷９に印加される電圧Ｖ１の位相ずれがなくなるように逆変換部５の作動周波数が制御され、逆変換部５から出力される交流電力の周波数が、インダクタンス成分Ｌおよびキャパシタンス成分Ｃを含む負荷９の共振周波数と一致する。これにより、電源装置１０１の効率を高めることが可能となる。   The PLL circuit 30 controls the operating frequency of the inverse conversion unit 5 so that the phase shift between the current I1 supplied to the load 9 and the voltage V1 applied to the load 9 is eliminated, and the AC power output from the inverse conversion unit 5 Is equal to the resonant frequency of the load 9 including the inductance component L and the capacitance component C. This makes it possible to increase the efficiency of the power supply apparatus 101.

しかし、負荷９側の回路の一部が短絡し、又は開放されるといった異常が発生すると、負荷９のインピーダンスが急激に変化し、共振周波数が大きく変動する。すると、ＰＬＬ回路３０は、負荷９の共振周波数に追従するように逆変換部５の作動周波数を調節し、過渡状態において、瞬間的に大きな電流や電圧が逆変換部５に発生し、パワー半導体素子Ｍ１〜Ｍ４が破壊される虞がある。特に、負荷９のインピーダンスの変化により、電流Ｉ１の位相が電圧Ｖ１の位相に対して進むと、大きなサージ電圧が発生し、このサージ電圧でパワー半導体素子Ｍ１〜Ｍ４が破壊される虞がある。そこで、異常検出回路３１は、変流器３２及び変圧器３３と協働して位相ずれ検出部を構成し、変流器３２によって検出される電流Ｉ１と変圧器３３によって検出される電圧Ｖ１との位相ずれを検出する。   However, when an abnormality occurs such as a part of the circuit on the load 9 side being shorted or opened, the impedance of the load 9 changes rapidly and the resonance frequency largely fluctuates. Then, the PLL circuit 30 adjusts the operating frequency of the inverse conversion unit 5 so as to follow the resonance frequency of the load 9, and in the transient state, a large current or voltage is instantaneously generated in the inverse conversion unit 5, and the power semiconductor The elements M1 to M4 may be broken. In particular, when the phase of the current I1 advances with respect to the phase of the voltage V1 due to a change in the impedance of the load 9, a large surge voltage may be generated, and the power semiconductor elements M1 to M4 may be broken by this surge voltage. Therefore, the abnormality detection circuit 31 constitutes a phase shift detection unit in cooperation with the current transformer 32 and the transformer 33, and the current I1 detected by the current transformer 32 and the voltage V1 detected by the transformer 33 To detect a phase shift of

異常検出回路３１には、変流器３２によって検出される電流Ｉ１及び変圧器３３によって検出される電圧Ｖ１が入力され、図６に示すように、入力された電圧Ｖ１の波形を所定の方形波に整える波形整形器５０と、入力された電流Ｉ１の波形を所定の方形波に整える波形整形器５１と、電圧Ｖ１及び電流Ｉ１の位相ずれを検出する位相ずれ検出手段としてのデータフリップフロップ５２と、このデータフリップフロップ５２の出力をホールドするラッチとしてのフリップフロップ５３と、電流Ｉ１の大きさが基準値に達したか否かを検出する比較器５４と、この比較器５４の出力信号を反転する反転器５５とが設けられている。   The current detection circuit 31 receives the current I1 detected by the current transformer 32 and the voltage V1 detected by the transformer 33, and as shown in FIG. A waveform shaper 50, a waveform shaper 51 for adjusting the waveform of the input current I1 into a predetermined square wave, and a data flip-flop 52 as phase shift detection means for detecting a phase shift of the voltage V1 and the current I1. The flip-flop 53 as a latch for holding the output of the data flip-flop 52, the comparator 54 for detecting whether the magnitude of the current I1 has reached the reference value, and the output signal of the comparator 54 are inverted. An inverter 55 is provided.

波形整形器５０は、データフリップフロップ５２に入力する電圧に応じた直流抵抗値を有する抵抗器５０Ａや、電圧Ｖ１の波形に含まれる不要な高調波分をカットするためのコンデンサ５０Ｂ等を備える。波形整形器５１は、波形整形器５０と同様に、データフリップフロップ５２に入力する電圧に応じた直流抵抗値を有する抵抗器５１Ａや、電流Ｉ１の波形に含まれる不要な高調波分をカットするためのコンデンサ５１Ｂ等を備える。   The waveform shaper 50 includes a resistor 50A having a DC resistance value corresponding to a voltage input to the data flip-flop 52, a capacitor 50B for cutting an unnecessary harmonic component included in the waveform of the voltage V1, and the like. Like the waveform shaper 50, the waveform shaper 51 cuts an unnecessary harmonic component included in the resistor 51A having a DC resistance value corresponding to the voltage input to the data flip-flop 52 and the waveform of the current I1. Capacitor 51B and the like.

データフリップフロップ５２は、クロック信号が入力されるクロック入力ポートＣＬと、データ信号が入力されるデータ入力ポートＤと、セット信号が入力されるセット入力ポートＳと、リセット信号が入力されるリセット入力ポートＲと、セット状態となるとセット信号を送出するセット信号ポートＱとを有し、クロック信号と同時にデータ信号が入力されると、セット状態となって、セット信号ポートＱからセット信号を送出する。   The data flip-flop 52 has a clock input port CL to which a clock signal is input, a data input port D to which a data signal is input, a set input port S to which a set signal is input, and a reset input to which a reset signal is input. It has port R and a set signal port Q that sends a set signal when it is in the set state, and when a data signal is input simultaneously with a clock signal, it enters the set state and sends a set signal from the set signal port Q .

比較器５４は、二つの入力ポートにそれぞれ入力される交流信号の大きさを比較するものである。比較器５４の一方の入力ポートには、負荷９に供給される電流Ｉ１の値を示す交流信号が入力されている。比較器５４の他方の入力ポートには、予め設定された基準値として、所定の交流電圧Ｖ２を可変抵抗器５６で分圧した交流信号が入力されている。電流Ｉ１が基準値よりも大きくなると、比較器５４から定常運転信号が出力されるようになっている。この定常運転信号は、反転器５５で反転されてデータフリップフロップ５２のリセット入力ポートＲに送られる。比較器５４、反転器５５及び可変抵抗器５６により、電流Ｉ１の値が基準値よりも大きくなるまで、データフリップフロップ５２にリセット信号を出力し続けるマスク手段５７が形成されている。   The comparator 54 compares the magnitudes of AC signals input to the two input ports. An alternating current signal indicating the value of the current I1 supplied to the load 9 is input to one input port of the comparator 54. An alternating current signal obtained by dividing a predetermined alternating current voltage V2 by a variable resistor 56 is input to the other input port of the comparator 54 as a preset reference value. When the current I1 becomes larger than the reference value, the steady operation signal is output from the comparator 54. The steady operation signal is inverted by the inverter 55 and sent to the reset input port R of the data flip flop 52. The comparator 54, the inverter 55 and the variable resistor 56 form the mask means 57 which keeps outputting the reset signal to the data flip flop 52 until the value of the current I1 becomes larger than the reference value.

以上の構成において、電源装置１の起動後、電源装置１の運転が定常状態に達するまで、具体的には、逆変換部５の作動周波数が負荷９の共振周波数に一致し、且つ負荷９に供給される電流Ｉ１が基準値よりも大きくなるまで、マスク手段５７がデータフリップフロップ５２にリセット信号を出力し続け、異常検出回路３１による位相ずれ検出動作は休止される。これにより、負荷９に供給される電流Ｉ１が不安定となり、位相が電圧と一致しない電源装置１の起動直後に強制的に停止されるといった不具合が解消される。そして、電源装置１の運転が定常状態に達すると、異常検出回路３１による位相ずれ検出動作が開始される。   In the above configuration, after activation of the power supply 1, until the operation of the power supply 1 reaches a steady state, specifically, the operating frequency of the reverse conversion unit 5 matches the resonant frequency of the load 9 and the load 9 The mask means 57 continues outputting the reset signal to the data flip-flop 52 until the supplied current I1 becomes larger than the reference value, and the phase shift detection operation by the abnormality detection circuit 31 is suspended. As a result, the problem that the current I1 supplied to the load 9 becomes unstable and is forcibly stopped immediately after startup of the power supply device 1 whose phase does not match the voltage is resolved. Then, when the operation of the power supply device 1 reaches a steady state, the phase shift detection operation by the abnormality detection circuit 31 is started.

ここで、負荷９の共振周波数が逆変換部５の作動周波数に一致し、電圧Ｖ１の位相と電流Ｉ１の位相とが相互に一致した状態となっている場合には、データフリップフロップ５２は、リセット状態のままとなり、セット状態へ移行することがなく、セット信号ポートＱからセット信号が送出されず、電源装置１は、そのまま運転が継続される。   Here, when the resonant frequency of load 9 matches the operating frequency of reverse conversion unit 5 and the phase of voltage V1 and the phase of current I1 match each other, data flip-flop 52 It remains in the reset state, does not shift to the set state, the set signal is not sent from the set signal port Q, and the operation of the power supply device 1 is continued.

一方、負荷９に異常が発生し、負荷９の共振周波数が逆変換部５の作動周波数からずれると、電圧Ｖ１の位相と電流Ｉ１の位相とが相互に一致せず、逆変換部５の異常となる。このような状態となった場合には、データフリップフロップ５２は、セット状態へ移行し、セット信号ポートＱからセット信号が送出され、このセット信号は、フリップフロップ５３を介して、逆変換部５の異常を示す異常信号としてＰＬＬ回路３０に入力される。   On the other hand, if an abnormality occurs in load 9 and the resonant frequency of load 9 deviates from the operating frequency of inverse conversion unit 5, the phase of voltage V1 and the phase of current I1 do not match each other, and the abnormality of inverse conversion unit 5 It becomes. In such a state, the data flip flop 52 shifts to the set state, and a set signal is sent from the set signal port Q. This set signal is inverted through the flip flop 53. Are input to the PLL circuit 30 as an abnormal signal indicating an abnormal condition.

異常信号が入力されたＰＬＬ回路３０は、パワー半導体素子Ｍ１〜Ｍ４を適宜オフ状態として、負荷９への電力供給を停止し、パワー半導体素子Ｍ１〜Ｍ４を保護する。なお、異常信号は、フリップフロップ５３がリセットされるまで出力され続ける。そして、異常信号が内部のＰＬＬ回路３０と異常検出回路３１との間で授受される制御部８により、図２に示した平滑部４では開閉素子１４が閉じられ、コンデンサ１０が第１放電抵抗１２を通して速やかに放電され、また図３に示した平滑部４では、開閉素子２６が閉じられ、第１コンデンサ２１及び第２コンデンサ２２が第１放電抵抗２３を通して速やかに放電される。   The PLL circuit 30 to which the abnormal signal is input turns off the power semiconductor devices M1 to M4 appropriately, stops the power supply to the load 9, and protects the power semiconductor devices M1 to M4. The abnormal signal continues to be output until the flip flop 53 is reset. The switching unit 14 is closed in the smoothing unit 4 shown in FIG. 2 by the control unit 8 which transmits and receives the abnormality signal between the PLL circuit 30 and the abnormality detection circuit 31 inside, and the capacitor 10 is the first discharge resistor. The switching element 26 is closed in the smoothing unit 4 shown in FIG. 3 and the first capacitor 21 and the second capacitor 22 are discharged quickly through the first discharge resistor 23.

上述した逆変換部５の異常の検出方法によれば、負荷９の共振周波数の変動に起因する電流Ｉ１と電圧Ｖ１との位相ずれから逆変換部５の異常を迅速に検出可能であり、逆変換部５の作動周波数を負荷９の共振周波数に追従させるＰＬＬ回路３０の動作が完了する前に、逆変換部５の異常を確実に検出することができる。そして、逆変換部５の異常を検出した場合に、逆変換部５のパワー半導体素子Ｍ１〜Ｍ４が適宜オフ状態とすることにより、パワー半導体素子Ｍ１〜Ｍ４の破壊を未然に防止できる。   According to the method of detecting abnormality of the inverse conversion unit 5 described above, abnormality of the inverse conversion unit 5 can be detected rapidly from the phase shift between the current I1 and the voltage V1 caused by the fluctuation of the resonance frequency of the load 9, An abnormality in the inverse conversion unit 5 can be reliably detected before the operation of the PLL circuit 30 that causes the operating frequency of the conversion unit 5 to follow the resonance frequency of the load 9 is completed. Then, when an abnormality in the inverse conversion unit 5 is detected, the power semiconductor elements M1 to M4 of the inverse conversion unit 5 are appropriately turned off, whereby destruction of the power semiconductor elements M1 to M4 can be prevented in advance.

また、電流Ｉ１と電圧Ｖ１との位相ずれを検出する異常検出回路３１が、クロック信号と同時に入力されるデータ信号によりセット状態となり、セット状態の信号であるセット出力を送出するデータフリップフロップ５２を含み、電流Ｉ１と電圧Ｖ１との位相がずれたときのみ、データフリップフロップ５２からセット信号（異常信号）が出力され、これにより、電流Ｉ１と電圧Ｖ１との位相ずれが、簡単な回路構成で検出可能となる。   Further, the abnormality detection circuit 31 for detecting the phase shift between the current I1 and the voltage V1 is brought into the set state by the data signal inputted simultaneously with the clock signal, and the data flip flop 52 sends out the set output which is a signal of the set state. In addition, the set signal (abnormal signal) is output from the data flip-flop 52 only when the phase of the current I1 and the voltage V1 is shifted, whereby the phase shift between the current I1 and the voltage V1 is simple. It becomes detectable.

さらに、異常検出回路３１は、負荷９に供給される電流Ｉ１の電流値と、予め設定された基準値とを比較し、電流Ｉ１の値が基準値よりも大きくなるまで、データフリップフロップ５２にリセット信号を出力し続けるマスク手段５７を含み、電流Ｉ１が不安定となり、電流Ｉ１の位相と電圧Ｖ１の位相とが相互に一致しない電源装置１の起動時には、異常検出回路３１の位相ずれ検出動作が一時的に休止されるので、起動直後に電源装置１が強制的に停止されるといった不都合も解消できる。   Further, the abnormality detection circuit 31 compares the current value of the current I1 supplied to the load 9 with a preset reference value, and continues to the data flip-flop 52 until the value of the current I1 becomes larger than the reference value. The phase shift detection operation of the abnormality detection circuit 31 at the start of the power supply 1 including the mask means 57 which continues outputting the reset signal, the current I1 becomes unstable, and the phase of the current I1 and the phase of the voltage V1 do not match each other. Is temporarily suspended, so that the disadvantage that the power supply 1 is forcibly shut down immediately after startup can be resolved.

以上説明した、ブレーカ６と制御部８とによって構成され、順変換部３の異常を検出する異常検出部、上記開扉検出部と制御部８とによって構成され、筐体７の異常を検出する異常検出部、異常検出回路３１を含む制御部８と変流器３２と変圧器３３とによって構成され、逆変換部５の異常を検出する異常検出部は、それぞれ単独で用いられてもよいし、複数組み合わされて用いられてもよい。   The abnormality detection unit configured by the breaker 6 and the control unit 8 described above and configured to detect an abnormality in the forward conversion unit 3 and the opening detection unit and the control unit 8 described above detects an abnormality in the casing 7 An abnormality detection unit, a control unit 8 including an abnormality detection circuit 31, a current transformer 32, and a transformer 33, and an abnormality detection unit for detecting an abnormality in the inverse conversion unit 5 may be used alone. , And may be used in combination.

１ 電源装置
２ 交流電源
３ 順変換部
４ 平滑部
５ 逆変換部
６ ブレーカ
７ 筐体
８ 制御部
９ 負荷
１０ コンデンサ
１１ リアクトル
１２ 第１放電抵抗
１３ 第２放電抵抗
１４ 開閉素子
２０ ダイオード
２１ 第１コンデンサ
２２ 第２コンデンサ
２３ 第１放電抵抗
２４ 第２放電抵抗
２５ 第３放電抵抗
２６ 開閉素子
３０ ＰＬＬ回路
３１ 異常検出回路
３２ 変流器
３３ 変圧器
４０ 位相比較回路
４１ アナログ加減算器
４２ 電圧制御発振器
４３ 信号制御回路
５０ 波形整形器
５０Ａ 抵抗器
５０Ｂ コンデンサ
５１ 波形整形器
５１Ａ 抵抗器
５１Ｂ コンデンサ
５２ データフリップフロップ
５３ フリップフロップ
５４ 比較器
５５ 反転器
５６ 可変抵抗器
５７ マスク手段
ＣＬ クロック入力ポート
Ｄ データ入力ポート
ｇ１〜ｇ４ 制御端子
Ｍ１〜Ｍ４ パワー半導体素子
Ｑ セット信号ポート
Ｒ リセット入力ポート
Ｓ セット入力ポート DESCRIPTION OF SYMBOLS 1 power supply device 2 alternating current power supply 3 forward conversion part 4 smoothing part 5 reverse conversion part 6 breaker 7 housing 8 control part 9 load 10 capacitor 11 reactor 12 1st discharge resistance 13 2nd discharge resistance 14 switching element 20 diode 21 1st capacitor 22 second capacitor 23 first discharge resistor 24 second discharge resistor 25 third discharge resistor 26 switching element 30 PLL circuit 31 abnormality detection circuit 32 current transformer 33 transformer 40 phase comparison circuit 41 analog adder-subtractor 42 voltage control oscillator 43 signal Control circuit 50 waveform shaper 50A resistor 50B capacitor 51 waveform shaper 51A resistor 51B capacitor 52 data flip flop 53 flip flop 54 comparator 55 inverter 56 variable resistor 57 mask means CL clock input port D data input port g1 g4 Control terminals M1 to M4 Power semiconductor Element Q set signal port R reset input port S set input port

本発明の一態様の電源装置は、交流電源から供給される交流電力を直流電力に変換する順変換部と、前記順変換部から出力されるリップルを含んだ直流電力を平滑する平滑部と、前記平滑部によって平滑された直流電力を交流電力に変換する逆変換部と、前記順変換部、前記平滑部、及び前記逆変換部を収納している筐体と、前記順変換部、前記逆変換部、及び前記筐体の少なくとも一つの異常を検出する異常検出部と、を備え、前記平滑部は、前記順変換部の出力に並列に接続されている少なくとも一つのコンデンサと、前記コンデンサを放電する第１放電抵抗と、前記第１放電抵抗と直列に接続されている開閉素子と、を含み、前記異常検出部によって異常が検出された場合に、前記開閉素子は前記異常検出部によって閉じられ、前記開閉素子が閉じられている場合に、前記コンデンサは前記第１放電抵抗によって放電され、前記平滑部は、前記コンデンサとして、前記順変換部の出力に順方向バイアスとなるように接続されたダイオードを介して接続されている第１コンデンサを含み、前記第１放電抵抗は、前記第１コンデンサと並列に接続されている。 A power supply device according to one aspect of the present invention includes: a forward conversion unit that converts alternating current power supplied from an alternating current power supply into direct current power; and a smoothing unit that smoothes direct current power including ripples output from the forward conversion unit. An inverse conversion unit that converts direct current power smoothed by the smoothing unit into alternating current power, a housing that houses the forward conversion unit, the smoothing unit, and the reverse conversion unit, the forward conversion unit, and the reverse conversion unit A conversion unit, and an abnormality detection unit for detecting at least one abnormality of the housing, wherein the smoothing unit includes at least one capacitor connected in parallel with the output of the forward conversion unit; The switching device is closed by the abnormality detecting unit when the abnormality detecting unit includes a first discharging resistor to be discharged and a switching device connected in series with the first discharging resistor, and the abnormality detecting unit detects an abnormality. And said open When the device is closed, the capacitor is discharged by said first discharge resistor, the smoothing unit, as the capacitor, via a diode connected so that a forward bias to the output of the forward converter unit The first discharge resistor is connected in parallel with the first capacitor .

Claims (9)

交流電源から供給される交流電力を直流電力に変換する順変換部と、
前記順変換部から出力されるリップルを含んだ直流電力を平滑する平滑部と、
前記平滑部によって平滑された直流電力を交流電力に変換する逆変換部と、
前記順変換部、前記平滑部、及び前記逆変換部を収納している筐体と、
前記順変換部、前記逆変換部、及び前記筐体の少なくとも一つの異常を検出する異常検出部と、
を備え、
前記平滑部は、
前記順変換部の出力に並列に接続されている少なくとも一つのコンデンサと、
前記コンデンサを放電する第１放電抵抗と、
前記第１放電抵抗と直列に接続されている開閉素子と、
を含み、
前記異常検出部によって異常が検出された場合に、前記開閉素子は前記異常検出部によって閉じられ、前記開閉素子が閉じられている場合に、前記コンデンサは前記第１放電抵抗によって放電される電源装置。 A forward conversion unit that converts AC power supplied from an AC power supply into DC power;
A smoothing unit for smoothing DC power including ripples output from the forward conversion unit;
An inverse conversion unit that converts DC power smoothed by the smoothing unit into AC power;
A housing that houses the forward conversion unit, the smoothing unit, and the reverse conversion unit;
An abnormality detection unit that detects an abnormality of at least one of the forward conversion unit, the inverse conversion unit, and the housing;
Equipped with
The smooth portion is
At least one capacitor connected in parallel with the output of the forward converter;
A first discharge resistor for discharging the capacitor;
A switching element connected in series with the first discharge resistor;
Including
The power supply apparatus in which the switching element is closed by the abnormality detection unit when an abnormality is detected by the abnormality detection unit, and the capacitor is discharged by the first discharge resistor when the switching element is closed. . 請求項１記載の電源装置であって、
前記平滑部は、前記第１放電抵抗と並列に接続されており、且つ前記コンデンサを常に放電する第２放電抵抗をさらに含み、
前記第２放電抵抗の抵抗値は、前記第１放電抵抗の抵抗値よりも大きい電源装置。 The power supply device according to claim 1, wherein
The smoothing unit further includes a second discharge resistor connected in parallel with the first discharge resistor and always discharging the capacitor.
The power supply device, wherein a resistance value of the second discharge resistor is larger than a resistance value of the first discharge resistor. 請求項１又は２記載の電源装置であって、
前記平滑部は、前記コンデンサとして、前記順変換部の出力にダイオードを介して接続されている第１コンデンサと、前記順変換部の出力に直接接続されており且つ前記第１コンデンサよりも静電容量が大きい第２コンデンサと、を含み、
前記第１放電抵抗は、前記第１コンデンサと並列に接続されている電源装置。 The power supply device according to claim 1 or 2, wherein
The smoothing unit is, as the capacitor, a first capacitor connected to the output of the forward conversion unit via a diode, and a direct connection to the output of the forward conversion unit, which is more electrostatic than the first capacitor. And a second capacitor having a large capacitance,
The power supply device, wherein the first discharge resistor is connected in parallel with the first capacitor. 請求項３記載の電源装置であって、
前記平滑部は、前記第２コンデンサと並列に接続されており、且つ前記第２コンデンサを常に放電する第３放電抵抗をさらに含み、
前記第３放電抵抗の抵抗値は、前記第１放電抵抗の抵抗値よりも大きい電源装置。 The power supply device according to claim 3, wherein
The smoothing unit further includes a third discharge resistor connected in parallel to the second capacitor and always discharging the second capacitor,
The power supply device, wherein a resistance value of the third discharge resistor is larger than a resistance value of the first discharge resistor. 請求項１から４のいずれか一項記載の電源装置であって、
前記開閉素子は、機械的接点を有する電源装置。 The power supply device according to any one of claims 1 to 4, wherein
The power supply device, wherein the switching element has a mechanical contact. 請求項１から４のいずれか一項記載の電源装置であって、
前記開閉素子は、半導体素子である電源装置。 The power supply device according to any one of claims 1 to 4, wherein
The switching device is a semiconductor device. 請求項１から６のいずれか一項記載の電源装置であって、
前記異常検出部は、前記交流電源から前記順変換部に過電流が流れた場合に前記順変換部に対する電力供給を遮断するブレーカを含み、前記順変換部に対する電力供給が前記ブレーカによって遮断された場合に前記開閉素子を閉じる電源装置。 The power supply device according to any one of claims 1 to 6, wherein
The abnormality detection unit includes a breaker that cuts off the power supply to the forward conversion unit when an overcurrent flows from the AC power supply to the forward conversion unit, and the power supply to the forward conversion unit is cut off by the breaker. In the case of the power supply device to close the switching element. 請求項１から６のいずれか一項記載の電源装置であって、
前記異常検出部は、前記筐体が開扉された場合に開扉を検出する開扉検出部を含み、開扉が前記開扉検出部によって検出された場合に前記開閉素子を閉じる電源装置。 The power supply device according to any one of claims 1 to 6, wherein
The power source apparatus, wherein the abnormality detection unit includes an open detection unit that detects an open door when the housing is opened, and closes the open / close element when the open detection is detected by the open detection unit. 請求項１から６のいずれか一項記載の電源装置であって、
前記逆変換部は、当該逆変換部の出力周波数が当該電源装置に接続される負荷の共振周波数となるように制御され、
前記異常検出部は、前記逆変換部の出力電圧と出力電流との位相ずれを検出する位相ずれ検出部を含み、位相ずれが前記位相ずれ検出部によって検出された場合に前記開閉素子を閉じる電源装置。 The power supply device according to any one of claims 1 to 6, wherein
The reverse conversion unit is controlled such that the output frequency of the reverse conversion unit is the resonance frequency of a load connected to the power supply device,
The abnormality detection unit includes a phase shift detection unit that detects a phase shift between an output voltage of the inverse conversion unit and an output current, and the power supply closes the switching element when the phase shift is detected by the phase shift detection unit. apparatus.
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