JP2017208992A - Electric circuit unit, power supply unit with circuit, and fuel battery system - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide an electric circuit unit that reflects an idea of aggregating a first electric potential and a second electric potential.SOLUTION: There exists a path passing through a first capacitor 331, a second anode 342a, and a second cathode 342c in this order from a first output part 351o to a second capacitor 332. There exists a path passing through a first anode 341a, a first cathode 341c, the second anode 342a, and the second cathode 342c in this order from a second terminal 312 to the second capacitor 332. There exists a path passing through a third anode 343a and a third cathode 343c in this order from the second terminal 312 to the second capacitor 332. The first output part 351o can output a first output electric potential determined depending on a first electric potential. The second terminal 312 is set to have a second electric potential. At the second capacitor 332 emerges a third electric potential.SELECTED DRAWING: Figure 2A

Description

  The present disclosure relates to an electric circuit unit, a power supply unit with circuit, and a fuel cell system.

  If a power source is connected to the electric circuit, the potential derived from the power source can be used. Patent Document 1 describes that two power sources are connected to an electric circuit, and two potentials derived from these power sources can be used.

  Patent Document 1 also describes a charge pump circuit. The n-stage charge pump circuit generates a potential that is n + 1 times that potential when there is one available potential. Here, n is an integer of 1 or more.

JP 2008-029085 A

  Patent Document 1 describes that, in a situation where one power supply exists, a potential different from the potential derived from this power supply is generated. However, Patent Document 1 does not mention generating a potential different from two potentials derived from these power sources in a situation where there are two power sources. The present inventors considered that an electric circuit reflecting the idea of adding the first potential and the second potential has utility value. The technology according to the present disclosure is based on such an idea.

That is, this disclosure
An electrical circuit in which a third potential portion appears when the first potential portion and the second potential portion are set,
A first terminal set to the first potential;
A second terminal set to the second potential;
A clock generator for generating a clock signal;
A first capacitor;
A second capacitor in which the third potential appears;
A first diode having a first anode and a first cathode;
A second diode having a second anode and a second cathode;
A third diode having a third anode and a third cathode;
A first switching element having a first output section capable of outputting a first output potential determined by the first potential,
The timing at which the potential of the first output unit becomes the first output potential and the timing at which the potential becomes not the first output potential are defined by the clock signal,
As a path connecting the first output unit and the second capacitor, the first capacitor, the second anode, and the second cathode in order from the first output unit to the second capacitor. There is a route through
As a path connecting the second terminal and the second capacitor, the first anode, the first cathode, the second capacitor in order from the second terminal toward the second capacitor. An electrical circuit unit comprising: a path passing through the anode and the second cathode; and a path passing through the third anode and the third cathode in order from the second terminal toward the second capacitor. provide.

  According to the technology according to the present disclosure, it is possible to generate the third potential based on the idea of adding the first potential and the second potential.

Configuration diagram of power supply unit with circuit Configuration diagram of drive unit Configuration diagram of drive unit Configuration diagram of drive unit Graph for explaining on-resistance of an example of MOSFET A perspective view showing a transformer mounted on a circuit board View of the transformer mounted on the circuit board as seen from above Enlarged view of transformer mounted on circuit board Enlarged view of transformer mounted on circuit board Diagram representing circuit board A diagram schematically showing the winding arrangement in a cross section parallel to the winding axis A diagram schematically showing the winding arrangement in a cross section parallel to the winding axis A diagram schematically showing the winding arrangement in a cross section parallel to the winding axis A diagram schematically showing the winding arrangement in a cross section perpendicular to the winding axis Illustration of the first winding Illustration of the second winding Front view of transformer Transformer side view Transformer bottom view Bobbin front view Bobbin side view Bottom view of bobbin The figure for demonstrating the advantage of the transformer of embodiment The figure for demonstrating the advantage of the transformer of embodiment The figure for demonstrating the advantage of the transformer of embodiment Configuration diagram of secondary circuit Diagram for explaining the current path Diagram for explaining the current path Configuration diagram of secondary circuit The figure for demonstrating the advantage of the electric circuit unit of embodiment The figure for demonstrating the advantage of the electric circuit unit of embodiment Configuration diagram of fuel cell system

(Knowledge by the present inventors)
In a situation where there is a first power source that provides a first potential and a second power source that provides a second potential that is greater than the first potential, the inventors have determined that the second potential is greater than the second potential. It was considered how to make the third potential usable, which is largely in the range below the sum of the first potential and the second potential, available.

  If a third power supply different from the first power supply and the second power supply is added, the third potential can be used. However, adding a power supply is expensive. Therefore, from the viewpoint of cost, it is desirable to generate the third potential by using two existing power supplies.

  It is also conceivable to multiply the first potential by an integer using a charge pump circuit. However, a just good potential in the above range is not necessarily generated. Moreover, even if it is in a situation where a good potential can be generated, the first power source needs to have a capacity corresponding to the number of stages of the required charge pump circuit.

  The inventors of the present invention are technologies that can generate a third potential within the above-described range in the above situation, and can generate the third potential by using two existing power sources. We studied a technology based on an idea that is different from the idea of multiplying by an integer. Through this study, the present inventors have come up with the idea of adding the first potential and the second potential. The technology according to the present disclosure is based on such an idea.

That is, the first aspect of the present disclosure is:
An electrical circuit unit in which a third potential portion appears when the first potential portion and the second potential portion are set;
A first terminal set to the first potential;
A second terminal set to the second potential;
A clock generator for generating a clock signal;
A first capacitor;
A second capacitor in which the third potential appears;
A first diode having a first anode and a first cathode;
A second diode having a second anode and a second cathode;
A third diode having a third anode and a third cathode;
A first switching element having a first output section capable of outputting a first output potential determined by the first potential,
The timing at which the potential of the first output unit becomes the first output potential and the timing at which the potential becomes not the first output potential are defined by the clock signal,
As a path connecting the first output unit and the second capacitor, the first capacitor, the second anode, and the second cathode in order from the first output unit to the second capacitor. There is a route through
As a path connecting the second terminal and the second capacitor, the first anode, the first cathode, the second capacitor in order from the second terminal toward the second capacitor. An electrical circuit unit comprising: a path passing through the anode and the second cathode; and a path passing through the third anode and the third cathode in order from the second terminal toward the second capacitor. provide.

  According to the first aspect, it is possible to generate the third potential based on the idea of adding the first potential and the second potential.

The second aspect of the present disclosure includes, in addition to the first aspect,
The first cathode and the second anode are connected to the same potential,
The first anode, the third anode, and the second terminal are connected to the same potential,
The second cathode, the third cathode, and the second capacitor provide an electric circuit unit connected to the same potential.

  The electric circuit unit of the second aspect is a specific example of the electric circuit unit of the first aspect.

The third aspect of the present disclosure, in addition to the first aspect or the second aspect,
The electric circuit unit is:
A second switching element having a second output section capable of outputting a second output potential determined by the third potential;
A third switching element driven by the potential of the second output unit,
The timing at which the potential of the second output unit becomes the second output potential and the timing at which the potential becomes not the second output potential provide an electric circuit unit defined by the clock signal.

  According to the third aspect, the generated third potential can be reflected in the output of the second switching element, and the third switching element can be driven by the output.

The fourth aspect of the present disclosure includes, in addition to the third aspect,
The second switching element is provided with an electric circuit unit to which the non-amplified clock signal is input.

  The electric circuit unit of the fourth aspect is easily configured.

The fifth aspect of the present disclosure includes, in addition to the third aspect,
The electrical circuit includes an amplifier that amplifies the clock signal,
An electric circuit unit to which the amplified clock signal is input is provided to the second switching element.

  In the fifth aspect, the amplified clock signal is input to the second switching element. For this reason, the operation of the second switching element tends to be stable.

The sixth aspect of the present disclosure includes, in addition to the third aspect,
The electric potential of the first output unit provides an electric circuit unit used by the second switching element as the amplified clock signal.

  Since the second switching element of the sixth aspect uses the amplified clock signal, it is easy to operate stably. In the sixth aspect, since the potential of the first output unit is used as the amplified clock signal, the operation of the second switching element is easily stabilized without providing an additional element such as an amplifier.

The seventh aspect of the present disclosure is in addition to any one of the third to sixth aspects,
A primary circuit having the third switching element;
With a transformer,
A secondary circuit,
The primary circuit and the transformer cooperate to generate an alternating voltage from the first direct voltage,
The secondary circuit provides an electric circuit unit that generates a second DC voltage from the AC voltage.

  According to the seventh aspect, power conversion using the third switching element can be performed.

The eighth aspect of the present disclosure is:
Any one electric circuit unit of the first to seventh aspects;
And at least one power source for generating direct-current power,
Provided is a power supply unit with circuit that uses the power supply power to set the potential of the first terminal to the first potential and to set the potential of the second terminal to the second potential.

  According to the eighth aspect, the first potential and the second potential can be easily set to the first terminal and the second terminal.

The ninth aspect of the present disclosure includes, in addition to the eighth aspect,
The power supply unit with circuit is provided in which the second potential is larger than the first potential.

  The circuit-equipped power supply unit according to the ninth aspect makes it possible to use a third potential that is larger than the second potential and within a range equal to or less than the sum of the first potential and the second potential.

A tenth aspect of the present disclosure includes
The electrical circuit unit of claim 7;
And at least one power source for generating direct-current power,
A circuit-equipped power supply unit is provided that generates the first DC voltage using the power supply power.

  According to the tenth aspect, the first DC voltage can be easily generated.

An eleventh aspect of the present disclosure includes
A power supply unit with a circuit according to any one of the eighth to tenth aspects,
The at least one power source provides a fuel cell system that is at least one fuel cell that generates the power from hydrogen and oxygen.

  According to the eleventh aspect, it is possible to provide a fuel cell system utilizing the circuit-equipped power supply unit according to the eighth to tenth aspects.

The twelfth aspect of the present disclosure includes, in addition to the eleventh aspect,
The at least one fuel cell includes a first port for extracting a voltage used for controlling an electronic component of the fuel cell system, and a second port for extracting a voltage used for controlling an auxiliary device of the fuel cell system. ,
The fuel cell system uses the first port to set the potential of the first terminal to the first potential, and uses the second port to set the potential of the second terminal to the second potential. Provided is a fuel cell system that is set to a potential of

  According to the twelfth aspect, the first potential and the second potential can be easily set to the first terminal and the second terminal.

  Hereinafter, embodiments of the present disclosure will be described with reference to the drawings. The present disclosure is not limited to the following embodiments.

  FIG. 1 shows a power supply unit 100 with circuit of this embodiment. The power supply unit with circuit 100 includes an electric circuit unit 200 and a power supply 600. The electric circuit unit 200 includes a primary side circuit 300, a transformer 400, and a secondary side circuit 500. The electric circuit unit 200 has a function of converting a voltage. When attention is paid to the function, the electric circuit unit 200 can be called a power converter. The electric circuit unit 200 has a circuit board (a circuit board 210 is shown as a specific example of the circuit board in FIG. 5), and a primary circuit 300 and a secondary circuit 500 are formed on the circuit board. The primary side circuit 300 is connected to the primary side terminal of the transformer 400. The secondary side circuit 500 is connected to the secondary side terminal of the transformer 400.

The power source 600 generates DC power. The circuit-equipped power supply unit 100 generates a DC voltage (first DC voltage) V _dc1 using power supply power. The primary circuit 300 and the transformer 400 cooperate to generate an AC voltage (AC voltage applied to the third winding 433) V _ac from the first DC voltage V _dc1 . The secondary circuit 500 generates a second DC voltage V _dc2 from the AC voltage V _ac .

As shown in FIG. 1, the primary circuit 300 includes a pair of switching elements 353A and 353B. The transformer 400 includes two primary windings (first windings 431 and 432) and one secondary winding (third winding 433). A first DC circuit in which one of the pair of switching elements (switching element 353A in FIG. 1) and the first winding 431 are connected in series is formed. A first DC voltage V _dc1 is applied to the first DC circuit. A second series circuit is formed in which the other of the pair of switching elements (switching element 353B in FIG. 1) and the second winding 432 are connected in series. The first DC voltage V _dc1 is applied to the second series circuit. One of the pair of switching elements (switching element 353A in FIG. 1) generates a voltage applied to the first winding 431 from the first DC voltage V _dc1 . A pair of the other switching element (Fig. 1, switching element 353B) generates a voltage to be applied from the first DC voltage V _dc1 to the second winding 432. At the timing when the switching element 353A is turned on, the switching element 353B is turned off. At this timing, a voltage is applied to the first winding 431 and a positive voltage is applied to the third winding 433. The switching element 353B is turned on at the timing when the switching element 353A is turned off. At this timing, a voltage is applied to the second winding 432 and a negative voltage is applied to the third winding 433. The AC voltage V _ac is applied to the third winding 433 by repeatedly shifting these timings. As understood from the above description, the power source 600, the pair of switching elements 353A and 353B, and the transformer 400 constitute a push-pull inverter circuit. The AC voltage V _ac is converted to the second DC voltage V _dc2 by the secondary circuit 500.

Note that a full-bridge inverter circuit (for example, see FIG. 15) may be employed instead of the push-pull inverter circuit. In addition, a configuration in which the primary circuit 300 includes one or three or more (four in a full bridge inverter circuit) similar switching elements instead of the pair of switching elements 353A and 353B may be employed. Even in such a configuration, the primary side circuit 300 and the transformer 400 cooperate to generate the AC voltage V _ac from the first DC voltage V _dc1 , and the secondary side circuit 500 generates the second DC from the AC voltage V _ac . It is possible to configure the electrical circuit unit to generate the voltage V _dc2 .

[Power supply 600]
The power source 600 generates DC power. As the power source 600, a known power source can be used. In FIG. 1, the power source 600 is a single power source, but two or more power sources may be used. That is, the power supply unit with circuit 100 may have at least one power supply. The at least one power source may be at least one fuel cell that generates power from hydrogen and oxygen. In this case, a fuel cell system including the power supply unit with circuit 100 can be configured (details will be described later).

The power supply 600 has a main port, a first port, and a second port not shown. A first DC voltage V _dc1 is extracted from the main port. The first port and the second port are configured to extract a voltage different from the first DC voltage V _dc1 . Specifically, from the first port, a voltage used to set the potential of a first terminal 311 (FIG. 2A or the like), which will be described later, to the first potential or to control an electronic component is taken out. . From the second port, a voltage used for setting the potential of the second terminal 312 to the second potential or controlling the auxiliary machine of the circuit-equipped power supply unit 100 is taken out. In the present embodiment, the voltage extracted from the first port is lower than the voltage extracted from the second port. In the present embodiment, each of the first port and the second port has a finite power supply capability.

[Primary circuit 300]
As described above, the primary circuit 300 generates the AC voltage V _ac from the first DC voltage V _{dc1 in} cooperation with the transformer 400. As illustrated in FIG. 1, the primary circuit 300 according to the present embodiment includes a pair of switching elements (third switching elements) 353A and 353B and at least one driving unit that drives them. .

  An example of the drive unit that drives the switching element 353A is the drive unit 301A illustrated in FIG. 2A. The drive unit 301A (electric circuit unit 200) includes a first terminal 311, a second terminal 312, a third terminal 313, a clock generator 320, a first capacitor 331, and a second capacitor. 332, a first diode 341, a second diode 342, a third diode 343, a first switching element 351, and a second switching element 352.

  The first terminal 311 is a terminal set at the first potential. The second terminal 312 is a terminal set at the second potential. In the present embodiment, the second potential is larger than the first potential.

  In the circuit-equipped power supply unit 100 of the present embodiment, the potential of the first terminal 311 is set to the first potential by using the direct-current power of the power supply 600. Further, the potential of the second terminal 312 is set to the second potential by using the DC power source of the power source 600.

  The clock generator 320 generates a clock signal. The clock generator 320 of this embodiment is a micro control unit (MCU). The clock signal of the present embodiment is a pulse wave having an amplitude that is a potential difference between the first potential and the ground potential. In the example of FIG. 2A, the clock generator 320 can generate such a pulse wave by being connected to the first terminal 311 and the ground potential.

  As the first capacitor 331, a known capacitor can be used.

  A known capacitor can be used as the second capacitor 332. In the second capacitor 332, a third potential appears. Specifically, the second capacitor 332 has one end 332m where the third potential appears and the other end 332n connected to the ground potential. In the present embodiment, the third potential is greater than the second potential and greater than the first potential.

  In the present embodiment, the capacity of the second capacitor 332 is made larger than the capacity of the first capacitor 331 from the viewpoint of stabilizing the potential of the one end 332 m of the second capacitor 332. From the same point of view, the ratio of the capacity of the second capacitor 332 to the capacity of the first capacitor 331 can be, for example, 3 to 20 times. Further, the capacitance of the first capacitor 331 can be set to, for example, 10 μF to 100 μF, and the capacitance of the second capacitor 332 can be set to, for example, 300 μF to 2000 μF.

  The first diode 341 includes a first anode 341a and a first cathode 341c. The second diode 342 includes a second anode 342a and a second cathode 342c. The third diode 343 includes a third anode 343a and a third cathode 343c. As the first diode 341, the second diode 342, and the third diode 343, known diodes can be used.

  In the present embodiment, the first cathode 341c and the second anode 342a are connected to the same potential. The first anode 341a, the third anode 343a, and the second terminal 312 are connected to the same potential. The second cathode 342c, the third cathode 343c, and the second capacitor 332 (one end 332m thereof) are connected to the same potential.

  The first switching element 351 of the present embodiment includes a first input unit 351i, a first output unit 351o, a first non-grounding unit 351u, and a first grounding unit 351g.

  The first output unit 351o can output the first output potential. The first output potential is determined by the first potential. The timing at which the potential of the first output unit 351o becomes the first output potential and the timing at which the potential becomes not the first output potential are defined by the clock signal. In the present embodiment, the potential of the first output unit 351o changes in a pulse shape between a first output potential and a potential that is not the first output potential. Specifically, the first output potential is the first potential. The potential that is not the first output potential is a potential lower than the first output potential in the present embodiment, and specifically, is a ground potential.

  In the example illustrated in FIG. 2A, the first input unit 351 i of the first switching element 351 is connected to the clock generator 320. The first non-grounding part 351u is set to the first potential. The first ground portion 351g is set to the ground potential. The potential of the first output unit 351o is switched between the first potential and the ground potential.

  As can be understood from FIG. 2A, there is one path as a path connecting the first output unit 351 o and the second capacitor 332. This one path is a path (path X) passing through the first capacitor 331, the second anode 342a, and the second cathode 342c in order from the first output unit 351o toward the second capacitor 332. There are two paths for connecting the second terminal 312 and the second capacitor 332. One of the two paths includes a first anode 341a, a first cathode 341c, a second anode 342a, and a second cathode 342c in order from the second terminal 312 toward the second capacitor 332. This is a route (route Y) through. The other of the two paths is a path (path Z) passing through the third anode 343a and the third cathode 343c in order from the second terminal 312 toward the second capacitor 332.

  The third terminal 313 is connected to the same potential as the one end 332 m of the second capacitor 332. A third potential can be extracted from the third terminal 313. However, the third terminal 313 can be omitted.

  The second switching element 352 is connected to the second capacitor 332 (one end 332m thereof). The second switching element 352 includes a second input unit 352i, a second output unit 352o, a second non-grounding unit 352u, and a second grounding unit 352g.

  The second output unit 352o can output the second output potential. The second output potential is determined by the third potential. The timing at which the potential of the second output unit 352o becomes the second output potential and the timing at which the potential becomes not the second output potential are defined by the clock signal. In the present embodiment, the potential of the second output unit 352o changes in a pulse shape between a second output potential and a potential that is not the second output potential. Specifically, the second output potential is the third potential. The potential that is not the second output potential is a potential lower than the second output potential in the present embodiment, and specifically, is a ground potential.

  In the example illustrated in FIG. 2A, an unamplified clock signal is input to the second switching element 352. For this reason, the electric circuit unit 200 is easily configured. In this example, the second switching element 352 generates a second output potential (specifically, a third potential) by amplifying the clock signal.

  In the example illustrated in FIG. 2A, the second input unit 352 i of the second switching element 352 is connected to the clock generator 320. The second non-grounding part 352u is set to the third potential. The second ground portion 352g is set to the ground potential. The potential of the second output unit 352o is switched between the third potential and the ground potential.

  The third switching element 353A (and 353B) is driven by the potential of the second output unit 352o.

  In the present embodiment, the third switching element 353A (and 353B) is a MOSFET (Metal Oxide Semiconductor Field Effect Transistor). The MOSFET 353A (and 353B) has a gate 353g, a drain 353d, and a source 353s. The gate 353g is connected to the second output unit 352o.

  Hereinafter, the operation of the drive unit 301A of the present embodiment will be described.

  In the initial state where the potential of the first output unit 351o is lower than the first output potential, the charge supplied from the second terminal 312 is accumulated in the other end 331n of the first capacitor 331. The potential of the other end 331n of the first capacitor 331 is a potential that depends on the second potential of the second terminal 312 and the voltage drop caused by the first diode 341. The charge supplied from the second terminal 312 is accumulated at one end 332 m of the second capacitor 332. The potential of the second capacitor 332 is a potential that depends on the second potential of the second terminal 312 and the voltage drop caused by the third diode 343 in the path Z.

  Next, when the potential of the first output unit 351o is switched to the first output potential, a charge is applied from the first output unit 351o (more precisely, from the first terminal 311) to the one end 331m of the first capacitor 331. Is supplied. By this supply, the potential of the first capacitor 331 at one end 331m and the other end 331n is raised by the amount corresponding to the first output potential. By this increase, the charge accumulated in the other end 331n of the first capacitor 331 moves to one end 332m of the second capacitor 332 through the path X. As a result, the potential of the one end 332m includes the first output potential of the first output unit 351o, the second potential of the second terminal 312, the voltage drop due to the first diode 341 existing in the path X, the path X and This depends on the voltage drop caused by the second diode 342 existing in the overlapping portion of the path Y. That is, the potential at the one end 332m is the third potential.

  Next, when the potential of the first output unit 351o is switched to a potential lower than the first output potential, charge is supplied from the second terminal 312 to the other end 331n of the first capacitor 331. At this time, the electric charge accumulated in the other end 331m of the first capacitor 331 is discharged through the first output unit 351o and the first ground unit 351g.

  Thereafter, the potential of the first output unit 351o is repeatedly switched between the first output potential and a potential lower than the first output potential. By repeating this, the movement of the charge from the other end 331n of the first capacitor 331 to the one end 332m of the second capacitor 332, the supply of the charge from the second terminal 312 to the other end 331n of the first capacitor 331, Is repeated. In the present embodiment, the capacity of the second capacitor 332 is larger than the capacity of the first capacitor 331. For this reason, after the potential of the first output unit 351o once becomes the first output potential, the timing at which the potential of the first output unit 351o becomes lower than the first output potential appears intermittently. The potential of the capacitor 332 does not drop significantly from the third potential. That is, in the steady state, the potential of the second capacitor 332 is substantially maintained at the third potential.

  As described above, the second output potential is determined by the third potential, and in the present embodiment, the third potential is larger than the second potential and larger than the first potential. For this reason, according to the present embodiment, a large second output potential can be ensured. Moreover, in the present embodiment, the potential of the one end 332m of the second capacitor 332 is substantially maintained at the third potential. For this reason, according to the present embodiment, the second output potential can be maintained at substantially the same magnitude. That is, the potential of the second output unit 352o can be made into a pulse shape with sufficiently large and uniform amplitude. Then, the third switching element 353A is driven by such a potential.

  Hereinafter, further description will be given with specific examples. In this specific example, the potential of the first output portion 351o changes in a pulse shape between 5 V (first potential) and 0 V (potential lower than the first potential), and the voltage drop due to the first diode 341 Is 0.8V, the voltage drop due to the second diode 342 is 0.8V, and the voltage drop due to the third diode 343 is 0.8V. It is assumed that the second output potential is the third potential. Further, it is assumed that the third switching element 353A is a MOSFET 353A.

  In this specific example, in the initial state where the potential of the first output unit 351o is 0V, the potential of the other end 331n of the first capacitor 331 is 12V of the second terminal 312 and the voltage drop due to the first diode 341. The potential depends on 0.8V. That is, the potential of the other end 331n is 12V−0.8V = 11.2V. The potential of one end 332m of the second capacitor 332 is a potential depending on 12V of the second terminal 312 and a voltage drop of 0.8V due to the third diode 343. That is, the potential of the one end 332m is 12V−0.8V = 11.2V.

  Next, when the potential of the first output unit 351o is switched to 5V, the potential of one end 331m and the other end 331n of the first capacitor 331 is increased by 5V, and becomes 11.2V + 5V = 16.2V. The potential of one end 332m of the second capacitor 332 includes 12V of the second terminal 312, 5V of the first output unit 351o, a voltage drop of 0.8V due to the first diode 341, and a voltage due to the second diode 342. It depends on the drop of 0.8V. That is, the potential of the one end 332m is 12V + 5V−0.8V−0.8V = 15.4V. This 15.4 V corresponds to the third potential.

  Next, the potential of the first output unit 351o is switched to 0V. Thereafter, the potential of the first output unit 351o is repeatedly switched between 5V and 0V. Thereby, the potential of the one end 332m of the second capacitor 332 is substantially maintained at 15.4V.

  In the case of the above specific example, the potential of the second output unit 352o can be changed in a pulse shape between 0V and 15.4V. This means that the potential of the gate 353g can be changed in a pulse shape between 0V and 15.4V.

  Usually, when the gate voltage for turning on the MOSFET is not sufficiently high, the on-resistance (the resistance between the drain and the source when the MOSFET is on) becomes high. In the example shown in FIG. 3, the on-resistance when the gate voltage is 5V or 12V exceeds 1 mΩ. On the other hand, the on-resistance when the gate voltage is 15.4 V is less than 1 mΩ. Therefore, when the gate voltage of the MOSFET is changed in a pulse shape between 5 V (first potential) and 0 V, or changed in a pulse shape between 12 V (second potential) and 0 V. It can be seen that pulsing between 15.4V and 0V helps reduce the on-resistance of the MOSFET and reduce the power loss in the MOSFET compared to.

  In the power supply unit with circuit 100 of the present embodiment, it is desirable to perform soft switching of the switching elements (MOSFETs) 353A and 353B. Specifically, a current resonance circuit is configured in the power supply unit with circuit 100, and the switching elements 353A and 353B perform switching when the current flowing through the switching elements 353A and 353B is zero or sufficiently small by utilizing the current resonance phenomenon. Is desirable. Such switching is called ZCS (Zero Current Switching). According to such switching, switching loss can be reduced. Note that when a fuel cell system including the circuit-equipped power supply unit 100 is configured, a large current tends to flow through the switching elements 353A and 353B. In such a case, having the switching elements 353A and 353B perform ZCS is particularly advantageous from the viewpoint of switching loss reduction.

  Also, all of the three switching elements 351, 352, and 353A shown in FIG. 2A operate based on the clock signal. That is, according to the present embodiment, the switching elements 351, 352, and 353A can be synchronized.

  In the modified embodiment, the electric circuit unit 200 amplifies the clock signal. The amplified clock signal is input to the second switching element 352. For this reason, the operation of the second switching element 352 is easily stabilized.

  An example of a modified embodiment will be described with reference to FIG. 2B. The driver 302A (302B) illustrated in FIG. 2B includes an amplifier 355 that amplifies the clock signal. The amplified clock signal is input to the second switching element 352 (second input portion 352i thereof). The clock generator 320, the amplifier 355, and the second switching element 352 are connected in this order.

  Specifically, the amplifier 355 includes a fourth switching element 354. The fourth switching element 354 includes a fourth input unit 354i, a fourth output unit 354o, a fourth non-grounding unit 354u, and a fourth grounding unit 354g. The fourth output unit 354o can output a fourth output potential determined by the first potential. The timing at which the potential of the fourth output unit 354o becomes the fourth output potential and the timing at which the potential becomes not the fourth output potential are defined by the clock signal. In the present embodiment, the potential of the fourth output unit 354o changes in a pulse shape between a fourth output potential and a potential that is not the fourth output potential. The potential of the fourth output unit 354o is used by the second switching element 352 as an amplified clock signal. Specifically, the fourth output potential is the first potential. The potential that is not the fourth output potential is a potential lower than the first potential in the present embodiment, and specifically, is a ground potential.

  In the example illustrated in FIG. 2B, the fourth input unit 354 i of the fourth switching element 354 is connected to the clock generator 320. The fourth non-grounding part 354u is set to the first potential. The fourth ground portion 354g is set to the ground potential. The potential of the fourth output unit 354o is switched between the first potential and the ground potential.

  Another example of the modified embodiment will be described with reference to FIG. 2C. In the drive unit 303A (303B) illustrated in FIG. 2C, the first output unit 351o of the first switching element 351 is connected to the second switching element 352 (the second input unit 352i) together with the first capacitor 331. ing. The potential of the first output unit 351o is used by the second switching element 352 as an amplified clock signal. According to the example of FIG. 2C, the operation of the second switching element 352 is easily stabilized without providing an additional element such as an amplifier.

  The switching element 353B can also be driven by the drive unit 301B, 302B, or 303B having the same configuration as the drive unit 301A, 302A, or 303A. That is, the two switching elements 353A and 353B can be driven by the two driving units.

  The driving of the two switching elements 353A and 353B can be realized by one driving unit 301A, 302A or 303A.

[Transformer 400]
As understood from FIG. 1, the transformer 400 generates an AC voltage V _ac from the first DC voltage V _{dc1 in} cooperation with the primary side circuit 300. The transformer 400 can be attached to the circuit board 210 (see FIGS. 4A to 5). Hereinafter, the transformer 400 will be described with reference to FIGS. 4A to 11. In FIGS. 6A to 6D, the bobbin 410 is omitted for easy viewing of the drawings. In FIG. 6B and FIG. 6C, the iron core 420 is omitted in consideration of easy viewing of the drawings. In FIG. 6C, the first winding 431 and the second winding 432 are omitted in view of easy viewing. The arrows in FIGS. 6A to 6D represent directions from the winding start position toward the winding end position.

  The circuit board 210 to which the transformer 400 is attached has a flat appearance. A solid pattern is formed on the circuit board 210. The solid pattern is composed of a group of metal parts. Specifically, the solid pattern has a uniform thickness and is formed of a group of metal parts. In the present embodiment, the circuit board 210 has a multilayer structure, and a solid pattern layer including a solid pattern is formed on the inner layer of the multilayer structure. However, a solid pattern can be formed on the surface layer of the circuit board 210. Examples of the metal constituting the solid pattern include copper and aluminum. The thickness of the solid pattern (a group of metal parts) is not particularly limited, but is, for example, 15 μm to 1000 μm from the viewpoint of ensuring heat dissipation. Further, from the viewpoint of ensuring heat dissipation, a plurality of solid pattern layers can be provided.

  FIG. 5 is a plan view of the circuit board 210 as viewed along its thickness direction. A region 211 indicated by a one-dot chain line is a region where a solid pattern is formed in the primary circuit 300. A region 401 indicated by a substantially square dotted line is a region where the transformer 400 is arranged. In the example of FIG. 5, more than half of the area 401 overlaps with the area 211. The area 211 extends to a position that does not overlap with the area 401. The area of the region 211 is larger than the area of the region 401. In the region 211, there are holes 241 and 242 into which the terminal pins 441 and 442 of the two primary windings 431 and 432 of the transformer 400 are inserted. Holes 241 and 242 guide terminal pins 441 and 442 to a solid pattern. Thus, the terminal pins 441 and 442 are in contact with the solid pattern and are connected to the primary circuit 300. A region 220 indicated by a two-dot chain line is a region corresponding to the secondary circuit 500. In the region 220, there are holes 243m and 243n into which the terminal pins 443m and 443n of the secondary winding 433 are inserted. The terminal pins 443m and 443n are connected to the secondary circuit 500 while being inserted into the holes 243m and 243n.

  The transformer 400 includes a bobbin 410 (see FIGS. 4A to 4D and FIGS. 8A to 9C), an iron core 420 (see FIGS. 4A, 4B, 4D, 6A, 6D, and 8A to 8C), a winding Line set 438 (see FIGS. 4B and 6A).

  As shown in FIGS. 9A to 9C, the bobbin 410 of this embodiment includes a terminal side flange portion 411, a lead wire side flange portion 412, and a body portion 415. As shown in FIGS. 8C and 9C, the terminal-side flange portion 411 includes at least one (a plurality of, specifically, four) first terminal pins 441 and at least one (shown in the drawing). In the example, there are a plurality of, specifically four) second terminal pins 442, at least one (one in the illustrated example) one end terminal pin 443m and at least one (one in the illustrated example). The other end side terminal pin 443n is fixed. The lead wire side flange portion 412 is provided on the side opposite to the terminal side flange portion 411 when viewed from the body portion 415. A winding set 438 is wound around the body portion 415. The bobbin 410 has a hole 419 for inserting a part of the iron core 420. The hole 419 passes through the body portion 415. Terminal pins 441, 442, 443m and 443n are made of metal. An example of the metal constituting the terminal pins 441, 442, 443m and 443n is copper. The terminal pins 441, 442, 443m and 443n may be made of iron wires whose surfaces are Sn-Cu plated.

  As shown in FIGS. 4A to 4D, 6A and 8A to 8C, the iron core 420 is attached to the bobbin 410. The iron core 420 includes a portion inserted into the hole 419 of the bobbin 410, a pair of portions at a position where the winding set 438 is sandwiched from the outer peripheral side of the winding shaft, and the pair of portions on the terminal side flange portion 411 side. It has the part to connect, and the part which connects this pair of part by the lead wire side flange part 412 side. Specifically, the iron core 420 is an EER type iron core. Examples of the material constituting the iron core 420 include ferrite, silicon steel, and permalloy.

  As shown in FIG. 4B, the winding set 438 is wound around the bobbin 410. As shown in FIG. 6A, the winding set 438 includes a primary side winding portion 435 and a secondary side winding portion 436. The primary winding 435 includes a first winding 431 and a second winding 432 that are primary windings. The secondary winding 436 has a third winding 433 that is a secondary winding. The first winding 431 and the third winding 433 (the first winding portion 431w and the third winding portion 433w) are magnetically coupled. The second winding 432 and the third winding 433 (the second winding portion 432w and the third winding portion 433w) are magnetically coupled. An insulating member 480 is interposed between the first winding 431 and the third winding 433 (between the first winding portion 431w and the third winding portion 433w). An insulating member 480 is interposed between the second winding 432 and the third winding 433 (between the second winding portion 432w and the third winding portion 433w). The insulating member 480 is, for example, an insulating tape. 4A to 4D, the insulating member 480 also covers a part of the outer periphery of the iron core 420.

  The number of turns of the third winding 433 is greater than the number of turns of the first winding 431 and is greater than the number of turns of the second winding 432. Therefore, the transformer 400 can boost the voltage of the primary side circuit 300 and output the boosted voltage to the secondary side circuit 500. In this case, the current flowing through the first winding 431 is larger than the current flowing through the third winding 433, and the current flowing through the second winding 432 is larger than the current flowing through the third winding 433. From the viewpoint of ensuring current resistance, the diameter of the first winding 431 is larger than the diameter of the third winding 433, and the diameter of the second winding 432 is larger than the diameter of the third winding 433. It is the diameter.

  7A, FIG. 8A, FIG. 8B, FIG. 8C, FIG. 9A, FIG. 9B, and FIG. 9C, one end 431m of the first winding 431 is at least one first terminal that can be inserted into the circuit board 210. The pin 441 is fixed to the bobbin 410. In the present embodiment, the first winding 431 is a bundle of a plurality of wires, and each of the plurality of wires constituting the first winding 431 is connected to different first terminal pins 441. In this example, the number of the wire rods is four, and the number of the first terminal pins 441 is four. Specifically, in this example, the first winding 431 approaches the first terminal pin 441 in a bundle of a plurality of wires before passing through the insulating sleeve 490, and after passing through the insulating sleeve 490, the first winding 431 is bundled. Is in a state of being released, and each wire reaches the first terminal pin 441 which is different from each other. In the present embodiment, the first winding 431 and the first terminal pin 441 are soldered.

  As can be understood from FIGS. 4C, 7B, 8B, 8C, 9B, and 9C, one end 432m of the second winding 432 is provided by at least one second terminal pin 442 that can be inserted into the circuit board 210. It is fixed to the bobbin 410. In the present embodiment, the second winding 432 is a bundle of a plurality of wires, and in the example of FIG. 4C, each of the plurality of wires constituting the second winding 432 is connected to different second terminal pins 442. Yes. In the example of FIG. 4C, the number of wires is four, and the number of second terminal pins 442 is also four. Specifically, in the example of FIG. 4C, the second winding 432 approaches the second terminal pin 442 in a bundle of a plurality of wires before passing through the insulating sleeve 490, and after passing through the insulating sleeve 490. Is in a state in which the bundle is unwound, and the respective wire rods reach different second terminal pins 442. In the present embodiment, the second winding 432 and the second terminal pin 442 are soldered.

  As understood from FIGS. 8A, 8C, 9A, and 9C, one end 433m of the third winding 433 is fixed to the bobbin 410 by at least one end-side terminal pin 443m that can be inserted into the circuit board 210. ing. As understood from FIGS. 4C, 8C, and 9C, the other end 433n of the third winding 433 is fixed to the bobbin 410 by at least one other end-side terminal pin 443n that can be inserted into the circuit board 210. .

  As shown in FIGS. 6B and 7A, the first winding 431 has a first winding portion 431w that is a portion from the winding start position to the winding end position. In the first winding 431 of the present embodiment, one end 431m of the first winding 431, one end 431wm of the first winding portion 431w, the other end 431wn of the first winding portion 431w, and the first winding 431 The other end 431n and the other end 431n not fixed to the bobbin 410 are arranged in this order. Then, as shown in FIG. 7A, when a plane passing through one end 431wm of the first winding part 431w and orthogonal to the winding axis 431wx of the first winding part 431w is defined as a first reference plane 431wr, The winding portion 431w has a shape (first shape) that moves away from the first reference plane 431wr while rotating in the first rotation direction 431wd. Specifically, the first shape is a spiral shape. The first winding portion 431w does not have a portion that approaches the first reference plane 431wr while rotating in the first rotation direction 431wd. In addition, the 1st rotation direction 431wd is a direction which goes around the winding shaft 431wx.

  As shown in FIGS. 6B and 7B, the second winding 432 has a second winding portion 432w that is a portion from the winding start position to the winding end position. In the second winding 432 of the present embodiment, one end 432m of the second winding 432, one end 432wm of the second winding portion 432w, the other end 432wn of the second winding portion 432w, and the second winding 432 The other end 432n and the other end 432n not fixed to the bobbin 410 are arranged in this order. Then, as shown in FIG. 7B, when a plane that passes through one end 432wm of the second winding portion 432w and is orthogonal to the winding axis 432wx of the second winding portion 432w is defined as a second reference plane 432wr, The winding portion 432w has a shape (second shape) that moves away from the second reference plane 432wr while rotating in the second rotation direction 432wd. Specifically, the second shape is a spiral shape. The second winding portion 432w does not have a portion that approaches the second reference plane 432wr while rotating in the second rotation direction 432wd. The second rotation direction 432wd is a direction that goes around the winding shaft 432wx, and is the opposite direction to the first rotation direction 431wd.

  Advantages based on the first winding 431 and the second winding 432 having the above-described configuration will be described in comparison with the transformer shown in FIG. 10A and the transformer shown in FIG. 10B.

  In the transformer 850 shown in FIG. 10A, each of the first winding 851, the second winding 852, and the third winding 853 is wound around the iron core 855 in the order of the arrows. In each of the first winding 851, the second winding 852, and the third winding 853, there are a portion that is wound up and a portion that is wound down, and an insulating member 854 is interposed between these portions. Yes. One end of the first winding 851 is fixed to the bobbin by a terminal pin 851Pm. The other end of the first winding 851 is fixed to the bobbin by a terminal pin 851Pn. One end of the second winding 852 is fixed to the bobbin by a terminal pin 852Pm. The other end of the second winding 852 is fixed to the bobbin by a terminal pin 852Pn. One end of the third winding 853 is fixed to the bobbin by a terminal pin 853Pm. The other end of the third winding 853 is fixed to the bobbin by a terminal pin 853Pn. Even if the transformer 850 is used instead of the transformer 400, the push-pull inverter circuit described with reference to FIG. 1 can be configured. Specifically, the terminal pin 851Pm may be disposed at the position 182 in FIG. 1, the terminal pin 851Pn may be disposed at the position 181, the terminal pin 852Pm may be disposed at the position 183, and the terminal pin 852Pn may be disposed at the position 184. However, the method of connecting both ends of the first winding 851 and both ends of the second winding 852 to the positions 181 to 184 using terminal pins is not necessarily suitable for ensuring the degree of freedom in designing the circuit board.

  In order to increase the degree of freedom in designing the circuit board, the portions wound down from the first winding 851 and the second winding 852 are eliminated, and a part of the first winding 851 and the second winding 852 is pulled out and pulled out. It may be necessary to modify the line. That is, instead of the first winding 851 and the second winding 852, the first winding 856 and the second winding 857 shown in FIG. 10B are adopted, and one end of the first winding 856 is used as a bobbin by the terminal pin 856P. One end of the second winding 857 is fixed to the bobbin by the terminal pin 857P, a part of the other end side of the first winding 856 is drawn out as a lead line 856L, and one end of the other end side of the second winding 857 is It seems that the part may be drawn out as a lead line 857L. This is because the reachable range of the leading end of the lead line is wide, and the connection position of the leading end of the lead line on the circuit board is unlikely to be a restriction on the design of the circuit board. However, this makes it difficult to obtain good heat dissipation. That is, when this modified transformer is used, the terminal pin 856P is arranged at the position 182 in FIG. 1, and the terminal pin 857P is arranged at the position 183 (in the example of FIG. 10B, the first winding 856 and the first winding 856P are arranged). Note that both of the two windings 857 have a first shape). However, as understood from FIG. 1, the position 182 and the position 183 are not connected to the same potential. This means that both the terminal pin 856P and the terminal pin 857P cannot be brought into contact with a group of metal parts (solid pattern or the like) on the circuit board. This does not provide good heat dissipation. Since the lead line 856L is disposed at the position 181, the lead line 856L and the terminal pin 857P can be brought into contact with a group of metal parts on the circuit board. However, even in this case, it is difficult to obtain good heat dissipation. In order to ensure insulation, it is necessary for the lead wire to be covered with a covering material, and the covering material usually has a thermal resistance close to that of the heat insulating material. This is to limit.

  On the other hand, in the first winding 431 of the transformer 400 of the present embodiment, the other end 431n is not fixed to the bobbin 410. For this reason, a part between the other end 431wn of the first winding part 431w and the other end 431n of the first winding 431 can be used as the lead line 431L. Similarly, a portion between the other end 432wn of the second winding portion 432w and the other end 432n of the second winding 432 can be used as the lead wire 432L. That is, the transformer 400 of this embodiment is more advantageous than the transformer 850 shown in FIG. 10A from the viewpoint of ensuring the degree of freedom in designing the circuit board.

  Moreover, in the transformer 400 of the present embodiment, the first winding portion 431w of the first winding 431 has the first shape, and the second winding portion 432w of the second winding 432 has the second shape. Yes. For this reason, the push-pull inverter circuit described with reference to FIG. 1 is realized by arranging the first terminal pin 441 at the position 181 and arranging the second terminal pin 442 at the position 183. The position 181 and the position 183 are connected to the same potential. Therefore, both the first terminal pins 441 and the second terminal pins 442 can be brought into contact with a group of metal parts (solid pattern) on the circuit board 210.

  For the reasons described above, the transformer 400 of this embodiment is suitable for achieving both heat transfer (heat dissipation) from the winding portion of the winding to the circuit board and ensuring the degree of design freedom of the circuit board. Actually, in the present embodiment, at least one first terminal pin 441 is inserted into the hole 241 of the circuit board 210, and at least one second terminal pin 442 is inserted into the hole 242 of the circuit board 210. Heat dissipation is ensured by bringing 442 into contact with a group of metal parts (solid pattern). Further, by using the portion between the other end 431wn and the other end 431n as the lead line 431L and using the portion between the other end 432wn and the other end 432n as the lead line 432L, the circuit board 210 can be freely designed. The degree is secured. These effects are also obtained in cases other than when the transformer 400 is used in the configuration of a push-pull inverter circuit. Specifically, when the transformer 400 is attached to the circuit board 210, one end of the first winding 431 and one end of the second winding 432 are connected to the same potential, and both ends of the first winding 431 are connected. When the other and the other end of the second winding 432 are not connected to the same potential, the same effect can be obtained. Note that the technology of the primary side circuit 300, the secondary side circuit 500, etc. of the present disclosure can be used in combination with the transformer 850 shown in FIG. 10A or the transformer shown in FIG. 10B. .

  Another advantage can be obtained by using a part including the other ends 431n and 432n of the windings 431 and 432 as the lead wires 431L and 432L while the terminal pins 441 and 442 are in contact with a group of metal parts (solid pattern). is there. That is, both when the transformer 400 of this embodiment is employed and when the transformer of FIG. 10A is employed, insulation between the position 181 and the position 183 and the position 182 shown in FIG. It is necessary to ensure insulation between 183 and position 184 and to secure insulation between position 183 and position 184. As shown in FIG. 10A, when both ends of the first winding 851 and both ends of the second winding 852 are connected to the circuit board using terminal pins, an area immediately below the bobbin in the circuit board (typically, the circuit It is necessary to secure these insulations in a relatively narrow region (a region overlapping with the bobbin when it is along the thickness direction of the substrate). On the other hand, when the lead wires 431L and 432L are employed as in the present embodiment, it is easy to increase the distance between one position and the other position that should be insulated from each other. This facilitates the above insulation. Needless to say, the fact that the terminal pins 441 and 442 are in contact with a group of metal parts (solid pattern) also contributes to easy insulation. The simplification of insulation leads to improvement in design flexibility of the circuit board, realization of the electric circuit unit 200 at a low cost, and the like.

  The distance between the other end 431wn of the first winding part 431w and the other end 431n of the first winding 431, and the distance between the other end 432wn of the second winding part 432w and the other end 432n of the second winding 432 The distance may be the same or different. In the illustrated example, the former distance is shorter than the latter distance.

  In the example illustrated in FIG. 4A, a crimp terminal 461 is attached to the other end 431 n of the first winding 431. The crimp terminal 461 and the circuit board 210 are fixed by screws 471. In this way, the other end 431n of the first winding 431 is connected to the primary circuit 300. A crimp terminal 462 is attached to the other end 432 n of the second winding 432. The crimp terminal 462 and the circuit board 210 are fixed by screws 472. In this way, the other end 432 n of the second winding 432 is connected to the primary circuit 300.

  In the transformer 400 of the present embodiment, the first winding portion 431w of the first winding 431 has a first shape, and the second winding portion 432w of the second winding 432 has a second shape. Therefore, as understood from FIGS. 6A, 6B, and 6D, when the first winding portion 431w is viewed along the winding axis 431wx of the first winding portion 431w, the first winding portion 431w is Part of the first winding 431 and another part of the first winding 431 are not arranged side by side. Similarly, when the second winding part 432w is viewed along the winding axis 432wx of the second winding part 432w, a part different from the part of the second winding 432 constituting the second winding part 432w. And do not line up side by side. For this reason, the size of the transformer 400 is difficult to increase.

  The first shape also has a cost advantage. That is, when there are a portion wound up around the first winding 851 and a portion wound down around the first winding 851 like the transformer 850 in FIG. 10A, it is necessary to interpose an insulating member between these portions. On the other hand, if the first shape is adopted, such an insulating member can be omitted. This also applies to the second shape.

  As shown in FIGS. 6C and 6D, the third winding 433 has a third winding portion 433w that is a portion from the winding start position to the winding end position. As understood from FIGS. 6A, 6B, and 6D, the third winding portion 433w is one of the first winding portion 431w and the second winding portion 432w (the second winding in FIGS. 6A, 6B, and 6D). The other part of the first winding part 431w and the second winding part 432w (the first winding part 431w in FIGS. 6A, 6B and 6D) is wound around the winding part 432w). It is wound so as to surround the turning portion 433w. This configuration is advantageous from the viewpoint of magnetic coupling. This point will be described in comparison with the configuration of FIG. The configuration shown in FIG. 11 is obtained by changing the configuration shown in FIG. 6A so that the position of the second winding 432 and the position of the third winding 433 are reversed (and the positions of the associated pins and the like are changed). It is. In the configuration of FIG. 11, the second winding portion 432w surrounds the third winding portion 433w, and the first winding portion 431w surrounds the second winding portion 432w. In the configuration of FIG. 11, the distance between the first winding part 431w and the third winding part 433w is longer than the distance between the second winding part 432w and the third winding part 433w. Therefore, the magnetic coupling between the first winding part 431w and the third winding part 433w tends to be weaker than the magnetic coupling between the second winding part 432w and the third winding part 433w. On the other hand, in the configuration of FIG. 6A, the distance between the first winding part 431w and the third winding part 433w and the distance between the second winding part 432w and the third winding part 433w The difference can be reduced. That is, according to the configuration of FIG. 6A, the magnetic coupling between the first winding part 431w and the third winding part 433w and the magnetic coupling between the second winding part 432w and the third winding part 433w. And tends to be uniform.

  As shown in FIGS. 6C and 6D, the transformer 400 includes a cylindrical insulating member 480t (480). The third winding 433 (specifically, the third winding portion 433w) is wound outside the insulating member and the inner portion 433i wound inside the cylindrical insulating member 480t. The outer portion 433o has a folded portion 433t that connects the inner portion 433i and the outer portion 433o. According to this feature, it is easy to increase the ratio of the number of turns of the third winding part 433w to the number of turns of the first winding part 431w and the ratio of the number of turns of the third winding part 433w to the number of turns of the second winding part 432w. That is, it is easy to increase the transformation ratio. In the present embodiment, the inner portion 433i has the same shape (specifically, a spiral shape) as the first shape described in FIG. 7A. The outer portion 433o has the same shape (specifically, a spiral shape) as the second shape described in FIG. 7B. However, the inner portion 433i may have the same shape as the second shape, and the outer portion 433o may have the same shape as the first shape.

  In the present embodiment, the winding axis 432wx, the winding axis 431wx, and the winding axis of the third winding portion 433w are the same. That is, the first winding part 431w, the second winding part 432w, and the winding axis of the third winding part 433w have a common winding axis (common axis). Further, in a state where the transformer 400 is attached to the circuit board 210, the first winding portion 431w rotates away from the circuit board 210 while rotating in the first rotation direction around the common shaft (specifically, a spiral). Shape). The second winding portion 432w has a shape (specifically, a spiral shape) that moves away from the circuit board 210 while rotating in a second rotation direction (a direction opposite to the first rotation direction) around the common shaft. ing. The inner part 433i of the third winding part 433w is a shape that moves away from the circuit board 210 while rotating in the rotation direction (specifically, the first rotation direction or the second rotation direction) around the common shaft (specifically, Has a spiral shape). The outer portion 433o of the third winding portion 433w is a shape that moves away from the circuit board 210 (specifically, while rotating in a rotational direction (specifically, the second rotational direction or the first rotational direction) around the common shaft). Has a spiral shape).

  As understood from FIG. 4D, the metal portion (solid pattern) of the circuit board 210 is separated from the iron core 420, and a gap 230 is formed between the circuit board 210 and the iron core 420. This feature is advantageous from the viewpoint of preventing magnetic leakage from the iron core 420 to the metal part (solid pattern) and magnetic leakage from the iron core 420 to other members in the circuit board 210.

[Secondary circuit 500]
FIG. 12 shows a secondary circuit 500 of the electric circuit unit 200. An AC voltage V _ac is applied to the secondary side terminal 407 of the secondary side circuit 500. The AC voltage V _ac is generated using the power source 600. The secondary circuit 500 generates a second DC voltage V _dc2 from the AC voltage V _ac . The secondary side terminal 407 is a terminal existing at both ends of the third winding 433 that is a secondary side winding. Similarly, terminals existing at both ends of the primary side windings (the first winding 431 and the second winding 432) can be called primary side terminals.

  The secondary circuit 500 includes a first diode 531, a second diode 532, a first resonance capacitor 511, a second resonance capacitor 512, a rectification capacitor 521, and an inverter 580. Yes.

The first diode 531, the second diode 532, the first resonance capacitor 511, the second resonance capacitor 512, and the rectification capacitor 521 cooperate to _generate the second DC voltage from the AC voltage V _ac . V _dc2 is generated. Inverter 580 generates an AC voltage from second DC voltage V _dc2 .

  The first diode 531 has a first anode 531a and a first cathode 531c. The second diode 532 has a second anode 532a and a second cathode 532c. As the first diode 531 and the second diode 532, known diodes can be used.

  The first resonance capacitor 511 and the second resonance capacitor 512 are capacitors for generating current resonance. As the first resonance capacitor 511 and the second resonance capacitor 512, known capacitors can be used.

A second DC voltage V _dc2 is applied to the rectifying capacitor 521. A known capacitor can be used as the rectifying capacitor 521.

  The capacity of the first resonant capacitor 511 is smaller than the capacity of the rectifying capacitor 521. The capacity of the second resonant capacitor 512 is smaller than the capacity of the rectifying capacitor 521. Specifically, in the present embodiment, the ratio of the capacity of the rectifying capacitor 521 to the capacity of the first resonant capacitor 511 is 10 times or more. The ratio may be 50 times or more, 100 times or more, or 500 times or more. The said ratio is 1000 times or less, for example. In the present embodiment, the ratio of the capacity of the rectifying capacitor 521 to the capacity of the second resonant capacitor 512 is 10 times or more, 50 times or more, 100 times or more, 500 times or more. It may be. The said ratio is 1000 times or less, for example.

  Although not particularly limited, the capacitance of the first resonance capacitor 511 is, for example, 0.01 to 50 μF. The capacity of the second resonance capacitor 512 is, for example, 0.01 to 50 μF. The capacity of the rectifying capacitor 521 is, for example, 100 to 10,000 μF.

  In the present embodiment, the capacity of the first resonance capacitor 511 and the capacity of the second resonance capacitor 512 are the same. However, the capacity of the first resonance capacitor 511 may be different from the capacity of the second resonance capacitor 512.

The inverter 580 converts the second DC voltage V _dc2 into an AC voltage. A known inverter can be used as the inverter 580.

  As understood from FIG. 12, there are four paths connecting the one end 407 t 1 of the secondary terminal 407 of the transformer 400 and the other end 407 t 2 of the secondary terminal 407. The first of the four paths is a path that passes through the first anode 531a, the first cathode 531c, and the first resonance capacitor 511 in order from one end 407t1 to the other end 407t2. The second is a path that passes through the first anode 531a, the first cathode 531c, the rectifying capacitor 521, and the second resonant capacitor 512 in order from the one end 407t1 to the other end 407t2. The third is a path that passes through the second resonance capacitor 512, the second anode 532a, and the second cathode 532c in order from the other end 407t2 toward the one end 407t1. The fourth is a path that passes through the first resonance capacitor 511, the rectifier capacitor 521, the second anode 532a, and the second cathode 532c in order from the other end 407t2 to the one end 407t1.

  Specifically, one end 511m of the first resonance capacitor 511 and the first cathode 531c are connected to the same potential. One end 512m of the second resonant capacitor 512 and the second anode 532a are connected to the same potential. The other end 511n of the first resonance capacitor 511 and the other end 512n of the second resonance capacitor 512 are connected to the same potential.

  As described above, there are four paths connecting the one end 407t1 of the secondary terminal 407 and the other end 407t2 of the secondary terminal 407. Due to the existence of these paths, four current paths are formed. That is, as shown in FIG. 13A, in the first mode in which the potential of the one end 407t1 of the secondary terminal 407 is higher than the potential of the other end 407t2 of the secondary terminal 407, the first from the one end 407t1 to the other end 407t2 A current path 551 and a second current path 552 are configured. As illustrated in FIG. 13B, in the second mode in which the potential at the other end 407t2 is higher than the potential at the one end 407t1, a third current path 553 and a fourth current path 554 are configured from the other end 407t2 to the one end 407t1. The first current path 551 is a current path through which current flows through one end 407 t 1, the first diode 531, the first resonant capacitor 511, and the other end 407 t 2 in this order. The second current path 552 is a current path through which current flows through one end 407 t 1, the first diode 531, the rectifying capacitor 521, the second resonance capacitor 512, and the other end 407 t 2 in this order. The third current path 553 is a current path through which current flows through the other end 407t, the second resonant capacitor 512, the second diode 532, and the one end 407t1 in this order. The fourth current path 554 is a current path through which current flows through the other end 407 t 2, the first resonant capacitor 511, the rectifier capacitor 521, the second diode 532, and the one end 407 t 1 in this order.

The secondary side circuit 500 has a boosting and rectifying function, specifically, a voltage doubler rectifying function for the reason described below. In the following description, the capacity of the first resonant capacitor 511 is C ₁ , the capacity of the second resonant capacitor 512 is C ₂ , the capacity of the rectifying capacitor 521 is C ₃ , and C ₃ is C ₁ . It is assumed that C ₃ is sufficiently large and C ₃ is sufficiently larger than C ₂ . In the second current path 552, the rectifier capacitor 521 and the second resonant capacitor 512 are connected in series. Considering that C ₃ is sufficiently larger than C ₂ , the following formula is established for the combined capacitance C ₃₂ of these capacitors.
1 / C ₃₂ = 1 / C ₃ / + 1 / C ₂ ≒ 1 / C ₂
Thus the combined capacitance C ₃₂ is approximated to C _2. It can be considered that the capacitor (first resonant capacitor 511) in the first current path 551 and the capacitors (rectifier capacitor 521 and second resonant capacitor 512) in the second current path 552 constitute a parallel capacitor circuit. . With respect to the combined capacitance C _x of the parallel capacitor circuit, the following formula is established.
C _x = C ₁ + C ₃₂ ≈C ₁ + C ₂
In the fourth current path 554, the first resonant capacitor 511 and the rectifying capacitor 521 are connected in series. Considering that C ₃ is sufficiently larger than C ₁ , the following formula is established for the combined capacitance C ₃₁ of these capacitors.
1 / C ₃₁ = 1 / C ₃ / + 1 / C ₁ ≒ 1 / C ₁
Thus the combined capacitance C ₃₁ is approximated to C _1. It can be considered that the capacitor in the third current path 553 (second resonant capacitor 512) and the capacitor in the fourth current path 554 (first resonant capacitor 511 and rectifier capacitor 521) constitute a parallel capacitor circuit. . Relates combined capacitance C _y of the parallel capacitor circuits, the following equation is established.
C _y = C ₂ + C ₃₁ ≈C ₂ + C ₁
That is, it can be considered that the combined capacitance C _x in the first mode and C _y in the second mode are substantially the same. Therefore, in both the first mode and the second mode, the rectifier capacitor 521 is charged in substantially the same manner so that the potential of the one end 521m of the rectifier capacitor 521 is higher than the potential of the other end 521n. In this manner, the boosting and rectifying functions in the secondary circuit 500, specifically, the voltage doubler rectifying function is realized. As a result, the second DC voltage V _dc2 is applied to the rectifying capacitor 521.

  The secondary circuit 500 has a current resonance function for the reason described below. That is, the secondary terminal 407 of the transformer 400 outputs an AC voltage having a frequency F. In the first mode, the leakage inductance (primary leakage inductance) of the transformer 400 and the capacitance component and the inductive component in the first current path 551 are the first series resonance circuit having the frequency F as the resonance frequency. Configure. In the second mode, the leakage inductance of the transformer 400 and the capacitive component and the inductive component in the third current path 553 constitute a second series resonant circuit having the frequency F as the resonant frequency. In this way, the function of the current resonance circuit is realized.

  The advantages of the secondary side circuit 500 of the present embodiment will be described in comparison with the configurations shown in FIGS.

  The configuration shown in FIG. 15 also has the functions of both a current resonance circuit and a rectifier circuit. The power source 710 in FIG. 15 generates a DC voltage. This DC voltage is supplied to the electric circuit unit 705. Specifically, the four switching elements 720 convert a DC voltage into an AC voltage (primary AC voltage). The transformer 737 boosts the primary side AC voltage and generates the secondary side AC voltage. Current resonance occurs due to the leakage inductance of the transformer 737 and the resonant capacitor 740. The secondary AC voltage is rectified by the four diodes 741 and the rectifying capacitor 704. The DC voltage obtained by the rectification is supplied to the inverter 780.

  In the electric circuit unit 705, only the transformer 737 is responsible for boosting. For this reason, in the electric circuit unit 705, the winding ratio of the primary side winding and the secondary side winding of the transformer 737 tends to increase. A large winding ratio tends to cause a decrease in voltage conversion efficiency, an increase in cost of the transformer, and an increase in size of the transformer.

  In order to solve the above problem, it is conceivable that the boosting function is shared not by the transformer alone but by the other mechanism. Specifically, it is conceivable to change the configuration of the transformer and the secondary side as shown in FIG.

  In FIG. 16, a transformer 837 is a transformer whose winding ratio is half of the winding ratio of the transformer 737 (in FIG. 16, the primary side winding of the transformer 837 is omitted). In the first mode in which the potential of one end 838t1 of the secondary winding of the transformer 837 is higher than the potential of the other end 838t2 of the winding, the one end 838t1, the diode 841A, the rectifier capacitor 804A, the resonant capacitor 840, and the other end 838t2 A first current path through which current flows in this order is configured. In the second mode in which the potential of one end 838t1 of the secondary winding of the transformer 837 is lower than the potential of the other end 838t2 of the same winding, the other end 838t2, the resonant capacitor 840, the rectifier capacitor 804B, the diode 841B, and the one end 838t1 A second current path through which current flows in this order is configured.

  The capacity of the resonant capacitor 840 is sufficiently smaller than the capacity of the rectifying capacitors 804A and 804B. For this reason, the combined capacity of the rectifying capacitor 804A and the resonant capacitor 840 in the first current path is substantially the same as the capacity of the resonant capacitor 840. In the first mode, the series resonance is based on the leakage inductance of the transformer 837 and the capacity of the resonant capacitor 840. It can be considered that a circuit is constructed. It can be considered that a series resonance circuit based on the leakage inductance of the transformer 837 and the capacitance of the resonance capacitor 840 is also formed in the second mode. That is, current resonance is realized in both the first mode and the second mode.

  In the first mode, the rectifying capacitor 804A is charged, and in the second mode, the rectifying capacitor 804B is charged. The rectifying capacitor 804A and the rectifying capacitor 804B constitute a series circuit by being connected in series. A boosted DC voltage appears across the series circuit. Thus, voltage doubler rectification is realized.

  As described above, according to the configuration of FIG. 16, current resonance and voltage doubler rectification are realized. The winding ratio of the transformer 837 is half of the winding ratio of the transformer 737, but voltage doubler rectification doubles the voltage. Therefore, according to the configuration of FIG. 16, the same combination as in the case of employing the configuration of FIG. 15 can be supplied to the inverter 780. Moreover, since the winding ratio of the transformer 837 is smaller than the winding ratio of the transformer 737, the transformer 837 can easily obtain high voltage conversion efficiency compared to the transformer 737, and can be easily realized at low cost. And it is easy to make small.

  However, the configuration of FIG. 16 requires two rectifying capacitors 804A and 804B. In general, a rectifying capacitor has a larger capacity than a resonant capacitor. Therefore, compared with the resonant capacitor, the rectifying capacitor tends to be expensive and large.

  On the other hand, according to the technique of this embodiment, the problem of the capacitor price and size can be alleviated. This point will be described using a specific example. In this specific example, the capacity of the first resonant capacitor 511 is 2.5 μF, the capacity of the second resonant capacitor 512 is 2.5 μF, and the capacity of the rectifying capacitor 521 is 250 μF. In order to provide the secondary side circuit of FIG. 16 with the same boosting function, current resonance function, and rectification function as the secondary side circuit 500 of this specific example, the capacity of the resonance capacitor 840 is 5 μF, and the capacity of the rectification capacitor 804A is The capacitance of the rectifying capacitor 804B needs to be 500 μF. The capacity of each capacitor in the secondary side circuit 500 may be half of the capacity of each capacitor in FIG. Moreover, unlike the secondary side circuit of FIG. 16 that requires two rectifying capacitors, the secondary side circuit 500 needs only one rectifying capacitor. From the above description, it is quantitatively understood that the secondary side circuit 500 of the present embodiment is advantageous from the viewpoint of size reduction and cost reduction compared to the secondary side circuit of FIG.

  In the present embodiment, half the capacity of the rectifying capacitor 521 is defined as a reference capacity, and an area occupied by at least one of the first current path 551, the second current path 552, the third current path 553, and the fourth current path 554. Is defined as region R, in region R, the number of capacitors having a capacity smaller than the reference capacity is larger than the number of capacitors having a capacity larger than the reference capacity. Specifically, the capacitor having a capacity larger than the reference capacity in the region R is only the rectifying capacitor 521. These features are advantageous in reducing the size and price of secondary circuit 500.

  In the example illustrated in FIG. 12, the electric circuit unit 200 (secondary circuit 500) includes a first connection path 571 and a second connection path 572. The first connection path 571 connects the other end 511 n of the first resonance capacitor 511 and the other end 512 n of the second resonance capacitor 512. The second connection path 572 connects the first connection path 571 and the other end 407 t 2 of the secondary side terminal 407. In the present embodiment, the second connection path 572 does not have a capacitor. This is advantageous for realizing the electric circuit unit 200 at a low cost. Specifically, in the present embodiment, the other end 511n of the first resonance capacitor 511, the other end 512n of the second resonance capacitor 512, and the other end 407t2 of the secondary terminal 407 are connected to the same potential. ing. More specifically, the first connection path 571 and the second connection path 572 are constituted by electric wires.

  However, the second connection path 572 may include a capacitor. In the modified embodiment shown in FIG. 14, the second connection path 572 includes a capacitor 560 for improving the design margin. It should be noted that the design margin should be within an error range in which the resistance component, the capacitance component, the inductive component, etc. in the electric circuit unit 200 are within the design value in order for the electric circuit unit 200 to perform a desired operation. It is an index representing Specifically, parasitic resistance, parasitic capacitance, parasitic inductance, etc. can cause errors. The capacitor 560 makes it easy to avoid a situation in which current resonance does not occur due to the error. In this example, the capacity of the capacitor 560 is smaller than the capacity of the first resonant capacitor 511 and smaller than the capacity of the second resonant capacitor 512. Since the capacity of the capacitor 560 is small, the addition of the capacitor 560 hardly increases the size of the secondary circuit 500 or significantly increases the cost. The capacity of the capacitor 560 is, for example, half or less of the capacity of the first resonance capacitor 511 or the second resonance capacitor 512, and may be 1/5 or less.

[Application to fuel cell systems]
A fuel cell system including the power supply unit with circuit 100 can be configured. FIG. 17 shows an example of such a fuel cell system. A fuel cell system 900 shown in FIG. 17 is a household fuel cell cogeneration system. However, the use of the fuel cell system including the power supply unit with circuit 100 is not limited to home use. Moreover, the fuel cell system including the power supply unit with circuit 100 may not constitute a cogeneration system.

  The fuel cell system 900 includes a fuel cell unit 920 and a hot water storage unit 930.

  The fuel cell unit 920 includes a fuel processor 921, a cell stack 922, a power conversion unit 923, and a heat exchanger 927.

  The fuel processor 921 generates hydrogen 953 from the fuel gas 951. Examples of the fuel gas 951 include city gas, liquefied petroleum gas (LP gas), and kerosene.

  The cell stack 922 generates DC power 961 from oxygen 952 and hydrogen 953. When the DC power 961 is generated, exhaust heat 971 is generated.

  The power converter unit 923 converts the DC power 961 into AC power 962. AC power 962 is used in the load.

  The hot water storage unit 930 includes a hot water storage tank 931 and a backup water heater 932.

  The cold water 981 of the hot water storage unit 930 is supplied to the heat exchanger 927 of the fuel cell unit 920. In the heat exchanger 927, hot water 982 is generated from the cold water 981 by the exhaust heat 971. The generated hot water 982 is stored in the hot water storage tank 931. Hot water 982 stored in the hot water storage tank 931 is taken out when necessary.

  The backup water heater 932 generates hot water 982 from the cold water 981 when the hot water 982 is insufficient.

  The cell stack 922 constitutes a fuel cell. The cell stack 922 can be used as the power source 600 of FIG. As the power conversion unit 923, the electric circuit unit 200 of FIG. 1 can be used. That is, the fuel cell system 900 shown in FIG. 17 includes a power supply unit with circuit 100 that uses a fuel cell that generates power from hydrogen 953 and oxygen 952 as a power source 600.

  Hereinafter, advantages of using the electric circuit unit 200 in the fuel cell system 900 will be described with reference to the related art.

  Conventionally, a fuel cell system including a fuel cell has been used. The fuel cell generates 1 kW class DC power, a voltage of 10 to 40 V, and a large current (a large current inversely proportional to the number of cells in the cell stack). Typically, a voltage of 10-40V is boosted to 400V. A transformer is used for this boosting. In order to convert a DC voltage of 10 to 40 V into a DC voltage of 400 V, it is necessary to increase the ratio of the number of turns of the secondary winding to the number of turns of the primary winding of the transformer (winding ratio). However, a large winding ratio leads to an increase in transformer size and a decrease in voltage conversion efficiency. Moreover, in recent years, the number of cell stacks tends to be reduced for the purpose of reducing the cost of the fuel cell, and thus the voltage generated by the fuel cell tends to decrease. For the above reason, the problem described with reference to FIG. 15 is easily manifested in recent fuel cell systems. Further, it is conceivable to solve this problem using the configuration of FIG. 16, but as described above, there is also a problem with the configuration of FIG. That is, it is a great advantage to include in the fuel cell system 900 an electric circuit unit that performs current resonance and rectification, has high voltage conversion efficiency, can be realized at low cost, and can be made compact. is there.

  The fuel cell system 900 of the present embodiment extracts a first port (not shown) for extracting a voltage used for controlling electronic components of the fuel cell system 900 and a voltage used for controlling an auxiliary device of the fuel cell system 900. And a second port (not shown). In this case, the fuel cell system 900 sets the potential of the first terminal 311 (see FIGS. 2A to 2C) to the first potential using the first port, and uses the second port to set the second potential. The potential of the terminal 312 can be set to the second potential. The electronic components of the fuel cell system 900 are the clock generator 320 in FIG. 2A and the like. The auxiliary equipment of the fuel cell system 900 is a pump, a valve, or the like.

  Further, it goes without saying that the fuel cell system 900 can also enjoy the advantages of the transformer 400 described with reference to FIGS. 4A to 11.

  The technology disclosed in this specification can be applied to a fuel cell system and the like.

100 Power supply unit with circuit 181 to 184 Position 200, 705 Electric circuit unit 210 Circuit board 211, 220, 401 Area 230 Air gap 241, 242, 243m, 243n, 419 Hole 300 Primary circuit 301A, 301B, 302A, 302B, 303A , 303B Drive unit 311, 312, 313 Terminal 320 Clock generator 331, 332, 511, 512, 521, 560, 704, 740, 804A, 804B, 840 Capacitor 341, 342, 343, 531, 532, 741, 841A, 841B Diode 351, 352, 353A, 353B, 354, 720 Switching element 355 Amplifier 400, 737, 837, 850 Transformer 407 Secondary side terminal 410 Bobbin 411 Terminal side flange 412 Lead line side Lung portions 420, 855 Iron cores 431, 432, 433, 851, 852, 853, 856, 857 Windings 431L, 432L, 856L, 857L Lead wires 431w, 432w, 433w Winding portions 431wd, 432wd Rotating directions 431wr, 432wr Reference plane 431wx, 432wx Winding shaft 433i Inner part 433o Outer part 433t Folded part 435, 436 Winding part 438 Winding set 441, 442, 443m, 443n, 851Pm, 851Pn, 852Pm, 852Pn, 853Pm, 853Pn, 856P, 857P Terminal pin 461,462 Crimp terminals 471,472 Screws 480, 480t, 854 Insulating member 490 Insulating sleeve 500 Secondary circuit 551,552,553,554 Current path 571,572 Connection path 5 0,780 Inverters 600, 710 Power supply 900 Fuel cell system 920 Fuel cell unit 921 Fuel processor 922 Cell stack 923 Power converter 927 Heat exchanger 930 Hot water storage unit 931 Hot water storage tank 932 Backup hot water heater 951 Fuel gas 952 Oxygen 953 Hydrogen 961 DC Electric power 962 AC power 963 Surplus power 971 Waste heat 981 Cold water 982 Hot water

Claims (12)

An electrical circuit unit in which a third potential portion appears when the first potential portion and the second potential portion are set;
A first terminal set to the first potential;
A second terminal set to the second potential;
A clock generator for generating a clock signal;
A first capacitor;
A second capacitor in which the third potential appears;
A first diode having a first anode and a first cathode;
A second diode having a second anode and a second cathode;
A third diode having a third anode and a third cathode;
A first switching element having a first output section capable of outputting a first output potential determined by the first potential,
The timing at which the potential of the first output unit becomes the first output potential and the timing at which the potential becomes not the first output potential are defined by the clock signal,
As a path connecting the first output unit and the second capacitor, the first capacitor, the second anode, and the second cathode in order from the first output unit to the second capacitor. There is a route through
As a path connecting the second terminal and the second capacitor, the first anode, the first cathode, the second capacitor in order from the second terminal toward the second capacitor. An electric circuit unit, wherein a path passing through the anode and the second cathode, and a path passing through the third anode and the third cathode in order from the second terminal toward the second capacitor. The first cathode and the second anode are connected to the same potential,
The first anode, the third anode, and the second terminal are connected to the same potential,
The electric circuit unit according to claim 1, wherein the second cathode, the third cathode, and the second capacitor are connected to the same potential. The electric circuit unit is:
A second switching element having a second output section capable of outputting a second output potential determined by the third potential;
A third switching element driven by the potential of the second output unit,
3. The electric circuit unit according to claim 1, wherein a timing at which the potential of the second output unit becomes the second output potential and a timing at which the potential becomes not the second output potential are defined by the clock signal. .   The electric circuit unit according to claim 3, wherein the clock signal that has not been amplified is input to the second switching element. The electrical circuit includes an amplifier that amplifies the clock signal,
The electric circuit unit according to claim 3, wherein the amplified clock signal is input to the second switching element.   The electric circuit unit according to claim 3, wherein the potential of the first output unit is used by the second switching element as the amplified clock signal. A primary circuit having the third switching element;
With a transformer,
A secondary circuit,
The primary circuit and the transformer cooperate to generate an alternating voltage from the first direct voltage,
The electric circuit unit according to claim 3, wherein the secondary circuit generates a second DC voltage from the AC voltage. The electric circuit unit according to any one of claims 1 to 7,
And at least one power source for generating direct-current power,
A power supply unit with circuit, wherein the power supply power is used to set the potential of the first terminal to the first potential and set the potential of the second terminal to the second potential.   The power supply unit with circuit according to claim 8, wherein the second potential is larger than the first potential. The electric circuit unit according to claim 7,
And at least one power source for generating direct-current power,
A circuit-equipped power supply unit that generates the first DC voltage using the power supply power. A power supply unit with circuit according to any one of claims 8 to 10,
The fuel cell system, wherein the at least one power source is at least one fuel cell that generates power from hydrogen and oxygen. The at least one fuel cell includes a first port for extracting a voltage used for controlling an electronic component of the fuel cell system, and a second port for extracting a voltage used for controlling an auxiliary device of the fuel cell system. ,
The fuel cell system uses the first port to set the potential of the first terminal to the first potential, and uses the second port to set the potential of the second terminal to the second potential. The fuel cell system according to claim 11, wherein the fuel cell system is set to a potential of

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