JP2010011142A - Modulator, demodulator, modem and communication instrument - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To carry out communication of a plurality of frequency bands by a single local oscillator. <P>SOLUTION: This modulator includes a local signal generator and a vector modulation part. The local signal generator generates a first local signal and a second local signal forming a phase difference of 360°/N (N is 3 or an integer not smaller than 5) from each other. The vector modulation part includes a first input terminal and a second input terminal respectively receiving first data and second data representing coordinates intersecting with each other at a predetermined phase difference, and generates a signal vector-modulated at the phase difference of 360°/N by mixing the first data with the first local signal, and mixing the second data with the second local signal. The modulator further includes a coordinate converter, and the coordinate converter coordinate-converts third data and fourth data representing coordinates orthogonal to each other to the first data and the second data representing coordinates intersecting with each other at a phase difference of 360°/N. <P>COPYRIGHT: (C)2010,JPO&INPIT

Description

  The present invention relates to a technology of a modulator, a demodulator, a modem, and a communication device, and more particularly to a technology for sharing a local oscillator in a modem of a multiband and multimode communication device.

  A direct conversion method is known as a transmitter / receiver in a wireless communication device such as a cellular phone. In the direct conversion method, a radio receiver mixes a received high-frequency signal with an output signal of a local oscillator having the same carrier frequency as this signal, and directly converts the signal into a baseband signal. Also in the wireless transmitter, a data signal from the baseband is mixed by an output signal of a local oscillator having substantially the same oscillation frequency as a high-frequency signal to be transmitted to generate a transmission signal.

  FIG. 20 is a block diagram illustrating a configuration example of a main part of a conventional direct conversion receiver. The high frequency signal received by the receiving antenna 400 passes through the band limiting filter 401 and is amplified by the low noise amplifier 402. In the frequency mixers 403 and 404, the amplified signal is received by a reception local signal having the same frequency as the received high-frequency signal, and a signal obtained by shifting the phase of the reception local signal by 90 degrees by the -90 degree phase shifter 405. Each is mixed. The mixed signals are frequency-converted to a baseband band and become orthogonal baseband signals. These baseband signals are output through buffers 408 and 409 after passing through low-pass filters 406 and 407, respectively.

  FIG. 21 is a block diagram illustrating a configuration example of a main part of a conventional direct conversion transmitter. The orthogonal baseband signals are a transmission local signal having the same frequency as the high frequency signal to be transmitted in the frequency mixers 410 and 411, and a signal obtained by shifting the phase of the transmission local signal by 90 degrees by the -90 degree phase shifter 405. Respectively. The mixed signal is added by an adder 412 to become a high-frequency signal to be transmitted, passes through a band limiting filter 414, is amplified by a power amplifier 413, and is transmitted as a transmission radio wave from an antenna 415 to be wirelessly transmitted. .

  Here, the reception and transmission local signals input to the frequency mixers 403, 404, 410, and 411 are generated by dividing the output of the local oscillator 416. The local oscillator 416 includes a VCO (not shown) and a frequency synthesizer, and generates a high frequency signal having a frequency different from that of the received high frequency signal and the transmitted high frequency signal. The output of the local oscillator 416 is input to the buffer 417. The high-frequency signal output from the buffer 417 is frequency-divided to 1 / Np (Np is a positive integer) by the frequency divider 418 and supplied to the frequency mixers 403 and 410 and the phase shifter 405 as reception and transmission local signals. Is done.

  In this manner, by making the reception and transmission local signals input to the frequency mixers 403 and 410 different from the output frequency of the local oscillator 416, the local oscillation frequency can be reduced from the interference wave at the reception and transmission frequencies of other wireless communication systems. I try not to be.

  However, in the high frequency region, the influence of the parasitic capacitance component and the parasitic inductor component generated in each part is inevitable, so that it is not easy to create a highly accurate phase shifter. Therefore, in many cases, a signal having a phase of 90 degrees is created by setting the frequency division number Np of the frequency divider 418 to an even number.

  In recent years, multi-band and multi-mode wireless communication devices have been made into one chip, and a large number of local oscillators are required in the chip. In order to create local signals for transmission and reception with a small number of local oscillators in a communication device that supports a large number of different frequency bands, not only an even number but also an odd number must be used.

A prior art technique related to solving this problem is disclosed in Japanese Patent Laid-Open No. 2003-78434. FIG. 22A shows a basic configuration of Japanese Patent Laid-Open No. 2003-78434. In order to create an arbitrary local frequency, the signal of the local oscillator 500 is divided into 1 / N1p and 1 / N2p (N1p and N2p are positive integers) by two dividers 501 and 502, and by a mixer 503. They are mixed to create sum and difference frequencies. The frequency of the sum and difference is removed except for the necessary signal by the filter 504, and is divided to 1 / N3p (N3p is a positive integer) by the frequency divider 505 to be a local signal for transmission and reception. FIG. 22B shows signals Ap of the local oscillator 500 and outputs Bp and Cp of the frequency divider 505.
JP 2003-78434 A

  With the progress of multiband and multimode wireless transceivers, a large number of local oscillators exist in the same chip, and the chip area increases. In order to reduce the chip area, it is necessary to share a local oscillator in different bands and modes. In order to share the local oscillator in different bands, it is necessary to widen the oscillation frequency width of the local oscillator or make the frequency dividing number not only an even number but also an odd number. However, when the oscillation frequency width is widened, signal noise is degraded, and it is difficult to avoid the degradation. The odd frequency divider has a problem that a signal having a phase difference of 90 degrees cannot be generated. There is also a problem that it is difficult to create a high-precision 90-degree phase shifter in a high-frequency signal band. As a conventional example related to the solution, there is JP-A-2003-78434. However, in this configuration, a large amount of current is required for the filter 504 and the mixer 503, and the power consumption increases and is unnecessary in the mixer 503. Harmonics are generated, and the characteristics of the mixed signal are deteriorated.

  The present invention solves the above-described conventional problems, and is used for a multiband and multimode communication device based on an oscillation signal having a frequency different from the transmission or reception frequency generated by one local oscillator. An object of the present invention is to generate a large number of local signals, suppress an increase in power consumption related to the generation of local signals, reduce unnecessary high frequencies, and improve the phase and frequency accuracy of the local signals.

  In order to achieve the above-described object, the modulator of the present invention generates a first local signal and a second local signal having a phase difference of 360 degrees / N (N is a positive integer of 3 or 5). A local signal generator has a first input terminal and a second input terminal for receiving first data and second data representing coordinates intersecting each other at a predetermined phase difference, and the first data is mixed with the first local signal. And a vector modulation unit that generates a signal that is vector-modulated with a phase difference vector of 360 degrees / N by mixing the second data with the second local signal.

  The demodulator according to the present invention includes a local signal generator that generates a first local signal and a second local signal that form a phase difference of 360 degrees / N (N is a positive integer of 3 or 5), a vector, A first input terminal for receiving the modulated signal and a second input terminal for receiving the modulated signal, the vector modulated signal is mixed with the first local signal to generate first data, and the vector modulated signal is converted to the second local signal. And a second demodulator for generating a second data, thereby performing vector demodulation so that the first data and the second data represent coordinates where the first data and the second data intersect with each other with a phase difference of 360 degrees / N.

  The modem according to the present invention includes the modulator described above and the demodulator described above.

  Moreover, the communication apparatus of this invention has the modulator mentioned above.

  Moreover, the communication apparatus of this invention has the demodulator mentioned above.

  Furthermore, the communication device of the present invention has the above-described modem.

  According to the modulator, demodulator, modem, and communication device of the present invention, a plurality of pairs of local signals corresponding to multiband and multimode are generated using one local oscillator and a plurality of frequency dividers. can do. Further, by using the coordinate converter, it is possible to vector-modulate the orthogonal modulation data or perform vector demodulation to the orthogonal modulation data corresponding to the phase difference of 360 degrees / N in the pair of local signals. As a result, using one local oscillator, a plurality of vector modulation signals corresponding to multiband and multimode are generated, or a plurality of vector modulation signals corresponding to multiband and multimode are demodulated. It is possible to generate orthogonal modulation data corresponding to the modulation signal. Furthermore, since the frequency divider and coordinate converter can be configured with a simple circuit, compared to the case of using a plurality of local oscillators or generating a plurality of systems of local signals using a mixer, It is possible to reduce power consumption, reduce a semiconductor chip area, reduce electromagnetic interference due to generation of unnecessary high frequencies, and improve the quality of vector modulation signals or quadrature modulation data.

  Several examples relating to the best mode for carrying out the present invention will be described below with reference to the drawings. In the drawings, elements that represent substantially the same configuration, operation, and effect are denoted by the same reference numerals. In addition, all the numbers described below are exemplified for specifically explaining the present invention, and the present invention is not limited to the illustrated numbers. In addition, logic levels represented by high / low or switching states represented by on / off are illustrative for the purpose of illustrating the invention, and different combinations of illustrated logic levels or switching states. Therefore, it is possible to obtain an equivalent result. In addition, the connection relationship between the components is exemplified for specifically explaining the present invention, and the connection relationship for realizing the function of the present invention is not limited to this. Furthermore, although the following embodiments are configured using hardware and / or software, the configuration using hardware can also be configured using software, and the configuration using software uses hardware. Can be configured.

(First embodiment)
FIG. 1 is a block diagram showing a configuration of a modulator 10T according to the first embodiment.
In FIG. 1, a modulator 10T according to the first embodiment includes a vector modulation unit 100T and a local signal generator 109. The vector modulation unit 100T includes an input terminal 105UT, an input terminal 106UT, an input terminal 105VT, an input terminal 106VT, a mixer 101UT, a mixer 101VT, and an adder 103. The local signal generator 109 generates a pair of local signals LU and LV representing two vectors having a phase difference of 360 degrees / N (N is an integer of 3 or 5). The local signal generator 109 generates the local signal LV so as to advance by a phase difference of 360 degrees / N with respect to the local signal LU. The local signals LU and LV are used as carrier vectors for vector modulation in the vector modulation unit 100T. The frequency of each local signal LU, LV is set in the local signal generator 109 so as to match the carrier frequency of the transmission signal transmitted from the antenna.

  The orthogonal modulation data IT and the orthogonal modulation data QT represent coordinates in a coordinate system orthogonal to each other. The non-orthogonal modulation data UT and the non-orthogonal modulation data VT represent coordinates of a coordinate system that intersect with each other with a phase difference of 360 degrees / N. The orthogonal modulation data QT is delayed by 90 degrees with respect to the orthogonal modulation data IT, and the non-orthogonal modulation data VT is delayed by a phase difference of 360 degrees / N with respect to the non-orthogonal modulation data UT. The orthogonal modulation data IT and the orthogonal modulation data QT are coordinate-converted into non-orthogonal modulation data UT and non-orthogonal modulation data VT. Input terminals 105UT and 106UT receive local signal LU and non-orthogonal modulation data UT, respectively, and input terminals 105VT and 106VT receive local signal LV and non-orthogonal modulation data VT, respectively. The mixer 101UT mixes the non-orthogonal modulation data UT with the local signal LU to generate a mixed signal S101UT. The mixer 101VT mixes the non-orthogonal modulation data VT with the local signal LV to generate a mixed signal S101VT. The adder 103 adds the mixed signal S101UT and the mixed signal S101VT to each other, and generates a vector modulation signal S100T representing a signal that is vector-modulated by two carrier vectors having a phase difference of 360 degrees / N. That is, the vector modulation unit 100T performs vector modulation on the non-orthogonal modulation data UT and VT based on the local signals LU and LV, and generates a vector modulation signal S100T.

  FIG. 2 is a block diagram showing another configuration of the modulator 10T according to the first embodiment. The modulator 10T shown in FIG. 2 further includes a coordinate converter 110T in addition to the vector modulation unit 100T and the local signal generator 109 described above. The coordinate converter 110T converts the orthogonal modulation data IT and QT representing coordinates orthogonal to each other into non-orthogonal modulation data UT and VT representing coordinates intersecting with each other with a phase difference of 360 degrees / N. As described above, the orthogonal modulation data QT is delayed by 90 degrees with respect to the orthogonal modulation data IT. The coordinate converter 110T performs coordinate conversion so that the non-orthogonal modulation data VT is delayed by a phase difference of 360 degrees / N with respect to the non-orthogonal modulation data UT.

  Here, orthogonal modulation data IT and QT are orthogonally modulated from baseband data based on, for example, an OFDM (Orthogonal Frequency Frequency Division Multiplexing) modulation method by a signal processor 141T (described later) positioned in front of the coordinate converter 110T. Represents the processed signal. The quadrature modulation data IT and QT may be digital signals or analog signals. In the case of a digital signal, the coordinate converter 110T is configured by, for example, a look-and-table method or a digital calculation method. The non-orthogonal modulation data UT and VT generated by the coordinate converter 110T are converted into analog signals by a digital / analog converter (not shown) and input to the input terminals 106UT and 106VT. Further, the vector modulation unit 100T may be configured by a digital processing method. In this case, the non-orthogonal modulation data UT and VT are input to the vector modulation unit 100T in a digital signal state. The vector modulation signal S100T digitally processed by the vector modulation unit 100T is converted into an analog signal by a digital / analog converter (not shown) located at the subsequent stage of the vector modulation unit 100T and transmitted.

Next, the detailed operation of the coordinate converter 110T will be described with reference to FIG. 3, FIG. 4, and FIG.
3 is an explanatory diagram showing signal point arrangement of orthogonal modulation data, FIG. 4 is an explanatory diagram showing signal point arrangement of non-orthogonal modulation data, and FIG. 5 is from orthogonal modulation data to non-orthogonal modulation data. It is explanatory drawing which shows the relationship of coordinate conversion. The orthogonal modulation data is expressed as coordinates relating to the basis vector x and the basis vector y that are orthogonal to each other, and the non-orthogonal modulation data is related to the basis vector x and the basis vector z that form a phase difference of 360 degrees / N (= θ). Represented as: The basis vector y is delayed by 90 degrees with respect to the basis vector x, and the basis vector z is delayed by a phase difference of 360 degrees / N with respect to the non-orthogonal modulation data UT. Signal points P1, P2, P3, P4 are represented using orthogonal modulation data (I, Q) with respect to the basis vectors x, y, and non-orthogonal modulation data (U, V) or ( U1, V).

このベクトル表現により、ベクトルｒは、基底ベクトルｘ、ｙを用いて、式１のように表すことができる。

同様に、ベクトルｒは、基底ベクトルｘ、ｚを用いて、式２のように表すことができる。

Here, for example, a vector r indicating the signal point P1 is written as follows.

With this vector representation, the vector r can be expressed as in Equation 1 using the basis vectors x and y.

Similarly, the vector r can be expressed as Equation 2 using the basis vectors x and z.

On the other hand, the unit vector z can be expressed as Equation 3 using the unit vector x and the unit vector y.

Substituting Equation 3 into Equation 2 yields Equation 4.

According to Formula 1 and Formula 4, I and Q can be expressed as Formula 5 and Formula 6.

U and V can be expressed as in Expression 7 and Expression 8 according to Expression 5 and Expression 6.

Substituting Equation 8 into Equation 7 yields Equation 9.

On the other hand, U1 can be expressed as Equation 10 from Equation 79 and FIG.

  As described above, the non-orthogonal modulation data (U, V) or (U1, V) representing the coordinates that intersect the orthogonal modulation data (I, Q) representing the coordinates orthogonal to each other with a phase difference of 360 degrees / N. Can be converted to coordinates. When the signal point is in the first quadrant or the third quadrant (that is, for example, P1 or P3) on the xy plane defined by the base vector x and the base vector y, the non-orthogonal modulation data is (U, V). When the signal point is in the second quadrant or the fourth quadrant (that is, in the case of P2 or P4, for example), the non-orthogonal modulation data is (U1, V). In the vector modulation unit 100T, if the non-orthogonal modulation data is mixed with local signals LU and LV having a phase difference of θ (= 360 degrees / N), a local signal having a phase difference different from 90 degrees is used. Vector modulation can be performed.

  FIG. 6 is a circuit diagram illustrating a detailed configuration example of the local signal generator 109 according to the first embodiment. In the local signal generator 109 of FIG. 6, N inverters are connected in series, and the output terminal of the final stage inverter is connected to the input terminal of the first stage inverter. That is, the local signal generator 109 has a configuration of a ring oscillator in which N inverters are connected in a ring shape. The local signals LU and LV representing the outputs of any two systems of inverters have a phase difference of 360 degrees / N from each other, and vector modulation can be performed using the local signals LU and LV. The oscillation frequency of the local signals LU and LV can be set to a desired height by adjusting the delay amount and the number of inverters. The phase difference between the local signals LU and LV can be set to a desired value by appropriately selecting the above-described K value.

  FIG. 7A is a circuit diagram showing a specific configuration example when N = 3 in the local signal generator 109 of FIG. FIG. 7B is a waveform diagram showing the operation of the local signal generator 109 in FIG. 7A. In the local signal generator 109 of FIG. 7A, three inverters are connected in series, and the output terminal of the final stage inverter is connected to the input terminal of the first stage inverter. In FIG. 7B, the output signal SA, the local signal LU, and the local signal LV of the first stage inverter form a phase difference of 360 degrees / 3 = 120 degrees. The local signal LV advances by a phase difference of 120 degrees with respect to the local signal LU.

  FIG. 8 is a block diagram showing another configuration of the local signal generator 109 according to the first embodiment. The local oscillator 109 in FIG. 8 includes a local oscillator 111 and a frequency divider 113. The local oscillator 111 generates an oscillation signal 112 having a predetermined frequency. The local oscillator 111 is configured, for example, to multiply the oscillation frequency of a crystal oscillator by a phase-locked loop (PLL). The frequency divider 113 divides the oscillation signal 112 by a ratio of 1 / N, and generates a local signal LU and a local signal LV that form a phase difference of 360 degrees / N. The frequency of the oscillation signal 112 is set in the local oscillator 111 so as to be different from the carrier frequency of the transmission signal transmitted from the antenna in order to avoid interference. The frequency of each local signal LU, LV is set in the frequency divider 113 so as to match the carrier frequency of the transmission signal transmitted from the antenna.

  9A, FIG. 10A, and FIG. 11A are circuit diagrams illustrating specific configuration examples of the frequency divider 113 when N = 3, N = 5, and N = 7, respectively. 9B, FIG. 10B, and FIG. 11B are waveform diagrams showing operations in the configurations of FIG. 9A, FIG. 10A, and FIG. 11A, respectively. 9A and 9B, the frequency divider 113 divides the oscillation signal 112 by a ratio of 1/3, and the AND circuits 121 and 120 generate local signals LU having a phase difference of 360 degrees / 3 = 120 degrees. , LV respectively. The local signal LV advances by a phase difference of 120 degrees with respect to the local signal LU. 10A and 10B, the frequency divider 113 divides the oscillation signal 112 by a ratio of 1/5, and the AND circuits 130 and 129 generate local signals LU and LV having a phase difference of 360 degrees / 5. Generate each. The local signal LV advances by a phase difference of 360 degrees / 5 with respect to the local signal LU. 11A and 11B, the frequency divider 113 divides the oscillation signal 112 by a ratio of 1/7, and the AND circuits 140 and 139 generate local signals LU and LV having a phase difference of 360 degrees / 7. Generate each. The local signal LV advances by a phase difference of 360 degrees / 7 with respect to the local signal LU. With such a simple configuration of the frequency divider 113, the local signal generator 109 capable of supporting an arbitrary transmission frequency band can be realized.

  As described above, the modulator 10T vector-modulates the orthogonal modulation data IT and QT representing coordinates orthogonal to each other based on the local signals LU and LV having a phase difference of 360 degrees / N, and 360 degrees / N. A vector modulation signal S100T representing a signal that is vector-modulated by two carrier vectors forming a phase difference is generated.

  As described above, according to the modulator 10T of the first embodiment, a plurality of pairs of local signals LU corresponding to multiband and multimode are used by using one local oscillator 111 and a plurality of frequency dividers 113. , LV can be generated. Further, in correspondence with the phase difference of 360 degrees / N in the pair of local signals LU, LV, the coordinate modulation 110T is used to coordinate-transform the orthogonal modulation data IT, QT and vector-modulate to 360 degrees / A vector modulation signal S100T having a phase difference of N can be generated. Thereby, the modulator 10T according to the first embodiment can generate a plurality of vector modulation signals S100T corresponding to multiband and multimode using one local oscillator 111. Furthermore, since the frequency divider 113 and the coordinate converter 110T can be configured with a simple circuit, compared to a case where a plurality of local oscillators are used or a plurality of local signals are generated using a mixer. Thus, it is possible to reduce power consumption, reduce the semiconductor chip area, reduce electromagnetic interference due to generation of unnecessary high frequency, and improve the C / N (carrier-to-noise ratio) of the vector modulation signal S100T.

(Second Embodiment)
The second embodiment will be described with a focus on differences from the first embodiment. Other configurations, operations, and effects are the same as those of the first embodiment, and thus description thereof is omitted.

FIG. 12 is a block diagram illustrating a configuration of a wireless transmitter according to the second embodiment including the modulator 10T according to the first embodiment.
In FIG. 12, the wireless transmitter according to the second embodiment includes a signal processor 141T, a modulator 10T, an amplifier 143T, a band limiting filter 142T, an amplifier 169T, and a transmission antenna 300T. The modulator 10T includes a coordinate converter 110T, a local signal generator 109, and a vector modulation unit 100T.

  The signal processor 141T performs signal processing such as OFDM modulation based on the baseband data BST, and generates orthogonal modulation data IT and QT representing coordinates orthogonal to each other. As described above in the first embodiment, the modulator 10T is a vector modulation that represents a signal that is vector-modulated by two carrier vectors having a phase difference of 360 degrees / N based on the orthogonal modulation data IT and QT. A signal S100T is generated. The amplifier 143T amplifies the vector modulation signal S100T to a predetermined magnitude, the band limiting filter 142T band-limits the amplified signal, the amplifier 169T power-amplifies the band-limited signal to a predetermined power, and the transmitting antenna 300T. Wirelessly transmits the power-amplified transmission signal S300T as a long-range radio wave. It is desirable that the characteristics of the band limiting filter 142T and the characteristics of the amplifiers 143T and 169T match the characteristics of the frequency band including the frequencies of the local signals LU and LV as much as possible.

  As described above, the radio transmitter in FIG. 12 performs vector modulation using the local signals LU and LV having a phase difference different from 90 degrees and the orthogonal coordinate data IT and QT, and based on the generated vector modulation signal S100T. A transmission signal S300T can be generated and wirelessly transmitted.

FIG. 13 is a block diagram illustrating a specific configuration of the wireless transmitter according to the second embodiment including the modulator 10T of the first embodiment and corresponding to a transmission signal of three bands in two modes.
The wireless transmitter illustrated in FIG. 13 includes a signal processor 141T, a transmission unit 20T, a local oscillator 111, a switch 301T, and a transmission antenna 300T. The transmission unit 20T includes coordinate converters 150T, 151T, and 152T, a 1/3 frequency divider 146, a 1/2 frequency divider 147, a 1/5 frequency divider 148, a vector modulation unit 153T, 154T, 155T, and 156T, and an amplifier. 161T, 162T, 163T, 164T, band limiting filters 157T, 158T, 159T, 160T, and amplifiers 170T, 171T, 172T, 173T. The coordinate converters 150T, 151T, and 152T, the local oscillator 111, the 1/3 frequency divider 146, the 1/2 frequency divider 147, the 1/5 frequency divider 148, and the vector modulators 153T, 154T, 155T, and 156T, A modulator 10T is configured.

  The signal processor 141T generates two types of quadrature modulation data, that is, quadrature modulation data IaT and QaT and quadrature modulation data IbT and QbT based on the baseband data BST. These two types of quadrature modulation data represent, for example, data that has been signal-processed based on the respective radio access schemes in a multimode radio transmitter corresponding to two different radio access schemes. Similarly, the configuration of the wireless transmitter illustrated in FIG. 13 can be expanded to a multimode wireless transmitter that supports three or more wireless access methods.

  As described above with reference to FIGS. 9A and 9B, the 1/3 frequency divider 146 divides the oscillation signal 112 by a ratio of 1/3, and a phase difference of 360 degrees / 3 (= 120 degrees). To generate local signals LU3 and LV3. The 1/2 divider 147 divides the oscillation signal 112 by a ratio of 1/2 to generate local signals LU2 and LV2 having a phase difference of 90 degrees. For example, the 1/2 frequency divider 147 generates the local signal LU2 by dividing the oscillation signal 112 by a ratio of 1/2, and the local signal LV2 is obtained by exclusive OR of the oscillation signal 112 and the local signal LU2. Is generated. As described above with reference to FIGS. 10A and 10B, the 1/5 frequency divider 148 divides the oscillation signal 112 by a ratio of 1/5 and has a phase difference of 360 degrees / 5 (= 72 degrees). To generate local signals LU5 and LV5.

  When the frequency of the local signals LU5 and LV5 is f0, the frequency of the local signals LU3 and LV3 is f0 × 1.67, and the frequency of the local signals LU2 and LV2 is f0 × 2.5. In this way, the frequency dividers 146, 147, and 148 generate three pairs of local signals corresponding to the three frequency bands. Similarly, the configuration of the radio transmitter shown in FIG. 13 can be expanded to a multiband radio transmitter having a carrier frequency of 4 bands or more or different from the above-described frequency (that is, having a different division ratio). It is.

  The coordinate converter 150T converts the quadrature modulation data IaT and QaT into non-orthogonal modulation data UaT and VaT representing coordinates that intersect each other with a phase difference of 360 degrees / 3. The vector modulation unit 153T performs vector modulation using two carrier vectors having a frequency of f0 × 1.67 and a phase difference of 360 degrees / 3 based on the non-orthogonal modulation data UaT and VaT and the local signals LU3 and LV3. A vector modulation signal S153T representing the received signal is generated. Based on the vector modulation signal S153T, the amplifier 161T, the band limiting filter 157T, and the amplifier 170T appropriately band limit and amplify the transmission signal in accordance with the characteristics of the frequency band including the carrier frequency of f0 × 1.67. S170T is generated.

  The coordinate converter 151T performs coordinate conversion of the orthogonal modulation data IbT and QbT into non-orthogonal modulation data UbT and VbT representing coordinates that intersect each other with a phase difference of 360 degrees / 3. The vector modulation unit 154T performs vector modulation with two carrier vectors having a frequency of f0 × 1.67 and a phase difference of 360 degrees / 3 based on the non-orthogonal modulation data UbT and VbT and the local signals LU3 and LV3. A vector modulation signal S154T representing the processed signal is generated. Based on the vector modulation signal S154T, the amplifier 162T, the band limiting filter 158T, and the amplifier 171T appropriately band limit and amplify the transmission signal according to the characteristics of the frequency band including the carrier frequency of f0 × 1.67. S171T is generated.

  The vector modulation unit 155T is a signal that is vector-modulated by two carrier vectors having a frequency of f0 × 2.5 and a phase difference of 90 degrees based on the orthogonal modulation data UaT and VaT and the local signals LU2 and LV2. Is generated as a vector modulation signal S155T. Based on the vector modulation signal S155T, the amplifier 163T, the band limiting filter 159T, and the amplifier 172T appropriately band limit and amplify the transmission signal in accordance with the characteristics of the frequency band including the carrier frequency of f0 × 2.5. S172T is generated.

  The coordinate converter 152T converts the quadrature modulation data IaT and QaT into non-orthogonal modulation data UcT and VcT representing coordinates that intersect each other with a phase difference of 360 degrees / 5. Based on the non-orthogonal modulation data UcT and VcT and the local signals LU5 and LV5, the vector modulation unit 156T outputs a signal that is vector-modulated by two carrier vectors having a frequency of f0 and a phase difference of 360 degrees / 5. A vector modulation signal S156T is generated. Based on the vector modulation signal S156T, the amplifier 164T, the band limiting filter 160T, and the amplifier 173T appropriately band limit and amplify corresponding to the characteristics of the frequency band including the carrier frequency of f0 to generate the transmission signal S173T. .

  As described above, the transmission signals S170T and S171T are generated corresponding to two different modes in the same frequency band, and the transmission signal S172T is generated and transmitted corresponding to a frequency band different from each of the transmission signals S170T and S171T. The signal S173T is generated corresponding to a different frequency band from the transmission signals S170T, S171T, and S172T. The switch 301T is based on a control signal S301T (generated by a transmission control unit (not shown)) indicating multimode and multiband states in the wireless transmitter, and includes four transmission signals S170T, S171T, S172T, and S173T. One of them is selected, and a transmission signal 300T representing the selected signal is output to the transmission antenna 300T. Here, energization of the coordinate converter, the vector modulation unit, the amplifier, the band limiting filter, and the frequency divider of the unselected system is stopped for power saving.

  As described above, the wireless transmitter illustrated in FIG. 13 can generate the transmission signal S300T corresponding to two different modes and three different frequency bands using one local oscillator 111. The configuration of the wireless transmitter shown in FIG. 13 can be expanded to three or more multimodes or four or more multibands.

  As described above, according to the wireless transmitter of the second embodiment, a plurality of pairs of local signals corresponding to multiband and multimode are generated using one local oscillator and a plurality of frequency dividers. be able to. Further, a vector having a phase difference of 360 degrees / N is obtained by changing the coordinates of the orthogonal modulation data using a coordinate converter and performing vector modulation corresponding to the phase difference of 360 degrees / N in the pair of local signals. A modulated signal can be generated. Thereby, the radio transmitter according to the second embodiment can generate a plurality of transmission signals corresponding to the multiband and the multimode by using one local oscillator. Furthermore, since the frequency divider and coordinate converter can be configured with a simple circuit, compared to the case of using a plurality of local oscillators or generating a plurality of systems of local signals using a mixer, It is possible to reduce power consumption, reduce the semiconductor chip area, reduce electromagnetic interference due to generation of unnecessary high frequency, and improve the C / N (carrier-to-noise ratio) of the transmission signal.

(Third embodiment)
In the third embodiment, a description will be given focusing on differences from the first embodiment. Other configurations, operations, and effects are the same as those of the first embodiment, and thus description thereof is omitted.

FIG. 14 is a block diagram illustrating a configuration of a demodulator 10R according to the third embodiment.
In FIG. 14, the demodulator 10 </ b> R of the third embodiment includes a vector demodulator 100 </ b> R and a local signal generator 109. The vector demodulator 100R includes an input terminal 105UR, an input terminal 106UR, an input terminal 105VR, an input terminal 106VR, a mixer 101UR, and a mixer 101VR. The local signal generator 109 has the same configuration as that of the local signal generator 109 of the first embodiment, and two local signal generators having a phase difference of 360 degrees / N (N is an integer of 3 or 5) are formed. A pair of local signals LU and LV representing a vector is generated. The local signal generator 109 generates the local signal LV so as to advance by a phase difference of 360 degrees / N with respect to the local signal LU. The local signals LU and LV are used as carrier vectors for vector demodulation in the vector demodulation unit 100R. The frequency of each local signal LU, LV is set in the local signal generator 109 so as to match the carrier frequency of the received signal to be demodulated received by the antenna.

  The vector modulation signal S100R represents a signal that is vector-modulated by two carrier vectors having a phase difference of 360 degrees / N. Input terminals 105UR and 106UR receive local signal LU and vector modulation signal S100R, respectively, and input terminals 105VR and 106VR receive local signal LV and vector modulation signal S100R, respectively. The mixer 101UR mixes the vector modulation signal S100R with the local signal LU, and generates non-orthogonal modulation data UR representing one coordinate that intersects each other with a phase difference of 360 degrees / N. The mixer 101VR mixes the vector modulation signal S100R with the local signal LV, and generates non-orthogonal modulation data VR representing the other coordinate that intersects with a phase difference of 360 degrees / N. That is, the vector demodulation unit 100R performs vector demodulation on the vector modulation signal S100R based on the local signals LU and LV, and generates non-orthogonal modulation data UR and VR. The non-orthogonal modulation data VR is coordinate-converted into orthogonal modulation data IR and orthogonal modulation data QR representing coordinates orthogonal to each other. The non-orthogonal modulation data VR is delayed from the non-orthogonal modulation data UR by a phase difference of 360 degrees / N, and the orthogonal modulation data QR is delayed by 90 degrees from the orthogonal modulation data IR.

  FIG. 15 is a block diagram showing another configuration of the demodulator 10R according to the third embodiment. A demodulator 10R shown in FIG. 15 further includes a coordinate converter 110R in addition to the vector demodulator 100R and the local signal generator 109 described above. The coordinate converter 110R converts the non-orthogonal modulation data UR and VR representing coordinates intersecting with each other with a phase difference of 360 degrees / N into the orthogonal modulation data IR and QR representing coordinates orthogonal to each other. As described above, the non-orthogonal modulation data VR is delayed from the non-orthogonal modulation data UR by a phase difference of 360 degrees / N. The coordinate converter 110R performs coordinate conversion so that the orthogonal modulation data QR is delayed by 90 degrees with respect to the orthogonal modulation data IR.

  Here, the orthogonal modulation data IR and QR are demodulated into baseband data based on, for example, an OFDM (Orthogonal Wave Frequency Division Multiplexing) demodulation method by a signal processor 141R (described later) located at the subsequent stage of the coordinate converter 110R. Represents the signal to be. The non-orthogonal modulation data UR and VR may be digital signals or analog signals. In the case of a digital signal, the coordinate converter 110R is configured by, for example, a look-and-table method or a digital calculation method. The non-orthogonal modulation data UR and VR generated by the vector demodulation unit 100R are converted into digital signals by an analog / digital converter (not shown) and input to the coordinate converter 110R. Furthermore, the vector demodulation unit 100R may be configured by a digital processing method. In this case, the received analog signal is converted into a digital signal by an analog / digital converter (not shown) located in the preceding stage of the vector demodulation unit 100R. The vector modulation signal S100R in the digital signal state is digitally processed by the vector demodulation unit 100R, and the non-orthogonal modulation data UR and VR in the digital signal state are input to the coordinate converter 110R.

  Since the detailed operation of the coordinate converter 110R is as described above with reference to FIGS. 3, 4, and 5 in the first embodiment, the description thereof is omitted. Further, the detailed configuration and operation of the local signal generator 109 in the first embodiment are shown in FIGS. 6, 7A, 7B, 8, 9A, 9B, 10A, 10B, 11A, and Since it is as having mentioned above with reference to FIG. 11B, description is abbreviate | omitted.

  As described above, the demodulator 10R receives a signal that is vector-modulated by two carrier vectors having a phase difference of 360 degrees / N based on the local signals LU and LV having a phase difference of 360 degrees / N. The vector modulation signal S100R represented is vector-demodulated to generate orthogonal modulation data IR and QR representing coordinates orthogonal to each other.

  As described above, according to the demodulator 10R of the third embodiment, a plurality of pairs of local signals LU corresponding to multiband and multimode are used by using one local oscillator 111 and a plurality of frequency dividers 113. , LV can be generated. Further, the vector modulation signal S100R is vector-demodulated in accordance with the phase difference of 360 degrees / N in the pair of local signals LU and LV, and the coordinate conversion is performed using the coordinate converter 110R, whereby the orthogonal modulation data IR, QR can be generated. As a result, the demodulator 10R of the third embodiment demodulates a plurality of vector modulation signals S100R corresponding to multiband and multimode using one local oscillator 111 and corresponds to the vector modulation signal S100R. Quadrature modulation data IR and QR can be generated. Furthermore, since the frequency divider 113 and the coordinate converter 110R can be configured with a simple circuit, the frequency divider 113 and the coordinate converter 110R can be configured with a plurality of local oscillators or a plurality of local signals using a mixer. Thus, it is possible to reduce power consumption, reduce the semiconductor chip area, reduce electromagnetic interference due to generation of unnecessary high frequency, and improve the S / N (signal-to-noise ratio) of the orthogonal modulation data IR and QR. .

(Fourth embodiment)
In the fourth embodiment, a description will be given focusing on differences from the first, second, and third embodiments. Other configurations, operations, and effects are the same as those in the first, second, and third embodiments, and thus description thereof is omitted.

FIG. 16 is a block diagram illustrating a configuration of a wireless receiver according to the fourth embodiment including the demodulator 10R of the third embodiment.
In FIG. 16, the radio receiver of the fourth embodiment includes a receiving antenna 300R, a band limiting filter 142R, an amplifier (also referred to as an LNA, ie, a low noise amplifier) 143R, a demodulator 10R, and a signal processor 141R. The demodulator 10R includes a local signal generator 109, a vector demodulator 100R, and a coordinate converter 110R.

  The receiving antenna 300R receives radio waves, the band limiting filter 142R band-limits the received signal S300R received, and the amplifier 143R amplifies the band-limited signal to a predetermined voltage to generate a vector modulation signal S100R. As described above in the third embodiment, the demodulator 10R has coordinates orthogonal to each other based on the vector modulation signal S100R representing a signal demodulated by two carrier vectors having a phase difference of 360 degrees / N. Is generated. The signal processor 141R performs signal processing such as OFDM demodulation based on the orthogonal modulation data IR and QR, and generates baseband data BSR. It is desirable that the characteristics of the band limiting filter 142R and the characteristics of the amplifier 143R match the characteristics of the frequency band including the frequencies of the local signals LU and LV as much as possible.

  As described above, the radio receiver in FIG. 16 performs vector demodulation using the local signals LU and LV having a phase difference different from 90 degrees and the vector modulation signal S100R, and based on the generated orthogonal coordinate data IR and QR. Signal processing can be performed to generate baseband data BSR.

FIG. 17 is a block diagram illustrating a specific configuration of the wireless receiver according to the fourth embodiment, which includes the demodulator 10R of the third embodiment and corresponds to the received signals of three bands in two modes.
The radio receiver shown in FIG. 17 includes a receiving antenna 300R, a switch 301R, a local oscillator 111, a receiving unit 20R, and a signal processor 141R. The receiving unit 20R includes band limiting filters 157R, 158R, 159R, 160R, amplifiers 161R, 162R, 163R, 164R, 1/3 frequency divider 146, 1/2 frequency divider 147, 1/5 frequency divider 148, vector Demodulating units 153R, 154R, 155R, 156R, and coordinate converters 150R, 151R, 152R are included. The local oscillator 111, the 1/3 frequency divider 146, the 1/2 frequency divider 147, the 1/5 frequency divider 148, the vector demodulation units 153R, 154R, 155R, 156R, and the coordinate converters 150R, 151R, 152R, A demodulator 10R is configured.

  The configurations and operations of the 1/3 frequency divider 146, the 1/2 frequency divider 147, and the 1/5 frequency divider 148 are as described above with reference to FIG. 13 in the second embodiment. Is omitted.

  When the frequency of the local signals LU5 and LV5 is f0, the frequency of the local signals LU3 and LV3 is f0 × 1.67, and the frequency of the local signals LU2 and LV2 is f0 × 2.5. In this way, the frequency dividers 146, 147, and 148 generate three pairs of local signals corresponding to the three frequency bands. Similarly, the configuration of the wireless receiver shown in FIG. 17 can be expanded to multiband wireless receivers having carrier frequencies of 4 bands or more or different from the above-described frequencies (that is, different division ratios). It is.

  The switch 301R corresponds to each of the received signals S170R, S171R, S172R, and S173R based on a control signal S301R (generated by a reception control unit (not shown)) that represents multimode and multiband states in the wireless receiver. One of the four paths is selected, and the reception signal 300R from the reception antenna 300R is passed. Here, energization of the band-limiting filter, amplifier, vector demodulator, coordinate converter, and frequency divider on the unselected path is stopped for power saving. The reception signals S170R and S171R correspond to two different modes in the same frequency band, the reception signal S172R corresponds to a frequency band different from each reception signal S170R and S171R, and the reception signal S173R corresponds to each reception signal S170R and S171R. , S172R corresponds to a different frequency band.

  The band limiting filter 157R and the amplifier 161R appropriately band-limit and amplify the received signal S170R corresponding to the characteristics of the frequency band including the carrier frequency of f0 × 1.67, and the frequency is f0 × 1.67. A vector modulation signal S153R representing a signal that is vector-modulated by two carrier vectors having a phase difference of 360 degrees / 3 is generated. The vector demodulation unit 153R generates non-orthogonal modulation data UaR and VaR representing coordinates that intersect with each other with a phase difference of 360 degrees / 3 based on the vector modulation signal S153R and the local signals LU3 and LV3. The coordinate converter 150R converts the non-orthogonal modulation data UaR and VaR into the orthogonal modulation data IaR and QaR.

  The band limiting filter 158R and the amplifier 162R appropriately band limit and amplify the received signal S171R corresponding to the characteristics of the frequency band including the carrier frequency of f0 × 1.67, and the frequency is f0 × 1.67. A vector modulation signal S154R representing a signal that is vector-modulated by two carrier vectors having a mutual phase difference of 360 degrees / 3 is generated. The vector demodulation unit 154R generates non-orthogonal modulation data UbR and VbR representing coordinates that intersect with each other with a phase difference of 360 degrees / 3 based on the vector modulation signal S154R and the local signals LU3 and LV3. The coordinate converter 151R converts the non-orthogonal modulation data UbR and VbR into the orthogonal modulation data IbR and QbR.

  The band limiting filter 159R and the amplifier 163R appropriately band limit and amplify the received signal S172R according to the characteristics of the frequency band including the carrier frequency of f0 × 2.5, and the frequency is f0 × 2.5. A vector modulated signal S155R representing a signal that is vector-modulated by two carrier vectors having a phase difference of 90 degrees is generated. The vector demodulation unit 154R generates orthogonal modulation data IaR and QaR based on the vector modulation signal S155R and the local signals LU2 and LV2.

  The band limiting filter 160R and the amplifier 164R appropriately band limit and amplify the received signal S173R according to the characteristics of the frequency band including the carrier frequency of f0, and the frequency is f0 and the phase difference between them is 360 degrees / 5 generates a vector modulation signal S156R representing a signal that is vector-modulated by two carrier vectors of 5. The vector demodulation unit 156R generates non-orthogonal modulation data UcR and VcR representing coordinates that intersect with each other with a phase difference of 360 degrees / 5 based on the vector modulation signal S156R and the local signals LU5 and LV5. The coordinate converter 152R converts the non-orthogonal modulation data UcR and VcR into the orthogonal modulation data IaR and QaR.

  The signal processor 141R generates baseband data BSR based on two types of quadrature modulation data, that is, quadrature modulation data IaR and QaR and quadrature modulation data IbR and QbR. These two types of quadrature modulation data represent, for example, data that has been signal-processed based on each wireless access method in a multimode wireless receiver that supports two different wireless access methods. Similarly, the configuration of the wireless receiver shown in FIG. 17 can be applied to a multimode wireless receiver corresponding to three or more wireless access methods.

  As described above, the radio receiver shown in FIG. 17 generates baseband data BSR using one local oscillator 111 based on received signals S300R corresponding to two different modes and three different frequency bands. be able to. The configuration of the wireless receiver shown in FIG. 17 can be developed for three or more multimodes or four or more multibands.

  As described above, according to the wireless receiver of the fourth embodiment, a plurality of pairs of local signals corresponding to multiband and multimode are generated using one local oscillator and a plurality of frequency dividers. be able to. Furthermore, quadrature modulation data can be generated by vector-demodulating a vector modulation signal corresponding to a phase difference of 360 degrees / N in a pair of local signals and performing coordinate conversion using a coordinate converter. As a result, the wireless receiver according to the fourth embodiment uses a single local oscillator to demodulate a plurality of systems of reception signals corresponding to multiband and multimode, and generates quadrature modulation data corresponding to the reception signals. It becomes possible to do. Furthermore, since the frequency divider and coordinate converter can be configured with a simple circuit, compared to the case of using a plurality of local oscillators or generating a plurality of systems of local signals using a mixer, Reduce power consumption, reduce semiconductor chip area, reduce electromagnetic interference due to generation of unnecessary high frequency, improve S / N (signal to noise ratio) of quadrature modulation data, and lower error rate before error correction It becomes possible.

(Fifth embodiment)
In the fifth embodiment, description will be made centering on differences from the first, second, third, and fourth embodiments. Other configurations, operations, and effects are the same as those of the first, second, third, and fourth embodiments, and thus description thereof is omitted.

FIG. 18 is a block diagram illustrating a configuration of a wireless transceiver according to the fifth embodiment.
18, the wireless transceiver according to the fifth embodiment includes a signal processor 141, a local oscillator 111, a transmission unit 20T, a reception unit 20R, a switch 301, and a transmission / reception antenna 300. The radio transceiver according to the fifth embodiment has the configurations of both the radio transmitter according to the second embodiment shown in FIG. 13 and the radio receiver according to the fourth embodiment shown in FIG.

  The signal processor 141 performs signal processing based on the baseband data BST, and generates quadrature modulation data IaT, QaT, IbT, and QbT. The transmission unit 20T performs transmission signal processing based on the orthogonal modulation data IaT, QaT, IbT, QbT and the oscillation signal 112, and generates transmission signals S170T, S171T, S172T, and S173T. The switch 301 selects one based on the transmission signals S170T, S171T, S172T, and S173T, and generates a transmission signal S300T. The transmission / reception antenna 300 transmits the transmission signal S300T as a radio wave.

  On the other hand, the transmitting / receiving antenna 300 receives a radio wave and outputs a reception signal S300R. The switch 301 generates any of the reception signals S170R, S171R, S172R, and S173R based on the reception signal S300R. The receiving unit 20R performs reception signal processing based on the reception signals S170R, S171R, S172R, S173R and the oscillation signal 112, and generates quadrature modulation data IaR, QaR, IbR, and QbR. The signal processor 141 performs signal processing based on the orthogonal modulation data IaR, QaR, IbR, and QbR to generate baseband data BST.

FIG. 19 is a block diagram showing another configuration of the wireless transceiver according to the fifth embodiment.
The configuration of the radio transceiver in FIG. 19 is different from the configuration of the radio transceiver in FIG. 18 in that the local oscillator 111 and the oscillation signal 112 output from the local oscillator 111 to the transmission unit 20T and the reception unit 20R are the local oscillator 111T. And the local oscillator 111R, the oscillation signal 112T output from the local oscillator 111T to the transmission unit 20T, and the oscillation signal 112R output from the local oscillator 111R to the reception unit 20R, respectively. Even the configuration of the wireless transceiver of FIG. 19 operates in the same manner as the configuration of the wireless transceiver of FIG. However, since there are two local oscillators, the effects are partially reduced in terms of power consumption and semiconductor chip area compared to the configuration of the wireless transceiver of FIG.

  In the above embodiment, a communication device that communicates using radio, that is, a wireless transmitter, a wireless receiver, and a wireless transceiver has been described. However, according to the present invention, the same effect can be obtained with a similar configuration and operation with respect to a communication device that communicates using a wire, for example, a cable television transceiver.

  Thus, according to the modulator, demodulator, modulator / demodulator, and communication device of the present invention, a plurality of pairs corresponding to multiband and multimode are used by using one local oscillator and a plurality of frequency dividers. A local signal can be generated. Further, by using the coordinate converter, it is possible to vector-modulate the orthogonal modulation data or perform vector demodulation to the orthogonal modulation data corresponding to the phase difference of 360 degrees / N in the pair of local signals. As a result, using one local oscillator, a plurality of vector modulation signals corresponding to multiband and multimode are generated, or a plurality of vector modulation signals corresponding to multiband and multimode are demodulated. It is possible to generate orthogonal modulation data corresponding to the modulation signal. Furthermore, since the frequency divider and coordinate converter can be configured with a simple circuit, compared to the case of using a plurality of local oscillators or generating a plurality of systems of local signals using a mixer, It is possible to reduce power consumption, reduce a semiconductor chip area, reduce electromagnetic interference due to generation of unnecessary high frequencies, and improve the quality of vector modulation signals or quadrature modulation data.

  The above description of the embodiments is merely an example embodying the present invention. The present invention is not limited to these examples, and can be easily configured by those skilled in the art using the technology of the present invention. It can be expanded to various examples.

  The present invention can be used for a modulator, a demodulator, a modem, and a communication device.

1 is a block diagram showing a configuration of a modulator according to a first embodiment of the present invention. The block diagram which shows another structure of the modulator which concerns on the 1st Embodiment of this invention Explanatory drawing which shows signal point arrangement | positioning of the orthogonal modulation data of this invention Explanatory drawing which shows signal point arrangement | positioning of the non-orthogonal modulation data of this invention Explanatory drawing which shows the relationship of the coordinate transformation from the orthogonal modulation data of this invention to non-orthogonal modulation data 1 is a circuit diagram showing a detailed configuration of a local signal generator according to a first embodiment of the present invention. 1 is a circuit diagram showing a specific configuration of a local signal generator according to a first embodiment of the present invention. Waveform diagram showing the operation of the local signal generator of FIG. 7A according to the first embodiment of the present invention The block diagram which shows another structure of the local signal generator based on the 1st Embodiment of this invention. 1 is a circuit diagram showing a detailed configuration of a frequency divider according to a first embodiment of the present invention. Waveform diagram showing the operation of the frequency divider of FIG. 9A according to the first embodiment of the present invention. 1 is a circuit diagram showing a detailed configuration of a frequency divider according to a first embodiment of the present invention. Waveform diagram showing the operation of the frequency divider of FIG. 10A according to the first embodiment of the present invention. 1 is a circuit diagram showing a detailed configuration of a frequency divider according to a first embodiment of the present invention. Waveform diagram showing the operation of the frequency divider of FIG. 11A according to the first embodiment of the present invention. The block diagram which shows the structure of the radio | wireless transmitter which concerns on the 2nd Embodiment of this invention. The block diagram which shows the detailed structure of the radio | wireless transmitter which concerns on the 2nd Embodiment of this invention. The block diagram which shows the structure of the demodulator based on the 3rd Embodiment of this invention. The block diagram which shows another structure of the demodulator based on the 3rd Embodiment of this invention. The block diagram which shows the structure of the radio | wireless receiver which concerns on the 4th Embodiment of this invention. The block diagram which shows the detailed structure of the radio | wireless receiver which concerns on the 4th Embodiment of this invention. The block diagram which shows the structure of the radio | wireless transmitter / receiver which concerns on the 5th Embodiment of this invention. The block diagram which shows another structure of the radio | wireless transmitter / receiver which concerns on the 5th Embodiment of this invention. The block diagram which shows the structural example of the direct conversion receiver which concerns on a prior art example The block diagram which shows the structural example of the direct conversion transmitter which concerns on a prior art example Block diagram showing a configuration example of a local oscillator of a direct conversion receiver according to a conventional example Waveform diagram showing operation of local oscillator of direct conversion receiver according to conventional example

Explanation of symbols

10T modulator 10R demodulator 20T transmitter 20R receiver 100T, 153T, 154T, 155T, 156T vector modulator 100U, 153U, 154U, 155U, 156U vector demodulator 101UT, 101VT, 101UR, 101VR mixer 103 adder 105UT, 106 UT, 105 VT, 106 VT, 105 UR, 106 UR, 105 VR, 106 VR input terminal 109 local signal generator 110 T, 150 T, 151 T, 152 T, 110 R, 150 R, 151 R, 152 R coordinate converter 111 local oscillator 114, 115, 116, 117, 122 , 123, 124, 125, 126, 131, 132, 133, 134, 135, 136 Flip-flop circuit 118, 127, 137 Inverter circuit 11 9, 128, 138 NAND circuit 120, 121, 129, 130, 139, 140 AND circuit 141T, 141R, 141 Signal processor 142T, 157T, 158T, 159T, 160T, 142R, 157R, 158R, 159R, 160R Band limiting filter 143T, 161T, 162T, 163T, 164T, 169T, 170T, 171T, 172T, 173T, 143R, 161R, 162R, 163R, 164R Amplifier 300T, 300R, 300 Antenna 301T, 301R, 301 Switch 146, 146 1/3 147, 147 1/2 divider 148, 148 1/5 divider

Claims (17)

A local signal generator for generating a first local signal and a second local signal that form a phase difference of 360 degrees / N (N is an integer of 3 or 5) from each other;
A first input terminal and a second input terminal for receiving first data and second data representing coordinates intersecting each other with a predetermined phase difference, respectively, and mixing the first data with the first local signal and second data And a vector modulation unit that generates a signal that is vector-modulated with a phase difference of 360 degrees / N by mixing the signal with the second local signal.   And a coordinate converter for converting the third data and the fourth data representing coordinates orthogonal to each other into the first data and the second data representing coordinates intersecting with each other at a phase difference of 360 degrees / N. 2. The modulator according to 1. The local signal generator is
A local oscillator that generates an oscillation signal of a predetermined frequency;
The modulator according to claim 2, further comprising: a frequency divider that divides the oscillation signal by a ratio of 1 / N to generate a first local signal and a second local signal. further,
M-1 (M is an integer of 2 or more) the frequency divider;
M-1 coordinate converters;
M-1 vector modulation units,
Each of the M frequency dividers divides the oscillation signal into one of different ratios among the M different ratios,
Each of the M coordinate converters converts the third data and the fourth data into first data and second data representing coordinates that intersect at one different phase difference among M different phase differences. The modulator according to claim 3, which performs coordinate transformation. The vector modulation unit is
A first mixer for mixing the first data with the first local signal and generating a first mixed signal;
A second mixer for mixing the second data with the second local signal to generate a second mixed signal;
The modulator according to claim 1, further comprising: an adder that adds the first mixed signal and the second mixed signal to each other to generate a vector-modulated signal.   The modulator according to claim 1, wherein the local signal generator includes a ring oscillator in which N inverters are configured in a ring shape. A local signal generator that generates a first local signal and a second local signal that form a phase difference of 360 degrees / N from each other (N is a positive integer of 3 or 5);
A first input terminal and a second input terminal for receiving a vector-modulated signal, the vector-modulated signal is mixed with the first local signal to generate first data, and the vector-modulated signal is transmitted to the second local signal A demodulator having a vector demodulator that performs vector demodulation so as to represent coordinates at which the first data and the second data intersect with each other with a phase difference of 360 degrees by mixing with a signal to generate second data.   The demodulator according to claim 7, further comprising a coordinate converter that converts the first data and the second data into third data and fourth data representing coordinates orthogonal to each other. The local signal generator is
A local oscillator that generates an oscillation signal of a predetermined frequency;
The demodulator according to claim 8, further comprising a frequency divider that divides the oscillation signal by a ratio of 1 / N and generates a first local signal and a second local signal. further,
M-1 (M is an integer of 2 or more) the frequency divider;
M-1 vector demodulation units;
M-1 coordinate converters,
Each of the M frequency dividers divides the oscillation signal into one of different ratios among the M different ratios,
10. Each of the M vector demodulation units performs vector demodulation so that the first data and the second data represent coordinates at which one of the M different phase differences intersects at one different phase difference. The demodulator described in 1. The vector demodulator
A first mixer for mixing the vector modulated signal with a first local signal to generate first data;
The demodulator according to claim 7, further comprising: a second mixer that mixes the vector-modulated signal with the second local signal to generate second data.   The demodulator according to claim 7, wherein the local signal generator includes a ring oscillator in which N inverters are configured in a ring shape. A modulator according to claim 1;
A demodulator having the demodulator according to claim 7.   The modem according to claim 13, wherein the modulator and the demodulator share at least a part.   A communication device comprising the modulator according to claim 1.   A communication device comprising the demodulator according to claim 7.   A communication device comprising the modem according to claim 13.

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