JP2009303240A - Receiver and computer program - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To improve reception accuracy by reproducing a reception signal when a CP is inserted, when the CP is not inserted at a transmitting side. <P>SOLUTION: A receiver 2 performs circular convolution operation upon a transmission line characteristic estimation calculated by using a reception known signal of a specific frame to an input signal for transmission line characteristic estimation, a known signal of the specific frame and a known signal of a post-stage frame of the specific frame just by a length of a maximum delay time of a transmission line and replaces a portion of the length of the maximum delay time of the transmission line from a head of the reception known signal of the specific frame with a result of the cyclic convolution operation to create a pseudo reception signal of a reception section from the reception known signal of the specific frame to the reception known signal of the post-stage frame of the specific frame. While defining the reception section from the reception known signal of the specific frame to the reception known signal of the post-stage frame of the specific frame as one equalization section, the pseudo reception signal is equalized in a frequency domain or a time domain. <P>COPYRIGHT: (C)2010,JPO&INPIT

Description

  The present invention relates to a receiver in a wireless communication system and a computer program for realizing the receiver using a computer.

  Suppressing self-path interference due to multipath propagation in a wireless communication system is important for realizing high-speed transmission. For example, a frequency domain equalization method is known as an effective self-path interference suppression technique in a wireless communication system using single carrier transmission. In particular, the frequency domain equalization method using the Minimum Mean Square Error norm can suppress noise enhancement in frequency components with a small channel gain, and is known as an effective equalization algorithm ( Hereinafter, the frequency domain equalization method based on this least mean square error criterion is referred to as an MMSE frequency equalization method).

  FIG. 5 is a block diagram showing a schematic configuration of a wireless communication system including a conventional receiver 300 using the MMSE frequency equalization method. In FIG. 5, a transmitter 1 inserts a cyclic prefix (hereinafter referred to as CP) by CP inserters 11a and 11b at the heads of transmission data and a transmission pilot signal, and then inserts these CPs. The subsequent transmission data and the transmission pilot signal are time-multiplexed by the time multiplexer 12, and the time-multiplexed signal is wirelessly transmitted from the antenna 13. FIG. 6 is a diagram illustrating a configuration example of a transmission frame of the transmission signal. In the example of FIG. 6, the last 32 symbols of the pilot signal are copied to the head part (CP part) of the pilot signal, and the last 32 symbols of the data are copied to the head part (CP part) of the data. The pilot signal is a known signal that is preliminarily matched with the receiver side.

  In receiver 300, CPs are removed by CP removers 22a and 22b from the received data and the received pilot signal of the signal received by antenna 21, respectively. Next, the transmission path estimator 310 obtains a transmission path characteristic estimation value and a noise power estimation value from the received pilot signal after CP removal. The MMSE frequency equalizer 24 equalizes and outputs the received data after CP removal in the frequency domain by using the transmission channel characteristic estimation value and the noise power estimation value according to the equation (1).

Here, d _r (n) is the received data after CP removal, d _r ′ (n) is the received data after MMSE frequency equalization, H _a (f) is the frequency domain channel characteristic estimation value, and N _a is the noise. Power estimation value, F {x} is a discrete Fourier transform of x, F ⁻¹ {x} is an inverse discrete Fourier transform of x, and ^* is a complex conjugate notation.

FIG. 7 is a block diagram showing a configuration of the conventional transmission path estimator 310 of FIG. 7, first, a discrete Fourier transformer 231a is CP after removal of the received pilot signal _p r (n), (n is from 0 _(integer N until p -1)) discrete Fourier transform of _{N p} points for (See equation (2)). However, N _p is the sequence length of the received pilot signal p _r (n) after CP removal, and p _r (f) is the signal after the discrete Fourier transform.

Next, the converted pilot signal P _r (f) is multiplied by a predetermined signal by the multiplier 234c, thereby obtaining a frequency domain transmission line characteristic estimated value H _a (f) shown in the equation (3). . However, P _t (f) is a frequency characteristic of a known pilot signal.

Here, since the channel characteristic estimated value H _a (f) is _a channel characteristic estimated value to which noise has been added, it is necessary to remove the influence of noise. To this end, the inverse discrete Fourier transformer 232 performs inverse discrete Fourier transform on the transmission path characteristic estimated value H _a (f) to obtain _a time domain transmission path characteristic estimated value h _a (n). The time domain transmission line characteristic estimated value h _a (n) represents the estimated delay profile. In general, the CP length N _CP is set to be longer than the maximum delay time of the transmission path, so that all components in the time domain longer than the CP length N _CP can be regarded as noise components. Thereby, the multiplier 234a multiplies the transmission line characteristic estimated value h _a (n) by the filter 235c having the coefficient g _NE (n) for extracting only the component within the CP length N _CP , thereby estimating the transmission line characteristic. The noise component is removed from the value h _a (n). Next, the transmission path estimation value interpolator 236 performs data interpolation on the transmission path characteristic estimation value after the noise removal. In general, the pilot length is shorter than the data length in order to reduce the overhead. Therefore, the shortage is interpolated with the data value “0” by the transmission line estimated value interpolator 236 to obtain a transmission line characteristic estimated value having the same length as the data length. Next, the discrete Fourier transformer 231b performs a discrete Fourier transform on the channel characteristic estimation value after data interpolation, and outputs a frequency domain channel characteristic estimation value H _a ′ (f) ((4), (5). ) See formula). This channel characteristic estimation value H _a ′ (f) is input to the MMSE frequency equalizer 24 and used as the frequency domain channel characteristic estimation value H _a (f) in the above equation (1).

Further, the multiplier 234b, with respect to the channel estimation value _h a (n), by multiplying the filter 235d having a coefficient of inverse characteristics of the coefficient _{g NE (n) (1-} g NE (n)) Then, a component outside the CP length N _CP is extracted from the transmission path characteristic estimated value h _a (n). Next, the noise power estimator 237 calculates and outputs _a noise power estimation value Na by integrating the output of the multiplier 234b (see equation (6)).

A. Czylwik, “Low Overhead Pilot-Aided Synchronization for Single Carrier Modulation with Frequency Domain Equalization,” Proc. GLOBECOM '98, pp. 2068-2073, Sydney, Australia, Nov. 1998.

  However, in the conventional technique described above, when the transmitter is not equipped with a CP inserter, there is a problem that the accuracy of the channel characteristic estimation value deteriorates because the CP is not inserted into the pilot signal. For this reason, in an existing standard wireless communication system that does not require a CP inserter, even if frequency domain equalization is performed, a sufficient effect cannot be obtained.

  FIG. 8 and FIG. 9 are conceptual diagrams for explaining the conventional influence due to the absence of CP insertion. In FIG. 8, CP (a copy of the symbol “E”) is inserted into the transmission pilot signal (“A” to “E” symbol) on the transmission side, so that an interference component (“O” symbol due to multipath propagation) is inserted. (The delay component) falls within the CP, and the interference component can be removed by the CP remover of the receiver. As a result, the frequency component after the discrete Fourier transform does not include an interference component, and only the amplitude and phase information of the path can be extracted by the above equation (3), so that the transmission path characteristic estimated value can be obtained with high accuracy.

  However, in FIG. 9, CP is not inserted in the transmission pilot signal (“A” to “E” symbols) on the transmission side, so that the interference component due to multipath propagation (delayed component of “O” symbol) is the transmission pilot signal. As a matter of course, the interference component cannot be removed even by the CP remover of the receiver. As a result, since the frequency component after the discrete Fourier transform includes an interference component, even if the transmission path characteristic estimation value is obtained by the above equation (3), the portion where the signal is not circulated (the symbol portion of “O”) A path amplitude or phase estimation error occurs. When the CP is not inserted in this way, the accuracy of the transmission path characteristic estimation value deteriorates, so that even if frequency domain equalization is performed, a sufficient effect cannot be obtained.

  Further, since the CP is not inserted into the pilot signal, there arises a problem that the noise power obtained by the above equation (6) is estimated to be larger than actual. 10 and 11 are waveform diagrams for explaining the conventional influence on noise power due to the absence of CP insertion. FIG. 10 shows an example of the time variation of the delay wave power. FIG. 11 shows a temporal change in the estimated noise power value of the delayed wave of FIG. 10 when no CP is inserted into the pilot signal. As shown in FIGS. 10 and 11, the estimated noise power is estimated to be proportional to the power of the delayed wave and larger than the actual noise power. This is because there was no CP insertion, so that interference components were included in the frequency characteristics of the received pilot signal, and the sum of the actual noise power and the interference power was estimated as the noise power. As the accuracy of the noise power estimation value deteriorates in this way, the MMSE frequency equalization method cannot suppress bit errors and may adversely affect communication quality.

  In addition, if a CP inserter can be connected to an existing standard transmitter that does not require a CP inserter, backward compatibility with an existing standard receiver without a CP remover is maintained. In particular, it is practically impossible to insert a CP into a pilot channel, which is a common channel.

  The present invention has been made in view of such circumstances, and an object of the present invention is to improve reception accuracy by reproducing a reception signal when the CP is inserted when the CP is not inserted on the transmission side. It is to provide a receiver that can.

  Another object of the present invention is to provide a computer program for realizing the receiver of the present invention using a computer.

  In order to solve the above problems, a receiver according to the present invention arranges a known signal and an unknown signal transmitted subsequently to the known signal in one frame, and continuously transmits the frame from the transmitter. In a receiver in a wireless communication system, transmission path characteristic estimated value calculation means for calculating a transmission path characteristic estimated value based on the known signal and a transmission path characteristic estimation input signal, and a specific frame received by the receiver The transmission path characteristic estimated value calculated by the transmission path characteristic estimated value calculation means using the received known signal as the transmission path characteristic estimation input signal, the known signal of the specific frame, and the subsequent frame of the specific frame The known signal is cyclically convolved with the length of the maximum delay time of the transmission path, and the portion of the length of the maximum delay time of the transmission path is calculated from the head of the received known signal of the specific frame. By replacing with the result of the convolution operation, pseudo received signal generating means for generating a pseudo received signal in a receiving section from the received known signal of the specific frame to the received known signal of the frame subsequent to the specific frame, and the specific frame An equalization unit configured to equalize the pseudo reception signal in a frequency domain or a time domain with a reception period from a reception known signal to a reception known signal of a frame subsequent to the specific frame as one equalization period; It is characterized by that.

The computer program according to the present invention performs a receiving process in a wireless communication system in which a known signal and an unknown signal transmitted subsequently to the known signal are arranged in one frame and the frame is continuously transmitted from a transmitter. A computer program for calculating a transmission path characteristic estimation value based on the known signal and a transmission path characteristic estimation input signal, and a received known signal of a specific frame received by the receiver in the transmission path A transmission path characteristic estimated value calculated by the transmission path characteristic estimated value calculation function using the characteristic estimation input signal, a known signal of the specific frame, and a known signal of a frame subsequent to the specific frame; A portion of the length of the maximum delay time of the transmission path from the beginning of the received signal of the specific frame. A function of creating a pseudo reception signal in a reception section from a reception known signal of the specific frame to a reception known signal of a frame subsequent to the specific frame by replacing with the result of the cyclic convolution operation, and a reception known signal of the specific frame And a function for equalizing the pseudo reception signal in the frequency domain or the time domain with a reception interval from the specific frame to the reception known signal of the frame subsequent to the specific frame as one equalization interval. And
The above-described computer program enables the above-described receiver to be realized using a computer.

  According to the present invention, by creating a pseudo reception signal from the first stage transmission path characteristic estimation value based on the received known signal and the known signal, the CP is inserted when the CP is not inserted on the transmission side. It is possible to reproduce the received signal at the time and improve the receiving accuracy.

It is a block diagram which shows schematic structure of the radio | wireless communications system which comprises the receiver 2 provided with the transmission path estimator 23 (transmission path characteristic estimation apparatus) which concerns on one Embodiment of this invention. It is a block diagram which shows the structure of the transmission path estimator 23 which concerns on the same embodiment. It is a conceptual diagram for demonstrating operation | movement of the interference compensator 233 shown in FIG. It is a conceptual diagram for demonstrating operation | movement of the interference compensator 233 shown in FIG. 1 is a block diagram showing a schematic configuration of a wireless communication system including a conventional receiver 300. FIG. It is a figure which shows the structural example of the transmission frame of the transmission signal with CP. It is a block diagram which shows the structure of the conventional transmission path estimator 310 shown in FIG. It is a conceptual diagram for demonstrating the conventional influence by no CP insertion. It is a conceptual diagram for demonstrating the conventional influence by no CP insertion. It is a wave form diagram for demonstrating the conventional influence on the noise electric power without CP insertion. It is a wave form diagram for demonstrating the conventional influence on the noise electric power without CP insertion.

Hereinafter, an embodiment of the present invention will be described with reference to the drawings.
FIG. 1 is a block diagram illustrating a schematic configuration of a wireless communication system including a receiver 2 including a transmission path estimator 23 (transmission path characteristic estimation apparatus) according to an embodiment of the present invention. In FIG. 1, a transmitter 100 does not include CP inserters 11a and 11b in the configuration of the transmitter 1 of FIG. In the transmitter 100, the time multiplexer 12 time-multiplexes transmission data and a transmission pilot signal without CP insertion. The time-multiplexed signal is wirelessly transmitted from the antenna 13. The transmission frame configuration of the transmission signal without CP is obtained by deleting the CP portion from the frame configuration of FIG. 6 described above, for example. The pilot signal is a known signal that is preliminarily matched with the receiver side.

In the receiver 2 shown in FIG. 1, only the transmission path estimator 23 is different from the conventional configuration of FIG. 5, and the other configurations are the same as the conventional configuration.
In the receiver 2, the CP remover 22 a performs CP removal processing on the received data of the signal received by the antenna 21, and the CP remover 22 b applies to the received pilot signal of the signal received by the antenna 21. A CP removal process is performed. Note that the CP removers 22a and 22b pass through the received signal transmitted without the CP without any processing.

  Next, the transmission path estimator 23 obtains a transmission path characteristic estimation value and a noise power estimation value from the received pilot signal after passing through the CP remover 22b. The MMSE frequency equalizer 24 uses the transmission channel characteristic estimation value and the noise power estimation value to equalize and output the received data after passing through the CP remover 22a in the frequency domain according to the above equation (1).

  Hereinafter, the transmission path estimator 23 (transmission path characteristic estimation apparatus) according to an embodiment of the present invention will be described in detail.

FIG. 2 is a block diagram showing a configuration of the transmission path estimator 23 according to the embodiment of the present invention.
In FIG. 2, the transmission path estimation unit 23 receives a received pilot signal p _r (n) having a sequence length N _p after passing through the CP remover 22b. With this input, first, the received pilot signal p _r (n) is input to the discrete Fourier transformer 231a by the switch SW1. Similarly to FIG. 7, the received pilot signal p _r (n) is subjected to discrete Fourier transform by the discrete Fourier transformer 231a, and a predetermined signal is obtained from the transformed pilot signal P _r (f) by the multiplier 234c. By multiplying, the frequency domain transmission line characteristic estimated value H _a (f) shown in the above equation (3) is obtained. Next, the channel characteristic estimation value H _a (f) is subjected to inverse discrete Fourier transform by the inverse discrete Fourier transformer 232 to obtain _a time domain channel characteristic estimation value h _a (n) after the conversion. This transmission path characteristic estimated value h _a (n) is input to the interference compensator 233 by the switch SW2.

The interference compensator 233 uses the transmission path characteristic estimation value h _a (n), the known pilot signal p _t (n), and the received pilot signal p _r (n) to receive the pilot when the CP is inserted. Create a pseudo signal. The known pilot signal p _t (n) is stored in advance in a memory (not shown) in the transmission path estimator 23. The received pilot signal p _r (n) is temporarily held in a memory (not shown) in the transmission path estimator 23.

3 and 4 are conceptual diagrams for explaining the operation of the interference compensator 233. FIG.
FIG. 3 shows a received pilot signal p _r (n) after CP removal when a CP is inserted on the transmission side. Here, h (n) is an actual transmission path characteristic value in the time domain. On the other hand, FIG. 4 shows a received pilot signal p _r (n) when no CP is inserted on the transmitting side. As shown in FIG. 4, when the CP is not inserted, an interference component is included in the portion from the head of the received pilot signal p _r (n) to the maximum delay time of the transmission path, and other received pilots There is no interference component in the signal. In view of this, the interference compensator 233 performs a cyclic convolution operation using the transmission path characteristic estimation value h _a (n) and the known pilot signal p _t (n) for the portion up to the maximum delay time of the transmission path. , A pseudo received pilot signal p _r ′ (n) when CP is inserted is created. This pseudo received pilot signal p _r ′ (n) is obtained by equation (7). As a result, a received pilot signal p _r ′ (n) having a small interference component is obtained.

However, N _delay is the maximum delay time of the transmission path and is a known value.

Next, returning to FIG. 2, the received pilot signal p _r ′ (n) output from the interference compensator 233 is input to the discrete Fourier transformer 231a by switching the switch SW1. The received pilot signal p _r ′ (n) is subjected to discrete Fourier transform by the discrete Fourier transformer 231a, and the transformed pilot signal P _r ′ (f) is multiplied by a predetermined signal by the multiplier 234c to thereby generate a frequency domain. The transmission path characteristic estimation value H _b (f) is obtained. Next, the transmission path characteristic estimation value H _b (f) is subjected to inverse discrete Fourier transform by the inverse discrete Fourier transformer 232 to obtain a time domain transmission path characteristic estimation value h _b (n) after the conversion. The transmission path characteristic estimated value h _b (n) is input to the multipliers 234a and 234b by switching the switch SW2.

In the multiplier 234a, similarly to FIG. 7, the transmission line characteristic estimated value h _b (n) is multiplied by the filter 235a to remove the noise component. Here, the filter 235a has a coefficient g _NE ′ (n) that extracts only the component within the maximum delay time N _delay of the transmission path. Next, the transmission path estimation value interpolator 236 interpolates the data value “0” with respect to the transmission path characteristic estimation value after the noise removal, and outputs a transmission path characteristic estimation value having the same length as the data length. Next, the discrete Fourier transformer 231b performs a discrete Fourier transform on the transmission path characteristic estimation value after data interpolation, and outputs a frequency domain transmission path characteristic estimation value H _a ′ (f). This transmission path characteristic estimated value H _a ′ (f) is expressed by equations (8) and (9).

As a result, the accuracy of the transmission path characteristic estimated value H _a ′ (f) is improved. Then, this channel characteristic estimated value H _a ′ (f) is input to the MMSE frequency equalizer 24 of FIG. 1 and used as the frequency domain channel characteristic estimated value H _a (f) in the above equation (1). Is done. This improves the frequency domain equalization accuracy when no CP is inserted in the pilot signal on the transmission side.

Further, in the multiplier 234b of FIG. 2, the filter 235b is multiplied to the transmission path characteristic estimated value h _b (n), as in FIG. Here, the filter 235b has a coefficient (1-g _NE ′ (n)) for extracting a component equal to or longer than the maximum delay time N _delay of the transmission path. Next, the noise power estimator 237 calculates and outputs _a noise power estimation value Na by integrating the output of the multiplier 234b (see equation (10)).

The noise power estimation value N _a is estimated using the transmission path characteristic estimation value h _b (n), but the transmission path used when the received pilot signal p _r ′ (n) is created. Since the interference component is included in the characteristic estimation value h _a (n), the influence may be manifested. Therefore, a memory 238 that holds the past noise power estimation value N _a is provided, and the selection unit 239 compares the current noise power estimation value N _a with the noise power estimation value N _MEM in the memory 238, _whichever is smaller. The noise power estimation value N _min is output (see equation (11)). The memory 238 stores the estimated noise power value N _min . Thereby, a noise power estimated value with a smaller interference component can be obtained from the past noise power estimated value.

Then, the noise power estimate _{N min} is input to the MMSE frequency equalizer 24 of FIG. 1, is used as the noise power estimate _{N a} in the above equation (1). This further improves the frequency domain equalization accuracy when no CP is inserted in the pilot signal on the transmission side.

The memory 238 may hold _a plurality of past noise power estimation values N _a (for example, the latest 10 values), and select and output an optimum value from the plurality of stored values.

  In addition, the noise power estimator 237 estimates the noise power spectral density in the frequency domain, and the memory 238 holds the past noise power spectral density estimation value. You may make it output.

Further, the noise power estimated value or the noise power spectral density estimated value may be calculated using the pseudo received pilot signal p _r ′ (n).

  In each of the above-described embodiments, the transmission path estimator 23 shown in FIG. 2 may be realized by dedicated hardware, and the transmission path estimator 23 includes a memory and a DSP (digital signal). The processor may be implemented by loading a program for realizing the function of the transmission path estimator 23 into the memory and executing the program.

Further, a program for realizing each function performed by the transmission path estimator 23 shown in FIG. 2 is recorded on a computer-readable recording medium, and the program recorded on the recording medium is read into a computer system and executed. Thus, the transmission path characteristic estimation process or the noise power estimation process may be performed. Here, the “computer system” may include an OS and hardware such as peripheral devices.
Further, the “computer system” includes a homepage providing environment (or display environment) if a WWW system is used.
The “computer-readable recording medium” means a flexible disk, a magneto-optical disk, a ROM, a writable nonvolatile memory such as a flash memory, a portable medium such as a CD-ROM, a hard disk built in a computer system, etc. This is a storage device.

Further, the “computer-readable recording medium” refers to a volatile memory (for example, DRAM (Dynamic DRAM)) in a computer system that becomes a server or a client when a program is transmitted via a network such as the Internet or a communication line such as a telephone line. Random Access Memory)), etc., which hold programs for a certain period of time.
The program may be transmitted from a computer system storing the program in a storage device or the like to another computer system via a transmission medium or by a transmission wave in the transmission medium. Here, the “transmission medium” for transmitting the program refers to a medium having a function of transmitting information, such as a network (communication network) such as the Internet or a communication line (communication line) such as a telephone line.
The program may be for realizing a part of the functions described above. Furthermore, what can implement | achieve the function mentioned above in combination with the program already recorded on the computer system, and what is called a difference file (difference program) may be sufficient.

The embodiment of the present invention has been described in detail with reference to the drawings. However, the specific configuration is not limited to this embodiment, and includes design changes and the like within a scope not departing from the gist of the present invention.
For example, a configuration for creating a pseudo received pilot signal when a CP is inserted and estimating transmission path characteristics again and past noise power estimation information (noise power estimation value or noise power spectral density estimation value) are retained. The configuration for outputting the optimum noise power estimation information may be provided independently.

Further, the first-stage transmission line characteristic estimation value h _a (n) input to the interference compensator 233 may be obtained directly in the time domain. Similarly, the second-stage channel characteristic estimation value h _b (n) estimated from the pseudo received pilot signal p _r ′ (n) may be calculated in the time domain.

  In addition, various algorithms can be used for deriving the first and second stage channel characteristic estimation values, and the present invention is not limited to the channel characteristic estimation value deriving algorithm, and is widely applied. It is something that can be done.

  In addition, by applying the present invention to the received data, it is possible to improve the reception accuracy when no CP is inserted in the data on the transmission side. Generally, a pilot signal and data are transmitted in pairs, for example, in the order of data following the pilot signal as shown in FIG. 6 (hereinafter, a pair of pilot signal and data is referred to as a frame). As a result, data is sandwiched between the pilot signal of the frame and the pilot signal of the next frame. Here, for two pilot signals sandwiching data, the front pilot signal is “pilot A” and the rear pilot signal is “pilot B”. Then, the section from pilot A to data and pilot B is regarded as one equalization section, and the reception data when the CP is inserted is created in a pseudo manner.

Specifically, a reception pilot A in the case where a CP is inserted is created in a pseudo manner based on known signals for the maximum delay time N _delay at the end of pilot B and the first-stage transmission path characteristic estimation value. Next, discrete Fourier transform is performed from the head of the pseudo reception pilot A to the actual reception data and the actual reception pilot B. Thereby, when the CP is not inserted into the data, it is possible to obtain the frequency characteristics of the received data having a smaller interference component. Alternatively, it is possible to obtain reception data with a smaller interference component when no CP is inserted into the data by time equalizing the pseudo reception pilot A and the actual reception data and reception pilot B as one block. It becomes.

  Further, the present invention can be applied to various wireless communication systems such as a wireless communication system using multicarrier transmission as well as a wireless communication system using single carrier transmission.

DESCRIPTION OF SYMBOLS 2 ... Receiver, 21 ... Antenna, 22a, 22b ... CP remover, 23 ... Transmission path estimator (transmission path characteristic estimation device), 24 ... MMSE frequency equalizer, 231a, 231b ... Discrete Fourier transformer, 232 ... Inverse discrete Fourier transformer, 233 ... interference compensator, 234a-c ... multiplier, 235a, 235b ... filter, 236 ... transmission path value interpolator, 237 ... noise power estimator, 238 ... memory, 239 ... selector, SW1, SW2 ... switch.

Claims (2)

In a receiver in a wireless communication system in which a known signal and an unknown signal transmitted subsequently to the known signal are arranged in one frame and the frame is continuously transmitted from the transmitter.
Transmission path characteristic estimated value calculating means for calculating a transmission path characteristic estimated value based on the known signal and the transmission path characteristic estimation input signal;
A transmission path characteristic estimated value calculated by the transmission path characteristic estimated value calculation means using a reception known signal of the specific frame received by the receiver as the transmission path characteristic estimation input signal, and a known signal of the specific frame And the known signal of the frame subsequent to the specific frame are cyclically convolved with the length of the maximum delay time of the transmission path, and the length of the maximum delay time of the transmission path is calculated from the beginning of the received known signal of the specific frame. By replacing a part with the cyclic convolution operation result, a pseudo reception signal creating means for creating a pseudo reception signal in a reception section from the reception known signal of the specific frame to the reception known signal of a frame subsequent to the specific frame;
An equalization means for equalizing the pseudo reception signal in the frequency domain or the time domain, with a reception interval from the reception known signal of the specific frame to a reception known signal of a frame subsequent to the specific frame as one equalization interval; ,
A receiver comprising: A computer program for performing reception processing in a wireless communication system in which a known signal and an unknown signal transmitted subsequently to the known signal are arranged in one frame and the frame is continuously transmitted from a transmitter,
A function of calculating a channel characteristic estimation value based on the known signal and the channel characteristic estimation input signal;
A channel characteristic estimation value calculated by the transmission channel characteristic estimation value calculation function using a known reception signal of the specific frame received by the receiver as the transmission channel characteristic estimation input signal, and a known signal of the specific frame And the known signal of the frame subsequent to the specific frame are cyclically convolved with the length of the maximum delay time of the transmission path, and the length of the maximum delay time of the transmission path is calculated from the beginning of the received known signal of the specific frame. A function of creating a pseudo reception signal in a reception section from a reception known signal of the specific frame to a reception known signal of a frame subsequent to the specific frame by replacing a part with the cyclic convolution calculation result;
A function of equalizing the pseudo received signal in the frequency domain or the time domain, with a reception section from the reception known signal of the specific frame to a reception known signal of a frame subsequent to the specific frame as one equalization section;
A computer program for causing a computer to realize the above.

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