JP2009268180A - Control apparatus for power conversion circuit and power conversion control system - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To solve the problem of difficulty in achieving both ensuring of a period for short-circuiting upper and lower arms of an inverter IV and suppression of common mode noise. <P>SOLUTION: The inverter IV is operated to apply a command voltage to a motor generator 10. In this case, dual phase modulation processing for shifting the command voltage to a high potential side is executed, and then, an operation signal of the inverter IV is generated based on comparison in magnitude of a carrier. The short circuit processing for short-circuiting the upper and lower arms is executed in a period when a zero vector V7 is indicated by the operation signal thus generated, thereby stepping up an output voltage of an impedance network IN. <P>COPYRIGHT: (C)2010,JPO&INPIT

Description

  The present invention relates to a switching element on a high potential side and a switching element on a low potential side, which are connected between a multiphase rotating machine and a power feeding means and connect the multiphase rotating machine to a high potential side and a low potential side, respectively. A control device for a power conversion circuit that is applied to a power conversion circuit including a series connection body for each phase of the multiphase rotating machine, and that performs a process of turning on the switching element so as to put the series connection body in a short-circuit state, And a power conversion control system including the same.

  For example, when power is supplied to a three-phase motor, a three-phase inverter that converts a DC voltage into an AC voltage is usually used. Thereby, an alternating voltage can be applied to each phase of the three-phase motor. The maximum value of the output voltage of this inverter is limited by the voltage of the DC power supply. For this reason, it is also well known that a booster circuit is provided between the DC power supply and the inverter. However, when a booster circuit is provided, a switching element of the booster circuit, a driver for turning on / off the switching element, and the like are provided, and an increase in the number of components cannot be ignored.

  Therefore, conventionally, as seen in Patent Document 1 below, for example, it has been proposed to provide an impedance network between the inverter and the DC power supply. According to this, by short-circuiting the upper and lower arms of the inverter, it is possible to boost the voltage of the DC power supply using the inductor constituting the impedance network. Therefore, the boosting operation can be performed only by operating the switching element of the inverter, and an increase in the number of parts can be suppressed.

However, when the process of short-circuiting the upper and lower arms is performed, the output voltage of the inverter becomes zero, so there is a possibility that the output voltage of the inverter cannot be used as the command voltage. On the other hand, the following Non-Patent Document 1 proposes that when the operation state of the inverter for setting the command voltage becomes a zero vector, the operation state of the inverter is changed to short-circuit the upper and lower arms. ing.
US Pat. No. 7,130,205 Z-Source Inverter for Fuel Cell Vehicles submitted to Oak Ridge National Laboratory Engineering Science and Technology Division Power Electrics Electric Machinery Research Center August 31 2005

  By the way, there are two types of zero vectors, one that short-circuits the upper arm and one that short-circuits the lower arm. Here, in the period in which the operation state of the inverter for controlling to the command voltage is a voltage vector for short-circuiting the lower arm, when performing the process of short-circuiting the upper and lower arms by changing the operation state of the inverter, three phases The neutral point voltage of the motor may fluctuate greatly. If the neutral point voltage fluctuates greatly, common mode noise may increase. On the other hand, the short-circuiting process may be performed only in a period in which the operation state of the inverter for controlling to the command voltage becomes a voltage vector for short-circuiting the upper arm. In this case, the short-circuiting process can be executed. Due to the shortening of the period, the output voltage of the impedance network is limited.

  The present invention has been made to solve the above-described problems, and an object of the present invention is to provide a series connection body of a pair of switching elements for connecting each phase of a multiphase rotating machine to each of a high potential side and a low potential side. An object of the present invention is to provide a power conversion circuit control device and a power conversion control system capable of suppressing the occurrence of common mode noise while ensuring a sufficient period for performing the process of short-circuiting.

  Hereinafter, means for solving the above-described problems and the operation and effects thereof will be described.

  According to the first aspect of the present invention, there is provided a high-potential-side switching element and a low-potential side that are connected between the multi-phase rotating machine and the power feeding means, and connect the multi-phase rotating machine to the high-potential side and the low-potential side. The power conversion circuit is applied to a power conversion circuit provided with a series connection body of switching elements for each phase of the multiphase rotating machine, and performs a process of turning on the switching element so that the series connection body is in a short-circuit state. In the control device, setting means for setting an operation state of the switching element so that a period in which all phases of the multiphase rotating machine are connected to a low potential side is set to zero, and the multiphase rotation by the setting means In a situation where an operation state in which all phases of the machine are connected to the high potential side is set, a process of changing the actual operation state of the switching element from the operation state by the setting means to the short circuit state Characterized in that it comprises a Cormorant short-circuiting means.

  In the above invention, the operation state of the switching element is set by the setting means while avoiding the operation state in which all phases of the multiphase rotating machine are connected to the low potential side. For this reason, in the setting means, a period in which the output voltage from the serial connection body to the multiphase rotating machine becomes zero is ensured by a period in which the operation state is established in which all phases of the multiphase rotating machine are connected to the high potential side. It becomes. For this reason, the operation state of the switching element set by the setting means sufficiently secures a period during which the operation state in which all phases of the multiphase rotating machine are connected to the high potential side is obtained. And by performing the process of setting the short circuit state during this period, the case where all the phases of the multi-phase rotating machine are connected to the high potential side as set by the setting means and the case where the process of setting the short circuit state are performed There is no change in the neutral point voltage of the phase rotating machine. For this reason, generation | occurrence | production of common mode noise can be suppressed, ensuring the period which performs the process made into a short circuit state fully.

  The setting means preferably performs the setting so as to control the voltage applied to the multiphase rotating machine to a command voltage. Further, the setting means preferably sets the operation state so that switching of the switching state of the switching element is performed one phase at a time.

  According to a second aspect of the present invention, in the first aspect of the invention, the power conversion circuit boosts the voltage of the power feeding means by setting the series connection body in a short-circuited state.

  In the above invention, by providing the setting means and the short-circuit processing means, fluctuations in the neutral point voltage of the rotating machine can be suitably suppressed during the boosting operation.

  It is desirable that the power conversion circuit is “a circuit that includes an inductor and boosts the voltage of the power feeding means by utilizing a phenomenon in which a counter electromotive force is generated in the inductor by releasing the short-circuit state”.

  The invention according to claim 3 is the invention according to claim 2, wherein the power conversion circuit includes an inductor connected between the switching element on the high potential side and a positive terminal of the power feeding means, and the switching element on the low potential side. And a pair of inductors connected between the negative terminals of the power supply means, and each of the pair of inductors is connected between the inductor and the switching element and between the other inductor and the power supply means. And an impedance network including a capacitor.

  In the above-described invention, by providing the pair of inductors and capacitors, the step-up operation can be appropriately performed by the processing for setting the short circuit state.

  According to a fourth aspect of the present invention, in the invention according to any one of the first to third aspects, the setting means maintains a relative magnitude relationship between the command voltages for each phase of the multiphase rotating machine. The shift means for shifting the maximum command voltage to the maximum value that can be realized by the voltage applied to the series connection body, and based on the magnitude relationship between the command voltage after the shift and the carrier The setting is performed.

  According to the above invention, when the output voltage to the multi-phase rotating machine is used as the command voltage, the period during which all the phases of the multi-phase rotating machine are required to be zero is set to the high potential. It can be a period connected to the side.

  According to a fifth aspect of the invention, in the fourth aspect of the invention, the carrier has a triangular wave shape.

  In the above invention, it is possible to avoid switching of switching elements in a plurality of phases at the same time, so that common mode noise can be further reduced.

  A sixth aspect of the present invention is a power conversion control system comprising the power conversion circuit control device according to any one of the first to fifth aspects and the power conversion circuit.

  In the above invention, since the setting means and the short-circuit processing means are provided, it is possible to realize a power conversion control system capable of suppressing common mode noise by control. For this reason, it is possible to realize a power conversion system that suppresses noise countermeasure requirements for hardware, and it is easy to realize a system with excellent cost performance.

  Hereinafter, an embodiment in which a power conversion circuit control device and a power conversion control system according to the present invention are applied to a hybrid vehicle will be described with reference to the drawings.

  FIG. 1 shows the system configuration of this embodiment. The illustrated motor generator 10 is a three-phase motor / generator. The motor generator 10 is connected to a high voltage battery 12 serving as a DC power source via a power conversion circuit including an inverter IV and an impedance network IN. The high voltage battery 12 is a secondary battery that applies a predetermined high voltage (for example, “288 V”).

  The inverter IV includes a serial connection body of switching elements Sup and Sun, a serial connection body of switching elements Svp and Svn, and a parallel connection body of a serial connection body of switching elements Swp and Swn. Here, the connection point of the switching element Sup and the switching element Sun is connected to the U phase of the motor generator 10, and the connection point of the switching element Svp and the switching element Svn is connected to the V phase of the motor generator 10. A connection point between the element Swp and the switching element Swn is connected to the W phase of the motor generator 10. Note that these switching elements Sup, Sun, Svp, Svn, Swp, Swn are constituted by insulated gate bipolar transistors (IGBTs), which are diodes Dup, Dun, Dvp, Dvn, Dwp, Dwn is connected.

  The impedance network IN includes an inductor 20 connected between the positive terminal side of the high voltage battery 12 and the high potential side input terminal of the inverter IV, and the negative terminal side of the high voltage battery 12 and the low potential side input terminal of the inverter IV. And an inductor 22 connected therebetween. Further, the impedance network IN includes a capacitor 24 that connects between the input terminal on the high potential side of the inverter IV and the inductor 20, and between the negative terminal and the inductor 22 of the high voltage battery 12, and between the positive terminal of the high voltage battery 12 and the inductor 20. A capacitor 26 that connects the input terminal on the low potential side of the inverter IV and the inductor 22 is provided.

  Between the positive terminal of the high-voltage battery 12 and the inductor 20, a diode 30 as a rectifier for backflow prevention and a switching element 32 for regeneration control are connected. In addition, a current sensor 34 that detects a U-phase current and a current sensor 36 that detects a V-phase current are provided on the electrical path between the inverter IV and the motor generator 10. In addition, a voltage sensor 38 that detects a voltage between the pair of input terminals of the inverter IV (a pair of output terminals of the impedance network IN) is provided.

  The outputs of the sensors in the high voltage system such as the current sensors 34 and 36 and the voltage sensor 38 are taken into the microcomputer (microcomputer 42) via the interface 40. The microcomputer 42 operates the switching elements Sup, Sun, Svp, Svn, Swp, Swn, and the switching element 32 based on the detection values of various sensors in the high-voltage system, the torque requested by the user, and the like. In other words, the inverter IV and the switching element 32 are operated. In particular, the microcomputer 42 operates the inverter IV by PWM processing so that the voltage applied to the motor generator 10 is a command voltage. Specifically, a command voltage is set as an operation amount for feedback-controlling the current flowing through motor generator 10 (detected values of current sensors 34 and 36) to a command current, and the operation state of the inverter is set based on this. Here, as a method for setting the command voltage, a well-known vector control may be used.

  Further, during this operation, the switching elements of both the upper arm and the lower arm are turned on, so that the series connection body of the switching elements Sup and Sun, the series connection body of the switching elements Svp and Svn, and the switching element Swp , Swn series connection body, a process of making a short circuit state (shoot-through: hereinafter short circuit process) is performed. This is a process for boosting the output voltage of the inverter IV. That is, the output voltage of the impedance network IN is made higher than the voltage of the high-voltage battery 12 by utilizing the phenomenon that a counter electromotive force is generated in the inductors 20 and 22 by canceling the short-circuit process after the short-circuit process is performed. Can do. Note that, in Patent Document 1, the switching period T and the short-circuit processing time of the series connection body are provided under the condition that the inductances of the inductors 20 and 22 are equal to each other and the capacitances of the capacitors 24 and 26 are equal to each other. There is an explanation that the output voltage is boosted to “Vo · T / (T−T0)” using the voltage Vo of the high voltage battery 12 at T0. Further, it is described that the AC voltage applied to the motor generator 10 using the modulation factor M is “M · Vo · T / {2 · (T−T0)}”.

  By performing the short-circuit process, the output voltage of the impedance network IN can be boosted, and as a result, the output voltage of the inverter IV can be boosted. However, the output voltage of the inverter IV becomes zero during the short circuit process. For this reason, even if the switching operation is performed according to the PWM process so that the voltage applied to the motor generator 10 is the command voltage, the actual output voltage of the inverter IV may not become the command voltage due to the short circuit process. Such a situation can be avoided by performing a short-circuit process in the zero vector period. The zero vector period is a zero vector V7 period in which all the switching elements Sup, Svp, Swp of the upper arm are turned on, and a zero vector V0 period in which all of the switching elements Sun, Svn, Swn of the lower arm are turned on. That's it. In other words, it is a period of two vectors out of eight voltage vectors (FIG. 2) expressing that one of the upper arm and the lower arm is turned on for each phase. That is, in the zero vector V0 and V7 periods, no voltage is output from the inverter IV. Therefore, even if the short circuit process is performed using this period, the voltage applied to the motor generator 10 does not change.

  FIG. 3 schematically shows a mode of PWM control based on the magnitude comparison between the command voltage and the carrier. Specifically, FIG. 3A shows the transition of the carrier and the three-phase command voltages Vur, Vvr, and Vwr, and FIGS. 3B to 3G show the switching elements Sup, Sun, Svp, The transition of the operation signal of Svn, Swp, Swn is shown, and the transition of the voltage vector is shown in FIG. However, in FIG. 3, the carrier cycle is shown to be extended for easy understanding of the voltage vector period.

  As shown in the figure, since the voltage vector indicating the operation state of the inverter IV for controlling the command voltages Vur, Vvr, and Vwr can be zero vectors V0 and V7, the short-circuit process can be executed during this period. However, when the short-circuit process is performed during the zero vector V0 period in which all phases of the motor generator 10 are connected to the terminals on the low potential side of the impedance network IN, the neutral point voltage of the motor generator 10 varies greatly. To do. This is because the neutral point voltage of the zero vector V0 period becomes the voltage VL on the low potential side of the impedance network IN, while the neutral point voltage is on the high potential side of the impedance network IN when performing the short circuit process. This is due to the voltage VH. For this reason, there is a possibility that common mode noise becomes conspicuous due to large fluctuations in the neutral point voltage.

  On the other hand, in the zero vector V7 period, the neutral point voltage becomes the voltage VH on the high potential side of the impedance network IN. However, if the short circuit process is performed only during the zero vector V7 period, the output voltage of the impedance network IN cannot be sufficiently boosted with respect to the voltage of the high voltage battery 12. For example, as described above, when the capacitances of the capacitors 24 and 26 are equal to each other and the inductances of the inductors 24 and 26 are equal to each other, the output voltage of the impedance network IN is inversely proportional to the difference of the short-circuit processing time T0 with respect to the switching period T. . For this reason, as the ratio of the short circuit processing time T0 to the switching period T becomes shorter, the output voltage of the impedance network IN can be suppressed lower.

  Therefore, in the present embodiment, when performing PWM processing, two-phase modulation processing is performed. FIG. 4 shows an aspect of the two-phase modulation process. Specifically, FIG. 4A shows the transition of the command voltages Vur, Vvr, and Vwr, and FIG. 4B shows the correction amounts (offset voltages) of the command voltages Vur, Vvr, and Vwr for two-phase modulation. FIG. 4C shows the transition of the command voltages Vur, Vvr, and Vwr after the two-phase modulation.

  Here, the two-phase modulation processing is the maximum value that can realize the maximum of these by the output voltage of the impedance network IN while maintaining the relative magnitude relationship between the command voltages Vur, Vvr, and Vwr for the motor generator 10. This is a process of shifting to “Vdc / 2”. This is because the difference between the maximum value of the command voltages Vur, Vvr, and Vwr for the motor generator 10 and the maximum value “Vdc / 2” that can be realized by the output voltage of the impedance network IN is used as an offset voltage, and the command voltages Vur, Vvr. , Vwr can be realized by offset correction. According to this, at least one of the command voltages Vur, Vvr, Vwr is always the maximum value “Vdc / 2”. In addition, since all the minimum values of the command voltages Vur, Vvr, Vwr are raised, the “shoot-through possible area” shown in FIG. 4C is expanded. This region is a region in which the zero vector V7 can be realized because the command voltage of all phases is larger than that of the carrier.

  FIG. 5 shows the procedure of the two-phase modulation process. This process is repeatedly executed by the microcomputer 42, for example, at a predetermined cycle.

  In this series of processing, first, in step S10, command voltages Vur, Vvr, and Vwr are acquired. In the subsequent step S12, the input voltage (power supply voltage Vdc) of the inverter IV detected by the voltage sensor 38 is acquired. In the subsequent step S14, the duty signals Du, Dv, Dw are calculated by normalizing the command voltages Vur, Vvr, Vwr with the power supply voltage Vdc. This is performed by dividing each of the command voltages Vur, Vvr, and Vwr by “½” of the power supply voltage Vdc. In the subsequent step S16, an offset amount Δ of the duty signals Du, Dv, Dw is calculated. This is performed by subtracting the maximum value of the duty signals Du, Dv, Dw from “1”. In step S18, the duty signals Du, Dv, Dw are corrected by adding an offset amount Δ to each of the duty signals Du, Dv, Dw. In addition, when the process of step S18 is completed, this series of processes is once complete | finished.

  FIG. 6 shows the effect of the two-phase modulation process. Specifically, FIGS. 2 (a1) and 2 (b1) show a case where two-phase modulation is not performed, and FIGS. 2 (a2) and 2 (b2) show a case where two-phase modulation is performed. Here, FIGS. 2 (a1) and 2 (a2) all show the duty signals Du, Dv, Dw and the carrier, and FIGS. 2 (b1) and 2 (b2) are both voltage vectors. Is shown. Here, the case where the update cycle of the duty signals Du, Dv, Dw (the update cycle of the command voltages Vur, Vvr, Vwr) is made coincident with the carrier cycle and the update timing is set to the valley of the carrier is illustrated. Yes.

  As illustrated, both periods of the zero vectors V0 and V7 when the two-phase modulation process is not performed become the zero vector period V7 by performing the two-phase modulation process. For this reason, when two-phase modulation processing is performed and the zero vector V7 period is set as an execution permission period of the short-circuit processing, execution of the short-circuit processing is permitted without performing the two-phase modulation processing and the zero vector V0 and V7 periods. The execution permission period can be matched with the period.

  FIG. 7 schematically shows the transition of the voltage vector after the two-phase modulation processing. 7A to 7H correspond to the previous FIGS. 3A to 3H. FIG. 7I illustrates a short-circuit processing period. As shown in the figure, by performing the two-phase modulation process, the zero vector V0 period can be eliminated and the zero vector V7 period can be expanded, so that the short circuit process can be sufficiently performed.

  FIG. 8A illustrates the neutral point voltage fluctuation according to the present embodiment, and FIG. 8B illustrates the neutral point voltage fluctuation when the two-phase modulation processing is not performed. In FIG. 8, the power supply voltage Vdc is “450 V”.

  As shown in the figure, when performing the two-phase modulation process, when the voltage vector indicating the operation state of the inverter IV shifts from the zero vector V7 to the voltage vectors V2, V4, V6, the voltage vectors V2, V4, When shifting from V6 to voltage vectors V1, V3, V5, when shifting from voltage vectors V1, V3, V5 to voltage vectors V2, V4, V6, when shifting from voltage vectors V2, V4, V6 to zero vector V7 The neutral point voltage changes by “Vdc / 3”. The neutral point voltage becomes the maximum value during the zero vector V7 period. And even if short circuit process ST is performed in the zero vector V7 period, a neutral point voltage does not change. For this reason, the fluctuation range of the neutral point voltage once can be set to about “Vdc / 3”.

  On the other hand, when the two-phase modulation process is not executed, the neutral point voltage increases by “Vdc” when the short-circuit process ST is executed during the zero vector V0 period in which the neutral point voltage becomes the minimum value. For this reason, the single fluctuation range of the neutral point voltage increases. In particular, according to the PWM processing that sets the operation state of the inverter IV based on the magnitude relationship between the command voltages Vur, Vvr, and Vwr and the triangular wave-shaped carrier as in the present embodiment, one operation state of the switching element is set. In switching, only the switching state of one phase is switched. Therefore, the fluctuation range of one neutral point voltage can be originally limited to about “Vdc / 3”. However, by incorporating a short-circuit process instead of the operation state by the PWM process, the single fluctuation range of the neutral point voltage increases to about three times. For this reason, common mode noise tends to increase.

  In FIG. 8, the neutral point voltage in the zero vector V0 period is not “0V”, but this is because the potential of the terminal on the low potential side of the impedance network IN is lower than the ground potential.

  According to the embodiment described in detail above, the following effects can be obtained.

  (1) The operation state of the inverter IV is set by the PWM process using the two-phase modulation process, and the short-circuit process is executed in the zero vector V7 period set thereby. Here, by using the two-phase modulation processing, when the output voltage to the motor generator 10 is used as the command voltage, the period in which all phases of the motor generator 10 are required to be zero in the output voltage to the motor generator 10 is required. It can be a period connected to the high potential side. And by performing a short circuit process in this period, generation | occurrence | production of common mode noise can be suppressed, ensuring the period which performs the process made into a short circuit state fully.

  (2) A triangular wave shaped carrier was used. As a result, it is possible to avoid switching of switching elements in a plurality of phases at the same time, so that common mode noise can be further reduced.

(Other embodiments)
The above embodiment may be modified as follows.

  In the above embodiment, the carrier has a triangular wave shape in which the gradual increase speed and the gradual decrease speed thereof are equal to each other, but the present invention is not limited to this. For example, a saw wave may be used. However, when a sawtooth wave is used, a phenomenon occurs in which switching states are switched in a plurality of phases at the same time. From the viewpoint of reducing common mode noise, a gradual wave shape in which both the gradual increase speed and the gradual decrease speed are equal to or less than a specified value is used. It is desirable.

  In the above-described embodiment, the update period of the command voltages Vur, Vvr, and Vwr is one carrier period and the update timing is a carrier valley. However, the present invention is not limited to this. For example, the update cycle may be sufficiently shorter than the carrier cycle. Also, the update timing may be a carrier mountain.

  In the above embodiment, the two-phase modulation processing is performed using the detection value of the voltage sensor 38 as the input voltage of the inverter IV (the output voltage of the impedance network IN), but the present invention is not limited to this. For example, the output voltage of the impedance network IN may be estimated based on the short circuit processing time, and the two-phase modulation process may be executed using this estimated value.

  The impedance network IN is not limited to that exemplified in the above embodiment. For example, FIG. As described in 3.4, a configuration in which several diodes and capacitors are additionally connected to the one shown in FIG. 1 may be used.

  The process for applying the command voltage to the rotating machine is not limited to the PWM process that modulates the carrier based on the command voltage. For example, so-called space vector modulation processing exemplified in JP-A-10-4696 may be used. Even in this case, it is considered that the zero vector V7 period can be expanded by setting to avoid the appearance of the zero vector V0. As a result, the short-circuit processing period is reduced while suppressing the common mode noise. It can be secured sufficiently.

  -The multi-phase rotating machine is not limited to a three-phase rotating machine. For example, a five-phase rotating machine may be used.

  -You may apply this invention not only to a hybrid vehicle but to the power converter circuit of an electric vehicle, for example. Further, the power conversion circuit is not limited to one in which one rotating machine is connected, and a plurality of power conversion circuits may be connected. The power supply means is not limited to a secondary battery, and may be a primary battery, for example.

The system block diagram concerning one Embodiment. The figure which shows a voltage vector. The time chart which shows typically the transition example of the voltage vector in a three-phase modulation system. The time chart which shows the method of a two-phase modulation process. The flowchart which shows the procedure of a two-phase modulation process. The time chart which shows the effect of a two-phase modulation process. The time chart which shows the effect of a two-phase modulation process. The time chart which shows the effect of this embodiment.

Explanation of symbols

  DESCRIPTION OF SYMBOLS 10 ... Motor generator, 12 ... High voltage battery (one Embodiment of electric power feeding means), IV ... Inverter, IN ... Impedance network, Sup, Sun, Svp, Svn, Swp, Swn ... Switching element.

Claims (6)

A series connection body of a switching element on the high potential side and a switching element on the low potential side connected between the multiphase rotating machine and the power supply means and connecting the multiphase rotating machine to each of the high potential side and the low potential side. In a control device for a power conversion circuit that is applied to a power conversion circuit provided for each phase of the multiphase rotating machine and performs a process of turning on the switching element so as to put the series connection body in a short-circuit state.
Setting means for setting an operation state of the switching element so that a period in which all phases of the multiphase rotating machine are connected to a low potential side is set to zero;
Under a situation where an operating state is set in which all the phases of the multi-phase rotating machine are connected to the high potential side by the setting means, the actual operating state of the switching element is changed from the operating state by the setting means, and the short circuit A control device for a power conversion circuit, comprising: short-circuit processing means for performing processing for setting a state.   2. The control device for a power conversion circuit according to claim 1, wherein the power conversion circuit boosts the voltage of the power feeding unit by setting the series connection body in a short-circuit state. 3.   The power conversion circuit includes a pair of an inductor connected between the switching element on the high potential side and the positive terminal of the power feeding means, and an inductor connected between the switching element on the low potential side and the negative terminal of the power feeding means. Each of the pair of inductors, and an impedance network configured to include a capacitor connected between the inductor and the switching element and between the other inductor and the power feeding means. The control apparatus for a power conversion circuit according to claim 2.   The setting means is a maximum that can be realized by the applied voltage to the series connection body while maintaining the relative magnitude relationship between the command voltages for each phase of the multiphase rotating machine. The shift means for shifting to a value is provided, and the setting is performed based on the magnitude relationship between the command voltage after the shift and the carrier. Power conversion circuit control device.   5. The control apparatus for a power conversion circuit according to claim 4, wherein the carrier has a triangular wave shape. A control device for a power conversion circuit according to any one of claims 1 to 5,
A power conversion control system comprising the power conversion circuit.

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