JP2009257807A - Physical quantity measuring device - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a physical quantity measuring device realizing a stable oscillation of an oscillator, improvement of accuracy in measuring a physical quantity, and improvement of yield of the oscillator. <P>SOLUTION: A physical quantity measuring device measures a physical quantity based on an output signal of an oscillator which oscillates according to electrostatic attraction force working between the oscillator on which the physical quantity to be measured acts and a first fixed electrode to which a bias voltage is applied, and comprises a second fixed electrode provided at a predetermined spacing to the first fixed electrode, and a driving part for driving the first fixed electrode in accordance with a first driving signal generated based on the output signal of the oscillator and for driving the second fixed electrode in accordance with a second driving signal which is a reverse phase to the first driving signal. <P>COPYRIGHT: (C)2010,JPO&amp;INPIT

Description

  The present invention relates to a physical quantity measuring device, and more particularly to improving measurement accuracy.

  A pressure measuring device that measures the pressure (physical quantity) of a fluid to be measured using a vibration sensor is generally known. As a method of vibrating the vibration sensor, there is one that vibrates according to a change in electrostatic attraction force acting between the vibration sensor and the electrode. Such a pressure measuring device will be described with reference to FIG. 4 showing a configuration diagram of the physical quantity measuring device 90.

  4, the physical quantity measuring device 90 includes a fixed electrode 10, a vibrator 11, a reference vibrator 12, current / voltage conversion units 20 and 21, a differential amplification unit 22, and a drive unit 30. The vibrator 11 and the reference vibrator 12 arranged on the left and right are disposed to face the fixed electrode 10 with a distance DISB.

  The vibrator 11 has a natural frequency determined by its shape (for example, the shape of a beam), and a self-excited circuit that vibrates the vibrator 11 at the natural frequency is formed. That is, the fixed electrode 10 to which the bias voltage Vb is applied, the electrostatic attraction force Fc acting between the fixed electrode 10 and the vibrator 11, the vibrator 11, the current / voltage conversion unit 20, the differential amplification unit 22, and the drive unit 30 and the feedback of the drive signal KB to the fixed electrode 10 forms a self-excited circuit (positive feedback loop).

  The vibration operation (self-excited vibration operation) of the vibrator 11 will be described in detail. A bias voltage Vb is applied between the fixed electrode 10 and the vibrator 11 and between the fixed electrode 10 and the reference vibrator 12 via a resistor.

  The fixed electrode 10 is driven by a drive signal KB. Note that the frequency of the drive signal KB matches the natural frequency of the vibrator 11. Since the voltage applied to the fixed electrode 10 is changed by the drive signal KB, the vibrator 11 vibrates at the natural frequency according to the change in the electrostatic attractive force Fc acting between the fixed electrode 10 and the vibrator 11. . At this time, the electrostatic current SB flows from the fixed electrode 10 to the vibrator 11 via the capacitance formed between the fixed electrode 10 and the vibrator 11. The electrostatic current SB is a current obtained by superimposing the noise current NA on the current in phase with the drive signal KB. The electrostatic current SB is output from the vibrator 11 and converted into a voltage by the current / voltage conversion unit 20.

  On the other hand, the natural frequency of the reference vibrator 12 and the natural frequency of the vibrator 11 are different. Therefore, even if the voltage applied to the fixed electrode 10 changes at the natural frequency of the vibrator 11, the reference vibrator 12 hardly vibrates, and the noise current NB having the same amplitude and the same phase as the noise current NA The current is output from the child 12 and converted into a voltage by the current / voltage converter 21.

  Since the differential amplifier 22 performs differential amplification of the output voltages of the current / voltage converters 20 and 21, the components of the noise currents NA and NB are canceled out and the natural frequency component of the vibrator 11 is output. For this reason, the frequency of the physical quantity output signal Po that is the output of the differential amplifier 22 matches the natural frequency of the vibrator 11.

  The physical quantity output signal Po is input to an auto gain control unit (hereinafter referred to as “AGC unit”) 31 and also to an AC / DC conversion unit 32. The AC / DC converter 32 converts the DC voltage to the amplitude of the physical quantity output signal Po, and outputs the DC voltage to the error amplifier 33. The error amplifier 33 amplifies the error between the DC voltage of the AC / DC converter 32 and the set voltage Vs (DC) and outputs the amplified error to the AGC unit 31. The AGC unit 31 outputs a drive signal KB (alternating current) in which the amplitude of the physical quantity output signal Po is matched with the set voltage Vs to the fixed electrode 10.

  In addition, when the pressure of the fluid to be measured acts on the vibrator 11, the distortion of the vibrator 11 changes, and the natural frequency changes. That is, the natural frequency of the vibrator 11 changes according to the pressure applied to the vibrator 11. Since the frequency of the physical quantity output signal Po matches the natural frequency of the vibrator 11, the pressure can be known from the frequency of the physical quantity output signal Po (pressure measurement signal).

  Note that Patent Document 1 describes that a vibrating gate vibrates according to a change in electrostatic attraction force.

Japanese Patent No. 3292286

  By the way, when an external vibration having a frequency close to the natural frequency of the reference vibrator 12 is transmitted to the reference vibrator 12, the reference vibrator 12 is vibrated by the external vibration, and this vibration signal causes the current / voltage conversion unit 21. The measurement accuracy of the physical quantity may deteriorate due to being superimposed on the physical quantity output signal Po.

  Further, in order to maintain insulation between the vibrator 11 and the reference vibrator 12, the vibrator 11 needs to be manufactured while keeping an accurate distance DISA from the reference vibrator 12. In addition to this, since it is necessary to separate the natural frequencies of the vibrator 11 so that the reference vibrator 12 does not vibrate at the natural frequency of the vibrator 11, the vibration of the vibrator 11 that determines the natural frequency and the reference vibrator 12 is determined. It is necessary to manufacture the shape accurately. As described above, the vibrator 11 and the reference vibrator 12 need to be accurately manufactured in the distance DISA and the shape of both, so that the manufacturing yield may be reduced and the manufacturing cost may be increased.

  Further, when the natural frequencies of the vibrator 11 and the reference vibrator 12 become close to each other due to manufacturing errors, the vibrator 11 vibrates at the natural frequency, and the reference vibrator 12 also vibrates. Sometimes. For this reason, the vibration energy of the vibrator 11 is absorbed by the reference vibrator 12, the vibration of the vibrator 11 becomes unstable, the frequency of the physical quantity output signal Po becomes unstable, and the measurement accuracy of the physical quantity deteriorates. There is.

  An object of the present invention is to provide a physical quantity measuring apparatus that realizes stable vibration of a vibrator, improvement in measurement accuracy of a physical quantity, and improvement in yield of the vibrator.

In order to achieve such an object, the invention of claim 1
The physical quantity is measured based on an output signal of the vibrator that vibrates according to an electrostatic attraction force acting between the vibrator on which the physical quantity to be measured acts and the first fixed electrode to which the bias voltage is applied. In physical quantity measuring equipment,
A second fixed electrode installed at a predetermined interval with respect to the first fixed electrode;
A drive unit that drives the first fixed electrode by a first drive signal generated based on an output signal of the vibrator, and drives the second fixed electrode by a second drive signal having a phase opposite to that of the first drive signal. With
It is characterized by that.
The invention of claim 2 is the invention of claim 1,
The first and second drive signals have amplitudes based on a first interval between the first fixed electrode and the transducer and a second interval between the second fixed electrode and the transducer,
It is characterized by that.
The invention of claim 3 is the invention of claim 2,
The amplitude ratio of the first and second drive signals is an amplitude ratio based on a ratio between the first interval and the second interval.
It is characterized by that.
The invention of claim 4 is the invention of claim 3,
The driving unit includes a first amplifying unit that outputs the first driving signal and a second amplifying unit that outputs the second driving signal,
An amplitude ratio between the first and second drive signals is determined based on a ratio between an amplification factor of the first amplification unit and an amplification factor of the second amplification unit.
It is characterized by that.
The invention of claim 5 is the invention of claim 4,
At least one of the first and second amplification units is a variable amplification unit that can change the amplification factor.
It is characterized by that.
The invention of claim 6 is the invention according to any one of claims 1 to 5, wherein the first fixed electrode, the second fixed electrode, and the vibrator are provided on the same silicon wafer.
It is characterized by that.

  According to the present invention, the vibrator is stably vibrated by improving the measurement accuracy of the physical quantity by driving the first and second fixed electrodes with drive signals having opposite phases to each other without using the reference vibrator. A physical quantity measuring device that improves the yield of the vibrator can be realized.

  An example of an embodiment of the present invention will be described with reference to FIG. FIG. 1 is a configuration diagram of the physical quantity measuring apparatus 190. The same components as those in FIG.

  In FIG. 1, a physical quantity measuring device 190 will be described by taking an example of measuring a pressure (physical quantity) of a fluid to be measured (object to be measured).

  The physical quantity measuring apparatus 190 includes a first fixed electrode 100 to which a bias voltage Vb is applied, a second fixed electrode 101 installed at a predetermined distance DIST with respect to the first fixed electrode 100, the first fixed electrode 100, and the second fixed electrode. 101 based on the output of the vibrator 102, the current / voltage converter 110 that converts the current of the output signal SENS of the vibrator 102 into a voltage, and the output (physical quantity output signal Po) of the current / voltage converter 110. A drive unit 120 that generates first and second drive signals KD1 and KD2 and drives the first and second fixed electrodes 100 and 101 is provided.

  The drive unit 120 also amplifies an error between the DC voltage converted by the AC / DC conversion unit 32 and the set voltage Vs (DC), which converts the physical quantity output signal Po (AC) into DC. Error amplifier 33, AGC unit 31 for outputting auto gain control output signal (hereinafter referred to as “AGC output signal”) SAGC in which the amplitude of physical quantity output signal Po is matched with set voltage Vs, and AGC output signal SAGC are amplified A first amplification unit 121 that drives the first fixed electrode 100 by the first drive signal KD1, a second amplification unit 122 that drives the second fixed electrode 101 by the second drive signal KD2 obtained by amplifying the AGC output signal SAGC, a first amplification The first feedback resistor R1 that determines the amplification factor of the unit 121, the second feedback resistor R2 that determines the amplification factor of the second amplification unit 122, and the first fixed resistor via the resistor. And a bias voltage Vb biases the electrode 100.

  The vibrator 102 is placed opposite to the first fixed electrode 100 and is placed opposite to the second fixed electrode 101. The vibrator 102 maintains a distance DIS1 (first interval) from the first fixed electrode 100, and maintains a distance DIS2 (second interval) from the second fixed electrode 101. For signals having frequencies other than the natural frequency of the vibrator 102, a capacitor C1 (not shown) is equivalently formed between the vibrator 102 and the first fixed electrode 100, and the vibrator 102 and the second A capacitor C <b> 2 (not shown) is equivalently formed between the fixed electrode 101. Note that the capacitance C1 is inversely proportional to the first interval DIS1, and the capacitance C2 is inversely proportional to the second interval DIS2.

  For the signal of the natural frequency of the vibrator 102, a resistor RS1 (not shown) is equivalently formed between the vibrator 102 and the first fixed electrode 100, and the vibrator 102 and the second fixed electrode. A resistor RS2 (not shown) is equivalently formed between the resistor 101 and the resistor 101.

  An example of the structure of the first fixed electrode 100, the second fixed electrode 101, and the vibrator 102 will be described with reference to FIG.

  In FIG. 2, a diaphragm 201 having a thin intermediate portion is formed on a silicon wafer 200, and a first fixed electrode 100, a second fixed electrode 101, and a vibrator 102 are formed in the diaphragm 201. As described above, the first fixed electrode 100, the second fixed electrode 101, and the vibrator 102 are provided on the same silicon wafer 200.

  The first fixed electrode 100 (shaded portion) and the second fixed electrode 101 (shaded portion) maintain a predetermined distance DIST. A vibrator 102 is formed between the first fixed electrode 100 and the second fixed electrode 101. The vibrator 102 is opposed to the first fixed electrode 100 while maintaining a first distance DIS1, and the second fixed electrode 101 and the second fixed electrode 101 are opposed to each other. The two faces DIS2 are kept facing each other.

  When the pressure PRS of the fluid to be measured is applied to the diaphragm 201, the diaphragm 201 is deformed, and the vibrator 102 is distorted.

  Returning to FIG. 1, the vibrator 102 has a natural frequency determined by its shape (for example, the shape of a beam), and a self-excited circuit that vibrates the vibrator 102 at the natural frequency is formed. That is, the first fixed electrode 100 to which the bias voltage Vb is applied, the electrostatic attraction force Fc acting between the first fixed electrode 100 and the vibrator 102, the vibrator 102, the current / voltage conversion unit 110, the driving unit 120, and A self-excited circuit (positive feedback loop) is formed by feedback of the first drive signal KD1 to the first fixed electrode 100.

  The vibration operation (self-excited vibration operation) of the vibrator 102 will be described in detail. First, a case will be described in which the first interval DIS1 and the second interval DIS2 are equal, and accordingly the capacitance C1 and the capacitance C2 are equal.

  The bias voltage Vb is connected between the first fixed electrode 100 and the circuit common voltage Vcom via a resistor. The vibrator 102 is (virtually) grounded to the circuit common voltage Vcom by the operational amplifier of the current / voltage conversion unit 110. As a result, the bias voltage Vb is applied between the first fixed electrode 100 and the vibrator 102. On the other hand, no bias voltage is applied between the second fixed electrode 101 and the vibrator 102.

  The first fixed electrode 100 is driven by the first drive signal KD1. The frequency of the first drive signal KD1 matches the natural frequency of the vibrator 102. Since the voltage applied to the first fixed electrode 100 is changed by the first drive signal KD1, the vibrator 102 responds to the change in the electrostatic attractive force Fc acting between the first fixed electrode 100 and the vibrator 102. Vibrates at the natural frequency.

  At this time, the first electrostatic current SD1 flows from the first fixed electrode 100 to the vibrator 102. The first electrostatic current SD1 is a current obtained by superimposing a noise current N1 on a current in phase with the first drive signal KD1. The current in phase with the first drive signal KD1 flows from the first fixed electrode 100 to the vibrator 102 via the resistor RS1, and the noise current N1 flows from the first fixed electrode 100 to the vibrator 102 via the capacitor C1. .

  On the other hand, the second fixed electrode 101 is driven by the second drive signal KD2 having a phase opposite to that of the first drive signal KD1, but since no bias voltage is applied, the second fixed electrode 101 is not connected between the second fixed electrode 101 and the vibrator 102. The electrostatic attraction force Fc corresponding to the frequency of the second drive signal KD2 does not work. Therefore, a noise current N2 having the same amplitude and opposite phase as the noise current N1 flows from the second fixed electrode 101 to the vibrator 102 as the second electrostatic current SD2 via the capacitor C2.

  Among the currents flowing into the vibrator 102, the noise current N1 and the noise current N2 have the same amplitude and opposite phase, and therefore cancel each other. For this reason, a current in phase with the first drive signal KD1 flows from the vibrator 102 to the current / voltage conversion unit 110 as the vibrator output signal SENS.

  The current / voltage conversion unit 110 converts the current of the transducer output signal SENS into a voltage and outputs the voltage as a physical quantity output signal Po. Note that the frequency of the physical quantity output signal Po matches the natural frequency of the vibrator 102.

  The physical quantity output signal Po is input to the AGC unit 31 and also input to the AC / DC conversion unit 32. The AGC unit 31, the AC / DC converting unit 32, and the error amplifying unit 33 are the same as those in FIG. 4, and the AGC unit 31 has an AGC output signal SAGC (AC) in which the amplitude of the physical quantity output signal Po matches the set voltage Vs. Is output to the first amplifying unit 121 and the second amplifying unit 122.

  The first amplifier 121 outputs a first drive signal KD1 obtained by amplifying the AGC output signal SAGC, and drives the first fixed electrode 100. The second amplification unit 122 outputs a second drive signal KD2 obtained by amplifying the AGC output signal SAGC, and drives the second fixed electrode 101.

  Since the sign of the amplification factor G1 of the first amplification unit 121 is different from the sign of the amplification factor G2 of the second amplification unit 122, the first drive signal KD1 and the second drive signal KD2 are in opposite phases.

  As shown in FIG. 2, when the pressure PRS of the fluid to be measured that acts (applies) to the vibrator 102 changes, the strain of the vibrator 102 changes and the natural frequency changes. That is, the natural frequency of the vibrator 102 changes according to the pressure applied to the vibrator 102. Since the natural frequency of the vibrator 102 in FIG. 1 matches the frequency of the physical quantity output signal Po, the pressure PRS can be known from the frequency of the physical quantity output signal Po (pressure measurement signal).

  Next, the signal waveforms of the respective parts described in FIG. 1 will be described with reference to FIG. 3, (a) is the AGC output signal SAGC (voltage), (b) is the first drive signal KD1 (voltage), (c) is the second drive signal KD2 (voltage), and (d) is the first electrostatic signal. The current SD1, (e) is the second electrostatic current SD2, (f) is the transducer output signal SENS (current), and (g) is the physical quantity output signal Po (voltage). The waveform (d) is a waveform obtained by superimposing (d2) on (d1).

  When the amplification factor G1 of the first amplifier 121 is positive, the AGC output signal SAGC (a) is in phase with the first drive signal KD1 (b). On the other hand, when the amplification factor G2 of the second amplifying unit 122 is negative, the second drive signal KD2 (c) is out of phase with the AGC output signal SAGC (a) and the first drive signal KD1 (b). The voltage amplitude of the first drive signal KD1 (b) is the first amplitude A1, and the voltage amplitude of the second drive signal KD2 (c) is the second amplitude A2.

  Of the first electrostatic current SD1 (d), SD1a (d1) is a current in phase with the first drive signal KD1 (b), and SD1b (d2) is a noise current N1.

  The second electrostatic current SD2 (e) is a noise current N2 having the same amplitude as that of SD1b (d2) and having a reverse phase.

  The transducer output signal SENS (f) is the same as SD1a (d1) because SD1b (d2) cancels out SD2 (e).

  The physical quantity output signal Po (g) is obtained by converting the current of the transducer output signal SENS (f) into a voltage, and the frequency thereof corresponds to the pressure PRS of the fluid to be measured.

  As described above, since the first interval DIS1 is equal to the second interval DIS2 and the capacitor C1 is equal to the capacitor C2, the impedance Z1 of the capacitor C1 is equal to the impedance Z2 of the capacitor C2. If the first amplitude A1 is equal to the second amplitude A2, according to Ohm's law, the noise current N1 (FIG. 3 (d2)) has the same amplitude as the noise current N2 (FIG. 3 (e)) and is opposite to each other. The two who are in phase relations cancel each other.

  In order to make the first amplitude A1 equal to the second amplitude A2, the absolute value of the amplification factor G1 may be made equal to the absolute value of the amplification factor G2. That is, when the ratio between the first interval DIS1 and the second interval DIS2 is “1”, the ratio between the first amplitude A1 and the second amplitude A2, and the absolute value of the amplification factor G1 and the absolute value of the amplification factor G2 If both ratios are set to “1”, the noise current N1 and the noise current N2 can be canceled.

  Next, for example, due to manufacturing errors, the first interval DIS1 may be smaller than the second interval DIS2 (DIS1 <DIS2), and the capacitance C1 may be larger than the capacitance C2 (C1> C2). . This case will be described.

  Since the capacitor C1 is larger than the capacitor C2, the impedance Z1 of the capacitor C1 is smaller than the impedance Z2 of the capacitor C2 (Z1 <Z2).

  Therefore, if the first amplitude A1 is made smaller than the second amplitude A2 (A1 <A2), the noise current N1 has the same amplitude as the noise current N2 according to Ohm's law, and the noise current N1 and the noise current N2 are Can be countered. In order to make the first amplitude A1 smaller than the second amplitude A2, the absolute value of the amplification factor G1 may be made smaller than the absolute value of the amplification factor G2 (| G1 | <| G2 |).

  Thus, the first amplitude A1 and the second amplitude A2 are based on the first interval DIS1 and the second interval DIS2. For example, the ratio between the first interval DIS1 and the second interval DIS2 (DIS1 / DIS2), the ratio between the first amplitude A1 and the second amplitude A2 (A1 / A2), the absolute value of the amplification factor G1, and the amplification factor G2. The ratio (| G1 | / | G2 |) with the absolute value of suffices to be proportional to each other.

  When the first interval DIS1 is larger than the second interval DIS2 (DIS1> DIS2), the magnitude relationship described above may be reversed.

  In order to realize the above-described proportional relationship, at least one of the first amplification unit 121 and the second amplification unit 122 may be a variable amplification unit that can change the amplification factors G1 and G2.

  According to the present embodiment, the measurement accuracy of the physical quantity can be improved by almost canceling out the noise current N1 and the noise current N2 and measuring the physical quantity (pressure).

  Since the reference vibrator is not used, external vibration can be prevented from being transmitted to the reference vibrator, and vibration energy of the vibrator 102 is not absorbed by the reference vibrator. As a result, the vibrator 102 vibrates stably, and the physical quantity measurement accuracy can be improved. In addition, since the vibrator 102 does not need to be accurately manufactured in relation to the reference vibrator (the distance and shape between the two), the yield of the vibrator 102 can be improved and the manufacturing cost can be reduced.

  Further, since the amplification factors G1 and G2 can be changed by selectively changing the first feedback resistor R1 and the second feedback resistor R2 in accordance with the first interval DIS1 and the second interval DIS2, the proportional relationship described above can be realized more easily. Then, the noise current N1 and the noise current N2 are almost canceled out, and the physical quantity measurement accuracy can be improved.

  Further, since the amplification factors G1 and G2 can be changed by variable amplification of the first and second amplification units 121 and 122 according to the first interval DIS1 and the second interval DIS2, the proportional relationship described above is realized more easily and flexibly. Then, the noise current N1 and the noise current N2 are almost canceled out, and the physical quantity measurement accuracy can be improved.

  Further, as shown in FIG. 2, by providing the first fixed electrode 100, the second fixed electrode 101, and the vibrator 102 on the same silicon wafer 200, the vibrator 102 can be manufactured more easily. Yield improvement and manufacturing cost can be reduced.

  Further, if the physical quantity acts on the vibrator 102 to change the distortion of the vibrator 102, the physical quantity can be measured. For this reason, the physical quantity measuring device 190 can also be used for measuring physical quantities such as a flow rate, a temperature, and a density that change the strain of the vibrator 102.

  In addition, this invention is not limited to the above-mentioned Example, In the range which does not deviate from the essence, many change and deformation | transformation are included. Moreover, combinations other than the combination of each part mentioned above can be included.

It is an example of the block diagram of the physical quantity measuring apparatus to which this invention is applied. It is an example of a structure figure of the 1st fixed electrode, the 2nd fixed electrode, and a vibrator. It is an example of the signal waveform figure of each part shown in FIG. It is an example of the block diagram of the physical quantity measuring apparatus shown by background art.

Explanation of symbols

DESCRIPTION OF SYMBOLS 100 1st fixed electrode 101 2nd fixed electrode 102 Vibrator 110 Current / voltage conversion part 120 Drive part 121 1st amplification part 122 2nd amplification part 190 Physical quantity measuring apparatus 200 Silicon wafer DIS1 1st space | interval DIS2 2nd space | interval DIST Predetermined space | interval Fc electrostatic attraction force KD1 first drive signal KD2 second drive signal Po physical quantity output signal PRS pressure SENS transducer output signal

Claims (6)

The physical quantity is measured based on an output signal of the vibrator that vibrates according to an electrostatic attraction force acting between the vibrator on which the physical quantity to be measured acts and the first fixed electrode to which the bias voltage is applied. In physical quantity measuring equipment,
A second fixed electrode installed at a predetermined interval with respect to the first fixed electrode;
A drive unit that drives the first fixed electrode by a first drive signal generated based on an output signal of the vibrator, and drives the second fixed electrode by a second drive signal having a phase opposite to that of the first drive signal. With
A physical quantity measuring device characterized by that. The first and second drive signals have amplitudes based on a first interval between the first fixed electrode and the transducer and a second interval between the second fixed electrode and the transducer,
The physical quantity measuring device according to claim 1. The amplitude ratio of the first and second drive signals is an amplitude ratio based on a ratio between the first interval and the second interval.
The physical quantity measuring device according to claim 2, wherein: The driving unit includes a first amplifying unit that outputs the first driving signal and a second amplifying unit that outputs the second driving signal,
An amplitude ratio between the first and second drive signals is determined based on a ratio between an amplification factor of the first amplification unit and an amplification factor of the second amplification unit.
The physical quantity measuring device according to claim 3. At least one of the first and second amplification units is a variable amplification unit that can change the amplification factor.
The physical quantity measuring device according to claim 4. The first fixed electrode, the second fixed electrode, and the vibrator are provided on the same silicon wafer,
The physical quantity measuring device according to any one of claims 1 to 5, wherein

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