JP2008076299A - Measuring unit and material testing machine - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To precisely detect an actual resistance component accompanying a resistance change of a bridge circuit, without being affected by a shift of a phase caused by a stray capacitance or the like between connection lines between the bridge circuit and a measuring instrument. <P>SOLUTION: A calibrating bridge equivalent to a load cell bridge impressed with an alternating current voltage signal is connected to a measuring circuit in advance to measurement. a compensation phase θv as to a measured signal of the resistance component is calculated based on vectors Av, Bv of a calibrating signal obtained from the calibrating bridge. A measured value x4 obtained by correcting a phase of the measured signal of the resistance component by the compensation phase θv is calculated as an actual measured value due to the resistance component, with respect to a measured value x3 of the resistance component output from the load cell bridge 20 and separated by a Fourier transformation circuit 115. <P>COPYRIGHT: (C)2008,JPO&INPIT

Description

  The present invention relates to a carrier-type measuring device that superimposes and outputs a signal that changes in accordance with a physical change of a measurement object on an AC voltage signal, and a material testing machine that uses the measuring device.

  2. Description of the Related Art Conventionally, a carrier-type strain measurement apparatus that has a bridge circuit including a resistance strain gauge and a measuring instrument and connects them with a plurality of cables or the like is known (Patent Document 1).

In this measuring apparatus, the effect of phase shift due to stray capacitance between connection lines such as cables is compensated as follows. In a conventional measuring apparatus, a compensation additional resistor and a switch for connecting and disconnecting the additional resistor to the Wheatstone bridge are provided in the bridge circuit. First, the 0 ° phase unbalance compensation signal and the 90 ° phase unbalance compensation signal are applied to the AC amplifier so that the measurement signal output from the bridge circuit in the no-load state becomes zero, and initial unbalance compensation is performed. Further, the compensation additional resistor is connected to the bridge circuit, and the phase delay due to the stray capacitance component is calculated from the output signal when the additional resistor that gives resistance change is connected. In actual measurement, the additional resistor is disconnected from the bridge circuit, and a measurement signal that compensates for the phase delay caused by the stray capacitance component is obtained.
JP 2005-19550 A

  However, the conventional measuring apparatus described above has the following problems. It is necessary to redo the compensation process every time the connection line connecting the bridge circuit and the measuring instrument is changed. If the above compensation is not performed even though the connection line routing is changed, an error occurs in the measurement result.

(1) According to the first aspect of the present invention, an AC voltage signal superimposed with a signal that changes in accordance with a physical change of an object to be measured is input from an external detection circuit to which the AC voltage signal is applied. This is a measurement circuit to be detected, and is applied to a measurement circuit in which an input signal includes a first component value that reflects a physical change and a second component value that does not reflect a physical change. The measuring apparatus according to claim 1 is based on a calibration circuit equivalent to a detection circuit, switching means for selectively switching between the detection circuit and the calibration circuit, and the AC voltage signal based on a calibration signal obtained from the calibration circuit. The phase delay calculating means for calculating the phase delay of the first component value with reference to the phase of the first component value, and the true value calculation for calculating the true value of the first component value by compensating the phase of the first component value by the phase delay Means.
(2) The invention according to claim 2 is the measuring apparatus according to claim 1, wherein the first component value changes due to the resistance component, and the second component value changes due to the capacitance component. And
(3) The invention of claim 3 is the measuring apparatus according to claim 1 or 2, wherein the detection circuit and the calibration circuit are bridge circuits.
(4) A material testing machine according to a fourth aspect of the invention is based on the measurement apparatus according to any one of the first to third aspects, a load actuator that loads a test piece, and a measurement signal measured by the measurement apparatus. And a control means for controlling the actuator to load the test piece.

  According to the present invention, prior to the measurement, the phase delay of the first component value reflecting the physical change of the measurement target, that is, the delay with respect to the phase of the AC voltage signal is detected. Thus, the first component value is detected by shifting the phase of the first component value. Therefore, it is possible to accurately detect a physical change of a measurement target without being affected by stray capacitance such as a cable connecting the measurement circuit and the measurement bridge.

  FIG. 1 is a block diagram showing a schematic configuration of an embodiment of a load cell type load measuring apparatus to which the present invention is applied. The measurement apparatus of this embodiment is a measurement apparatus in which a detection signal is superimposed on a carrier wave, and includes a measurement circuit 10 including a calibration bridge 16, a load cell bridge 20, and a power supply circuit 30. . The measurement circuit 10 is connected to the load cell bridge 20 by a connection cable 61 and is connected to the material testing machine 50 by a connection cable 62.

  The outline of the measuring apparatus according to this embodiment will be described first. When an AC voltage signal that is a carrier wave is applied to a resistance bridge, the potential difference between the output terminals due to the resistance change is expressed as (potential difference Δvr due to resistance component + potential difference Δvc due to capacitance component). The potential differences Δvr and Δvc are 90 degrees out of phase. Based on this assumption, the following compensation process (i) and measurement process (ii) are performed to calculate the actual potential difference ΔvrA due to the resistance component.

(I) Compensation processing:
A calibration bridge 16 that is not affected by the capacitance component is connected to the measurement circuit 10, and the phase of the potential difference Δvr due to the resistance component is measured in advance. This phase is a phase lag with respect to the carrier wave and is called a compensation phase θv.

(Ii) Measurement processing:
(Ii-1) The load cell bridge 20 is connected to the measurement circuit 10 via the cable 61, and a measurement signal on which the potential difference of the capacitance component is superimposed is acquired. This measurement signal is subjected to Fourier transform, and the potential difference Δvr due to the resistance component and the potential difference Δvc due to the capacitance component are separated and calculated.
(Ii-2) The phase of the potential difference Δvr due to the resistance component is rotated, that is, shifted by the compensation phase θv obtained by the compensation process, and the actual potential difference ΔvrA due to the resistance component is calculated.

  Therefore, the calibration bridge 16 does not compensate for a delay due to a capacitive component such as the cable 61.

  The material testing machine 50 is, for example, a tensile / compressed material testing machine, and the controller 51 controls the entire testing machine. The controller 51 includes a monitor 52 that displays test results and the like, an input device 53, and an actuator 54 that loads a test piece. The controller 51 inputs measurement signals from the measurement circuit 10 and performs known signal processing to control the test speed, test method, and the like of the material testing machine. Further, the input device 53 outputs a compensation command, which will be described later, by a user input operation, and outputs a test command at the start of the test.

  The measurement circuit 10 includes a digital arithmetic circuit 11, a DA converter 12 that converts a digital output signal of the digital arithmetic circuit 11 into an analog signal, a low-pass filter 13, an AC amplifier 14, a relay 15, and a calibration bridge 16. Is provided.

  The measurement circuit 10 also includes an AC amplifier 17 that amplifies a signal input from the calibration bridge 16 or the load cell bridge 20, a low-pass filter 18, and an AD converter 19 that converts an analog measurement signal into a digital signal. Yes. The relay 15 switches whether the AC amplifier 14 and the AC amplifier 17 are connected to the calibration bridge 16 or the load cell bridge 20.

  As shown in FIG. 2, the relay 15 has photoMOS switches SW1 to SW8. When a compensation command is instructed from the input device 53 of the material testing machine 50, the switches SW1 to SW4 are closed, the switches SW5 to SW8 are opened, and the calibration bridge 16 is connected to the measurement circuit 10. When a test start command is instructed from the input device 53, the switches SW1 to SW4 are opened, the switches SW5 to SW8 are closed, and the load cell bridge 20 is connected to the measurement circuit 10. In other words, the relay 15 is a switching unit that alternatively connects the bridge to the measurement circuit 10, and the load cell bridge 20 is connected during measurement and the calibration bridge 16 is connected during calibration.

  The calibration bridge 16 is provided in the final output stage and the input first stage of the measurement circuit 10 and is a calibration circuit for compensating for the phase delay θ1 due to the capacitance component of the analog circuit and the phase delay θ2 due to the data hold of the digital circuit. Here, the phase delay θ2 due to data hold is a delay due to Z conversion in a so-called digital circuit. In the present specification, the two phase delays θ1 + θ2 described above are referred to as a total delay θ for convenience of explanation.

  The calibration bridge 16 includes four resistors R11 to R14 constituting a Wheatstone bridge, an additional resistor R21 connected in parallel to the resistor R11, an R22 connected in parallel to the resistor R14, and an additional resistor R21 and R22 as a resistor R11. And switch SW11 and switch SW12 for controlling whether to connect or disconnect to R12. When the switch SW11 and the switch SW12 are closed, the additional resistors R21 and R22 are connected in parallel to the resistors R11 and R12, and the equilibrium state of the bridge is changed.

  The calibration bridge 16 is composed only of a resistance component so that stray capacitance is not generated, and the pattern circuit on the substrate connecting the relay 15 and the calibration bridge 16 is composed only of the resistance component. Stray capacitance is not generated. Therefore, the calibration signal represents only the potential difference due to the resistance component.

  The load cell bridge 20 is a Wheatstone bridge in which four resistors R1 to R4 are bridge-connected. The load cell bridge 20 is provided in a load cell (not shown) and outputs a signal indicating a change in resistance value according to a load load generated on a test piece. The resistance values of the additional resistors R21 and R22 of the calibration bridge 16 are resistance values having a magnitude corresponding to the resistance value change width of the load cell bridge 20 during the actual test.

  The voltage signal output from the AC amplifier 14 to the load cell bridge 20 and the calibration bridge 16 is a carrier wave signal having a predetermined frequency and a predetermined amplitude. The voltage signal output from the load cell bridge 20 or the calibration bridge 16 and amplified by the AC amplifier 17 is a voltage signal in which a signal corresponding to a bridge resistance value change is superimposed on a carrier wave. The digital arithmetic circuit 11 removes the carrier wave component from the voltage signal and obtains a measurement signal corresponding to the resistance value change. The measurement signal is calibrated to zero when the load cell bridge 20 is in an equilibrium state.

  As shown in FIG. 3, the digital arithmetic circuit 11 outputs a carrier wave signal (AC voltage signal) that is a sine wave having a predetermined frequency and a predetermined amplitude to the DA converter 12. Therefore, the digital arithmetic circuit 11 includes a carrier generation circuit 111, a sine wave generation circuit 112, and an amplitude adjustment circuit 113. The sine wave generation circuit 112 generates a sine wave based on the frequency signal generated by the carrier generation circuit 111. The amplitude adjustment circuit 113 adjusts the amplitude of the sine wave output from the sine wave generation circuit 112 to an amplitude corresponding to the load cell bridge 20 or the calibration bridge 16 and outputs the amplitude to the DA converter 12.

  The digital arithmetic circuit 11 inputs a digital measurement signal from the AD converter 19, performs a measurement process on the input signal, and outputs the measurement signal to a host device, for example, a controller 51 of a material testing machine. Therefore, the digital arithmetic circuit 11 includes a wavelet transform circuit 114, a Fourier transform circuit 115, a phase adjustment circuit 116, an amplitude adjustment circuit 117, and an offset adjustment circuit 118. The wavelet transform circuit 114 and the Fourier transform circuit 115 are synchronized with the carrier generation circuit 111.

  The wavelet transform circuit 114 is a noise filter. The measurement signal from which noise has been removed by the wavelet transform circuit 114 is input to the Fourier transform circuit 115. The Fourier transform circuit 115 performs frequency analysis and calculates a measurement signal in a frequency band corresponding to the carrier frequency.

  When an input measurement signal is represented in a complex space as shown in Equation (10) described later, the Fourier transform circuit 115 converts the signal value of the resistance component to the real axis as will be described later with reference to FIG. And the signal value due to the capacitance component are calculated as imaginary axis values. That is, as shown in equation (16) described later, the potential difference Δvr (x coordinate value) of the resistance component and the potential difference Δvc (y coordinate value) of the capacitance component are calculated separately. Here, as described above, the signal value due to the capacitive component is the signal component value caused by the delay caused by various capacitive components of the analog circuit and the delay caused by the data hold of the digital circuit, that is, the total delay. Means the signal component value produced by.

  FIG. 4 is a diagram for explaining the bridge output signal as a complex coordinate system with the horizontal axis representing the real axis and the vertical axis representing the imaginary axis. When the bridge output signal is superimposed on the carrier wave and the change component of the bridge output is measured, a total delay θ is generated that combines the delay due to the capacitance component of the analog circuit in the measurement system and the delay due to the data hold of the digital circuit. At this time, the signal affected by the total delay θ has a phase delay of 90 degrees with respect to the signal representing the resistance component. In the coordinate system of FIG. 4, the value on the real axis is represented by the resistance component, and the value on the imaginary axis is represented by the total delay component.

  The phase adjustment circuit 116 stores the compensation phase θv measured in advance prior to measurement, and adjusts the phase of the measured measurement signal. That is, the phase adjustment circuit 116 adjusts the phase of the potential difference Δvr due to the resistance component by the stored compensation phase θv, and calculates the coordinate value x described above. This coordinate value x is the actual potential difference ΔvrA due to the resistance component. The amplitude adjustment circuit 117 is a circuit that gives a predetermined gain to the actual potential difference ΔvrA. The gain is determined by a calibration process performed prior to measurement. The offset adjustment circuit 118 adjusts an offset value for canceling a self-weight component such as a gripping tool of the material testing machine with respect to the measurement value whose amplitude is adjusted. This offset value is also calculated in advance by an offset process performed prior to measurement. The offset-adjusted measurement value is output to a host device such as a material testing machine.

  An operation for compensating for the influence of the phase delay performed by such a measuring apparatus will be described. This compensation operation is performed prior to the measurement process. A compensation command is input to the relay 15, the switches SW1 to SW4 are closed, the switches SW5 to SW8 are opened, and the measurement circuit 10 is connected to the calibration bridge 16. At this time, the switch SW11 and the switch SW12 of the calibration bridge 16 are opened. In this state, a carrier wave signal having a predetermined frequency and a predetermined amplitude is applied from the AC amplifier 14 to the calibration bridge 16. The measurement signal output from the calibration bridge 16 is subjected to signal processing by a digital arithmetic circuit to obtain a measurement signal. That is, the Fourier transform circuit 115 of the digital arithmetic circuit 11 stores the measurement value obtained by Fourier transforming the input signal as the coordinate value (x1, y1). This measured value is indicated by a vector Av in FIG.

  Next, the switch SW11 and the switch SW12 of the calibration bridge 16 are closed, and a carrier wave signal having a predetermined frequency and a predetermined amplitude is applied from the AC amplifier 14 to the calibration bridge 16 in this state. The measurement signal output from the calibration bridge 16 is subjected to signal processing by the digital arithmetic circuit 11 to obtain a measurement signal. That is, the Fourier transform circuit 115 of the digital arithmetic circuit 11 stores the measurement value obtained by Fourier transforming the input signal as the coordinate value (x2, y2). This measured value is indicated by a vector Bv in FIG. The phase adjustment circuit 116 of the digital arithmetic circuit 11 obtains the difference between the vector Av and the vector Bv as the vector difference Bv−Av based on the coordinate value (x1, y1) and the coordinate value (x2, y2). Then, the phase adjustment circuit 116 calculates and stores the above-described compensation phase θv based on the vector difference Bv−Av.

With reference to FIG. 4, it can be explained as follows.
In FIG. 4, a vector Av represents a measurement signal output from the balanced calibration bridge 16, and a vector Bv is a state in which the additional resistors R21 and R22 are added to the balanced calibration bridge 16 to lose the balance. Represents a measurement signal output from the calibration bridge 16. A vector difference Bv−Av that is a difference between the vector Av and the vector Bv is delayed by θv with respect to the reference phase of the AC voltage signal. This θv is the phase lag of the potential difference due to the resistance component with respect to the phase of the carrier wave, that is, the compensation phase θv.

When starting a test, a test command is input to the relay 15, the switches SW1 to SW4 are opened, the switches SW5 to SW8 are closed, the measurement circuit 10 is connected to the load cell bridge 20, and a predetermined frequency and a predetermined amplitude. A carrier wave signal is applied from the AC amplifier 14 to the load cell bridge 20. The actuator 54 is driven to apply a load to the test piece, and the measurement signal output from the load cell bridge 20 is processed by the digital arithmetic circuit 11 to obtain the measurement signal. The Fourier transform circuit 115 of the digital arithmetic circuit 11 stores the coordinate value (x3, y3). This measured value is indicated by a vector Cv in FIG. The phase adjustment circuit 116 corrects the value of the coordinate value x3 based on the compensation phase θv stored in advance, calculates the coordinate value x4 by, for example, the following equation, and stores it as a load cell measurement value.
x4 = a × x3 + b × y3
Where a and b are vectors represented by a = x2-x1, b = y2-y1

  Conceptually, a vector Cvr obtained by returning the direction of the vector Cv by the compensation phase θv stored in the compensation operation is calculated, and a coordinate value x4 of the vector Cvr is calculated.

また、スケーリング係数をa，時間シフト量をbとして、ウェーブレット変換関数ψ(t)を次式（２）で定義する。

Next, signal processing of the wavelet transform circuit 114 will be described.
The mother wavelet φ (t) is expressed by the following equation (1).

Further, the wavelet transform function ψ (t) is defined by the following equation (2), where a is a scaling coefficient and b is a time shift amount.

と表すと、ウェーブレット変換関数ψ(t)に対する入力信号f(t)のウェーブレット変換Φ(t)は、次式（４）で計算される。

Input signal f (t)

In other words, the wavelet transform Φ (t) of the input signal f (t) with respect to the wavelet transform function ψ (t) is calculated by the following equation (4).

のとき，f(t)=0となる時刻tにおいて、ψ(t)=0となるためには、

であり、式（５）を次式（６）のように書き直すことができる。

したがって、スケーリング係数aは、

となる。ただし、fは入力信号f(t)の周波数[Hz]である。 here,

In order to satisfy ψ (t) = 0 at time t when f (t) = 0,

Equation (5) can be rewritten as the following equation (6).

Therefore, the scaling factor a is

It becomes. Here, f is the frequency [Hz] of the input signal f (t).

したがって、フーリエ変換回路１１５の入力信号f(t)は次式（９）で表すことができる。

The wavelet transform function ψ (t) when f = 10kHz is

Therefore, the input signal f (t) of the Fourier transform circuit 115 can be expressed by the following equation (9).

  The Fourier transform circuit 115 in FIG. 3 will be described in detail. As described above, the Fourier transform circuit 115 calculates coordinates (x, y) as shown in the following equations (12) and (13).

とすると、入力信号f(t)のフーリエ変換F(ω)は、

で表される。このとき、入力信号の座標（ｘ，ｙ）は、

で求められる。 Input signal f (t)

Then, the Fourier transform F (ω) of the input signal f (t) is

It is represented by At this time, the coordinates (x, y) of the input signal are

Is required.

When the equation (11) is substituted into the equation (12) and rewritten, the x coordinate is expressed by the following equation (14).

Similarly, the y coordinate is expressed by the following equation (15).

のように求めることができる。 Therefore, the coordinates (x, y) of the input signal are

Can be obtained as follows.

  A graph of the wavelet transform function ψ (t) and the input signal f (t) of the Fourier transform circuit 115 is shown in FIG. As can be seen from FIG. 5, the wavelet transform function ψ (t) indicated by the symbol L1 shows a very strong correlation with the input signal f (t) indicated by L2. FIG. 6 is a graph of ψ (t) × f (t) that is an output signal of the wavelet transform circuit 114. By using the signal subjected to such wavelet transform as an input signal, the Fourier transform circuit 115 Only the measurement signal in the band near the carrier oscillation frequency generated by the carrier generation circuit 111 can be measured with high accuracy.

  FIG. 7 shows the effect obtained by applying the wavelet transform process to the input signal prior to the Fourier transform process. That is, the result when the wavelet transform is not performed before the Fourier transform is indicated by L11, and the result when the wavelet transform is performed after the Fourier transform is indicated by L12. As can be seen from FIG. 7, in the curve L12, it can be seen that when the carrier frequency is exceeded, the frequency response is extremely lowered.

The measuring apparatus according to the embodiment described above can achieve the following operational effects.
(1) The calibration bridge circuit 16 is provided at the final output stage and the first input stage of the measurement circuit 10 and, prior to the test, the phase difference of the potential difference due to the resistance component is compensated for the phase θv based on the phase of the AC voltage signal that is a carrier wave. It was calculated and memorized as. The phase of the measurement signal of the resistance component obtained at the time of measurement is shifted by the compensation phase θv, and the actual measurement value of the resistance component is calculated. As a result, the measurement apparatus according to the present embodiment is not affected by stray capacitance such as a cable connecting the measurement circuit 10 and the load cell bridge 20. Therefore, even if the connection cable routing changes, the detection value is not affected.

(2) As a pre-process of the Fourier transform process, a filtering process by wavelet transform was performed instead of the conventional low-pass filter. As a result, the Fourier transform circuit 115 can perform frequency analysis on the input signal that has been subjected to the wavelet transform, and can extract the measurement signal with improved response to the measurement signal in the frequency band of the carrier wave. As a result, a measurement signal in a band near the carrier frequency can be accurately measured. Further, it is possible to reliably separate noise in a band near the carrier frequency.

(3) When a low-pass filter is provided in the previous stage of the Fourier transform circuit to remove a frequency higher than the frequency of the carrier wave as in the prior art, changing the carrier frequency changes the parameters of the digital filter constituting the low-pass filter. There was a need to do. However, even if the frequency of the carrier wave is changed by performing a filtering process by wavelet transform instead of the low-pass filter, the parameter changing process of the conventional digital filter is unnecessary.

  In the measurement apparatus according to the above embodiment, the load cell bridge has been described. However, the present invention can be applied to a differential transformer type extensometer, a capacitance type load cell, and the like as long as it is a carrier type measurement circuit. A bridge circuit is not essential. In addition, the mother wavelet of the wavelet transform circuit is defined by equation (2), but it is also possible to use a mother wavelet defined by another equation as long as it is a mother wavelet that improves the frequency response near the carrier frequency band. is there.

  The present invention is not limited to the embodiments described above as long as the characteristics are not impaired. That is, the present invention is a measurement circuit for detecting a physical change by inputting an AC voltage signal on which a signal that changes in accordance with a physical change of an object to be measured is input from an external detection circuit to which an AC voltage signal is applied. However, the embodiment is not limited to the embodiment described in the embodiment as long as it is a measurement circuit that inputs a signal including a first component value that reflects a physical change and a second component value that does not reflect a physical change. For example, in the above, the physical change of the measurement object is detected as a change in the strain resistance value, and the influence of the phase delay due to the capacitance component is removed. However, like the above-described differential transformer type extensometer, the physical change of the measurement target may be detected as a change in the inductance of the coil, and the influence of the phase delay due to the capacitance component may be removed.

  In the correspondence relationship between the claims and the components according to the embodiment, the detection circuit corresponds to the load cell bridge 20, the calibration circuit corresponds to the calibration bridge 16, the switching means corresponds to the relay 15, and the phase delay calculation. The means and the true value calculation means correspond to the digital arithmetic circuit 11, and the control means corresponds to the controller 51 of the material testing machine 50. Further, the first component value corresponds to the resistance component measurement signal, the second component value corresponds to the capacitance component measurement signal, and the compensation phase corresponds to the phase delay. The above description is merely an example, and when interpreting the invention, there is no limitation or restriction on the correspondence between the items described in the above embodiment and the items described in the claims.

The block diagram which shows an example in the case of using the measuring apparatus which concerns on embodiment of this invention for a material testing machine Circuit diagram showing details of relay 15 and calibration bridge 16 of FIG. Block diagram showing details of digital arithmetic circuit 11 The figure explaining the measurement signal expressed with the vector of the complex coordinate system Graph showing wavelet transform function ψ (t) and input signal f (t) of Fourier transform circuit 115 Graph of ψ (t) × f (t) that is output signal of wavelet transform circuit 114 The figure explaining the effect by performing wavelet transform processing

Explanation of symbols

11 Digital Operation Circuit 15 Relay 16 Calibration Bridge 20 Load Cell Bridge 50 Material Testing Machine 114 Wavelet Transform Circuit 115 Fourier Transform Circuit

Claims (4)

A measurement circuit for detecting the physical change by inputting an AC voltage signal on which a signal that changes according to a physical change of a measurement target is input from an external detection circuit to which an AC voltage signal is applied, In the measurement circuit in which the input signal includes a first component value that reflects the physical change and a second component value that does not reflect the physical change,
A calibration circuit equivalent to the detection circuit;
Switching means for selectively switching between the detection circuit and the calibration circuit;
A phase lag calculating means for calculating a phase lag of the first component value on the basis of a phase of the AC voltage signal based on a calibration signal obtained from the calibration circuit;
True value calculating means for calculating the true value of the first component value by compensating the phase of the first component value by the phase delay based on the measurement signal output from the detection circuit. Characteristic measuring device. The measuring apparatus according to claim 1,
The measuring apparatus according to claim 1, wherein the first component value changes due to a resistance component, and the second component value changes due to a capacitance component. The measuring apparatus according to claim 1 or 2,
The measuring device, wherein the detection circuit and the calibration circuit are bridge circuits. A measuring device according to any one of claims 1 to 3,
A load actuator for loading the specimen;
A material testing machine comprising: control means for controlling the actuator based on a measurement signal measured by the measuring device and loading the test piece.

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