JP2007104156A - Converter and antenna element equipped with converter - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a converter which can enhance transmission characteristics of power. <P>SOLUTION: The converter 10 comprises a waveguide 1 and a feeding material 2. The feeding material 2 includes a dielectric 21, a microstrip line 22, and a conductor 23. The waveguide 1 has suppression posts 11 and 12, and a tapered structure 13. Each suppression post 11, 12 comprises a metal rod and the tapered structure 13 has a surface subjected to metal plating. The dielectric 21 is arranged in contact with the waveguide 1 and the microstrip line 22 is provided on a surface opposing the surface of the dielectric 21 in contact with the waveguide 1. The surface of the dielectric 21 in contact with the waveguide 1 is grounded. The conductor 23 has one end coupled with the tapered structure 13 and the other end coupled with the microstrip line 22. <P>COPYRIGHT: (C)2007,JPO&INPIT

Description

  The present invention relates to a converter that feeds power from a power feeding circuit to an antenna element and an antenna device including the converter.

  Conventionally, a converter that feeds power via a coaxial cable is known as a converter that feeds power from a feeding circuit to an antenna element (Non-Patent Documents 1 and 2). FIG. 22 is a perspective view showing a configuration of a conventional converter. FIG. 23 is a cross-sectional view of the converter taken along line XXIII-XXIII shown in FIG.

  The conventional converter 300 includes a waveguide 310, a coaxial cable 320, a microstrip line 330, and a dielectric 340. Suppression posts 311 and 312 and a tapered structure 313 are formed in the waveguide 310. Suppression posts 311 and 312 are used for matching between the waveguide 310 and the coaxial cable 320.

  The microstrip line 330 is disposed on a surface of the dielectric 340 facing the surface on the waveguide 310 side. The coaxial cable 320 includes an inner conductor 321 and an outer conductor 322. The inner conductor 321 of the coaxial cable 320 has one end connected to the tapered structure 313 of the waveguide 310 and the other end connected to the microstrip line 330. Further, both ends of the outer conductor 322 of the coaxial cable 320 are in contact with the waveguide 310 and the dielectric 340, respectively.

  In the converter 300, the microstrip line 330 receives power from the power feeding circuit and supplies the received power to the waveguide 310 via the coaxial cable 320.

  The waveguide 310 propagates the power received from the microstrip line 330 and supplies it to the antenna element.

Thus, the conventional converter 300 employs a structure that supplies the power received from the power feeding circuit to the waveguide 310 via the coaxial cable 320.
Kato, Hirokawa, Ando, “Basic study on coaxial feed structure of millimeter-wave band post-wall waveguide”, IEICE Technical Report, AP2003-259 (2004-1). Higashi, Hirokawa, Ando, “Low-loss connection of millimeter-wave RF planar circuit and radial waveguide via coaxial structure”, IEICE Technical Report, AP2002-121 (2003-1).

  However, the conventional converter has a problem that it is difficult to improve the transfer characteristic of power from the feeding circuit to the antenna element. Further, the conventional converter has a problem that it is difficult to increase the bandwidth.

  Therefore, the present invention has been made to solve such a problem, and an object of the present invention is to provide a converter capable of improving the power transfer characteristic.

  Another object of the present invention is to provide a converter that can easily be widened.

  Furthermore, another object of the present invention is to provide a converter suitable for mass production.

  Furthermore, another object of the present invention is to provide an antenna device including a converter capable of improving the power transfer characteristic.

  Furthermore, another object of the present invention is to provide an antenna device including a converter that can easily be widened.

  Furthermore, another object of the present invention is to provide an antenna device suitable for mass production.

  According to this invention, a converter is a converter arrange | positioned between a feed circuit and an antenna element, Comprising: A waveguide and a feed member are provided. The waveguide is disposed on the antenna element side. The power supply member is disposed on the power supply circuit side and directly supplies power from the power supply circuit to the waveguide.

  Preferably, the power supply member includes a dielectric, a microstrip line, and a conductor. The dielectric is disposed in contact with the waveguide. The microstrip line is provided on the surface facing the surface in contact with the dielectric waveguide. The conductor has one end connected to the waveguide and the other end connected to the microstrip line.

  Preferably, the power supply member includes another waveguide and a conductor. The other waveguide is disposed in contact with the waveguide. The conductor has one end connected to the waveguide and the other end connected to the other waveguide.

  According to the invention, the antenna device includes an antenna element and a converter. The converter is connected to the antenna element, and supplies power from the power feeding circuit to the antenna element. And a converter consists of a converter of any 1 paragraph of Claims 1-3, and a waveguide is connected with an antenna element.

  In the present invention, the converter disposed between the power feeding circuit and the antenna element has a configuration in which a power feeding member that receives power from the power feeding circuit directly feeds power to the waveguide disposed on the antenna element side. As a result, the number of connection portions is relatively reduced.

  Therefore, according to the present invention, the transfer characteristics of the converter can be improved. In addition, the bandwidth of the converter can be widened.

  According to the present invention, the antenna device includes a converter having improved transfer characteristics or a converter having a wide band.

  Therefore, according to the present invention, the transfer characteristics of the antenna device can be improved. In addition, the band of the antenna device can be widened.

  Embodiments of the present invention will be described in detail with reference to the drawings. In the drawings, the same or corresponding parts are denoted by the same reference numerals and description thereof will not be repeated.

[Embodiment 1]
1 is a perspective view showing a configuration of a converter according to Embodiment 1 of the present invention. FIG. 2 is a cross-sectional view of the converter taken along line II-II shown in FIG. A converter 10 according to Embodiment 1 of the present invention includes a waveguide 1 and a feeding member 2. The power feeding member 2 includes a dielectric 21, a microstrip line 22, and a conductor 23. The converter 10 supplies power to an antenna element that transmits and receives millimeter wave radio waves.

  The waveguide 1 is made of a dielectric having a relative dielectric constant of 2.08, and includes suppression posts 11 and 12 and a taper structure 13. The length L of the waveguide 1 is, for example, 11.0 mm, the width W1 of the waveguide 1 is, for example, 3.08 mm, and the thickness D1 of the waveguide 1 is, for example, 1 .2 mm.

  The suppression posts 11 and 12 are made of metal bars. And the diameter of the suppression posts 11 and 12 is 0.3 mm, for example. The taper structure 13 has a substantially V-shaped cross-sectional shape, and the surface 13A is metal-plated. The center of the taper structure 13 is provided at a distance L1 from one end 1A of the waveguide 1, and the distance L1 is set to 3.0 mm, for example. As a result, the distance L2 between the center of the taper structure 13 and the other end 1B of the waveguide 1 is set to 8.0 mm, for example. The tapered structure 13 has a diameter r1 of, for example, 2.0 mm on the main surface 1D, and has a diameter r2 of, for example, 0.3 mm on the main surface 1E.

  The suppression posts 11 and 12 are formed in the waveguide 1 by opening a hole having a diameter of 0.3 mm in the waveguide 1 and inserting the hole into the opened hole. The tapered structure 13 is formed in the waveguide 1 by forming a recess having a substantially V-shaped cross section in the waveguide 1 and metal plating the surface of the formed recess.

  The dielectric 21 is disposed such that the main surface 21A is in contact with the main surface 1C of the waveguide 1, and the main surface 21A is grounded. The dielectric 21 has a thickness D2 of 0.12 mm, for example. The microstrip line 22 is made of a conductor and is disposed on a main surface 21B facing the main surface 21A in contact with the waveguide 1 of the dielectric 21. The microstrip line 22 has an extension part 221, and the length h_line of the extension part 221 is set to 1.4 mm, for example.

  The conductor 23 has a circular cross-sectional shape with a diameter r2, and is made of an inner conductor of a coaxial cable. The conductor 23 has one end connected to the tapered structure 13 of the waveguide 1 and the other end connected to the microstrip line 22 via the dielectric 21.

  FIG. 3 is a plan view of the converter 10 shown in FIGS. 1 and 2. 3A is a plan view of the converter 10 viewed from the direction A shown in FIG. 1, and FIG. 3B is a plan view of the converter 10 viewed from the direction B shown in FIG. is there.

  The suppression posts 11 and 12 are provided at a distance q from the center of the taper structure 13 and a distance L3 from the center line AX1. The distance q is set to 0.7 mm, for example, and the distance L3 is set to 1.2 mm, for example. As a result, the suppression posts 11 and 12 are arranged symmetrically with respect to the center line AX1 (see FIG. 3A).

  The dielectric 21 has, for example, a width W2 of 3.3 mm and a length L that is the same as the length L of the waveguide 1. The microstrip line 22 is disposed at the center of the dielectric 21 in the width direction, and has a width W3 of 0.3 mm, for example.

  The suppression posts 11 and 12 and the extension 221 of the microstrip line 22 are provided for impedance matching.

  FIG. 4 is a perspective view showing a specific example of the waveguide 1 shown in FIG. The waveguide 30 includes suppression posts 11 and 12, a tapered structure 13, a dielectric 31, via holes 32 to 55, and a hole 56. The suppression posts 11 and 12 and the tapered structure 13 are formed on the dielectric 31 in the same manner as described with reference to FIGS.

  The dielectric 31 is made of, for example, Teflon (registered trademark). The dielectric 31 has an emission surface 31A. The via holes 32 to 55 are made of metal rods, and are formed in the dielectric 31 so as to be arranged along the side surfaces excluding the emission surface 31A.

  The hole 56 has a circular cross section having a diameter r <b> 2, and is formed between the bottom surface 31 </ b> B of the dielectric 31 and the taper structure 13. The hole 56 is a hole for connecting one end of the conductor 23 shown in FIG.

  FIG. 5 is a plan view of the waveguide 30 as viewed from the direction C shown in FIG. If the wavelength of the radio wave propagating through the dielectric 31 is λ, each of the via holes 32 to 55 has a diameter r3 of 0.08λ. The interval d between two adjacent via holes is set to 0.16λ.

  Thus, the waveguide 30 is supplied to the tapered structure 13 by forming the plurality of via holes 32 to 55 having the predetermined diameter r3 in the dielectric 31 in a substantially U-shape with the predetermined interval d. The transmitted radio wave is propagated in the direction of the arrow 3 and radiated from the emission surface 31A.

  FIG. 6 is a perspective view showing another specific example of the waveguide 1 shown in FIG. The waveguide 60 includes suppression posts 11 and 12, a taper structure 13, a hollow conductor 61, and a hole 62. The suppression posts 11 and 12 are formed on the hollow conductor 61 in the same manner as described with reference to FIGS.

  The hollow conductor 61 has a rectangular cross-sectional shape and has a hollow portion 63 inside. The hollow conductor 61 has an emission port 61A. The hole 62 is provided on the bottom surface 61 </ b> B of the hollow conductor 61 so as to face the taper structure 13. The hole 62 is a hole for introducing the conductor 23 into the hollow conductor 61 in order to connect one end of the conductor 23 shown in FIG.

  FIG. 7 is a plan view of the waveguide 60 viewed from the direction D shown in FIG. The waveguide 60 propagates the radio wave supplied to the taper structure 13 to the cavity 63, and further propagates the cavity 63 in the direction of the arrow 4 and radiates it from the emission port 61A.

  In the waveguide 60, the cavity 63 of the hollow conductor 61 may be filled with a dielectric such as Teflon (registered trademark).

  In the converter 10, the waveguide 1 includes any of the waveguides 30 and 60 described above. When the waveguide 1 includes the waveguide 30, one end of the conductor 23 is inserted into the hole 56 of the dielectric 31 and is connected to the tapered structure 13. When the waveguide 1 is composed of the waveguide 60, one end of the conductor 23 is inserted into the cavity 63 through the hole 62 of the cavity conductor 61 and connected to the taper structure 13.

  When the converter 10 is used in an antenna device, the waveguide 1 is disposed on the antenna element side, and the power feeding member 2 (mainly the dielectric 21 and the microstrip line 22) is disposed on the power feeding circuit side. The microstrip line 22 receives power from the power supply circuit and supplies the received power to the tapered structure 13 of the waveguide 1 through the conductor 23. That is, the power supply member 2 including the dielectric 21, the microstrip line 22 and the conductor 23 directly supplies power received from the power supply circuit to the waveguide 1.

  The taper structure 13 propagates the electric power received from the power supply member 2 to the dielectric 31 or the hollow conductor 61, and the waveguide 1 supplies electric power to the antenna element from the emission surface 31A or the emission port 61A.

  In the converter 10, the dielectric 21 is disposed in contact with the waveguide 1 by connecting the conductor 23 to the taper structure 13 and the microstrip line 22. As a result, since the waveguide 1 is supported by the dielectric 21, the mechanical strength of the transducer 10 can be increased. The converter 10 is suitable for mass production because the microstrip line 22 is used.

  FIG. 8 is a diagram showing frequency characteristics of the converter 10 shown in FIG. The frequency characteristics shown in FIG. 8 are matched so that the transfer characteristics are optimized at 62.5 GHz by changing the length h_line of the extension 221 of the microstrip line 22 and the positions (= q) of the suppression posts 11 and 12. It is a frequency characteristic when taking. The frequency characteristics shown in FIG. 8 were analyzed by a finite element method simulator.

FIG. 8A shows the frequency dependence of the amplitudes of S ₁₁ indicating input reflection characteristics and S ₂₁ indicating transfer characteristics. In FIG. 8A, the vertical axis represents the amplitudes of S ₁₁ and S ₂₁ , and the horizontal axis represents the frequency. FIG. 8B shows the frequency dependence of the phases S ₁₁ and S ₂₁ . In FIG. 8B, the vertical axis represents the phases of S ₁₁ and S ₂₁ and the horizontal axis represents the frequency.

From the results shown in (a) of FIG. 8, the reflection characteristic _{S 11} is less fractional bandwidth -15dB is 3.84% fractional band transmission characteristic _{S 21} is not less than -0.5dB is 3.2% It is. Further, from the results shown in FIG. 8 (b), the phase characteristics of reflection characteristics _{S 11} and transmission characteristic _{S 21} is becomes non-linear in the frequency range of 62GHz～63GHz, in other frequency ranges, it becomes linear .

  FIG. 9 is a diagram showing the frequency characteristics of converter 300 shown in FIGS. 22 and 23. The frequency characteristics shown in FIG. 9 are also matched by changing the length h_line of the extension portion of the microstrip line 330 and the positions (= q) of the suppression posts 311 and 312 so that the transmission characteristics are optimal at 62.5 GHz. This is the frequency characteristic when taken, and was analyzed by a finite element method simulator. In the analysis of the frequency characteristics shown in FIG. 9, q = 2.6 mm and h_line = 1.95 mm were set.

FIG. 9A shows the frequency dependence of the amplitudes of the reflection characteristic S ₁₁ and the transfer characteristic S ₂₁ . In FIG. 9A, the vertical axis represents the amplitudes of S ₁₁ and S ₂₁ , and the horizontal axis represents the frequency. FIG. 9B shows the frequency dependence of the phases S ₁₁ and S ₂₁ . In FIG. 9B, the vertical axis represents the phases of S ₁₁ and S ₂₁ , and the horizontal axis represents the frequency.

From the results shown in (a) of FIG. 9, the reflection characteristic _{S 11} is less fractional bandwidth -15dB is 2.56% fractional band transmission characteristic _{S 21} is not less than -0.5dB is 0% . Further, from the results shown in FIG. 9 (b), the phase characteristics of reflection characteristics _{S 11} and transmission characteristic _{S 21} becomes nonlinearly in the frequency range of 62GHz～63GHz.

From the results shown in FIGS. 8 and 9, the converter 10 that feeds power directly from the microstrip line 22 to the waveguide 1 is more than the converter 300 that feeds power from the microstrip line 330 to the waveguide 310 via the coaxial cable 320. even a fractional bandwidth of the reflection characteristic _{S 11} and transmission characteristic _{S 21} is widened.

  This is because, in the conventional converter 300, the coaxial cable 320 is used, so that the number of connection portions is relatively large, and the number of locations for matching is relatively large. This is because power is directly supplied from 22 to the waveguide 1, so that the number of connection portions is relatively small and the number of locations for matching is relatively small. That is, since the converter 10 has the same structure as that of the conventional converter 300 in which the length of the coaxial cable 320 is set to zero, the matching between the microstrip line 22 and the coaxial cable and the coaxial cable and the waveguide 1 are performed. This is because there is no need to match with the above.

  Therefore, by adopting a structure in which the microstrip line 22 is linearly fed to the waveguide 1, the transmission characteristics can be improved and the specific band can be widened.

[Embodiment 2]
FIG. 10 is a perspective view showing the configuration of the converter according to the second embodiment. FIG. 11 is a cross-sectional view of the converter taken along line XI-XI shown in FIG. The converter 20 according to the second embodiment is the same as the converter 10 except that the power supply member 2 of the converter 10 shown in FIG. The converter 20 also feeds power to an antenna element that transmits and receives millimeter wave radio waves.

  The power supply member 70 includes a waveguide 71 and a conductor 72. The waveguide 71 has suppression posts 73 and 74 and a taper structure 75. The suppression posts 73 and 74 are made of metal bars. The taper structure 75 has a substantially V-shaped cross-sectional shape, and the surface 75A thereof is metal-plated. The suppression posts 73 and 74 and the tapered structure 75 are formed in the waveguide 71 by the same method as the suppression posts 11 and 12 and the tapered structure 13 are formed in the waveguide 1, respectively.

  The conductor 72 connects the tapered structure 13 of the waveguide 1 and the tapered structure 75 of the waveguide 71 so that the waveguide 71 is in contact with the waveguide 1. As a result, the waveguide 1 is supported by the waveguide 71, and the mechanical strength of the transducer 20 can be improved.

  More specifically, the waveguide 71 includes the waveguide 30 (see FIGS. 4 and 5) or the waveguide 60 (see FIGS. 6 and 7).

  In the converter 20, the suppression posts 11 and 12 are disposed at a position of q = 1.7 mm from the center of the taper structure 13, and the suppression posts 73 and 74 are q = 1.7 mm from the center of the taper structure 75. It is arranged at the position.

  In the converter 20, the waveguide 71 receives power from the power feeding circuit and feeds the received power to the waveguide 1 through the conductor 72. That is, the power supply member 70 directly supplies the power received from the power supply circuit to the waveguide 1. The waveguide 1 propagates and radiates the power received from the waveguide 71. Therefore, in the converter 20, power propagates sequentially in the direction of the arrow 8 and the direction of the arrow 9.

  FIG. 12 is a perspective view showing a configuration of a conventional converter. FIG. 13 is a cross-sectional view of the converter taken along line XIII-XIII shown in FIG. The conventional converter 400 is the same as the converter 20 except that the conductor 72 of the converter 20 shown in FIGS. 10 and 11 is replaced with a coaxial cable 410.

  The coaxial cable 410 includes an inner conductor 411 and an outer conductor 412. The diameter of the inner conductor 411 is, for example, 0.3 mm, and the diameter of the outer conductor 412 is, for example, 1.03 mm. The coaxial cable 410 has, for example, a relative dielectric constant of 2.2.

  The inner conductor 411 of the coaxial cable 410 is connected to the taper structure 13 of the waveguide 1 and the taper structure 75 of the waveguide 71, and both ends of the outer conductor 412 are connected to the waveguide 1 and the waveguide 71, respectively. Arranged to touch.

  In the converter 400, the suppression posts 11 and 12 are arranged at a position of q = 2.0 mm from the center of the taper structure 13, and the suppression posts 73 and 74 are q = 2.0 mm from the center of the taper structure 75. It is arranged at the position.

  In the converter 400, the waveguide 71 receives power from the power feeding circuit and feeds the received power to the waveguide 1 through the coaxial cable 410. The waveguide 1 propagates and radiates the power received from the waveguide 71. Therefore, in converter 400, power propagates sequentially in the direction of arrow 14 and the direction of arrow 15.

  FIG. 14 is a diagram illustrating frequency characteristics of the converter 20 illustrated in FIGS. 10 and 11. The frequency characteristics shown in FIG. 14 are frequency characteristics when the positions (= q) of the suppression posts 11, 12, 73, and 74 are changed and matching is performed so that the transfer characteristics are optimum at 62.5 GHz. It was analyzed by a finite element simulator.

FIG. 14A shows the frequency dependence of the amplitudes of S ₁₁ indicating input reflection characteristics and S ₂₁ indicating transfer characteristics. In FIG. 14A, the vertical axis represents the amplitudes of S ₁₁ and S ₂₁ , and the horizontal axis represents the frequency. Further, (b) of FIG. 14 _shows the frequency dependence of the phase of S _{11, S 21.} In FIG. 14B, the vertical axis represents the phases of S ₁₁ and S ₂₁ , and the horizontal axis represents the frequency.

From the results shown in (a) of FIG. 14, the reflection characteristic _{S 11} is less fractional bandwidth -15dB is 6.72% fractional band transmission characteristic _{S 21} is not less than -0.5dB is 9.6% It is. Further, the phase characteristic from the results shown in (b) of FIG. 14, the reflection characteristic _{S 11} and transmission characteristic _{S 21} is linear in the frequency range of 57GHz～67GHz.

  FIG. 15 is a diagram illustrating frequency characteristics of converter 400 shown in FIGS. 12 and 13. The frequency characteristics shown in FIG. 15 are also the frequency characteristics when the positions (= q) of the suppression posts 11, 12, 73, and 74 are changed and matching is performed so that the transfer characteristics are optimized at 62.5 GHz. It was analyzed by a finite element simulator.

FIG. 15A shows the frequency dependence of the amplitudes of the reflection characteristic S ₁₁ and the transfer characteristic S ₂₁ . In FIG. 15A, the vertical axis represents the amplitudes of S ₁₁ and S ₂₁ , and the horizontal axis represents the frequency. FIG. 15B shows the frequency dependence of the phases S ₁₁ and S ₂₁ . In FIG. 15B, the vertical axis represents the phases S ₁₁ and S ₂₁ , and the horizontal axis represents the frequency.

From the result shown in FIG. 15A, the ratio band where the reflection characteristic S ₁₁ is −15 dB or less is 4,32%, and the ratio band where the transfer characteristic S ₂₁ is −0.5 dB or more is 8%. . Further, from the results shown in FIG. 15 (b), the phase characteristics of reflection characteristics _{S 11} and transmission characteristic _{S 21} becomes nonlinearly in the frequency range of 63GHz～64GHz.

From the results shown in FIGS. 14 and 15, the converter 20 that feeds power directly from the waveguide 71 to the waveguide 1 is more than the converter 400 that feeds power from the waveguide 71 to the waveguide 1 via the coaxial cable 410. even a fractional bandwidth of the reflection characteristic _{S 11} and transmission characteristic _{S 21} is widened.

  This is because, in the conventional converter 400, since coaxial cables are used, the number of connecting portions is relatively large and the number of locations for matching is relatively large. This is because power is directly supplied to the waveguide 1 so that the number of connection portions is relatively small and the number of locations for matching is relatively small. That is, the converter 20 has the same structure as that of the conventional converter 400 in which the length of the coaxial cable 410 is set to zero. Therefore, the matching between the waveguide 71 and the coaxial cable and the coaxial cable and the waveguide 1 are performed. This is because there is no need to match with the above.

  Therefore, by adopting a structure in which linear feeding is performed from the waveguide 71 to the waveguide 1, it is possible to improve transfer characteristics and widen the specific band.

  Table 1 is a comparison table of the ratio band and phase characteristics of converter 10 according to Embodiment 1, converter 20 according to Embodiment 2, and conventional converters 300 and 400.

  In Table 1, MSL represents a microstrip line.

When the converter 300 that feeds power from the microstrip line 330 to the waveguide 310 via the coaxial cable 320 is compared with the converter 10 that feeds power directly from the microstrip line 22 to the waveguide 1, the converter 10 is partially Is common to the converter 300 in that it has a non-linear phase characteristic, but it is understood that the ratio band of the reflection characteristic S ₁₁ and the transfer characteristic S ₂₁ is wider than that of the converter 300.

Further, when the converter 400 that feeds power from the waveguide 71 to the waveguide 1 via the coaxial cable 410 is compared with the converter 20 that feeds power directly from the waveguide 71 to the waveguide 1, the converter 20 It can be seen that the phase characteristic is improved over the converter 400 and the ratio band of the reflection characteristic S ₁₁ and the transfer characteristic S ₂₁ is wider than the converter 400.

Accordingly, even when receiving the power from the power supply circuit in any of the microstrip line 22 and waveguide 71, reflection characteristics S ₁₁ and transmitted by adopting the structure for feeding directly the received power to the waveguide 1 the fractional bandwidth characteristic _{S 21} can be widened.

  Hereinafter, an antenna apparatus using the converters 10 and 20 according to the present invention will be described. FIG. 16 is a perspective view showing a configuration of an antenna device using the converter 10 according to the first embodiment. FIG. 17 is a cross-sectional view of the antenna device taken along line XVII-XVII shown in FIG. The antenna device 100 includes a converter 10 and a horn antenna 80.

  Horn antenna 80 is coupled to the exit surface of waveguide 1 of transducer 10. More specifically, when the waveguide 1 includes the waveguide 30 (see FIGS. 4 and 5), the horn antenna 80 is connected to the emission surface 31A, and the waveguide 1 is connected to the waveguide 60 (see FIG. 6 and FIG. 7), the horn antenna 80 is connected to the exit 61A.

  The converter 10 receives power from the power feeding circuit on the microstrip line 22, feeds the received power directly to the waveguide 1 through the conductor 23, and feeds power from the waveguide 1 to the horn antenna 80. Horn antenna 80 radiates the electric power received from converter 10. Therefore, in antenna device 100, power propagates through converter 10 sequentially in the directions of arrows 5 and 6 and is radiated from horn antenna 80 in the direction of arrow 7.

  Thus, the antenna device 100 radiates a directional beam having directivity in the direction of the arrow 7.

As described above, in the converter 10, since the fractional bandwidth of the reflection characteristic S ₁₁ and transmission characteristic S ₂₁ may be wider than a conventional converter 300 using a coaxial cable, the antenna device 100, a band in the millimeter wave band Can be relatively wide.

  Moreover, since the converter 10 has a mechanical strength stronger than that of the conventional converter 300 using a coaxial cable and is suitable for mass production, the mechanical strength and mass productivity of the antenna device 100 can be improved.

  FIG. 18 is another perspective view showing the configuration of the antenna device using the converter 10 according to the first embodiment. The antenna device 110 has a structure in which the waveguide 1 is rotated by an angle θ in the antenna device 100.

  In the antenna device 110, it is possible to prevent deterioration in characteristics by optimizing the positions of the suppression posts 11 and 12 and achieving matching. Therefore, even in the antenna device 110 in which the waveguide 1 is rotated by the angle θ, the band in the millimeter wave band can be relatively widened, and the mechanical strength and mass productivity can be improved.

  FIG. 19 is a perspective view showing a configuration of an antenna device using the converter 20 according to the second embodiment. 20 is a cross-sectional view of the antenna device taken along line XX-XX shown in FIG. The antenna device 200 according to the second embodiment includes a converter 20 and a horn antenna 80.

  Horn antenna 80 is connected to the exit surface of waveguide 1 of converter 20. More specifically, when the waveguide 1 includes the waveguide 30 (see FIGS. 4 and 5), the horn antenna 80 is connected to the emission surface 31A, and the waveguide 1 is connected to the waveguide 60 (see FIG. 6 and FIG. 7), the horn antenna 80 is connected to the exit 61A.

  The converter 20 receives power from the feeding circuit in the waveguide 71, feeds the received power directly to the waveguide 1 through the conductor 72, and feeds power from the waveguide 1 to the horn antenna 80. Horn antenna 80 radiates the electric power received from converter 20. Therefore, in antenna device 200, power propagates sequentially through converter 20 in the direction of arrow 16 and in the direction of arrow 17, and is radiated from horn antenna 80 in the direction of arrow 18.

  As a result, the antenna device 200 radiates a directional beam having directivity in the direction of the arrow 18.

As described above, the converter 20, since the fractional bandwidth of the reflection characteristic S ₁₁ and transmission characteristic S ₂₁ may be wider than a conventional converter 400 using a coaxial cable, the antenna device 200, a band in the millimeter wave band Can be relatively wide.

  Moreover, since the converter 20 has stronger mechanical strength than the conventional converter 400 using a coaxial cable, the mechanical strength of the antenna device 200 can be improved.

  FIG. 21 is another perspective view showing the configuration of the antenna device using the converter 20 according to the second embodiment. The antenna device 210 has a structure in which the waveguide 1 is rotated by an angle θ in the antenna device 200.

  In the antenna device 210, it is possible to prevent deterioration in characteristics by optimizing the positions of the suppression posts 11, 12, 73, and 74 to achieve matching. Therefore, even in the antenna device 210 in which the waveguide 1 is rotated by the angle θ, the band in the millimeter wave band can be relatively widened and the mechanical strength can be improved.

  In the above description, the suppression posts 11 and 12 are made of metal rods. However, the present invention is not limited to this, and the suppression posts 11 and 12 are formed by forming holes in the dielectric 31. It may be produced by metal plating the wall of the hole.

  In addition, although it has been described that the via holes 32 to 55 are made of a metal rod, in the present invention, the via holes 32 to 55 are not limited to this, and the via holes 32 to 55 form a plurality of holes along the side surfaces of the dielectric 31 excluding the emission surface 31A. And it may be produced by metal plating the side walls of the formed holes.

  Furthermore, the conductor 23 in the converter 10 and the conductor 72 in the converter 20 may be composed of holes and metal plating formed on the side walls of the holes.

  Furthermore, the taper structure 13 and the taper structure 75 may be configured by a conductor disposed so as to be fitted into a substantially V-shaped recess by removing the metal plating formed on the surfaces 13A and 75A.

  The embodiment disclosed this time should be considered as illustrative in all points and not restrictive. The scope of the present invention is shown not by the above description of the embodiments but by the scope of claims for patent, and is intended to include meanings equivalent to the scope of claims for patent and all modifications within the scope.

  The present invention is applied to a converter capable of improving power transfer characteristics. Further, the present invention is applied to a converter that can easily be widened. Furthermore, the present invention is applied to a converter suitable for mass production. Furthermore, the present invention is applied to an antenna device including a converter capable of improving the power transfer characteristic. Furthermore, the present invention is applied to an antenna device including a converter that can easily be widened. Furthermore, the present invention is applied to an antenna device suitable for mass production.

It is a perspective view which shows the structure of the converter by Embodiment 1 of this invention. It is sectional drawing of the converter between the lines II-II shown in FIG. FIG. 3 is a plan view of the converter shown in FIGS. 1 and 2. It is a perspective view which shows the specific example of the waveguide shown in FIG. It is a top view of the waveguide seen from the C direction shown in FIG. It is a perspective view which shows the other specific example of the waveguide shown in FIG. It is a top view of the waveguide seen from the D direction shown in FIG. It is a figure which shows the frequency characteristic of the converter shown in FIG. It is a figure which shows the frequency characteristic of the converter shown to FIG. 22 and FIG. It is a perspective view which shows the structure of the converter by Embodiment 2. FIG. It is sectional drawing of the converter between the lines XI-XI shown in FIG. It is a perspective view which shows the structure of the conventional converter. It is sectional drawing of the converter between the lines XIII-XIII shown in FIG. It is a figure which shows the frequency characteristic of the converter shown to FIG. 10 and FIG. It is a figure which shows the frequency characteristic of the converter shown to FIG. 12 and FIG. It is a perspective view which shows the structure of the antenna apparatus using the converter by Embodiment 1. FIG. It is sectional drawing of the antenna apparatus between the lines XVII-XVII shown in FIG. It is another perspective view which shows the structure of the antenna apparatus using the converter by Embodiment 1. FIG. It is a perspective view which shows the structure of the antenna apparatus using the converter by Embodiment 2. FIG. It is sectional drawing of the antenna apparatus between the lines XX-XX shown in FIG. It is another perspective view which shows the structure of the antenna apparatus using the converter by Embodiment 2. FIG. It is a perspective view which shows the structure of the conventional converter. It is sectional drawing of the converter between the lines XXIII-XXIII shown in FIG.

Explanation of symbols

  1,30,60,71,310 Waveguide, 1A One end, 1B The other end, 1C, 1D, 1E, 21A, 21B Main surface, 2,70 Feed member, 3-9, 14-18 Arrow 10, 20, 300, 400 Converter, 11, 12, 73, 74 Suppression post, 13, 75 Tapered structure, 13A, 75A Surface, 21, 31, 340 Dielectric, 22, 330 Microstrip line, 23, 72 Conductor, 31A Output surface, 31B bottom surface, 32-55 via hole, 56, 62 hole, 61 hollow conductor, 61A output port, 63 cavity, 80 horn antenna, 100, 110, 200, 210 antenna device, 221 extension, 320, 410 coaxial Cable, 321, 411 inner conductor, 322, 412 outer conductor.

Claims (4)

A converter disposed between the feeding circuit and the antenna element,
A waveguide disposed on the antenna element side;
A converter comprising: a power supply member that is disposed on the power supply circuit side and that directly supplies power from the power supply circuit to the waveguide. The power supply member is
A dielectric disposed in contact with the waveguide;
A microstrip line provided on a surface of the dielectric facing the surface in contact with the waveguide;
The converter according to claim 1, further comprising: a conductor having one end connected to the waveguide and the other end connected to the microstrip line. The power supply member is
Another waveguide disposed in contact with the waveguide;
The converter of claim 1 including a conductor having one end coupled to the waveguide and the other end coupled to the other waveguide. An antenna element;
A converter connected to the antenna element and supplying power from the feeding circuit to the antenna element;
The converter comprises the converter according to any one of claims 1 to 3,
The said waveguide is an antenna apparatus connected with the said antenna element.

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