JP2006333611A - Paired multiphase power converter - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To obtain a paired multiphase power converter capable of preventing a switching operation from simultaneously occurring at a plurality of phases of a load 2. <P>SOLUTION: This paired multiphase power converter includes a main circuit 3 connected between an AC power supply 1 and the load 2; an input controller 10 for generating an input control ratio RI for determining a time rate when the phase of the AC power supply 1 is connected to the load 2, and for generating an input control pulse TI for determining the phase of the AC power supply 1 connected to the load 2 on a time basis; a voltage command device 20 for generating a voltage command value supplied to the load 2; an output controller 30 for generating an output control pulse for determining, on a time basis, the phase of the load 2 connected to the AC power supply 1 based on the voltage command value and the input control ratio RI; and a gate controller 40 for generating a gate control pulse TG for determining, on a time basis, selective control of a plurality of switches of the main circuit 3 based on the input control pulse TI and the output control pulse. A switching detector 12 for detecting that a phase of the AC voltage is switched from one phase to another phase is provided inside the input controller 10. <P>COPYRIGHT: (C)2007,JPO&INPIT

Description

  The present invention relates to a multi-relative multi-phase power converter that is connected between an AC power source and a load, and switches the AC voltage of the AC power source by a plurality of switches to selectively supply the AC voltage to the load. .

  In the conventional multi-relative multi-phase power converter, the phase combination of the AC power supply used by connecting to the load depends on where in the section where the AC power supply voltage phase is divided by 60 degrees. Determine. The phase of the AC power source used simultaneously by the load phase is at most two phases, and the voltage between the two phases is a constant DC voltage in a sufficiently short time when the two phases are fixedly connected. By virtually considering this virtual DC voltage in each fixed connection state in the same manner as the PWM inverter and outputting it to the load, the above virtual DC voltage is pulse-widthed. Modulates and supplies power to the load.

  For example, in a section where the T-phase voltage vT and the R-phase voltage vR of the AC power supply are positive voltages, the positive T-phase voltage vT and the R-phase voltage vR are used as the positive poles of the virtual DC voltage. Then, the S-phase voltage vS, which is a negative voltage, is used as a virtual negative DC voltage negative electrode. In the control period that is sufficiently shorter than the period of 6 times the frequency of the AC power supply voltage, the negative electrode always uses the S-phase voltage vS, while the positive electrode uses the T-phase voltage vT and the R-phase voltage during one control period. Switch vR for use. The time during which the T-phase voltage vT and the R-phase voltage vR are used in the control period is the time during which the control period is distributed in proportion to the ratio of the T-phase voltage vT and the R-phase voltage vR. A triangular carrier wave for pulse width modulation is generated in each distributed time to perform pulse width modulation control, and an arbitrary voltage given by a voltage command device is supplied to a load (for example, see Patent Document 1) ).

Japanese Examined Patent Publication No. 8-32177 (page 11, right line 11 to page 4, right line 25, FIG. 3, FIG. 4, FIG. 5)

  Since the conventional multi-relative multi-phase power converter is configured as described above, a switching operation different from the switching operation by the above-described pulse width modulation control may occur. It may be performed simultaneously for a plurality of phases. From this, the surge voltage generated in the switch by the switching operation interferes with each other switch and generates an excessive voltage, and the neutral point voltage fluctuates in the phase of the load related to the switching. When a delay occurs in the switching operation of some switches due to leakage current, a fault occurs, such as a short circuit between the two phases of the AC power supply, resulting in excessive current. The relative multi-phase power converter and load equipment were broken and there was a risk of electric shock to the human body. In addition, the occurrence of the switching operation increases the number of switching operations and increases power loss, which causes a problem of improving the device efficiency of the multi-relative multi-phase power converter.

  The present invention has been made to solve the above-described problems, and an object of the present invention is to obtain a multi-relative multi-phase power converter that prevents switching operations from occurring simultaneously in a plurality of phases of a load.

  The multi-relative multi-phase power converter according to the present invention includes a conversion detector for detecting that the phase of the AC voltage has been switched from one phase section to another phase section inside the input controller.

  According to the present invention, the phase of the AC voltage is switched in the one that switches the phase of the AC power source connected to the load phase in the middle of the control period that is a basic time unit for controlling the multi-relative multi-phase power converter. Since the conversion detector that detects the conversion from the section to another phase section is provided, there is an effect that switching can be prevented from occurring simultaneously in a plurality of phases of the load.

Embodiment 1 FIG.
FIG. 1 is a configuration diagram showing a multi-relative multi-phase power conversion device according to Embodiment 1 of the present invention. In the figure, a main circuit 3 is connected between an AC power source 1 and a load 2, and the AC power source 1 The AC voltage is supplied to the load 2 by switching with a plurality of switches that selectively control the AC voltage.

  Based on the AC voltage of the AC power supply 1, the input controller 10 temporally determines the input control ratio for determining the ratio of the time for connecting the phase of the AC power supply to the load 2 and the phase of the AC power supply 1 connected to the load 2. A predetermined input control pulse is generated. In this input controller 10, the section detector 11 determines which phase section the phase of the AC voltage of the AC power supply 1 is divided into 60 degrees each from the phase of the AC power supply 1 based on the AC voltage of the AC power supply 1. The conversion detector 12 generates a conversion signal indicating that the section signal has been converted based on the section signal by the section detector 11, and the energization sequence controller 13 generates the conversion signal. Based on the conversion signal from the detector 12, an energization order signal that determines the order of connection to the phase load 2 of the AC power supply 1 is generated. The input control ratio is generated on the basis of the section signal by the conversion detector 12, the conversion signal by the conversion detector 12, and the energization sequence signal by the energization sequence controller 13, and an input pulse is generated. Raw device 15 is section signal by the section detector 11, based on the input control ratio supply order signal by supply order controller 13, and by the voltage ratio calculator 14 to produce an input control pulse.

  The voltage commander 20 generates a voltage command value that is a command value of a voltage supplied to the load 2. The output controller 30 generates an output control pulse that temporally determines the phase of the load 2 connected to the AC power supply 1 based on the voltage command value by the voltage commander 20 and the input control ratio by the input controller 10. It is. The gate controller 40 generates a gate control pulse that temporally determines selective control of a plurality of switches of the main circuit 3 based on the input control pulse by the input controller 10 and the output control pulse by the output controller 30. To do.

Next, the operation will be described.
The AC power supply 1 used as a virtual DC voltage in a control period, which is a basic unit time for controlling the multi-relative multiphase power converter, which is sufficiently shorter than a period of 6 times the frequency of the AC power supply voltage. In a multi-relative multi-phase power converter that supplies power to the load 2 by switching the phase between positive and negative and modulating the virtual DC voltage by pulse width modulation control using a triangular carrier wave, during the control period A triangular carrier wave is generated so that no switching operation other than that by the pulse width modulation control occurs at the change of the control period.

  In the section where the phase of the AC power source 1 used as the positive pole of the virtual DC voltage is switched within the control period, the apex at the transition of the control period is taken as the lowest point and synchronized with the time when the phase of the AC power source 1 is switched. In the section where the apex is taken as the highest point, a triangular carrier wave having a “mountain” shape is generated within the control period, and the phase of the AC power supply 1 used as the negative pole of the virtual DC voltage is switched within the control period. Taking the vertex at the turn of the period as the top point, taking the vertex synchronized with the time of switching the phase of the AC power supply 1 as the bottom point, generating a triangular carrier wave that shows the shape of the “valley” within the control period, The switching operation is not generated during the control period. And the pole of the virtual direct-current voltage which switches and uses two phases of alternating current power supply 1 within a control period changes the order which uses the two phases for every control period, and is the above-mentioned at the change of a control period. Avoid switching operations.

  In such a multi-relative multi-phase power converter, the phase of the AC power source 1 changes in a certain control period, and the shape of the triangular carrier wave changes when the control period ends and changes to the next control period. The movement from the “mountain” to the “valley” and the vertex of the triangular carrier wave moves from the lowest point to the highest point, or the shape of the triangular carrier wave changes from “valley” to “mountain” and the vertex of the triangular carrier wave One of the movements that instantaneously move from the highest point to the lowest point occurs. As a result, the output control pulses related to the plurality of phases of the load 2 are simultaneously switched and the virtual DC voltage poles are also switched at the same time, so that the switching operation is simultaneously generated for the plurality of phases of the load 2.

  From the above, the surge voltage generated in the switch by the switching operation interferes with each other switch and generates an excessive voltage. When there is a delay in the switching operation of some switches, a short circuit occurs between the two phases of the AC power supply 1 and an excessive current is generated. Also, the occurrence of the switching operation increases the number of switching operations and increases power loss, which is an obstacle to improving the device efficiency of the multi-relative multi-phase power converter.

The details of this problem will be described below.
FIG. 2 is a configuration diagram showing a multi-relative multi-phase power converter for explaining the problem. In the figure, an AC power source 1 and a load 2 are connected by a main circuit 3, and switches 3UR, 3US, 3UT, 3VR, 3VS, 3VT are selectively switched to supply power to the load 2 to the main circuit 3. , 3WR, 3WS and 3WT. 5U, 5V, and 5W are U, V, and W phase current detectors of the load 2, respectively. The U phase current iU, the V phase current iV, and the W phase current iW that flow from the main circuit 3 to the load 2 are provided. And current measurement values iUs, iVs, and iWs are output.

The voltage commander 20 outputs command values vU ^* , vV ^* , and vW ^* of voltages to be output from the main circuit 3 to the load 2. The current measurement values iUs, iVs, iWs, etc. may be used for calculating these voltage command values vU ^* , vV ^* , vW ^* . The output controller 30 is synchronized with the control period of the input controller 10u based on the input control ratio RI obtained from the input controller 10u and the voltage command values vU ^* , vV ^* , vW ^* obtained from the voltage commander 20. Output control pulses TU, TV, TW are generated and output. The gate controller 40 generates a gate control pulse TG from the input control pulse TI obtained from the input controller 10 u and the output control pulses TU, TV, TW obtained from the output controller 30 and outputs them to the main circuit 3. Note that the generation of the gate control pulse TG is applied to the measured values vRs, vSs, vTs of the AC power supply 1 vRs, vSs, vTs or the load 2 in addition to the input control pulse TI and the output control pulses TU, TV, TW. You may perform based on the measured value iUs, iVs, iWs of the flowing electric current.

  Next, the operation of the input controller 10u will be described. The input controller 10u includes a section detector 11, an energization sequence controller 13u, a voltage ratio calculator 14u, and an input pulse generator 15, and the measured values vRs, vSs, and vV, vS, and vT of the AC power supply 1 are measured. vTs is input, an input control ratio RI is calculated, an input control pulse TI is generated, and each is output.

  The section detector 11 receives the measured values vRs, vSs, vTs of the voltages vR, vS, vT, detects which section the phase of the AC power supply 1 is in, and outputs a section signal Sct. The energization sequence controller 13u controls the virtual DC voltage pole used by switching between the two phases of the AC power supply 1 within the control period to instruct that the order of use is changed every control period. An energization order signal Flg in which 0 and 1 appear alternately every period is output. The voltage ratio calculator 14u inputs the measured values vRs, vSs, vTs, the section signal Sct, and the energization sequence signal Flg of the voltages vR, vS, vT of the AC power supply 1, and calculates the input control ratio RI at every change of the control period. And output. Based on the section signal Sct, one is selected from the three voltage ratios vT / (vT + vR), vS / (vS + vT), and vR / (vR + vS) calculated from the measured voltage values vRs, vSs, and vTs of the AC power source 1. To calculate. Based on the energization sequence signal of the next control period output by the energization sequence controller 13u, it is determined whether to use the calculated voltage ratio as it is or to use a value obtained by subtracting the calculated voltage ratio from 1. Output as the input control ratio RI.

  The input pulse generator 15 receives the section signal Sct, the energization sequence signal Flg, and the input control ratio RI, and generates an input control pulse TI. Based on the section signal Sct, the input control pulse TI is determined to be always set to 1 within the control period, always set to 0 within the control period, and switched within the control period. Based on the energization sequence signal Flg, the switching from 1 to 0 and the switching from 0 to 1 are determined from among those switching within the control period, and the switching is controlled based on the input control ratio RI. It is performed at the time when the product of the input control ratio RI and the control period Tc has elapsed from the start time of the period. As for the input control pulse TI in one control period, it is assumed that waveforms for the control period Tc are collectively determined at the start of the control period. It is assumed that the input control pulse in the control period does not change even if the RI varies. For this reason, when the section signal Sct changes within the control period, the input control pulse TI is generated according to the section after the conversion from the next control period.

  FIG. 3 is a timing chart showing the operation of the section detector for explaining the problem, and shows the correspondence between the fluctuations in the voltages vR, vS, vT of the AC power supply 1 and the section signal Sct output from the section detector 11. Is. Since the combination of whether the voltages vR, vS, and vT of the AC power supply 1 are positive voltages or negative voltages changes every 60 degrees of the phase of the AC power supply 1, the section detector 11 has the positive / negative combination. The section signal Sct is determined and output according to the above.

  Table 1 shows the phase of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage corresponding to the section signal Sct, and the virtual DC used by switching between the two phases of the AC power supply 1 within the control period. The voltage poles, the order of using the two phases at the poles, and the correspondence between the energization order signal Flg are respectively shown. The correspondence relationship in Table 1 shows that, in each section, out of the six combinations of phases of the AC power supply 1 that can be used as virtual DC voltages, the voltage that appears as a virtual DC voltage is the largest positive value, It means to use two kinds of voltages of the second largest value. As an example, when the section signal Sct is 1, the positive pole of the virtual DC voltage uses two phases of the AC power source 1 by switching between the T phase and the R phase within one control period, and the negative pole is the AC The S phase of the power supply 1 is always used within one control period. The order of using the phase of the AC power supply 1 at the positive electrode for switching is such that the T phase is used first in the control period in which the energization order signal Flg is 1, and then the R phase is used, and then the energization order signal Flg is 0. In the control period, the R phase is used first and then the T phase is used.

  The input pulse generator 15 generates the input control pulse TI based on the section signal Sct, the energization order signal Flg, and the input control ratio RI in accordance with the correspondence relationship in FIG. 3 and Table 1.

  FIG. 4 is a flowchart showing the operation of the energization order controller for explaining the problem. When the pulse generation operation of the previous control period is completed in the input controller 10u, the output controller 30 and the gate controller 40 (step ST10), the energization sequence controller 13u outputs the energization sequence signal Flg as the energization sequence control operation B10u. The signal is inverted (step ST12) and used as an energization sequence signal for the next control period. As a result, the energization order control operation B10u ends, and the end of the following voltage ratio selection operation B20 is awaited (step ST14).

  FIG. 5 is a flowchart showing the operation of the voltage ratio calculator for explaining the problem. The operation of the calculator is as follows: a voltage ratio selection operation B20 for selecting and calculating one of three voltage ratio calculation expressions, and a voltage ratio output operation for calculating and outputting the input control ratio RI from the calculated voltage ratio. It consists of two stages of B30u.

  When the pulse generation operation of the previous control period is completed in the input controller 10u, the output controller 30, and the gate controller 40 (step ST10), the voltage ratio calculator 14u starts the voltage ratio selection operation B20. When the section signal Sct is 1 or 4 (step ST21), the voltage ratio vT / (vT + vR) is calculated (step ST23), and when the section signal Sct is 2 or 5 (step ST22), the voltage ratio vS / (vS + vT) is calculated (step ST24). If none of the above applies, the voltage ratio vR / (vR + vS) is calculated (step ST25). Thus, by calculating the voltage ratio, the voltage ratio selection operation B20 ends.

  As soon as the energization sequence control operation B10u is completed when the voltage ratio selection operation B20 is completed, if the energization sequence control operation B10u is not completed, it waits for the completion (step St26u), and then the voltage ratio output operation B30u. To start. If the energization order signal in the next control period is 1 (step ST32), the voltage ratio calculated in the voltage ratio selection operation B20 is output as the input control ratio RI (step ST34), and the energization order signal is 0. For example, a value obtained by subtracting the voltage ratio from 1 is output as the input control ratio RI (step ST35). Thus, by setting the input control ratio RI, the voltage ratio output operation B30u ends.

  When the voltage ratio output operation B30u is completed, the input control ratio RI is output to the input pulse generator 15 and the output controller 30, and the input control pulse TI and the output control pulses TU, TV, TW for the next control period are generated, respectively. The

  FIG. 6 is a timing chart showing the operation of the multi-relative multi-phase power converter for explaining the problem. The input controller is controlled by the fluctuation of the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10u. 10u, the calculation result of the input control ratio RI output from the output controller 30 and the gate controller 40, the section signal Sct, the energization sequence signal Flg, the input control pulse TI, the pulse width modulation result in the output controller 30, the U phase 4 is an example of the operation of the output control pulse TU and the switch control pulses TUR, TUS, TUT according to FIG. Switch control pulses TUR, TUS, TUT not shown in FIG. 2 control the on / off of the switches corresponding to the switches 3UR, 3US, 3UT, respectively.

  The input control pulse TI is a control pulse group having twice as many ports as the phase of the AC power supply 1. One control pulse is a signal indicating by 1 and 0 whether or not to use each phase of the AC power supply 1 for each pole of the virtual DC voltage, and using the R phase as the positive electrode of the virtual DC voltage. It includes a control pulse TRP indicating whether or not to use, TRN indicating whether or not to use as a negative electrode, TSP and TSN corresponding to each, and T-phase control pulses TTP and TTN. Control pulses related to the positive pole of the virtual DC voltage are TRP, TSP, TTP, and control pulses related to the negative pole are TRN, TSN, TTN.

  Of the two poles of the virtual DC voltage, in the pole that is used without switching all phases of the AC power supply 1 within the control period, all input control pulses related to that pole during the control period The input control pulse related to one phase of the AC power supply 1 used by the pole in the control period is always 1, and all the AC power supplies 1 not used by the pole in the other control periods are fixed. The input control pulse related to the phase is always 0.

  In the pole that switches between two phases of the AC power supply 1 within the control period, the input control pulse related to two or more phases of the AC power supply 1 that the pole uses in the control period is 1 in the control period. From 0 to 0 or from 0 to 1, the input control pulses related to all phases of the AC power supply 1 that are not used by the pole in the other control period are always 0. The switching operation is such that one input control pulse is changed from 1 to 0 and the other one input control pulse is 0 so that two or more phases of the AC power supply 1 are not simultaneously used in one pole. From 1 to 1, the time is switched in synchronization. The switching time is the time when the product of the input control ratio RI and the control period Tc has elapsed since the start of the control period.

  Since the energization order signal Flg input to the input pulse generator 15 alternately indicates 0 and 1 for each control period, the input control pulse to be switched within the control period is changed from 1 to 0 in a certain control period. When switching, the control period is switched from 0 to 1 in the next control period, and further switched from 1 to 0 in the next control period. Therefore, the input control pulse immediately before and after the change of the control period takes the same value, and switching of the input control pulse does not occur at the change.

The output control pulses TU, TV, and TW are logic signals that are set to 1 when connected to the positive pole of the virtual DC voltage for each phase of the load 2 and set to 0 when connected to the negative pole. In the pulse width modulation control in the output controller 30, a triangular carrier wave whose vertex is synchronized at the time when either the positive electrode or the negative electrode of the virtual DC voltage switches between the two phases is used. For each of the U, V, and W phases of the load 1, when the voltage command value is large compared to the instantaneous value of the voltage command value vU ^* , vV ^* , vW ^{* and} the instantaneous value of the triangular carrier wave, the triangular carrier wave is When it is larger, 0 is output. Since the triangular carrier wave is the highest point or the lowest point at the change of the control period and the switching time, the output control pulses TU, TV, and TW are not switched at the change and the switching time.

  The switch control pulses TUR, TUS, and TUT related to the U phase are logic signals that are set to 1 when the corresponding switches 3UR, 3US, and 3UT are turned on, and set to 0 when the corresponding switches 3UR, 3US, and 3UT are turned off. Operate with an expression.

負荷２の他の相に係るスイッチ制御パルスについても同様の演算式となる。

The same calculation formula is applied to the switch control pulses related to the other phases of the load 2.

  In this example, since vT and vR are positive voltages and vS is a negative voltage, the section signal Sct is 1. The energization order signal Flg alternately outputs 0 and 1 for each control period in accordance with the energization order control operation B10u in the flowchart shown in FIG. The input control ratio RI is calculated by calculating the voltage ratio vT / (vT + vR) because the section signal Sct is 1 in accordance with the voltage ratio selection operation B20 of the flowchart shown in FIG. 5, and the voltage ratio of the flowchart shown in FIG. According to the output operation B30u, as 0 and 1 appear alternately in the energization order signal Flg, the value of the voltage ratio calculated as the input control ratio RI and the value obtained by subtracting the voltage ratio from 1 are alternately output. .

  Since the negative pole of the virtual DC voltage always uses the S phase of the AC power supply 1 and the positive pole switches between the T phase and the R phase of the AC power supply 1 and uses the input control pulse TI, In the input control pulse, the input control pulse TSN related to the S phase is 1, and the other two input control pulses TRN and TTN are 0, and in the three input control pulses related to the positive electrode, the input control pulses TTP and R related to the T phase are used. The input control pulse TRP related to the phase is switched at the same time within the control period, and the input control pulse TSP related to the S phase not used in the positive electrode becomes zero.

  The triangular carrier wave used for pulse width modulation control in the output controller 30 has a section signal Sct of 1, and the pole used by switching between the two phases of the AC power supply 1 within the control period is the positive electrode. The triangular carrier wave indicating the shape of “mountain”. At this time, the output control pulse TU related to the U phase of the load 2 becomes 1 at the change of the control period, and becomes 0 at the time when the two phases of the AC power supply 1 are switched at the positive electrode. This also applies to the output control pulses TV and TW related to the V phase and the W phase, which are the other phases of the load 1.

As a result, since the input control pulse TI and the output control pulses TU, TV, and TW are not switched at the change of the control period, switching by the nine switch control pulses is not performed at all. At the time when the two phases of the AC power supply 1 are switched at the positive electrode, the input control pulse TTP related to the T phase and the input control pulse TRP related to the R phase are switched among the three input control pulses related to the positive electrode. Since all of the control pulses TU, TV, and TW are 0, the nine switch control pulses are not switched at this time.
The above operation similarly changes even in the control period in which the section signal Sct is other than 1.

  FIG. 7 is a timing chart showing the operation of the multi-relative multi-phase power converter for explaining the problem. The input controller is controlled by the fluctuations in the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10u. 10u, calculation result of input control ratio RI, output signal 30 and gate controller 40, section signal Sct, energization sequence signal Flg, input control pulse TI, pulse width modulation result in output controller 30, U phase It is another example of operation | movement of the output control pulse TU which concerns on, and switch control pulse TUR, TUS, TUT. In this example, with respect to the voltage of the AC power supply 1, vR is a positive voltage, vS is a negative voltage, and vT is changed from a positive voltage to a negative voltage in the first control period Tc1u ′. Sct is converted from 1 to 2.

  An operation in the first control period Tc1u ′ and the second control period Tc2u ′ will be described. The energization order signal Flg is 1 in the first control period Tc1u ′ and is inverted to 0 in the second control period Tc2u ′ according to the energization order control operation B10u of the flowchart shown in FIG. The input control ratio RI is calculated as vT / (vT + vR) in the first control period Tc1u ′ and vS / (vS + vT) in the second control period Tc2u ′ according to the voltage ratio selection operation B20 of the flowchart shown in FIG. Then, according to the voltage ratio output operation B30u of the flowchart shown in FIG. 5, the energization order signal Flg is 1 in the first control period Tc1u ′, so that vT / (vT + vR) remains as it is and the second control period Tc2u ′. Then, since the energization order signal Flg is 0, a value obtained by subtracting vS / (vS + vT) from 1 is output as the input control ratio RI.

  For the input control pulse TI, since the section signal Sct is 1 in the first control period Tc1u ′, the combination of phases of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage is shown in FIG. In the second control period Tc2u ′, the section signal Sct is 2, or the positive pole of the virtual DC voltage always uses the R phase of the AC power supply 1 so that the negative pole is Each is generated so as to switch between the S phase and the T phase of the AC power supply 1. Since the energization sequence signal Flg is 1 in the first control period Tc1u ′, the phase of the AC power source 1 that the positive electrode of the virtual DC voltage is used at the end of the control period according to Table 1 is the R phase and the negative electrode is used. The phase of the alternating current power source 1 to be operated is the S phase. Since the energization order signal Flg is 0 in the second control period Tc2u ′, the phase of the AC power supply 1 that the positive electrode of the virtual DC voltage uses at the start of the control period according to Table 1 uses the R phase and the negative electrode The phase of the AC power supply 1 to be performed is the T phase. Therefore, at the transition from the first control period Tc1u ′ to the second control period Tc2u ′, the phase of the AC power source 1 used by the positive electrode is fixed to the R phase, but the phase of the AC power source 1 used by the negative electrode is The T phase is switched to the S phase.

The triangular carrier wave used for generating the output control pulses TU, TV, and TW has a “mountain” shape when the section signal Sct is 1, and the control period when the section signal Sct is 2, as in the operation example shown in FIG. Since the pole used by switching between the two phases of the AC power source 1 is the negative electrode, the shape of the “valley” is shown. Therefore, at the transition from the first control period Tc1u ′ to the second control period Tc2u ′, an operation occurs in which the vertex of the triangular carrier wave moves from the lowest point to the highest point, and all output control pulses TU are generated. , TV, TW switches from 1 to 0 at the transition. As a result, the phase of the AC power source 1 to which all phases of the load 2 are connected is the R phase that is the positive electrode of the virtual DC voltage at the end of the first control period Tc1u ′, and the second control period Tc2u ′. At the start, the phase becomes the negative phase of the virtual DC voltage, and the six switch control pulses TUR, TUT, TVR, TVT, TWR, Switching operations occur simultaneously in the TWT.
The above operation changes in the same manner even when the section is switched except when the section signal Sct is switched from 1 to 2.

  FIG. 8 is a timing chart showing the operation of the multi-relative multi-phase power converter for explaining the problem. The input controller is controlled by the variation of the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10u. 10u, the calculation result of the input control ratio RI output from the output controller 30 and the gate controller 40, the section signal Sct, the energization sequence signal Flg, the input control pulse TI, the pulse width modulation result in the output controller 30, the U phase It is another example of operation | movement of the output control pulse TU which concerns on, and switch control pulse TUR, TUS, TUT. In this example, the voltage of the AC power supply 1 and the operation of the section signal Sct associated therewith are the same as those of the operation example shown in FIG. 7, but the energization sequence signal from the first control period Tc1u ″ to the fourth control period Tc4u ″. Flg operation is reversed.

  The operation in the first control period Tc1u ″ and the second control period Tc2u ″ will be described. The energization order signal Flg is 0 in the first control period Tc1u ″ and is inverted to 1 in the second control period Tc2u ″ in accordance with the energization order control operation B10u in the flowchart shown in FIG. The input control ratio RI is calculated as vT / (vT + vR) in the first control period Tc1u ″ and vS / (vS + vT) in the second control period Tc2u ″ according to the voltage ratio selection operation B20 of the flowchart shown in FIG. Then, in accordance with the voltage ratio output operation B30u of the flowchart shown in FIG. 5, since the energization order signal Flg is 1 in the first control period Tc1u ″, the value obtained by subtracting vT / (vT + vR) from 1 In the control period Tc2u ″, since the energization order signal Flg is 0, vS / (vS + vT) is output as it is as the input control ratio RI.

  The input control pulse TI is generated such that the combination of phases of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage is the same as the operation example shown in FIG. Since the energization sequence signal Flg is 0 in the first control period Tc1u ″, the phase of the AC power supply 1 that the positive electrode of the virtual DC voltage uses at the end of the control period according to Table 1 is the T phase and the negative electrode is used. The phase of the alternating current power supply 1 is the S phase. Since the energization order signal Flg is 1 in the second control period Tc2u ″, the positive electrode of the virtual DC voltage is used at the start of the control period according to Table 1. The phase of the AC power source 1 is the R phase, and the phase of the AC power source 1 used by the negative electrode is the S phase. Therefore, at the transition from the first control period Tc1u ″ to the second control period Tc2u ″, the phase of the AC power source 1 used by the positive electrode is switched from the T phase to the R phase, and the phase of the AC power source 1 used by the negative electrode is It will be fixed to the S phase.

The shape indicated by the triangular carrier wave used for generating the output control pulses TU, TV, and TW is the same as that of the operation example shown in FIG. 7, and the triangle is formed at the transition from the first control period Tc1u ″ to the second control period Tc2u ″. Since the operation of moving the vertex of the carrier wave from the lowest point to the highest point occurs, all the output control pulses TU, TV, TW are switched from 1 to 0 at the transition. As a result, the phase of the AC power source 1 to which all phases of the load 2 are connected is the T phase that is the positive pole of the virtual DC voltage at the end of the first control period Tc1u ″, and the second control period Tc2u ″. At the start, it becomes the S phase which is the negative pole of the virtual DC voltage, and the six switch control pulses TUR, TUT, TVR, TVT, TWR, Switching operations occur simultaneously in the TWT.
The above operation changes in the same manner even when the section is switched except when the section signal Sct is switched from 1 to 2.

  As described above, in the multi-relative multi-phase power converter, there has been a problem that the switches related to a plurality of phases of the load simultaneously generate a switching operation at every opportunity when the section signal Sct is switched.

Hereinafter, the operation of the first embodiment will be described.
In FIG. 1, the same or corresponding parts as those in FIG.
The operation of the input controller 10 will be described. The input controller 10 includes a section detector 11, a conversion detector 12, an energization sequence controller 13, a voltage ratio calculator 14, and an input pulse generator 15, and measured values of the voltages vR, vS, and vT of the AC power supply 1. vRs, vSs, and vTs are input, an input control ratio RI is calculated, and an input control pulse TI is generated and output.

The conversion detector 12 receives the section signal Sct and outputs the conversion signal TSc as 1 when the section signal Sct is converted.
The energization order controller 13 instructs the virtual DC voltage pole to be used by switching between the two phases of the AC power source 1 within the control period to change the order of use for each control period. An energization order signal Flg in which 0 and 1 appear alternately every control period is output. However, when the conversion signal TSc input to the energization sequence controller 13 is 1, the energization sequence signal of the next control period is output as 0 regardless of the energization sequence signal of the previous control period.

  The voltage ratio calculator 14 inputs the measured values vRs, vSs, vTs of the voltage vR, vS, vT of the AC power supply 1, the section signal Sct, the conversion signal TSc, and the energization sequence signal Flg, and sets the input control ratio RI in the control period. Calculate and output at each turn. Based on the section signal Sct, one is selected from the three voltage ratios vT / (vT + vR), vS / (vS + vT), and vR / (vR + vS) calculated from the measured voltage values vRs, vSs, and vTs of the AC power source 1. To calculate. Based on the energization sequence signal of the next control period output by the energization sequence controller 13, it is determined whether to use the calculated voltage ratio as it is or to use a value obtained by subtracting the calculated voltage ratio from 1. Output as the input control ratio RI. However, when the conversion signal TSc is 1, it is determined whether the input control ratio RI is set to 0 or a value obtained by subtracting the calculated voltage ratio from 1 by referring to the energization sequence signal of the previous control period. And the conversion signal TSc is set to 0.

  FIG. 9 is a flowchart showing the operation of the energization sequence controller according to Embodiment 1 of the present invention. In the figure, the same parts as those in FIG. When the pulse generation operation of the previous control period is completed in the input controller 10, the output controller 30, and the gate controller 40 (step ST10), the energization sequence controller 13 starts the energization sequence control operation B10. If the conversion signal TSc is 0 (step ST11), the energization order signal of the previous control period is inverted (step ST12), and if the conversion signal TSc is 0 as the energization order signal of the next control period, the previous The energization sequence signal for the next control period is set to 0 regardless of the energization sequence signal for the control period (step ST13). As a result, the energization order control operation B10 ends, and the end of the following voltage ratio selection operation B20 is awaited (step ST14).

  FIG. 10 is a flowchart showing the operation of the voltage ratio calculator according to the first embodiment of the present invention. In FIG. 10, the same or equivalent parts as in FIG. A description of the operation of ST27 is omitted. The operation of the calculator is performed by selecting a voltage ratio selection operation B20 for selecting and calculating one of three voltage ratio calculation expressions, and a voltage ratio output operation B30 for calculating and outputting RI from the calculated voltage ratio. Consists of stages.

The voltage ratio output operation B30 will be described. If the conversion signal TSc is 0 (step ST31), the operation is the same as the voltage ratio output operation B30u shown in FIG. 5 with reference to the energization order signal in the next control period. If the conversion signal TSc is 1, the energization sequence signal of the previous control period is referred to. If the energization sequence signal is 1 (step ST33), the input control ratio RI is output as 0 (step ST36). If the energization sequence signal is 0, a value obtained by subtracting the voltage ratio calculated in the voltage ratio selection operation B20 from 1 is output as the input control ratio RI (step ST37), and the conversion signal output from the conversion detector 12 is output. TSc is set to 1 to 0 (step ST38). Thus, by setting the input control ratio RI, the voltage ratio output operation B30 ends.
When the voltage ratio output operation B30 ends, the input control ratio RI is output to the input pulse generator 15 and the output controller 30, and the input control pulse TI and the output control pulses TU, TV, TW for the next control period are generated, respectively. The

  Next, the calculation result of the input control ratio RI output by the input controller 10, the output controller 30 and the gate controller 40 due to the fluctuation of the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10. , Section signal Sct, conversion signal TSc, energization order signal Flg, input control pulse TI, pulse width modulation result in output controller 30, output control pulse TU related to U phase, operation of switch control pulses TUR, TUS, TUT explain.

  The operation when the section signal Sct is 1 and not converted is the same as the operation example shown in FIG. 6, the switching operation of the nine switch control pulses is not performed at the change of the control period, and the section signal Sct is other than 1. Since it changes similarly even if it is a certain control period, description is abbreviate | omitted.

  FIG. 11 is a timing chart showing the operation of the multi-relative multi-phase power conversion device according to Embodiment 1 of the present invention. The calculation result of the input control ratio RI, the section signal Sct, the conversion signal TSc, the energization order signal Flg, the input control pulse TI, and the pulse from the output controller 30 output from the controller 10, the output controller 30 and the gate controller 40. It is another example of operation | movement of the output control pulse TU and switch control pulse TUR, TUS, TUT which concern on a width modulation result and a U phase. In this example, the voltage of the AC power supply 1 and the operation of the section signal Sct associated therewith are the same as the operation example shown in FIG. 7, but the conversion signal TSc becomes 1 with the conversion of the section signal Sct, and the energization sequence signal Flg This operation follows the energization order control operation B10 of the flowchart shown in FIG.

  The operation in the first control period Tc1 ′ is the same as the first control period Tc1u ′ in the operation example shown in FIG. The operation in the second control period Tc2 ′ will be described. Since the conversion signal TSc is 1 in the first control period Tc1 ′ in accordance with the energization order control operation B10 in the flowchart shown in FIG. 9, the energization order signal Flg is related to the energization order signal in the previous control period. It becomes zero. The input control ratio RI calculates vS / (vS + vT) according to the voltage ratio selection operation B20 of the flowchart shown in FIG. 10, but the conversion signal TSc is 1 before the voltage ratio output operation B30 of the flowchart shown in FIG. Since the energization order signal Flg in the control period is 1, the input control ratio RI is output as 0, and the conversion signal TSc output from the conversion detector 12 is set to 0.

  Regarding the input control pulse TI, the combination of phases of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage is generated to be the same as the operation example shown in FIG. Since the energization order signal Flg is 1 in the first control period Tc1 ′, the phase of the AC power supply 1 that the virtual positive voltage positive electrode uses at the end of the control period according to Table 1 is the R phase and the negative electrode is used. The phase of the alternating current power source 1 to be operated is the S phase. Since the energization order signal Flg is 0 in the second control period Tc2 ′, the phase of the AC power source 1 that the positive electrode of the virtual DC voltage uses at the start of the control period according to Table 1 is the T phase and the negative electrode is used. The phase of the AC power source 1 to be operated should be the S phase, but since the input control ratio RI during the control period is 0, the time for the positive electrode to use the T phase is 0, and is used after that. The R phase is used from the beginning of the control period. Therefore, at the transition from the first control period Tc1 ′ to the second control period Tc2 ′, the phase of the AC power supply 1 used by the positive electrode is the R phase, and the phase of the AC power supply 1 used by the negative electrode is the S phase. Each will be fixed.

  The shape indicated by the triangular carrier wave used for generating the output control pulses TU, TV, and TW is the same as that in the operation example of FIG. 7, but the input control ratio RI in the second control period Tc2 ′ is 0. In the control period, the first half of the triangular carrier wave that should show the shape of the “valley” disappears, and the sawtooth wave rises to the right. Accordingly, both the end of the first control period Tc1 ′ and the top of the first triangular carrier wave of the second control period Tc2 ′ are the lowest points, and the first control period Tc1 ′ to the second control period Tc2 ′. Since the apex of the triangular carrier does not move at the transition, all the output control pulses TU, TV, TW are not switched at the transition.

As a result, at the transition from the first control period Tc1 ′ to the second control period Tc2 ′, the input control pulse TI and the output control pulses TU, TV, TW are not switched at all. There will be no switching at all.
The above operation changes in the same manner even when the section is switched except when the section signal Sct is switched from 1 to 2.

  FIG. 12 is a timing chart showing the operation of the multi-relative multi-phase power conversion device according to Embodiment 1 of the present invention. The calculation result of the input control ratio RI, the section signal Sct, the conversion signal TSc, the energization order signal Flg, the input control pulse TI, and the pulse from the output controller 30 output from the controller 10, the output controller 30 and the gate controller 40. It is another example of operation | movement of the output control pulse TU and switch control pulse TUR, TUS, TUT which concern on a width modulation result and a U phase. In this example, the operation of the voltage of the AC power supply 1 and the operation of the section signal Sct and conversion signal TSc associated therewith are the same as the operation example shown in FIG. 11, but the energization sequence signal Flg in the first control period Tc1 ″. Is 0.

  The operation in the first control period Tc1 ″ is the same as the first control period Tc1u ″ in the operation example shown in FIG. The operation in the second control period Tc2 ″ will be described. The energization sequence signal Flg becomes 1 in the first control period Tc1 ″ in accordance with the energization sequence control operation B10 in the flowchart shown in FIG. Therefore, it becomes 0 regardless of the energization order signal of the previous control period. As for the input control ratio RI, vS / (vS + vT) is calculated according to the voltage ratio selection operation B20 of the flowchart shown in FIG. 10, and the conversion signal TSc is 1 before the voltage ratio output operation B30 of the flowchart shown in FIG. Since the energization order signal Flg in the control period is 0, a value obtained by subtracting the voltage ratio from 1 is output as the input control ratio RI, and the conversion signal TSc output from the conversion detector 12 is set to 0.

  The input control pulse TI is generated so that the combination of phases of the AC power source 1 used by the positive and negative electrodes of the virtual DC voltage is the same as the operation example shown in FIG. Since the energization sequence signal Flg is 0 in the first control period Tc1 ″, the phase of the AC power supply 1 that is used by the positive electrode of the virtual DC voltage at the end of the control period according to Table 1 is the T phase and the negative electrode is used. The phase of the alternating current power supply 1 is the S phase. Since the energization order signal Flg is 0 in the second control period Tc2 ″, the positive pole of the virtual DC voltage is used at the start of the control period according to Table 1. The phase of the AC power source 1 is the R phase, and the phase of the AC power source 1 used by the negative electrode is the T phase. Therefore, at the transition from the first control period Tc1 ″ to the second control period Tc2 ″, the phase of the AC power source 1 used by the positive electrode is switched from the T phase to the R phase, and the phase of the AC power source 1 used by the negative electrode is The S phase is switched to the T phase.

The shape indicated by the triangular carrier wave used for generating the output control pulses TU, TV, and TW is the same as that in the operation example shown in FIG. 8, and at the transition from the first control period Tc1 ″ to the second control period Tc2 ″. Since the operation of moving the apex of the triangular carrier wave from the lowest point to the highest point occurs, all the output control pulses TU, TV, TW are switched from 1 to 0 at the transition. However, as a result of combining with the switching operation of the input control pulse TI, the phase of the AC power source 1 to which all phases of the load 2 are connected is the positive electrode of the virtual DC voltage at the end of the first control period Tc1 ″. At the start of the T phase and the second control period Tc2 ″, the phase becomes a T phase which is a negative pole of a virtual DC voltage, and at the transition from the first control period Tc1 ″ to the second control period Tc2 ″, the load 2 The phase of the AC power supply 1 connected to the phase is not switched, and switching with nine switch control pulses is not performed at all.
The above operation changes in the same manner even when the section is switched except when the section signal Sct is switched from 1 to 2.

  As described above, according to the first embodiment, the AC power source 1 connected to the phase of the load 2 during the control period is the control period that is a basic time unit for controlling the multi-relative multi-phase power converter. The operation of switching the order of connecting the phases of the AC power supply 1 connected to the phase of the load 2 or the operation of setting the time for connecting the phase of a certain AC power supply 1 to 0 is used. Thus, the phase of the AC power supply 1 to which the phase of the load 2 is connected can be fixed before and after the change of the control period, so that switching of the switch control pulse can be prevented at all the changes of the control period. Thus, it is possible to prevent the switching operations of the switches related to the plurality of phases of the load 2 from occurring simultaneously.

Embodiment 2. FIG.
FIG. 13 is a block diagram showing a multi-relative multi-phase power converter according to Embodiment 2 of the present invention. In the input controller 10a shown in FIG. 13, the energization sequence controller 13u is connected to the phase load 2 of the AC power source 1. The voltage ratio computing unit 14a generates an energization sequence signal that defines the sequence to be performed. The voltage ratio calculator 14a generates an AC voltage from the AC power source 1, a section signal from the section detector 11, a conversion signal from the conversion detector 12, and Based on the order signal, an input control ratio and a holding signal are generated, and the input pulse generator 15 a performs section control by the section detector 11, energization order signal by the energization order controller 13, and input control by the voltage ratio calculator 14. Based on the ratio and the hold signal, an input control pulse is generated. Other configurations are the same as those in FIG.

Next, the operation will be described.
In the circuit shown in FIG. 1, the voltage ratio calculator 14 outputs the input control ratio RI and inputs it to the input pulse generator 15 and the output controller 30, but as shown in FIG. The voltage ratio calculator 14a may be configured to output the holding signal KSc together with the input control ratio RI and input it to the input pulse generator 15a and the output controller 30.

  In this configuration, when the phase of the load 2 matches the condition in which the phase of the AC power source 1 is connected in the control period in which the section is changed, the phase of the AC power source 1 to which the phase of the load 2 is connected in the control period. Is maintained until the next control period, so that the phase of the AC power source 1 used by the positive and negative electrodes of the virtual DC voltage is not switched at the transition to the next control period. It is possible to prevent the switching operation from occurring at the change of the period.

In FIG. 6, the same or corresponding parts as those in FIGS. 1 and 2 are denoted by the same reference numerals and description thereof is omitted.
The operation of the input controller 10a will be described. The input controller 10a includes a section detector 11, a conversion detector 12, an energization sequence controller 13u, a voltage ratio calculator 14a, and an input pulse generator 15a, and measured values of the voltages vR, vS, and vT of the AC power supply 1. vRs, vSs, and vTs are input, an input control ratio RI is calculated, and an input control pulse TI is generated and output.

  The voltage ratio calculator 14a receives the measurement values vRs, vSs, vTs of the voltages vR, vS, vT of the AC power supply 1, the section signal Stc, the conversion signal TSc, and the energization sequence signal Flg, and calculates and holds the input control ratio RI. The signal KSc is generated and output every change of the control period. The operation when the holding signal KSc is 0 and the conversion signal TSc is 0 is the same as the operation when the conversion signal TSc is 0 in the voltage ratio calculator 14 of FIG. When the conversion signal TSc is 1, it is determined whether the input control ratio RI is set to 0 or the value obtained by subtracting the input control ratio from the previous control period from 1 with reference to the energization sequence signal of the previous control period. In addition, the holding signal KSc is output as 1 with reference to the energization order signal, or the conversion signal TSc output from the conversion detector 12 is set to 0. If the holding signal KSc is 1 at the time when the voltage ratio calculator 14a starts calculation, the input control ratio RI is output as 0, and the holding signal KSc and the conversion signal TScc output by the conversion detector 12 are output. Both are set to 0.

The input pulse generator 15a receives the section signal Sct, the energization order signal Flg, the holding signal KSc, and the input control ratio RI, and generates an input control pulse TI. The operation of the generator in the control period in which the holding signal KSc is 0 is equivalent to the operation of the input pulse generator 15 in FIG.
The control period in which the holding signal KSc is 1 may appear only when the section signal Sct is changed in the control period before the control period. At this time, in terms of the operation of the generator in the control period, the input control is performed while the section signal Sct referred to by the input pulse generator 15a is maintained without being changed from that in the control period before the control period. A pulse TI is generated.

  FIG. 14 is a flowchart showing the operation of the voltage ratio calculator according to the second embodiment of the present invention. In FIG. 14, the same or corresponding parts as those in FIGS. Description of the operations of B20 and step ST26u is omitted. The operation of the voltage ratio calculator 14a includes a voltage ratio selection operation B20 for selecting and calculating one of three voltage ratio calculation expressions, and a voltage for calculating and outputting the input control ratio RI from the calculated voltage ratio. It is composed of two stages of ratio output operation B30a.

  The voltage ratio output operation B30a will be described. If the hold signal KSc is 0 at the start of the operation (step ST41), the operation shifts to an operation substantially equivalent to the voltage ratio output operation B30 in the flowchart shown in FIG. If the conversion signal TSc is 0 (step ST31), the operation is the same as the voltage ratio output operation B30u shown in FIG. 5 with reference to the energization sequence signal in the next control period. If the conversion signal TSc is 1, the energization sequence signal of the previous control period is referred to. If the energization sequence signal is 1 (step ST33), the input control ratio RI is set to 0 (step ST36), and the conversion is performed. The conversion signal TSc output from the detector 12 is changed from 1 to 0 (step ST38). If the energization order signal is 0, the value obtained by subtracting the input control ratio RI of the previous control period from 1 is the next control. The input control ratio RI for the period is output (step ST43), and the holding signal KSc is output as 1 (step ST44). If step ST44 has been performed in the voltage ratio output operation B30a immediately before the previous control period, since the holding signal KSc is 1 in the previous control period, the voltage ratio output immediately after the previous control period ends. In operation B30a, the hold signal KSc is set to 1 to 0 (step ST42), the input control ratio RI is set to 0, and the conversion signal TSc output from the conversion detector 12 is set to 1 to 0.

  When the voltage ratio output operation B30a ends, the input control ratio RI is output to the input pulse generator 15a and the output controller 30, and the input control pulse TI and the output control pulses TU, TV, TW for the next control period are generated, respectively. The

  Next, the calculation result of the input control ratio RI output by the input controller 10a, the output controller 30 and the gate controller 40 due to the fluctuations in the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10a. , Section signal Sct, conversion signal TSc, energization order signal Flg, holding signal KSc, input control pulse TI, pulse width modulation result in output controller 30, output control pulse TU relating to U phase, switch control pulses TUR, TUS, The operation of the TUT will be described.

  The operation when the section signal Sct is 1 and is not converted is the same as the operation example of FIG. 1, and the switching operation of the nine switch control pulses is not performed at the change of the control period, and the control period when the section signal Sct is other than 1. However, since it changes similarly, description is abbreviate | omitted. The operation when the section signal Sct is changed from 1 to 2 and the energization order signal Flg in the control period at the time of the change is 1 is the holding signal KSc according to the voltage ratio output operation B30a of the flowchart shown in FIG. Since it remains 0, the operations of the energization sequence signal Flg, the input control ratio RI, and the output control pulses TU, TV, and TW in the control period and the next control period are the same as the operation example shown in FIG. Therefore, at this time, the switching operation of the nine switch control pulses is not performed at the change of the control period, and the transition is the same even in the section switching other than when the section signal Sct is switched from 1 to 2. The description is omitted.

FIG. 15 is a timing showing the operation of the multi-relative multi-phase power converter according to Embodiment 2 of the present invention. In FIG. 15, the fluctuations in the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10a The calculation result of the input control ratio RI, the section signal Sct, the conversion signal TSc, the energization sequence signal Flg, the holding signal KSc, the input control pulse TI, and the output, which are output from the input controller 10a, the output controller 30 and the gate controller 40 It is an example of the operation | movement of the output control pulse TU concerning U phase, switch control pulse TUR, TUS, TUT concerning the pulse width modulation result in the controller 30. In this example, the operation of the voltage of the AC power supply 1 and the operation of the section signal Sct and conversion signal TSc associated therewith are the same as the operation example shown in FIG. 12, and the energization sequence signal Flg in the first control period Tc1a ″. Is 0.
The operation in the first control period Tc1a ″ is the same as the first control period Tc1 ″ in the operation example shown in FIG.

  An operation in the second control period Tc2a ″ and the third control period Tc3a ″ will be described. The energization order signal Flg is 1 in the first control period Tc1a ″ and is inverted to 0 in the second control period Tc2a ″ according to the energization order control operation B10u of the flowchart shown in FIG. The period Tc3a ″ is inverted again to become 1. The input control ratio RI is vS in both the second control period Tc2a ″ and the third control period Tc3a ″ in accordance with the voltage ratio selection operation B20 in the flowchart shown in FIG. / (VS + vT) is calculated, but according to the voltage ratio output operation B30a of the flowchart of FIG. Since Flg is 0, the value obtained by subtracting the input control ratio in the previous control period from 1 is output as the input control ratio RI, and the holding signal KSc is output as 1. In the third control period Tc3a ″, since the holding signal KSc is set to 1 in the voltage ratio output operation B30a immediately before the previous control period, the holding signal KSc is output as 0 and the input control ratio RI is set as 0, respectively. The conversion signal TSc output from the detector 12 is set to zero.

  The input control pulse TI is generated such that the combination of phases of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage is the same as the operation example shown in FIG. Since the holding signal KSc is 1 in the second control period Tc2a ″, the section signal Sct referred to by the input pulse generator 15a becomes 1 which is the section signal of the previous control period, and the control period before the control period Since the energization sequence signal Flg is inverted from the first control period Tc1a ″ to the second control period Tc2a ″, switching of the input control pulse TI occurs as in the operation example shown in FIG. In the second control period Tc2a ″, the energization sequence signal Flg is 1 with reference to 1 which is the section signal of the previous control period, so that the virtual DC voltage at the end of the control period according to Table 1 The phase of the AC power source 1 used by the positive electrode is the R phase, and the phase of the AC power source 1 used by the negative electrode is the S phase. In the third control period Tc3a ″, the hold signal KSc becomes 0, the section signal Sct referred to by the input pulse generator 15a becomes 2, and the energization order signal Flg is 0. Therefore, the control period starts according to Table 1. Sometimes the phase of the AC power supply 1 used by the positive electrode of the virtual DC voltage is the T phase, and the phase of the AC power supply 1 used by the negative electrode is the S phase, but the input control ratio RI is 0. 11, the triangular carrier wave in the control period becomes a sawtooth wave rising to the right. Therefore, the operation at the transition from the second control period Tc2a ″ to the third control period Tc3a ″ is also shown in FIG. This is the same as the operation example shown in FIG.

  The shape indicated by the triangular carrier wave used for generating the output control pulses TU, TV, TW is the same as that of the operation example shown in FIG. 11, and the output control pulses TU, TV, TW are output from the first control period Tc1a ″ to the second. The change to the control period Tc2a ″ is the same as the operation example shown in FIG. 6, and the change from the second control period Tc2a ″ to the third control period Tc3a ″ is the same as the operation example shown in FIG. For this reason, switching is not performed at all transitions of the control period.

As a result, the input control pulse TI and the output control pulses TU, TV, and TW are not switched at all changes in the control period of the operation example shown in FIG. 15, and therefore switching with nine switch control pulses is not performed at all. Will not be done.
The above operation changes in the same manner even when the section is switched except when the section signal Sct is switched from 1 to 2.

  As described above, according to the second embodiment, the AC power source 1 connected to the phase of the load 2 during the control period is the control period, which is a basic time unit for controlling the multi-relative multi-phase power converter. The phase of the AC power supply 1 to which the phase of the load 2 is connected can be changed in a certain control period, and the operation for setting the time for connecting the phase of the AC power supply 1 to 0 can be used. By doing so, the phase of the AC power source 1 to which the phase of the load 2 is connected can be fixed before and after the change of the control period, so that the switch control pulse is not switched at all the changes of the control period. Thus, it is possible to prevent the switching operations of the switches related to a plurality of phases of the load 2 from occurring simultaneously.

Embodiment 3 FIG.
FIG. 16 is a block diagram showing a multi-relative multi-phase power converter according to Embodiment 3 of the present invention. In the input controller 10b shown in FIG. 16, the voltage ratio calculator 14b is an AC voltage / section detector of the AC power source 1. The input control ratio and the holding signal are generated based on the section signal by 11, the conversion signal by the conversion detector 12, and the energization sequence signal by the energization sequence controller 13. Other configurations are the same as those in FIG. 1 or FIG.

Next, the operation will be described.
In the circuit shown in FIG. 1, the voltage ratio calculator 14 outputs the input control ratio RI and inputs it to the input pulse generator 15 and the output controller 30, but as shown in FIG. The voltage ratio calculator 14a may be configured to output the holding signal KSc together with the input control ratio RI and input it to the input pulse generator 15a and the output controller 30.

In this configuration, when the phase of the load 2 matches the condition in which the phase of the AC power source 1 is connected in the control period in which the section is changed, the phase of the AC power source 1 to which the phase of the load 2 is connected in the control period. Is held until the next control period, the phase of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage at the transition to the next control period, and pulse width modulation By combining the switching of the pulse signal by the control, it is possible to prevent the switching operation from occurring at the change of the control period.
In FIG. 16, the same or corresponding parts as those in FIGS. 1 and 13 are denoted by the same reference numerals and description thereof is omitted.

  The operation of the input controller 10b will be described. The input controller 10b includes a section detector 11, a conversion detector 12, an energization sequence controller 13, a voltage ratio calculator 14b, and an input pulse generator 15a, and measures the voltages vR, vS, and vT of the AC power supply 1. The values vRs, vSs, and vTs are input, the input control ratio RI is calculated, and the input control pulse TI is generated and output.

  The voltage ratio calculator 14b receives the measured values vRs, vSs, vTs, the section signal Sct, the conversion signal TSc, and the energization sequence signal Flg of the voltages vR, vS, vT of the AC power supply 1, and calculates and holds the input control ratio RI. The signal KSc is generated and output every change of the control period. The operation when the holding signal KSc is 0 and the conversion signal TSc is 0 is the same as the operation when the conversion signal TSc is 0 in the voltage ratio calculator 14 shown in FIG. When the conversion signal TSc is 1, referring to the energization sequence signal of the previous control period, use a value obtained by subtracting the calculated voltage ratio from 1 or a value obtained by subtracting the input control ratio of the previous control period from 1. It is determined whether to use it, and this is output as the input control ratio RI. Also, the holding signal KSc is output as 1 with reference to the energization sequence signal, or the conversion signal TSc output from the conversion detector 12 is set to 0. And If the holding signal KSc is 1 at the time when the voltage ratio calculator 14b starts the calculation, a value obtained by subtracting the calculated voltage ratio from 1 is output as the input control ratio RI, and the holding signal KSc and the change detection are output. Both conversion signals TSc output from the device 12 are set to zero.

  FIG. 17 is a flowchart showing the operation of the voltage ratio calculator according to the third embodiment of the present invention. In FIG. 17, the same or corresponding parts as those in FIGS. Description of the operations of B20 and step ST26u is omitted. The operation of the voltage ratio calculator 14b includes a voltage ratio selection operation B20 for selecting and calculating one of three voltage ratio calculation expressions, and a voltage for calculating and outputting the input control ratio RI from the calculated voltage ratio. It consists of two stages of ratio output operation B30b.

  The voltage ratio output operation B30b will be described. If the hold signal KSc is 0 at the start of the operation (step ST41), the operation shifts to an operation substantially equivalent to the voltage ratio output operation B30 in the flowchart shown in FIG. If the conversion signal TSc is 0 (step ST31), the operation is the same as the voltage ratio output operation B30u shown in FIG. 5 with reference to the energization sequence signal in the next control period. A value obtained by subtracting the input control ratio RI of the previous control period from 1 if the turn-on signal TSc is 1 with reference to the energization order signal of the previous control period and if the energization order signal is 1 (step ST33). Is output as the input control ratio RI for the next control period (step ST43), the holding signal KSc is output as 1 (step ST44), and if the energization sequence signal is 0, the voltage calculated in the voltage ratio selection operation B20 A value obtained by subtracting the ratio from 1 is output as the input control ratio RI (step ST36), and the conversion signal TSc output from the conversion detector 12 is changed from 1 to 0 (step ST38). If the voltage ratio output operation B30b immediately before the previous control period has undergone step ST44, since the holding signal KSc is 1 in the previous control period, the voltage ratio output immediately after the previous control period ends. In the operation B30b, the holding signal KSc is changed from 1 to 0 (step ST42), the value obtained by subtracting the voltage ratio calculated in the voltage ratio selection operation B20 from 1 is output as the input control ratio RI, and the conversion detector 12 outputs it. The converted signal TSc is changed from 1 to 0.

  When the voltage ratio output operation B30b ends, the input control ratio RI is output to the input pulse generator 15a and the output controller 30, and the input control pulse TI and the output control pulses TU, TV, TW for the next control period are generated, respectively. The

  Next, the calculation result of the input control ratio RI output by the input controller 10b, the output controller 30 and the gate controller 40 due to the fluctuation of the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10b. , Section signal Sct, conversion signal TSc, energization order signal Flg, holding signal KSc, input control pulse TI, pulse width modulation result in output controller 30, output control pulse TU relating to U phase, switch control pulses TUR, TUS, The operation of the TUT will be described.

  The operation when the section signal Sct is 1 and is not converted is the same as the operation example shown in FIG. Since it changes similarly even if it is a certain control period, description is abbreviate | omitted.

  The operation when the section signal Sct is changed from 1 to 2 and the energization order signal Flg in the control period at the time of the change is 0 is the holding signal KSc according to the voltage ratio output operation B30b of the flowchart shown in FIG. Since it remains 0, the operations of the energization sequence signal Flg, the input control ratio RI, and the output control pulses TU, TV, TW in the control period and the next control period are the same as the operation example shown in FIG. Therefore, at this time, the switching operation of the nine switch control pulses is not performed at the change of the control period, and the transition is the same even in the section switching other than when the section signal Sct is switched from 1 to 2. The description is omitted.

  FIG. 18 is a timing chart showing the operation of the multi-relative multi-phase power converter according to Embodiment 3 of the present invention. In FIG. The calculation result of the input control ratio RI, the section signal Sct, the conversion signal TSc, the energization sequence signal Flg, the holding signal KSc, the input control pulse TI, and the output, which are output from the input controller 10b, the output controller 30 and the gate controller 40. It is an example of the operation | movement of the output control pulse TU and switch control pulse TUR, TUS, TUT which concern on the pulse width modulation result in the controller 30, and a U phase. In this example, the operation of the voltage of the AC power supply 1 and the operation of the section signal Sct and conversion signal TSc associated therewith are the same as the operation example shown in FIG. 11, and the energization sequence signal Flg in the first control period Tc1b ′ is It is 1.

The operation in the first control period Tc1b ′ is the same as that in the first control period Tc1 ′ in the operation example shown in FIG.
An operation in the second control period Tc2b ′ and the third control period Tc3b ′ will be described. Since the conversion signal TSc is 1 in the first control period Tc1b ′ in accordance with the energization order control operation B10 in the flowchart shown in FIG. 9, the energization order signal Flg is related to the energization order signal in the previous control period. Furthermore, even in the third control period Tc3b ′, the conversion signal TSc remains 1 in the previous control period, and therefore becomes 0 regardless of the energization order signal in the previous control period.

  The input control ratio RI calculates vS / (vS + vT) in the second control period Tc2b ′ and the third control period Tc3b ′ according to the voltage ratio selection operation B20 of the flowchart shown in FIG. According to the voltage ratio output operation B30a of the flowchart shown in the figure, since the holding signal KSc is 0 and the conversion signal TSc is 1 in the second control period Tc2b ′, the energization order signal Flg in the previous control period is 1, A value obtained by subtracting the input control ratio of 1 in the control period from 1 is output as the input control ratio RI, the holding signal KSc is output as 1, and the voltage ratio output operation immediately before the previous control period is output in the third control period Tc3b ′. Since the hold signal KSc is set to 1 in 30b, the hold signal KSc is set to 0, and the value obtained by subtracting the voltage ratio calculated in the voltage ratio selection operation B20 from 1 is set as the input control ratio R. And output as a converted signal TSc the conversion detector 12 outputs a zero.

  The input control pulse TI is generated so that the combination of phases of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage is the same as the operation example shown in FIG. Since the holding signal KSc is 1 in the second control period Tc2b ′, the section signal Sct referred to by the input pulse generator 15a becomes 1 which is the section signal of the previous control period, and the control period before the control period Since the energization sequence signal Flg is inverted from the first control period Tc1b ′ to the second control period Tc2b ′, the switching of the input control pulse TI is performed as in the operation example shown in FIG. Does not occur. In the second control period Tc2b ′, the energization order signal Flg is 0 with reference to 1 which is the section signal of the previous control period. Therefore, according to Table 1, the positive polarity of the virtual DC voltage at the end of the control period The phase of the alternating current power supply 1 used by is the T phase, and the phase of the alternating current power supply 1 used by the negative electrode is the S phase. In the third control period Tc3b ′, the holding signal KSc becomes 0, the section signal Sct referred to by the input pulse generator 15a becomes 2, and the energization order signal Flg is 0. Therefore, the control period starts according to Table 1. Sometimes the phase of the AC power supply 1 used by the positive electrode of the virtual DC voltage is the R phase, and the phase of the AC power supply 1 used by the negative electrode is the T phase. Therefore, the operation at the transition from the second control period Tc2b ′ to the third control period Tc3b ′ is the same as the operation example shown in FIG.

The shape indicated by the triangular carrier wave used for generating the output control pulses TU, TV, and TW is the same as that in the operation example shown in FIG. 12, and the output control pulses TU, TV, and TW are generated from the first control period Tc1b ′. The change to the second control period Tc2b ′ is the same as the operation example shown in FIG. 6, and thus the change is not performed. At the change from the second control period Tc2b ′ to the third control period Tc3b ′, FIG. Since this is the same as the operation example shown in FIG. 12, the change is made from 1 to 0 at the change. However, the result of combining with the switching operation of the input control pulse TI is the same as the operation example shown in FIG. 12, and as a result, the phase of the load 2 is changed at all the transitions of the control period of the operation example shown in FIG. The phase of the connected AC power supply 1 is not switched, and switching with nine switch control pulses is not performed at all.
The above operation changes in the same manner even when the section is switched except when the section signal Sct is switched from 1 to 2.

  As described above, according to the third embodiment, the AC power source 1 connected to the phase of the load 2 during the control period is the control period, which is a basic time unit for controlling the multi-relative multi-phase power converter. The phase combination of the AC power supply 1 connected to the phase of the load 2 is changed by changing the combination of the phases of the AC power supply 1 connected to the phase of the load 2 in a certain control period. By making the operation available, the phase of the AC power source 1 to which the phase of the load 2 is connected can be fixed before and after the change of the control period, so that the switch control pulse can be switched at all the changes of the control period. It is possible to prevent the switching operation of the switches related to the plurality of phases of the load 2 from occurring simultaneously.

Embodiment 4 FIG.
FIG. 19 is a block diagram showing a multi-relative multi-phase power converter according to Embodiment 4 of the present invention. In the figure, the input controller 10c is an AC connected to the load 2 based on the AC voltage of the AC power source 1. An input control pulse for temporally determining the phase of the power supply 1 is generated.
In the input controller 10c, the section detector 11c is based on the AC voltage of the AC power supply 1 and in which phase section the phase of the AC voltage of the AC power supply 1 is divided into 60 degrees each. An intermediate section signal indicating whether or not there is generated. The conversion detector 12c has a first intermediate conversion signal indicating that the intermediate section signal has been converted from an even value to an odd value based on the intermediate section signal from the section detector 11c, and the intermediate section signal has an odd value to an even value. A second intermediate conversion signal indicating that the signal has been converted to is generated. The input pulse generator 15c generates an input control pulse based on the intermediate section signal from the section detector 11c and the first intermediate conversion signal and the second intermediate conversion signal from the conversion detector 12c.
The output controller 30 c generates an output control pulse that temporally determines the phase of the load 2 connected to the AC power supply 1 based on the voltage command value by the voltage commander 20. Other configurations are the same as those in FIG.

Next, the operation will be described.
In the circuit shown in FIG. 1, the section detector 11 outputs the section signal Sct, the conversion detector 12 outputs the conversion signal TSc, and inputs the conversion signal TSc to the input pulse generator 15. The input pulse generator 15 An output control pulse TI is output based on the Sct, energization sequence signal Flg and the input control ratio RI, and the output controller 30 outputs the output control pulse based on the voltage command values vU ^* , vV ^* , vW ^* and the input control ratio RI. As shown in FIG. 19, the section detector 11c outputs the intermediate section signal Scm, and the conversion detector 12c outputs the first intermediate conversion signal TSm1 and the second intermediate conversion signal TSm2. Are input to the input pulse generator 15c, and the input pulse generator 15c receives the intermediate section signal Scm and the first intermediate And it outputs the input control pulse TI on the basis of the signal TSm1 and second intermediate conversion signal TSm2, output controller 30c voltage command value vU ^*, vV ^*, vW ^* output control pulse TU based on, TV, a TW output You may comprise so that it may do.

  In this configuration, when generating an input control pulse that does not switch the phase of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage within one control period, the phase of the load 2 is controlled by pulse width modulation control. When the intermediate section is switched, the phase of the AC power supply 1 to which the phase of the load 2 is connected is switched for a certain time when the virtual section is connected to the positive and negative electrodes of the virtual DC voltage. By delaying, the switching of the phase of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage and the switching of the pulse signal by the pulse width modulation control are combined at the transition of the control period immediately after the intermediate section is changed. Thus, the switching operation can be prevented from occurring at the change of the control period.

In FIG. 19, the same or corresponding parts as in FIG.
The output controller 30c generates output control pulses TU, TV, TW synchronized with the control period of the input controller 10c based on the voltage command values vU ^* , vV ^* , vW ^* obtained from the voltage commander 20. Output.
When pulse width modulation control using a triangular carrier wave is performed by the output controller 30c, either a triangular carrier wave having a “peak” shape in the control period or a triangular carrier wave having a “valley” shape in the control period is used. May be. The time at which the peak of the middle of the control period is taken may be any time within the control period, but as an example here, the time when the time corresponding to one half of the control period Tc has elapsed since the start of the control period, To do.

  The operation of the input controller 10c will be described. The input controller 10c includes a section detector 11c, a conversion detector 12c, and an input pulse generator 15c. RI is calculated to generate an input control pulse TI and output it.

  The section detector 11c receives the measured values vRs, vSs, vTs of the voltages vR, vS, vT, detects which intermediate section the phase of the AC power supply 1 is in, and outputs an intermediate section signal Scm. The conversion detector 12c receives the intermediate section signal Scm, and when the signal is converted from the even value to the odd value, the first intermediate conversion signal TSm1 is set to 1, and the signal is converted from the odd value to the even value. Sometimes the second intermediate conversion signal TSm2 is set to 1 and output.

  The input pulse generator 15c receives the intermediate section signal Scm, the first intermediate conversion signal TSm1, and the second intermediate conversion signal TSm2, and generates an input control pulse TI. Based on the intermediate section signal Scm, an input control pulse TI that is always set to 1 within the control period and one that is always set to 0 within the control period is determined. The operation for collectively determining the waveform of the input control pulse TI in one control period at the start of the control time is the same as that of the input pulse generator 15 in FIG.

  As a signal for instructing to hold the input control pulse TI of the previous control period for a certain time after the change of the control period, the first intermediate when the shape of the triangular carrier wave in the control period is “mountain” When the shape of the triangular carrier wave in the control period is “valley”, the second intermediate conversion signal TSm2 is selected for the conversion signal TSm1. When the selected intermediate conversion signal is 1, until the time corresponding to one half of the control period Tc elapses from the start of the next control period, The input control pulse TI in the control period is held in the next control period.

  FIG. 20 is a timing chart showing the operation of the section detector according to the fourth embodiment of the present invention. In the figure, fluctuations in the voltages vR, vS, vT of the AC power supply 1 and the intermediate section signal output by the section detector 11c are shown. The correspondence with Scm is shown. Comparison is made for all three combinations of two selected from the voltages vR, vS, and vT of the AC power supply 1, and the combination of the three magnitude relationships changes every 60 degrees of AC power supply phase, so section detection The device 11c operates to determine and output the intermediate section signal Scm according to the combination.

Table 2 shows the phases of the AC power supply 1 respectively used by the positive and negative electrodes of the virtual DC voltage corresponding to the intermediate section signal Scm. The correspondence relationship of Table 2 uses the maximum positive voltage that appears as a virtual DC voltage among the six combinations of phases of the AC power supply 1 that can be used as a virtual DC voltage in each section. Means that. As an example, when the intermediate section signal Scm is 1, the positive phase of the virtual DC voltage always uses the R phase of the AC power supply 1 and the negative polarity always uses the S phase of the AC power supply 1 in the control period.
The input pulse generator 15c generates an input control pulse TI based on the intermediate section signal Scm according to the correspondence relationship in FIG. 20 and Table 2.

  Next, the intermediate section signal Scm, the first output from the input controller 10c, the output controller 30c, and the gate controller 40 due to the fluctuations in the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10c. The operation of the intermediate conversion signal TSm1, the second intermediate conversion signal TSm2, the input control pulse TI, the pulse width modulation result in the output controller 30c, the output control pulse TU related to the U phase, and the switch control pulses TUR, TUS, TUT will be described. .

  Regarding the operation when the intermediate section signal Scm is 1 and does not change, the input control pulse TI is the AC phase of the AC power source 1 used by the positive pole of the virtual DC voltage according to Table 2 and the AC phase used by the negative pole. The phase of the power source 1 is generated so as to be fixed to the S phase, and the output control pulses TU, TV, TW are generated using a triangular carrier wave that is not switched at the change of the control period. As a result, since the input control pulse TI and the output control pulses TU, TV, and TW are not switched at the change of the control period, the switching with the nine switch control pulses is not performed at all. Even in the control period in which Sct is other than 1, the same transition occurs.

  FIG. 21 is a timing chart showing the operation of the multi-relative multi-phase power converter according to Embodiment 4 of the present invention. In the figure, depending on the fluctuations in the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10c. The intermediate section signal Scm, the second intermediate conversion signal TSm1, the second intermediate conversion signal TSm2, the input control pulse TI, and the output controller 30c output from the input controller 10c, the output controller 30c, and the gate controller 40. It is an example of operation | movement of the output control pulse TU and switch control pulse TUR, TUS, TUT which concern on a pulse width modulation result and a U phase. In this example, the pulse width modulation control in the output controller 30c is based on a triangular carrier wave indicating the shape of a “mountain”, and the input pulse generator 15c is the next when the second intermediate conversion signal TSm1 becomes 1. The input control pulse TI of the control period before the next control period is held in the next control period until the time corresponding to one half of the control period Tc elapses from the start of the control period. And As for the voltage of the AC power supply 1 in this example, the magnitude relationship between vT and vS is reversed in the first control period Tc1c ′, and at the same time, the intermediate section signal Scm is changed from 1 to 2, The intermediate conversion signal TSm2 is 1.

An operation in the first control period Tc1c ′ and the second control period Tc2c ′ will be described.
Regarding the input control pulse TI, since the intermediate section signal Scm is 1 in the first control period Tc1c ′, the phase of the AC power supply 1 used as the positive electrode of the virtual DC voltage is used as the R phase and as the negative electrode. Since the phase of the AC power supply 1 is fixed to the S phase, and the intermediate section signal Scm is 2 in the second control period Tc2c ′, the phase of the AC power supply 1 used as the positive electrode of the virtual DC voltage is R. The phase of the AC power source 1 used as the negative electrode is fixed to the T phase. Therefore, at the transition from the first control period Tc1c ′ to the second control period Tc2c ′, the phase of the AC power source 1 used by the positive electrode is fixed to the R phase, but the phase of the AC power source 1 used by the negative electrode is The S phase is switched to the T phase.

  The triangular carrier wave used for generating the output control pulses TU, TV, TW shows a “mountain” shape. Therefore, at the transition from the first control period Tc1c ′ to the second control period Tc2c ′, the apex of the triangular carrier wave is the lowest point, and all output control pulses TU, TV, TW become 1 at the transition. As a result, the phase of the AC power source 1 to which all phases of the load 2 are connected is the positive polarity of the virtual DC voltage at the end of the first control period Tc1c ′ and at the start of the second control period Tc2c ′. The phase of the AC power source 1 connected to the phase of the load 2 is not switched at the change point, and switching with nine switch control pulses is not performed.

  The above operation is performed in the intermediate section in which the second intermediate conversion signal TSm2 becomes 1, except when the intermediate section signal Scm changes from 1 to 2, that is, the intermediate section signal Scm changes from 3 to 4 or 5 to 6 Even when switching to, the same trend occurs.

  FIG. 22 is a timing chart showing the operation of the multi-relative multi-phase power converter according to Embodiment 4 of the present invention. In the figure, the fluctuations in the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10c are shown. The intermediate section signal Scm, the first intermediate conversion signal TSm1, the second intermediate conversion signal TSm2, the input control pulse TI, and the output controller 30c output from the input controller 10c, the output controller 30c, and the gate controller 40. It is another example of operation | movement of the output control pulse TU and switch control pulse TUR, TUS, TUT which concern on a pulse width modulation result and a U phase. In this example, the magnitude relation between vR and vS is reversed in the first control period Tc1c ″ with respect to the voltage of the AC power supply 1, and at the same time, the intermediate section signal Scm is changed from 2 to 3, The signal TSm1 is 1.

The operation in the first control period Tc1c ″ and the second control period Tc2c ″ will be described.
Regarding the input control pulse TI, since the intermediate section signal Scm is 2 in the first control period Tc1c ″, the phase of the AC power supply 1 used as the positive electrode of the virtual DC voltage is used as the R phase and as the negative electrode. Since the phase of the AC power source 1 is fixed to the T phase, and the intermediate section signal Scm is 3 in the second control period Tc2c ″, the phase of the AC power source 1 used as the positive electrode of the virtual DC voltage is S. The phase of the AC power source 1 used as the negative electrode is fixed to the T phase. Here, since the first intermediate conversion signal TSm1 is 1 in the first control period Tc1c ″, the input pulse generator 15c is in the second control period Tc2c ″ which is the control period next to the control period. The input control pulse TI of the first control period Tc1c ″ that is the previous control period is held and output until the time when one half of the control period Tc has elapsed from the start of the control period. At the transition from the first control period Tc1c ″ to the second control period Tc2c ″, the phase of the AC power source 1 used by the positive electrode is fixed to the R phase, and the phase of the AC power source 1 used by the negative electrode is fixed to the T phase. The phase of the AC power supply 1 used at the positive electrode is switched from the R phase to the S phase at a time intermediate the control period Tc2c ″.

  The triangular carrier wave used for generating the output control pulses TU, TV, TW shows a “mountain” shape. Therefore, at the transition from the first control period Tc1c ″ to the second control period Tc2c ″, the apex of the triangular carrier wave is the lowest point, and at the middle time of the second control period Tc2c ″, all output control is performed. The pulse TU, TV, TW becomes 1 at the transition and becomes 0 at the intermediate time, so that the phase of the AC power supply 1 to which all phases of the load 2 are connected is at the end of the first control period Tc1c ″. And at the start of the second control period Tc2c ″, both become the R phase that is the positive pole of the virtual DC voltage, and before and after the intermediate time, both become the T phase that is the negative pole of the virtual DC voltage. The phase of the AC power source 1 connected to the phase of the load 2 is not switched at the change point and the intermediate time, and the switching with nine switch control pulses is not performed.

  The above operation is performed in the intermediate section in which the first intermediate conversion signal TSm1 becomes 1, except when the intermediate section signal Scm changes from 2 to 3, that is, the intermediate section signal Scm changes from 4 to 5, or 6 to 1. Even when switching to, the same trend occurs.

  Further, the pulse width modulation control in the output controller 30c is based on a triangular carrier wave having a “valley” shape, and when the input pulse generator 15c has the second intermediate conversion signal TSm2 set to 1, The input control pulse TI of the control period before the next control period is held in the next control period until the time corresponding to one half of the control period Tc elapses from the start of the next control period. Even if it is, the operation when the intermediate section signal Scm is changed is the same as the operation example shown in FIGS.

  As described above, according to the fourth embodiment, the time for switching the phase of the AC power supply 1 to which the phase of the load 2 is connected in the control period that is the basic time unit for controlling the multi-relative multi-phase power converter. Since the phase of the AC power source 1 to which the phase of the load 2 is connected can be fixed before and after the change of the control period, all the changes of the control period can be fixed. Thus, it is possible to prevent switching of the switch control pulses and to prevent the switching operations of the switches related to the plurality of phases of the load 2 from occurring simultaneously.

Embodiment 5. FIG.
FIG. 23 is a block diagram showing a multi-relative multi-phase power converter according to Embodiment 5 of the present invention. In the input controller 10c shown in FIG. 23, the section detector 11d is based on the AC voltage of the AC power source 1. A section signal indicating which phase section the AC voltage phase of the power supply 1 is in a phase section in which the phase of the AC power supply 1 is divided into 60 degrees, and the phase of the AC power supply 1 is divided into 60 degrees in different divisions The intermediate section signal indicating which phase section is the phase section is generated. The conversion detector 12d generates an intermediate conversion signal indicating that the intermediate section signal has been converted based on the intermediate section signal from the section detector 11d. The voltage ratio calculator 14d generates an input control ratio based on the AC voltage of the AC power supply 1, the section signal by the section detector 11d, the intermediate section signal, and the intermediate conversion signal by the conversion detector 12d. The input pulse generator 15d generates an input control pulse based on the section signal by the section detector 11d, the intermediate section signal, the intermediate conversion signal by the conversion detector 12d, and the input control ratio by the voltage ratio calculator 14d. is there. Other configurations are the same as those in FIG.

Next, the operation will be described.
In the circuit shown in FIG. 1, the section detector 11 outputs the section signal Sct and the conversion detector 12 outputs the conversion signal TSc and inputs them to the voltage ratio calculator 14 and the input pulse generator 15 to calculate the voltage ratio. The generator 14 calculates the input control ratio RI based on the measured values vRs, vSs, vTs of the voltages vR, vS, vT of the AC power supply 1, the section signal Sct, the conversion signal TSc, and the energization sequence signal Flg, and generates an input pulse. The device 15 is configured to output the input control pulse TI based on the section signal Sct, the energization order signal Flg, and the input control ratio RI. However, as shown in FIG. 23, the section detector 11d includes the section signal Sct and The intermediate section signal Scm is output by the conversion detector 12d and the intermediate conversion signal TSm is output. Then, the voltage ratio calculator 14d receives the measured values vRs, vSs, vTs of the AC power supply 1, the section signal Sct, the intermediate section signal Scm, and the intermediate conversion signal TSm. And the input pulse generator 15d is configured to output the input control pulse TI based on the section signal Sct, the intermediate section signal Scm, the intermediate conversion signal TSm, and the input control ratio RI. You may do it.

  In this configuration, when one control period is composed of two modulation periods and pulse width modulation control using a triangular carrier wave is performed in each modulation period, a certain control period is composed of only one modulation period, and 1 By reversing the order in which the positive and negative electrodes of the virtual DC voltage use the phases of the AC power supply 1 in one modulation period, the positive and negative electrodes of the virtual DC voltage at the transition of the control period immediately after the section is changed By combining the switching of the phase of the AC power supply 1 and the switching of the output control pulse, respectively, the switching operation can be prevented from occurring at the change of the control period.

In FIG. 23, the same or corresponding parts as in FIG.
The operation of the input controller 10d will be described. The input controller 10d is composed of a section detector 11d, a conversion detector 12d, a voltage ratio calculator 14d, and an input pulse generator 15d, and the measured values vRs, vSs, vTs of the voltages vR, vS, vT of the AC power supply 1 are obtained. Input, calculate the input control ratio RI, generate the input control pulse TI, and output each.

  The section detector 11d receives the measured values vRs, vSs, and vTs of the voltages vR, vS, and vT, detects in which section and the intermediate section the phase of the AC power supply is in accordance with FIG. 3 and FIG. Sct and intermediate section signal Scm are output.

The conversion detector 12d receives the intermediate section signal Scm and outputs the intermediate conversion signal TSm as 1 when it is converted.
The voltage ratio calculator 14d receives the measured values vRs, vSs, vTs, the section signal Sct, the intermediate section signal Scm, and the intermediate conversion signal TSm of the voltages vR, vS, vT of the AC power supply 1, and inputs the input control ratio RI in the control period. Calculate and output at each turn. Based on the section signal Sct from the three voltage ratios vT / (vT + vR), vS / (vS + vR), vR / (vR + vS) calculated from the measured values vRs, vSs, vTs of the voltage vR, vS, vT of the AC power supply 1. Select one to calculate. Based on the result of comparing the intermediate section signal Scm with the section signal, it is determined whether to use the calculated voltage ratio as it is or to use a value obtained by subtracting the calculated voltage ratio from 1, and output this as the input control ratio RI To do. However, when the intermediate conversion signal TSm is 1, a value obtained by subtracting the calculated voltage ratio from 1 regardless of the intermediate section signal Scm is output as the input control ratio RI.

  The input pulse generator 15d receives the section signal Sct, the intermediate section signal Scm, the intermediate conversion signal TSm, and the input control ratio RI, and generates an input control pulse TI. Based on the section signal Sct, among the input control pulses TI, one that is always set to 1 within the control period, one that is always set to 0 within the control period, and one that is switched within the control period are determined, respectively. Based on the result of comparing the section signal Scm with the section signal, the switching is performed within the control period, and the switching is switched from 1 to 0 in the first half of the modulation period and from 0 to 1 in the second half of the modulation period. And switching between 0 and 1 in the first half of the control period and switching from 1 to 0 in the second half of the control period, and switching between 1 and 0 in the second half of the modulation period. At the time when the product of one half of the input control ratio RI and the control period Tc has elapsed from the start time of the first half modulation period, the switching is controlled in the second half modulation period. In only one of the products of 2 minutes elapsed time in the second half of the start time from the input control ratio RI drawn from 1 (1-RI) of the modulation period and the control period Tc, to perform respectively. However, when the intermediate conversion signal TSm becomes 1, the next control period is composed of one modulation period, and the control period is set to one half of the normal control period Tc. The operation of switching the pulse TI within the control period is performed only once corresponding to the first half of the modulation period, and is performed at the time when the product of one half of the input control ratio RI and the control period Tc has elapsed from the start time of the control period. Shall. The control period may be the normal control period Tc. In this case, the switching is performed at the time when the product of the input control ratio RI and the control period Tc has elapsed from the start time of the control period. The input pulse generator 15d sets the intermediate conversion signal TSm to 0 simultaneously with the start of the output of the input control pulse TI during the control period.

  Table 3 shows the phase of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage corresponding to the section signal Sct, and the virtual DC used by switching between the two phases of the AC power supply 1 within the control period. The correspondence between the voltage pole, the order of using the two phases at the pole, and the section signal Sct, the intermediate section signal Scm, and the intermediate conversion signal TSm is shown. In Table 3, the correspondence between each section and a voltage used as a virtual DC voltage is the same as the correspondence in Table 1. As an example, when the section signal Sct is 1, the positive pole of the virtual DC voltage uses two phases of the AC power source 1 by switching between the T phase and the R phase within one control period, and the negative pole is the AC The S phase of the power supply 1 is always used within one control period. When the intermediate section signal Scm is not equal to the section signal Sct, the order of using the phase of the AC power supply 1 at the positive electrode for switching is to use the R phase first in the first half of the modulation period and then T If the intermediate section signal Scm is equal to the section signal Sct by using the T phase in the latter half of the modulation period and then using the R phase thereafter, the first modulation period in the control period In the latter half of the modulation period, the R phase is used first and then the T phase is used. Further, the control period in which the intermediate conversion signal TSm is 1 is composed of one modulation period, and in the control period, the R phase is used first and then the T phase is used.

  The input pulse generator 15d generates an input control pulse TI based on the section signal Sct, the intermediate section signal Scm, the intermediate conversion signal TSm, and the input control ratio RI in accordance with the correspondence relationship shown in FIGS.

  FIG. 24 is a flowchart showing the operation of the voltage ratio calculator according to the fifth embodiment of the present invention. In FIG. 24, the same or corresponding parts as those in FIG. Description of is omitted. The operation of the voltage ratio calculator 14d includes a voltage ratio selection operation B20 for selecting and calculating one of three voltage ratio calculation expressions, and a voltage ratio output operation for calculating and outputting RI from the calculated voltage ratio. It consists of two stages of B30d.

  The voltage ratio output operation B30d will be described. The voltage ratio calculator 14d starts the voltage ratio output operation B30d as soon as the voltage ratio selection operation B20 is completed. If the intermediate conversion signal TSm is 0 (step ST45), the intermediate section signal Scm is compared with the section signal Sct. If the signal value is equal (step ST46), the voltage ratio calculated in the voltage ratio selection operation B20 is used as it is. The signal is output as the input control ratio RI (step ST34). If the signal values are not equal, a value obtained by subtracting the voltage ratio from 1 is output as the input control ratio RI (step ST35). If the intermediate conversion signal TSm is 1, regardless of the intermediate section signal Scm, a value obtained by subtracting the voltage ratio from 1 is output as the input control ratio RI. By determining the input control ratio RI in this way, the voltage ratio output operation B30d ends.

  When the voltage ratio output operation 30d is completed, the input control ratio RI is output to the input pulse generator 15d and the output controller 30, and the input control pulse TI and the output control pulses TU, TV, TW for the next control period are generated, respectively. The

  Next, the calculation result of the input control ratio RI output by the input controller 10d, the output controller 30 and the gate controller 40 due to the fluctuations in the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10d. , Section signal Sct, intermediate section signal Scm, intermediate conversion signal TSm, input control pulse TI, pulse width modulation result in output controller 30, output control pulse TU related to U phase, operation of switch control pulses TUR, TUS, TUT Will be described.

  For the operation when the section signal Sct is 1 and the intermediate section signal Scm is 6, and both are not switched, the operation in one control period corresponds to the operation in two consecutive control periods in the operation example shown in FIG. Therefore, the switching operation of the nine switch control pulses is not performed at the change of the control period, and the combination of the section signal Sct and the intermediate section signal Scm is a combination other than this. Since it changes similarly even if it is a period, description is abbreviate | omitted.

  FIG. 25 is a timing chart showing the operation of the multi-relative multi-phase power converter according to Embodiment 5 of the present invention. In FIG. 25, the fluctuations in the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10d are shown. The input controller 10d, the output controller 30 and the gate controller 40 output the calculation result of the input control ratio RI, the section signal Sct, the intermediate section signal Scm, the intermediate conversion signal TSm, the input control pulse TI, and the output controller. 30 shows an example of the operation of the pulse width modulation result at 30, the output control pulse TU related to the U phase, and the switch control pulses TUR, TUS, TUT. In this example, regarding the voltage of the AC power source 1, vT and vR are positive voltages, vS is a negative voltage, and the section signal Sct is 1, but in the first modulation period Tm1d ′ within the first control period Tc1d ′. The magnitude relationship between vT and vR is reversed, and at the same time, the intermediate section signal Scm changes from 6 to 1, and the intermediate conversion signal TSm becomes 1. Since there is no conversion of the section signal Sct, the combination of phases of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage is the same as the operation example shown in FIG.

  Operations in the first control period Tc1d ′, the intermediate conversion control period Tcmd ′, and the second control period Tc2d ′ will be described. Since the intermediate conversion signal TSm is 1 in the first modulation period Tm1d ′, the intermediate conversion control period Tcmd ′, which is the next control period, is configured by one modulation period, and the control period time is set to the normal time. One half of the control period Tc. Since the intermediate conversion signal TSm remains 0 in the intermediate conversion control period Tcmd ′, the second control period Tc2d ′, which is the next control period, is composed of two control periods, and the control period time is also normal. The control period is Tc. The input control ratio RI is calculated by calculating vT / (vT + vR) according to the voltage ratio selection operation B20 of the flowchart shown in FIG. 24, and the first control period Tc1d ′ according to the voltage ratio output operation B30d of the flowchart shown in FIG. Since the intermediate conversion signal TSm is 0 and the intermediate section signal Scm is 6 and is not equal to the section signal Sct, the voltage ratio calculated in the voltage ratio output operation B30d is set to a value obtained by subtracting 1 from the intermediate conversion control period Tcmd '. Since the conversion signal TSm is 1, the voltage ratio is subtracted from 1, and in the second control period Tc2d ′, the intermediate conversion signal TSm is 0, the intermediate section signal Scm is 1, and equal to the section signal Sct. Therefore, the voltage ratio is output as it is.

  The input control pulse TI is generated so that the combination of phases of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage is the same as the operation example shown in FIG. In the operation example shown in FIG. 25, the negative electrode always uses the S phase. Since the section signal Sct is 1 in the first control period Tc1d ′ and the intermediate section signal Scm is 6 and is not equal to the section signal Sct, the phase of the AC power supply 1 used by the positive electrode in the control period according to Table 3 is R. After switching from the phase to the T phase, the phase is switched again to the R phase. Since the intermediate conversion signal TSm is 1 in the intermediate conversion control period Tcmd ′, the phase of the AC power source 1 used by the positive electrode in the control period according to Table 3 Switching from the R phase to the T phase, the section signal Sct is 1 in the second control period Tc2d ′, and the intermediate section signal Scm is 1 and equal to the section signal Sct. The AC power source 1 is generated so that the phase of the AC power supply 1 is switched from the T phase to the R phase and then switched to the T phase again. As a result, at the change of the modulation period not corresponding to the change of the control period, the phase of the AC power supply 1 used by the positive electrode of the virtual DC voltage is fixed as in the operation example shown in FIG. The phase of the AC power supply 1 used by the positive electrode is fixed to the R phase at the change from Tc1d ′ to the intermediate conversion control period Tcmd ′, and the positive electrode is used at the change from the intermediate conversion control period Tcmd ′ to the second control period Tc2d ′. The phase of the AC power supply 1 to be fixed is fixed to the T phase.

  The triangular carrier wave used for generating the output control pulses TU, TV, and TW has a section signal Sct of 1, and the pole used by switching between the two phases of the AC power supply 1 within the control period is the positive electrode. It is a triangular carrier wave indicating the shape of a “mountain” within the period. Therefore, since the apex of the triangular carrier wave takes the lowest point at all changes in the control period and all changes in the modulation period, the output control pulse TU, TV, TW is 1 at the change, and the two phases of the AC power source 1 are positive. Since the apex of the triangular carrier wave takes the highest point at the time of switching, the output control pulses TU, TV, TW are 0 at that time.

  As a result, since the input control pulse TI and the output control pulses TU, TV, and TW are not switched at the change of the control period, the switching with the nine switch control pulses is not performed at all. At the time when the two phases of the AC power supply 1 are switched at the positive electrode, the input control pulse TTP related to the T phase and the input control pulse TRP related to the R phase are switched among the three input control pulses related to the positive electrode. Since all of the control pulses TU, TV, and TW are 0, the nine switch control pulses are not switched at this time.

  The above operation changes in the same manner even when the section is switched except when the intermediate section signal Scm is switched from 6 to 1.

  FIG. 26 is a timing chart showing the operation of the multi-relative multi-phase power converter according to Embodiment 5 of the present invention. In FIG. 26, the fluctuations in the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10d are shown. The input controller 10d, the output controller 30 and the gate controller 40 output the operation result of the input control ratio RI, the section signal Sct, the intermediate section signal Scm, the intermediate conversion signal TSm, the input control pulse TI, and the output controller. 30 shows another example of the operation of the pulse width modulation result at 30, the output control pulse TU related to the U phase, and the switch control pulses TUR, TUS, TUT. In this example, the voltage of the AC power supply 1 and the operation of the section signal Sct associated therewith are the same as the operation example shown in FIG. 12, the intermediate section signal Scm is not converted, and the intermediate conversion signal TSm remains zero.

  An operation in the first control period Tc1d ″ and the second control period Tc2d ″ will be described. Since the intermediate conversion signal TSm remains 0, both the first control period Tc1d ″ and the second control period Tc2d ″ are composed of two control periods, and the control period is also the normal control period Tc. . The input control ratio RI is calculated as vT / (vT + vR) in the first control period Tc1d ″ and vS / (vS + vT in the second control period Tc2d ″ in accordance with the voltage ratio selection operation B20 in the flowchart shown in FIG. ) And according to the voltage ratio output operation B30d of the flowchart shown in FIG. 24, the intermediate conversion signal TSm is 0, the intermediate section signal Scm is 1, and equal to the section signal Sct in the first control period Tc1d ″. In the second control period Tc2d ″, the intermediate conversion signal TSm is 0, the intermediate section signal Scm is 1, and is not equal to the section signal Sct, and the voltage ratio calculated in the voltage ratio output operation B30d remains unchanged. A value obtained by subtracting the calculated voltage ratio from 1 is output.

  The input control pulse TI is generated such that the combination of phases of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage is the same as the operation example shown in FIG. The operation at the change of the modulation period not corresponding to the change of the control period is the same as the operation example shown in FIG. Since the section signal Sct is 1 and the intermediate section signal Scm is 1 and equal to the section signal Sct in the first control period Tc1d ″, the input control pulse TI is the AC power source 1 that the positive electrode uses in the control period according to Table 3. The phase of the AC power supply 1 used by the negative electrode is fixed to the S phase after the phase of the T is switched from the T phase to the R phase, and the section signal Sct is 2 in the second control period Tc2d ″. Since the intermediate section signal Scm is 1 and not equal to the section signal Sct, the phase of the AC power source 1 used by the positive electrode is fixed to the R phase in the control period according to Table 3, and the AC power source 1 used by the negative electrode is fixed. The phases are respectively generated so as to switch the phase from the T phase to the S phase and then switch again to the T phase. As a result, at the transition from the first control period Tc1d ″ to the second control period Tc2d ″, the phase of the AC power source 1 used by the positive electrode is switched from the T phase to the R phase, and the phase of the AC power source 1 used by the negative electrode is The S phase is switched to the T phase.

  The shape indicated by the triangular carrier wave used for generating the output control pulses TU, TV, TW is the same as that in the operation example shown in FIG. 12, and the triangle is shown at the transition from the first control period Tc1d ″ to the second control period Tc2d ″. Since the operation of moving the vertex of the carrier wave from the lowest point to the highest point occurs, all the output control pulses TU, TV, TW are switched from 1 to 0 at the change point. However, as a result of combining with the switching operation of the input control pulse TI, the phase of the AC power source 1 to which all phases of the load 2 are connected is the positive pole of the virtual DC voltage at the end of the first control period Tc1d ″. At the start of a certain T phase and the second control period Tc2d ″, the phase becomes a T phase that is the negative pole of the virtual DC voltage, and at the transition from the first control period Tc1d ″ to the second control period Tc2d ″, the load 2 The phase of the AC power supply 1 connected to the other phase is not switched, and the switching with nine switch control pulses is not performed at all.

  The above operation changes in the same manner even when the section is switched except when the section signal Sct is switched from 1 to 2.

  As described above, according to the fifth embodiment, the AC power supply 1 connected to the phase of the load 2 during the control period is the control period that is a basic time unit for controlling the multi-relative multi-phase power converter. The operation of switching the phase of the AC power source 1 to a different phase and then switching to the original phase again is used. During a certain control period, the phase of the AC power source 1 connected to the phase of the load 2 is switched once to a different phase. By making the operation only possible, the phase of the AC power source 1 to which the phase of the load 2 is connected can be fixed before and after the change of the control period. The switching operation of the switches related to a plurality of phases of the load 2 can be prevented from occurring simultaneously.

Embodiment 6 FIG.
FIG. 27 is a block diagram showing a multi-relative multi-phase power converter according to Embodiment 6 of the present invention. In the input controller 10c shown in FIG. 27, the conversion detector 12e is based on the section signal by the section detector 11d. A conversion signal indicating that the section signal has been converted is generated, and an intermediate conversion signal indicating that the intermediate section signal has been converted is generated based on the intermediate section signal. The voltage ratio calculator 14e generates an input control ratio based on the AC voltage of the AC power source 1, the section signal by the section detector 11d, the intermediate section signal, the conversion signal by the conversion detector 12e, and the intermediate conversion signal. is there. The input pulse generator 15e generates an input control pulse based on the section signal by the section detector 11d, the intermediate section signal, the conversion signal by the conversion detector 12e, the intermediate conversion signal, and the input control ratio by the voltage ratio calculator 14e. To do. Other configurations are the same as those in FIG.

Next, the operation will be described.
In the circuit shown in FIG. 23, the conversion detector 12d outputs the intermediate conversion signal TSm, and the voltage ratio calculator 14d measures the measured values vRs, vSs, vTs of the voltages vR, vS, vT of the AC power supply 1, and the section signal. An input control ratio RI is calculated based on Sct, intermediate section signal Scm and intermediate conversion signal TSm, and input pulse generator 15d is based on section signal Sct, intermediate section signal Scm, intermediate conversion signal TSm and input control ratio RI. However, as shown in FIG. 20, the conversion detector 12e outputs the conversion signal TSc and the intermediate conversion signal TSm, and the voltage ratio calculator 14e is connected to the AC power source 1 as shown in FIG. Measured values vRs, vSs, vTs, section signal Sct, intermediate section signal Scm, conversion signal The input control ratio RI is calculated based on the TSc and the intermediate conversion signal TSm, and the input pulse generator 15e is based on the section signal Sct, the intermediate section signal Scm, the conversion signal TSc, the intermediate conversion signal TSm, and the input control ratio RI. An input control pulse TI may be output.

  In this configuration, when one control period is composed of two modulation periods and pulse width modulation control using a triangular carrier wave is performed in each modulation period, the positive and negative electrodes of a virtual DC voltage are controlled in one control period. Even if the order of using the phases of the AC power supply is reversed from that in the fifth embodiment, a certain control period is composed of only one modulation period, and a positive pole of a virtual DC voltage is generated in one modulation period. The order in which the phases of the AC power source and the negative electrode are reversed is reversed, and another control period is configured by only one modulation period, and the positive and negative electrodes of the virtual DC voltage are respectively used in one modulation period. By fixing the phase of the AC power supply to be used, the phase of the AC power supply used by the positive and negative electrodes of the virtual DC voltage is not switched at the change of the control period immediately after the section is changed. Unishi Te, it is possible to prevent the generation of the switching operation at the turn of the control period.

In FIG. 27, the same or corresponding parts as in FIG.
The operation of the input controller 10e will be described. The input controller 10e includes a section detector 11d, a conversion detector 12e, a voltage ratio calculator 14e, and an input pulse generator 15e. The input controller 10e is configured to measure the measured values vRs, vSs, and vTs of the voltages vR, vS, and vT of the AC power supply 1. Input, calculate the input control ratio RI, generate the input control pulse TI, and output each. When the section signal Sct is input and converted, the conversion signal TSc is set to 1, and when the intermediate section signal Scm is input and converted, the intermediate conversion signal TSm is set to 1 and output.

  The voltage ratio calculator 14e receives the measured values vRs, vSs, vTs, the section signal Sct, the intermediate section signal Scm, the conversion signal TSc, and the intermediate conversion signal TSm of the voltages vR, vS, vT of the AC power supply 1, and the input control ratio. RI is calculated and output every change of the control period. Based on the section signal Sct from the three voltage ratios vT / (vT + vR), vS / (vS + vT), vR / (vR + vS) calculated from the measured values vRs, vSs, vTs of the voltage vR, vS, vT of the AC power supply 1. Select one to calculate. Based on the result of comparing the intermediate section signal Scm with the section signal, it is determined whether to use the calculated voltage ratio as it is or to use a value obtained by subtracting the calculated voltage ratio from 1, and output this as the input control ratio RI To do. However, when the intermediate conversion signal TSm is 1, regardless of the intermediate section signal Scm, the value obtained by subtracting the calculated voltage ratio from 1 is used as the input control ratio RI, and when the conversion signal TSc is 1, the intermediate section signal Scm is obtained. Regardless, the input control ratio RI is set to 0 and output.

  The input pulse generator 15e receives the section signal Sct, the intermediate section signal Scm, the conversion signal TSc, the intermediate conversion signal TSm, and the input control ratio RI, and generates an input control pulse TI. The operation of the generator when the conversion signal TSc remains 0 is the same as the operation of the input pulse generator 15d shown in FIG. 23, but the virtual switching of the two phases of the AC power supply 1 within the control period is performed. The correspondence between the order in which the direct DC voltage poles use the two phases and the comparison result of the intermediate section signal Scm and the section signal Sct is reversed. When the intermediate conversion signal TSm or the conversion signal TSc becomes 1, the next control period is composed of one modulation period, and the time of the control period is set to one half of the normal control period Tc. A time when the operation of switching the input control pulse TI within the control period is performed only once corresponding to the first half of the modulation period, and the product of one half of the input control ratio RI and the control period Tc has elapsed from the start time of the control period It shall be done in The control period may be the normal control period Tc. In this case, the switching is performed at the time when the product of the input control ratio RI and the control period Tc has elapsed from the start time of the control period. As for the operation when the conversion signal TSc becomes 1, the input control ratio RI output from the voltage ratio calculator 14e is 0. Therefore, in the control period as in the operation example shown in FIG. The switching operation of the input pulse TI does not occur. The input pulse generator 15e sets the signal that is 1 out of the conversion signal TSc or the intermediate conversion signal TSm to 0 simultaneously with the start of the output of the input control pulse TI in the control period.

  Table 4 shows the phase of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage corresponding to the section signal Sct, and the virtual DC used by switching between the two phases of the AC power supply 1 within the control period. The poles of the voltage, the order in which the two phases are used at the poles, and the correspondences between the section signal Sct, the intermediate section signal Scm, the conversion signal TSc and the intermediate conversion signal TSm are respectively shown. In Table 4, the correspondence between each section and the voltage used as a virtual DC voltage is the same as the correspondence in Table 1. As an example, when the section signal Sct is 1, the positive pole of the virtual DC voltage uses two phases of the AC power source 1 by switching between the T phase and the R phase within one control period, and the negative pole is the AC The S phase of the power supply 1 is always used within one control period. When the intermediate section signal Scm is not equal to the section signal Sct, the order of using the phase of the AC power supply 1 at the positive electrode for switching is to use the T phase first in the first half modulation period in the control period and then the R phase. When the intermediate section signal Scm is equal to the section signal Sct using the R phase first in the second half modulation period and then using the T phase, the first modulation period first in the control period is used first. The R phase is used and then the T phase is used. In the latter half of the modulation period, the T phase is used first and then the R phase is used. The control period in which the conversion signal TSc or the intermediate conversion signal TSm is 1 is composed of one modulation period. In the control period, when the conversion signal TSc is 1, the intermediate conversion signal is always used by using the T phase. When TSm is 1, the T phase is used first, and then the R phase is used. When the conversion signal TSc is 1, the phase of the AC power supply 1 used by the positive pole of the virtual DC voltage does not occur during the control period because the input control ratio RI is 0 by the operation of the voltage ratio calculator 14e. This is because the time for using the R phase that the positive electrode uses first in that control period is zero.

  The input pulse generator 15e generates an input control pulse TI based on the section signal Sct, the intermediate section signal Scm, the conversion signal TSc, the intermediate conversion signal TSm, and the input control ratio RI in accordance with the correspondence relationship shown in FIGS. Is generated.

  FIG. 28 is a flowchart showing the operation of the voltage ratio calculator according to the sixth embodiment of the present invention. In FIG. 28, the same or corresponding parts as those in FIG. Description of is omitted. The operation of the voltage ratio calculator 14e includes a voltage ratio selection operation B20 for selecting and calculating one of three voltage ratio calculation expressions, and a voltage for calculating and outputting the input control ratio RI from the calculated voltage ratio. It consists of two stages of ratio output operation B30e.

  The voltage ratio output operation B30e will be described. The voltage ratio calculator 14e starts the voltage ratio output operation B30e as soon as the voltage ratio selection operation B20 is completed. If the conversion signal TSc is 0 (step ST31), the intermediate conversion signal TSm is referred to. If the intermediate conversion signal TSm is 0 (step ST45), the intermediate section signal Scm is compared with the section signal Sct. If the signal values are equal (step ST46), a value obtained by subtracting the voltage ratio calculated in the voltage ratio selection operation B20 from 1 is output as the input control ratio RI (step ST35). If the signal values are not equal, the voltage ratio Is directly output as the input control ratio RI (step ST34). If the intermediate conversion signal TSm is 1, regardless of the intermediate section signal Scm, a value obtained by subtracting the voltage ratio from 1 is output as the input control ratio RI. If the conversion signal TSc is 1, the input control ratio RI is output as 0 (step ST36). Thus, by setting the input control ratio RI, the voltage ratio output operation B30e ends.

  When the voltage ratio output operation B30e is completed, the input control ratio RI is output to the input pulse generator 15e and the output controller 30, and the input control pulse TI and the output control pulses TU, TV, TW for the next control period are generated, respectively. The

  Next, the calculation result of the input control ratio RI output from the input controller 10e, the output controller 30 and the gate controller 40 due to the fluctuation of the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10e. , Section signal Sct, intermediate section signal Scm, conversion signal TSc, intermediate conversion signal TSm, input control pulse TI, pulse width modulation result in output controller 30, output control pulse TU related to U phase, switch control pulses TUR, TUS The operation of the TUT will be described.

  For the operation when the section signal Sct is 1 and the intermediate section signal Scm is 6, and both are not switched, the operation in one control period corresponds to the operation in two consecutive control periods in the operation example shown in FIG. Therefore, the switching operation of the nine switch control pulses is not performed at the change of the control period, and the control period in which the combination of the section signal Sct and the intermediate section signal Scm is a combination other than this. However, since it changes similarly, description is abbreviate | omitted.

  FIG. 29 is a timing chart showing the operation of the multi-relative multi-phase power converter according to Embodiment 6 of the present invention. In FIG. The input controller 10e, the output controller 30 and the gate controller 40 output the calculation result of the input control ratio RI, the section signal Sct, the intermediate section signal Scm, the conversion signal TSc, the intermediate conversion signal TSm, and the input control pulse TI. FIG. 11 is an example of operations of a pulse width modulation result in the output controller 30, an output control pulse TU related to the U phase, and switch control pulses TUR, TUS, TUT. In this example, the operation of the voltage of the AC power supply 1, the accompanying section signal Sct, the intermediate section signal Scm, and the intermediate conversion signal TSm is the same as the operation example shown in FIG. Since there is no conversion of the section signal Sct, the conversion signal TSc remains 0, and the combination of phases of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage is the same as the operation example shown in FIG.

  Operations in the first control period Tc1e ′, the intermediate conversion control period Tcme ′, and the second control period Tc2e ′ will be described. The number of modulation periods constituting the control period and the time of the control period are the same as those in the operation example shown in FIG. The input control ratio RI is calculated by calculating vT / (vT + vR) according to the voltage ratio selection operation B20 of the flowchart shown in FIG. 28, and the first control period Tc1e ′ according to the voltage ratio output operation B30e of the flowchart shown in FIG. Since the conversion signal TSc and the intermediate conversion signal TSm are both 0, and the intermediate section signal Scm is 6 and not equal to the section signal Sct, the voltage ratio calculated in the voltage ratio output operation B30d remains as it is, and the intermediate conversion control period Tcme ′ In the second control period Tc2e ′, the conversion signal TSc and the intermediate conversion signal TSm are both 0 and the intermediate section signal Scm is 0 because the conversion signal TSc is 0 and the intermediate conversion signal TSm is 1. Since 1 is equal to the section signal Sct, the voltage ratio is subtracted from 1, Each Re to output.

  The input control pulse TI is generated so that the combination of phases of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage is the same as the operation example shown in FIG. The operation at the change of the modulation period not corresponding to the change of the control period is the same as the operation example shown in FIG.

  In the operation example shown in FIG. 29, the negative electrode always uses the S phase. Since the section signal Sct is 1 in the first control period Tc1e ′ and the intermediate section signal Scm is 6 and is not equal to the section signal Sct, the phase of the AC power source 1 used by the positive electrode in the control period according to Table 4 is T After switching from the phase to the R phase, the phase is switched again to the T phase. Since the intermediate conversion signal TSm is 1 in the intermediate conversion control period Tcme ′, the phase of the AC power source 1 used by the positive electrode in the control period according to Table 4 Switching from the T phase to the R phase, the section signal Sct is 1 in the second control period Tc2e ′, and the intermediate section signal Scm is 1 and equal to the section signal Sct. The AC power source 1 is generated so that the phase of the AC power supply 1 is switched from the R phase to the T phase and then switched again to the R phase. As a result, at the transition from the first control period Tc1e ′ to the intermediate conversion control period Tcme ′, the phase of the AC power supply 1 used by the positive electrode is fixed to the T phase, and from the intermediate conversion control period Tcme ′ to the second control period Tc2e. At the change to ', the phase of the AC power source 1 used by the positive electrode is fixed to the R phase.

  The triangular carrier wave used for generating the output control pulses TU, TV, TW shows a “mountain” shape. Therefore, since the apex of the triangular carrier wave takes the lowest point at all changes in the control period and all changes in the modulation period, the output control pulse TU, TV, TW is 1 at the change, and the two phases of the AC power source 1 are positive. Since the apex of the triangular carrier wave takes the highest point at the time of switching, the output control pulses TU, TV, TW are 0 at that time.

  As a result, since the input control pulse TI and the output control pulses TU, TV, and TW are not switched at the change of the control period, the switching with the nine switch control pulses is not performed at all. At the time when the two phases of the AC power supply 1 are switched at the positive electrode, the input control pulse TTP related to the T phase and the input control pulse TRP related to the R phase are switched among the three input control pulses related to the positive electrode. Since all of the control pulses TU, TV, and TW are 0, the nine switch control pulses are not switched at this time.

  The above operation changes in the same manner even when the section is switched except when the intermediate section signal Scm is switched from 6 to 1.

  FIG. 30 is a timing chart showing the operation of the multi-relative multi-phase power converter according to Embodiment 6 of the present invention. In the figure, the fluctuations in the voltages vR, vS, vT of the AC power supply 1 and the operation of the input controller 10e are shown. The input controller 10e, the output controller 30 and the gate controller 40 output the calculation result of the input control ratio RI, the section signal Sct, the intermediate section signal Scm, the conversion signal TSc, the intermediate conversion signal TSm, and the input control pulse TI. FIG. 11 shows another example of the operation of the pulse width modulation result in the output controller 30, the output control pulse TU related to the U phase, and the switch control pulses TUR, TUS, TUT. In this example, the operation of the voltage of the AC power source 1, the accompanying section signal Sct, the intermediate section signal Scm, and the intermediate conversion signal TSm is the same as the operation example shown in FIG. The section signal Sct is converted from 1 to 2, and the conversion signal TSc is 1 accordingly.

  The operation in the first control period Tc1e ″, the intermediate control period Tcte ″ and the second control period Tc2e ″ will be described. Since the conversion signal TSc is 1 in the first control period Tc1e ″, The intermediate control period Tcte ″, which is the control period of the control period, is composed of one modulation period, and the time of the control period is set to one half of the normal control period Tc. In the intermediate control period Tcte ″, the conversion signal TSc remains 0. Therefore, the second control period Tc2e ″, which is the next control period, is composed of two control periods, and the control period is also the normal control period Tc. The input control ratio RI is shown in FIG. According to the voltage ratio selection operation B20 of the flowchart shown, vT / (vT + vR) is calculated in the first control period Tc1e ″, and in the intermediate control period Tcte ″ and the second control period Tc2e ″. vS / (vS + vT) is calculated, and in accordance with the voltage ratio output operation B30e of the flowchart shown in FIG. 28, the conversion signal TSc and the intermediate conversion signal TSm are both 0 in the first control period Tc1e ″, and the intermediate section signal Scm 1 is equal to the section signal Sct, the voltage ratio calculated in the voltage ratio output operation B30e is subtracted from 1, and the conversion signal TSc is 1 in the intermediate control period Tcte ″. In the control period Tc2e ″, both the conversion signal TSc and the intermediate conversion signal TSm are 0, and the intermediate section signal Scm is 1 and not equal to the section signal Sct. Therefore, the voltage ratio is output as it is.

  The input control pulse TI is generated so that the combination of phases of the AC power supply 1 used by the positive and negative electrodes of the virtual DC voltage is the same as the operation example shown in FIG. The operation at the change of the modulation period not corresponding to the change of the control period is the same as the operation example shown in FIG. Since the section signal Sct is 1 and the intermediate section signal Scm is 1 and equal to the section signal Sct in the first control period Tc1e ″, the input control pulse TI is the AC power source 1 that the positive electrode uses in the control period according to Table 4. The phase of the AC power source 1 used by the negative electrode is fixed to the S phase after the phase of the phase is switched from the R phase to the T phase, and the conversion signal TSm is 1 in the intermediate control period Tcte ″. Thus, according to Table 4, the phase of the AC power source 1 used by the positive electrode in the control period is fixed to the R phase, and the phase of the AC power source 1 used by the negative electrode is fixed to the S phase, and the second control period Tc2e ″ Since the section signal Sct is 2 and the intermediate section signal Scm is 1 and not equal to the section signal Sct, the phase of the AC power source 1 used by the positive electrode in the control period according to Table 4 is determined. The phase of the AC power supply 1 used by the negative electrode is generated so as to switch from the S phase to the T phase and then switch again to the S phase. As a result, the first control period Tc1e " In both the transition to the control period Tcte ″ and the transition from the intermediate control period Tcte ″ to the second control period Tc2e ″, the phase of the AC power supply 1 used by the positive electrode is the R phase and the AC used by the negative electrode The phase of the power source 1 is fixed to the S phase.

  The shape indicated by the triangular carrier wave used for generating the output control pulses TU, TV, TW is the same as the operation example shown in FIG. 11, and the input control ratio RI in the intermediate control period Tcte ″ is 0. Since the sawtooth wave rises to the right during the control period, the apex of the triangular carrier wave is the lowest point at the end of the first control period Tc1e ″ and the beginning of the intermediate control period Tcte ″, and the end and the end of the intermediate control period Tcte ″. At the beginning of the second control period Tc2e ″, the top of the triangular carrier wave is the highest point, and the movement of the top of the triangular carrier wave does not occur at every change in the control period, so all output control pulses TU, TV, TW Will not switch.

  As a result, since the input control pulse TI and the output control pulses TU, TV, and TW are not switched at the change of the control period, the switching with the nine switch control pulses is not performed at all.

  The above operation changes in the same manner even when the section is switched except when the section signal Sct is switched from 1 to 2.

  As described above, according to the sixth embodiment, the AC power source 1 connected to the phase of the load 2 during the control period is the control period that is a basic time unit for controlling the multi-relative multi-phase power converter. The phase of the AC power source 1 connected to the phase of the load 2 is changed to a different phase once during a certain control period. The operation of switching only can be used, and the operation of setting the time for connecting the phase of the AC power supply 1 to 0 in another certain control period can be used, so that the load 2 is changed before and after the change of the control period. Since the phase of the AC power supply 1 to which the phase is connected can be fixed, it is possible to prevent switching of the switch control pulse at all transitions of the control period, and to switch the switches related to a plurality of phases of the load 2. Quenching operation can be realized that you do not occur simultaneously.

Embodiment 7 FIG.
In the multi-relative multi-phase power conversion device according to any of the first to sixth embodiments of the present invention, the pulse width modulation control in the output controller 30 or the output controller 30c is based on a triangular carrier wave. The order of connecting the phases of the load 2 to the phases of the AC power supply 1 may be based on the concept of the instantaneous space voltage vector, which is the same as the pulse width modulation control using the triangular carrier wave.

  Regarding the operation of connecting the phase of the load 2 to each phase of the AC power supply 1, the time for connecting each phase of the AC power supply 1 may be different from the pulse width modulation control by the triangular carrier wave. The order in which the phases are connected is the same as that of the triangular carrier wave. Therefore, the switching operation with nine switch control pulses is exactly the same as that with the triangular carrier wave.

  As described above, according to the seventh embodiment, in the pulse width modulation control of the multi-relative multiphase power converter, the order in which the phase of the load 2 connects the phases of the AC power supply is changed to the pulse width modulation control by the triangular carrier wave. Even if the concept is based on the same instantaneous space voltage vector, the phase of the AC power source 1 to which the phase of the load 2 is connected can be fixed before and after the change of the control period. Thus, it is possible to prevent switching of the switch control pulses and to prevent the switching operations of the switches related to the plurality of phases of the load 2 from occurring simultaneously.

Embodiment 8 FIG.
In the multi-relative multi-phase power conversion device according to any one of Embodiments 1 to 7 of the present invention, pulse width modulation based on the concept of a triangular carrier wave or an instantaneous spatial voltage vector in output controller 30 or output controller 30c. In the control, the virtual DC voltage pole is switched once or twice for all phases of the load 2 within the control period. However, the virtual DC voltage pole is switched for any one phase of the load 2. The poles of the virtual DC voltage may be switched once or twice within the control period so as to be fixed and connected within the control period.

As an example, the operation when the pulse width modulation operation of the eighth embodiment of the present invention is performed in the multi-relative multiphase power conversion device of the first embodiment of the present invention will be described.
The operation when the section signal Sct does not change is that the phase of the AC power supply 1 is not switched at all for the phase of the load 2 in which the pole of the virtual DC voltage is fixed and connected within the control period. For the other phases, only the switching operation by the pulse width modulation control is performed as in the operation example shown in FIG.

  The operation at the transition of the control period immediately after the section signal Sct is changed is that the phase of the load 2 that has been connected with the fixed pole of the virtual DC voltage until the control period when the section is changed is after the next control period. The virtual DC voltage pole is switched within the control period, and one of the other phases of the load 2 is fixedly connected to the virtual DC voltage pole after the next control period. It becomes like this. For the former, the output control pulse related to the phase is switched at the change of the control period immediately after the section is changed, and for the latter, the output control pulse related to the phase is not changed at the change.

  As a result of combining the switching operation of the output control pulses TU, TV, and TW with the switching operation of the input control pulse TI at the turning point, switching of the switch control pulse is performed in one of the above two phases of the load 2. Although it is performed, the switch control pulse is not switched in the other phase. Further, switching is not performed at all for the switch control pulses related to the other phases of the load 2 as in the operation examples shown in FIGS.

  The above operation similarly changes in any of the multi-relative multi-phase power converters according to the second to seventh embodiments of the present invention.

  As described above, according to the eighth embodiment, any one phase of the load 2 is fixedly connected to one phase of the AC power supply 1 for the pulse width modulation control of the multi-relative multi-phase power converter. Even in such a pulse width modulation control, the phase of the load 2 for switching the phase of the AC power supply 1 connected before and after the change of the control period can be at most one, so that the switches related to a plurality of phases of the load 2 It is possible to prevent the switching operations from occurring simultaneously.

Embodiment 9 FIG.
FIG. 31 is a block diagram showing a multi-relative multi-phase power converter according to Embodiment 9 of the present invention. In the figure, a main circuit 3D is connected between an AC power source 1 and a load 2, and the AC power source 1 The AC voltage is supplied to the load 2 by switching with a plurality of switches that selectively control the AC voltage. Other configurations are the same as those in FIG.

Next, the operation will be described.
Any of the multi-relative multi-phase power conversion device according to any of the second, fourth and sixth embodiments of the present invention and any of the second, fourth and sixth embodiments of the present invention, either of the seventh or eighth embodiments of the present invention In the multi-relative multi-phase power conversion device to which the above is applied, for example, in the circuit of FIG. 13, switches 3UR, 3US, 3UT, 3VR, which selectively switch so that the main circuit 3 supplies power to the load 2. 3VS, 3VT, 3WR, 3WS, and 3WT are included, but as shown in FIG. 31, the main circuit 3D selectively switches switches 3PR, 3PS, 3PT, 3NR, 3NS, 3NT and a half-bridge circuit. 3UB, 3VB, 3WB, one end of switches 3PR, 3PS, 3PT and half bridge circuit 3UB, 3VB One end of 3WB is connected to the positive electrode 3P of the DC circuit, one end of the switches 3NR, 3NS, 3NT and the other end of the half bridge circuits 3UB, 3VB, 3WB are connected to the negative electrode 3N of the DC circuit, and the switches 3PR, 3PS, The 3PT, 3NR, 3NS, and 3NT may selectively switch to output an arbitrary DC voltage between the positive electrode 3P and the negative electrode 3N of the DC circuit.

  In the circuit shown in FIG. 1, the input control pulse TI is a signal indicating by 1 and 0 whether or not each phase of the AC power supply 1 is used for each pole of the virtual DC voltage. In the circuit shown in FIG. 2, the signals indicating whether the phases of the AC power supply 1 are connected to the positive electrode 3P of the DC circuit or the negative electrode 3N of the DC circuit are 1 and 0, respectively. For example, the control pulses TRP, TRN, TSP, TSN, TTP, and TTN in the operation example shown in FIG. 11 correspond to the switches 3PR, 3NR, 3PS, 3NS, 3PT, and 3NT, respectively, and control ON / OFF of the switches. To do.

  In the circuit shown in FIG. 1, the output control pulses TU, TV, and TW are logic signals that are set to 1 when each phase of the load 2 is connected to the positive pole of a virtual DC voltage, and 0 when connected to the negative pole. However, in the circuit shown in FIG. 31, the logic signal is 1 when each phase of the load 2 is connected to the positive electrode 3P of the DC circuit and 0 when it is connected to the negative electrode 3N of the DC circuit. Output control pulses TU, TV, and TW correspond to the half-bridge circuits 3UB, 3VB, and 3WB, respectively, and control ON / OFF of switch elements included in the half-bridge circuits.

  As an example, in the operation example shown in FIG. 15 according to the second embodiment of the present invention, all output control pulses TU, TV, TW always have the same value of 0 or 1 at the change of the control period, and are switched at the change. Is never done. This means that all the phases of the load are fixed to the positive electrode 3P or the negative electrode 3N of the DC circuit at the change point and do not switch, and the switching operation of the switches related to all the phases of the load does not occur at the change point. To do.

  The above operation is the same as that of Embodiments 7 and 8 of the present invention for any of the multi-relative multiphase power conversion devices of Embodiments 4 and 6 of the present invention and any of Embodiments 2, 4 and 6 of the present invention. The same applies to any of the multi-relative multi-phase power converters to which these are applied.

  As described above, according to the ninth embodiment, with respect to the circuit configuration of the multi-relative multi-phase power converter, the phase of the AC power source is selectively connected to the positive electrode or the negative electrode of the DC circuit by the switch that selectively performs switching. Even if the voltage of the DC circuit is supplied to the load 2 by the half bridge circuit by outputting an arbitrary voltage between the positive electrode and the negative electrode, the load phase is connected before and after the change of the control period. The pole of the direct current circuit can be fixed, so that switching of the switch control pulse is not performed at all the transitions of the control period, and the switching operations of the switches related to the plurality of phases of the load 2 occur simultaneously. It can be realized not to.

Embodiment 10 FIG.
FIG. 32 is a block diagram showing a multi-relative multi-phase power converter according to Embodiment 10 of the present invention. In the figure, a main circuit 3S is connected between an AC power source 1 and a load 2, and the AC power source 1 The AC voltage is supplied to the load 2 by switching with a plurality of switches that selectively control the AC voltage. Other configurations are the same as those in FIG.

Next, the operation will be described.
In the multi-relative multi-phase power conversion device according to the ninth embodiment of the present invention, in the circuit shown in FIG. 31, the main circuit 3D has the switches 3PR, 3PS, 3PT, 3NR, 3NS, 3NT and half that selectively perform switching. Bridge circuit 3UB, 3VB, 3WB is included, one end of switch 3PR, 3PS, 3PT and one end of half bridge circuit 3UB, 3VB, 3WB are connected to positive electrode 3P of the DC circuit, one end of switch 3NR, 3NS, 3NT and half bridge The other ends of the circuits 3UB, 3VB, and 3WB are connected to the negative electrode 3N of the DC circuit, and the switches 3PR, 3PS, 3PT, 3NR, 3NS, and 3NT are selectively switched to perform positive switching 3P and negative electrode 3N of the DC circuit. Is configured to output an arbitrary DC voltage between As shown, the main circuit 3S includes a circuit 3RC and half-bridge circuits 3UB, 3VB, 3WB, one end of the half-bridge circuits 3UB, 3VB, 3WB is connected to the positive electrode 3P of the DC circuit, and the other end of the DC circuit The circuit 3RC connected to the negative electrode 3N may be configured to output an arbitrary DC voltage between the positive electrode 3P and the negative electrode 3N of the DC circuit by selectively performing switching. Further, the circuit 3RC may be any circuit configuration as long as it is composed of a switch element and a diode and generates an arbitrary voltage between the positive electrode 3P and the negative electrode 3N of the DC circuit. In this configuration, on / off of the switch elements in the circuit 3RC is controlled by the control pulses TRP, TRN, TSP, TSN, TTP, and TTN in the operation example shown in FIG.

  The operation of outputting an arbitrary DC voltage between the positive electrode 3P and the negative electrode 3N of the DC circuit by selectively switching is configured by the switches 3PR, 3PS, 3PT, 3NR, 3NS, and 3NT shown in FIG. 32 has the same function as that of the circuit 3RC shown in FIG. 32. Therefore, the operation of connecting the phase of the load 2 to the positive electrode 3P or the negative electrode 3N of the DC circuit at the change of the control period is also equivalent. From this, all phases of the load are fixed to the positive electrode 3P or the negative electrode 3N of the DC circuit at the change, and the switching operation of the switches related to all the phases of the load does not occur at the change. To do.

  As described above, according to the tenth embodiment, with respect to the circuit configuration of the multi-relative multi-phase power converter, the phase of the AC power supply 1 is selectively set to the positive electrode of the DC circuit or the circuit composed of the switch element and the diode. Even if it is connected to the negative electrode and outputs an arbitrary voltage between the positive electrode and the negative electrode, and the voltage of the DC circuit is supplied to the load 2 by the half-bridge circuit, the load 2 before and after the change of the control period Since the pole of the DC circuit to which the phase of the circuit is connected can be fixed, switching of the switch control pulse can be prevented at all the transitions of the control period, and the switching of the switches related to the plurality of phases of the load 2 can be prevented. It is possible to prevent the operations from occurring simultaneously.

1 is a configuration diagram showing a multi-relative multi-phase power conversion device according to Embodiment 1 of the present invention. It is a block diagram which shows the multiple relative multiphase power converter device for demonstrating a subject. It is a timing chart which shows operation of a section detector for explaining a subject. It is a flowchart which shows operation | movement of the electricity supply order controller for demonstrating a subject. It is a flowchart which shows operation | movement of the voltage ratio calculator for demonstrating a subject. It is a timing chart which shows operation | movement of the multi relative multi-phase power converter device for demonstrating a subject. It is a timing chart which shows operation | movement of the multi relative multi-phase power converter device for demonstrating a subject. It is a timing chart which shows operation | movement of the multi relative multi-phase power converter device for demonstrating a subject. It is a flowchart which shows operation | movement of the electricity supply order controller by Embodiment 1 of this invention. It is a flowchart which shows operation | movement of the voltage ratio calculator by Embodiment 1 of this invention. It is a timing chart which shows operation | movement of the multi relative polyphase power converter device by Embodiment 1 of this invention. It is a timing chart which shows operation | movement of the multi relative polyphase power converter device by Embodiment 1 of this invention. It is a block diagram which shows the multiple relative polyphase power converter device by Embodiment 2 of this invention. It is a flowchart which shows operation | movement of the voltage ratio calculator by Embodiment 2 of this invention. It is a timing chart which shows operation | movement of the multi relative polyphase power converter device by Embodiment 2 of this invention. It is a block diagram which shows the multi relative polyphase power converter device by Embodiment 3 of this invention. It is a flowchart which shows the operation | movement of the voltage ratio calculator by Embodiment 3 of this invention. It is a timing chart which shows operation | movement of the multi relative multiphase power converter device by Embodiment 3 of this invention. It is a block diagram which shows the multiple relative polyphase power converter device by Embodiment 4 of this invention. It is a timing chart which shows operation | movement of the section detector by Embodiment 4 of this invention. It is a timing chart which shows operation | movement of the multiple relative multiphase power converter device by Embodiment 4 of this invention. It is a timing chart which shows operation | movement of the multiple relative multiphase power converter device by Embodiment 4 of this invention. It is a block diagram which shows the multiple relative polyphase power converter device by Embodiment 5 of this invention. It is a flowchart which shows operation | movement of the voltage ratio calculator by Embodiment 5 of this invention. It is a timing chart which shows operation | movement of the multiple relative multiphase power converter device by Embodiment 5 of this invention. It is a timing chart which shows operation | movement of the multiple relative multiphase power converter device by Embodiment 5 of this invention. It is a block diagram which shows the multiple relative polyphase power converter device by Embodiment 6 of this invention. It is a flowchart which shows operation | movement of the voltage ratio calculator by Embodiment 6 of this invention. It is a timing chart which shows operation | movement of the multi relative polyphase power converter device by Embodiment 6 of this invention. It is a timing chart which shows operation | movement of the multi relative polyphase power converter device by Embodiment 6 of this invention. It is a block diagram which shows the multiple relative polyphase power converter device by Embodiment 9 of this invention. It is a block diagram which shows the multiple relative polyphase power converter device by Embodiment 10 of this invention.

Explanation of symbols

1 AC power supply, 2 loads, 3, 3D, 3S main circuit, 3UR, 3US, 3UT, 3VR, 3VS, 3VT, 3WR, 3WS, 3WT, 3PR, 3PS, 3PT, 3NR, 3NS, 3NT switch, 3UB, 3VB, 3WB half bridge circuit, 3RC circuit, 3P positive electrode, 3N negative electrode, 5U, 5V, 5W current detector, 10, 10a, 10b, 10c, 10d, 10e, 10u input controller, 11, 11c, 11d section detector, 12 , 12c, 12d, 12e conversion detector, 13, 13u energization sequence controller, 14, 14a, 14b, 14d, 14e, 14u voltage ratio calculator, 15, 15a, 15b, 15c, 15d input pulse generator, 20 voltage Commander, 30, 30c Output controller, 40 Gate controller.

Claims (9)

A main circuit connected between the AC power source and the load, and switched by a plurality of switches that selectively control the AC voltage of the AC power source to supply the AC voltage to the load;
Based on the AC voltage of the AC power supply, an input control ratio that determines a ratio of time for connecting the phase of the AC power supply to the load, and an input control pulse that temporally determines the phase of the AC power supply connected to the load. An input controller to generate,
A voltage command device for generating a voltage command value to be supplied to the load;
An output controller for generating an output control pulse for temporally determining the phase of the load connected to the AC power source based on a voltage command value by the voltage command device and an input control ratio by the input controller;
A gate controller that generates a gate control pulse that temporally determines selective control of the plurality of switches of the main circuit based on an input control pulse by the input controller and an output control pulse by the output controller; With
The input controller is
A section detector for detecting which phase section the phase of the AC voltage of the AC power supply is;
A conversion detector for detecting that the phase section has changed;
An energization sequence controller for determining an order of connection to the load of the phase of the AC power supply;
A voltage ratio calculator for determining the input control ratio based on a conversion signal from the conversion detector;
A multi-relative multi-phase power converter comprising an input pulse generator for generating the input control pulse. Section detector
Based on the AC voltage of the AC power supply, generate a section signal indicating which phase section the phase of the AC voltage of the AC power supply is a phase section obtained by dividing the phase of the AC power supply by 60 degrees,
Conversion detector
Based on the section signal from the section detector, a conversion signal is generated to indicate that the section signal has been converted,
The energization sequence controller
Based on the conversion signal from the conversion detector, an energization sequence signal is generated,
The voltage ratio calculator is
Based on the AC voltage of the AC power source, the section signal by the section detector, the conversion signal by the conversion detector, and the energization sequence signal by the energization sequence controller, an input control ratio is generated,
The input pulse generator is
2. The multi-relative method according to claim 1, wherein an input control pulse is generated based on a section signal from the section detector, an energization sequence signal from the energization sequence controller, and an input control ratio from the voltage ratio calculator. Multiphase power converter. The voltage ratio calculator is
Based on the AC voltage of the AC power source, the section signal by the section detector, the conversion signal by the conversion detector, and the energization sequence signal by the energization sequence controller, an input control ratio and a holding signal are generated,
The input pulse generator is
3. An input control pulse is generated based on a section signal from the section detector, an energization sequence signal from the energization sequence controller, and an input control ratio and hold signal from the voltage ratio calculator. Multi-relative multi-phase power converter. Section detector
Based on the AC voltage of the AC power supply, generate a section signal indicating which phase section the phase of the AC voltage of the AC power supply is a phase section obtained by dividing the phase of the AC power supply by 60 degrees,
Conversion detector
Based on the section signal from the section detector, a conversion signal is generated to indicate that the section signal has been converted,
The energization sequence controller
Generate energization sequence signal,
The voltage ratio calculator is
Based on the AC voltage of the AC power source, the section signal by the section detector, the conversion signal by the conversion detector, and the energization sequence signal by the energization sequence controller, an input control ratio and a holding signal are generated,
The input pulse generator is
2. An input control pulse is generated based on a section signal from the section detector, an energization sequence signal from the energization sequence controller, and an input control ratio and hold signal from the voltage ratio calculator. Multi-relative multi-phase power converter. A main circuit connected between the AC power source and the load, and switched by a plurality of switches that selectively control the AC voltage of the AC power source to supply the AC voltage to the load;
An input controller for generating an input control pulse for temporally determining a phase of the AC power source connected to the load based on an AC voltage of the AC power source;
A voltage command device for generating a voltage command value to be supplied to the load;
An output controller that generates an output control pulse that temporally determines a phase of the load connected to the AC power supply based on a voltage command value by the voltage commander;
A gate controller that generates a gate control pulse that temporally determines selective control of the plurality of switches of the main circuit based on an input control pulse by the input controller and an output control pulse by the output controller; With
The input controller is
A section detector for detecting which phase section the phase of the AC voltage of the AC power supply is;
A conversion detector for detecting that the phase section has changed;
A multi-relative multi-phase power converter, comprising: an input pulse generator that generates the input control pulse based on a conversion signal from the conversion detector. Section detector
Based on the AC voltage of the AC power supply, generate an intermediate section signal indicating which phase section the phase of the AC voltage of the AC power supply is about the phase section obtained by dividing the phase of the AC power supply by 60 degrees,
Conversion detector
Based on the intermediate section signal from the section detector, a first intermediate conversion signal indicating that the intermediate section signal has converted from an even value to an odd value, and that the intermediate section signal has converted from an odd value to an even value. Generate a second intermediate conversion signal,
The input pulse generator is
6. The multi-relative polyphase according to claim 5, wherein an input control pulse is generated based on the intermediate section signal by the section detector and the first intermediate conversion signal and the second intermediate conversion signal by the conversion detector. Power conversion device. A main circuit connected between the AC power source and the load, and switched by a plurality of switches that selectively control the AC voltage of the AC power source to supply the AC voltage to the load;
Based on the AC voltage of the AC power supply, an input control ratio that determines a ratio of time for connecting the phase of the AC power supply to the load, and an input control pulse that temporally determines the phase of the AC power supply connected to the load. An input controller to generate,
A voltage command device for generating a voltage command value to be supplied to the load;
An output controller for generating an output control pulse for temporally determining the phase of the load connected to the AC power source based on a voltage command value by the voltage command device and an input control ratio by the input controller;
A gate controller that generates a gate control pulse that temporally determines selective control of the plurality of switches of the main circuit based on an input control pulse by the input controller and an output control pulse by the output controller; With
The input controller is
A section detector for detecting which phase section the phase of the AC voltage of the AC power supply is;
A conversion detector for detecting that the phase section has changed;
A voltage ratio calculator for determining the input control ratio based on a conversion signal from the conversion detector;
A multi-relative multi-phase power converter, comprising: an input pulse generator that generates the input control pulse based on a conversion signal from the conversion detector. The section detector
Based on the AC voltage of the AC power supply, the section signal indicating which phase section the phase of the AC voltage of the AC power supply is a phase section obtained by dividing the phase of the AC power supply by 60 degrees, and the phase of the AC power supply is 60 Generate an intermediate section signal that indicates which phase interval is in the phase interval divided by different delimiters each time,
Conversion detector
Based on the intermediate section signal from the section detector, an intermediate conversion signal is generated to indicate that the intermediate section signal has been converted,
The voltage ratio calculator is
Based on the AC voltage of the AC power source, the section signal by the section detector, the intermediate section signal, and the intermediate conversion signal by the conversion detector, an input control ratio is generated,
The input pulse generator is
8. The input control pulse is generated based on a section signal by the section detector, an intermediate section signal, an intermediate conversion signal by the conversion detector, and an input control ratio by the voltage ratio calculator. Multi-relative multi-phase power converter. Section detector
Based on the AC voltage of the AC power supply, the section signal indicating which phase section the phase of the AC voltage of the AC power supply is a phase section obtained by dividing the phase of the AC power supply by 60 degrees, and the phase of the AC power supply is 60 Generate an intermediate section signal that indicates which phase interval is in the phase interval divided by different delimiters each time,
Conversion detector
Based on the section signal from the section detector, a conversion signal indicating that the section signal has been converted is generated, and on the basis of the intermediate section signal, an intermediate conversion signal indicating that the intermediate section signal has been converted is generated. ,
The voltage ratio calculator is
An input control ratio is generated based on the AC voltage of the AC power source, the section signal by the section detector, the intermediate section signal, and the conversion signal by the conversion detector, the intermediate conversion signal,
The input pulse generator is
An input control pulse is generated based on a section signal by the section detector, an intermediate section signal, a conversion signal by the conversion detector, an intermediate conversion signal, and an input control ratio by the voltage ratio calculator. Item 8. The multi-relative multiphase power converter according to Item 7.

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