JP2006276006A - Harmonic analysis method in power system - Google Patents
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本発明は電力系統における電圧・電流に対し,高調波を含む実効値・位相角の高精度な計測方法に関するものである。 The present invention relates to a highly accurate measurement method for effective values and phase angles including harmonics with respect to voltage and current in a power system.
周期的な信号波形に含まれる周波数成分を分析する方法としてフーリエ変換がある。これをディジタル信号処理によって求める場合には,信号波形を等間隔にサンプリングし,得られたデータ列に対して演算を行う。この演算を離散フーリエ変換(以下,「DFT」とする)という。電力系統においては,電圧や電流波形に含まれる高調波成分を解析する場合に用いられる。 There is a Fourier transform as a method for analyzing frequency components contained in a periodic signal waveform. When this is obtained by digital signal processing, the signal waveform is sampled at equal intervals, and an operation is performed on the obtained data string. This operation is called discrete Fourier transform (hereinafter referred to as “DFT”). In the power system, it is used to analyze harmonic components contained in voltage and current waveforms.
具体的に,下記の数式1で表される電圧波形を例にして,その波形の実効値Veと位相角φ0を求める計算について説明する。ここでは,基本波成分について説明するが,高調波成分も同様の考え方で求めることができる。 Specifically, the calculation for obtaining the effective value V e and the phase angle φ 0 of the waveform represented by the following Equation 1 will be described as an example. Here, the fundamental wave component will be described, but the harmonic component can be obtained in the same way.
v0,v1,・・・,v10,v11 (2)
このデータ列に対し,下記の数式2に従ってDFT演算を行うと,複素数値V11を得る。
When a DFT operation is performed on this data string according to the following Equation 2, a complex value V 11 is obtained.
f0はフーリエ変換の基本周波数(以下,「設定周波数」とする)を表しており,f0=1/(N・TS)の関係がある。系統周波数fと設定周波数f0が等しければ,数式2の計算結果はV11=Ve・exp(jφ0)となるので,DFT演算によって実効値Veと位相角φ0を求めることができる。 f 0 represents a fundamental frequency of Fourier transform (hereinafter referred to as “set frequency”), and has a relationship of f 0 = 1 / (N · T S ). If the system frequency f is equal to the set frequency f 0 , the calculation result of Equation 2 is V 11 = V e · exp (jφ 0 ), and therefore the effective value V e and the phase angle φ 0 can be obtained by DFT calculation. .
ここで,下記の数式3で定義される関数Wi
v1,・・・,v11,v12 (6)
となるので,DFT演算は下記の数式5のようになる。
v 1 , ..., v 11 , v 12 (6)
Therefore, the DFT operation is as shown in Equation 5 below.
しかし,電力系統の周波数は標準周波数(東日本50Hz,西日本60Hz)に対し最大±0.3Hzの幅をもって周波数が変動している。したがって,電圧波形や電流波形の周波数も時々刻々変動しているため,系統周波数fと設定周波数f0との間に偏差が生じる。この周波数偏差が生じるとVr=Ve・exp(jφ0)とならず,正確に実効値Veと位相角φ0を求めることができないという問題点がある。 However, the frequency of the power system fluctuates with a maximum width of ± 0.3 Hz with respect to the standard frequency (eastern Japan 50 Hz, western Japan 60 Hz). Therefore, since the frequency of the voltage waveform and the current waveform is also momentarily varies, deviation occurs between the set frequency f 0 and the system frequency f. When this frequency deviation occurs, V r = V e · exp (jφ 0 ) is not obtained, and there is a problem that the effective value V e and the phase angle φ 0 cannot be obtained accurately.
具体的な例として,系統周波数59.7[Hz],実効値100.0[V]の交流電圧に対して,設定周波数60.0[Hz]のRDFT演算を行った結果を図4に示す。100.0[V]の実効値の波形に対し,演算結果には誤差を含んでおり,正確に実効値を求めることができていない。 As a specific example, FIG. 4 shows a result of performing RDFT calculation at a set frequency 60.0 [Hz] on an AC voltage having a system frequency 59.7 [Hz] and an effective value 100.0 [V]. For the RMS value waveform of 100.0 [V], the calculation result includes an error, and the RMS value cannot be obtained accurately.
このような周波数偏差による誤差の補正方法を説明するため,周波数偏差と誤差の関係について説明する。系統周波数fが設定周波数f0からΔf(=f−f0)だけ偏差を持っている場合を考える。このとき,r番目のサンプリングデータは,下記の数式9で表すことができる。
このデータに対して数式8を用いてRDFT演算を行うと,下記の数式10で表される演算結果を得る。
実効値は,複素数値Vrの大きさとして求められるので,数式10の計算結果から,下記の数式11のようになる。
したがって,元の波形の実効値Veと比較すると下記の数式12の結果が,周波数偏差によって生じる誤差となる。
したがって,下記の数式13で表されるErrが実効値に対する誤差の割合となる。
数式10に示すように,A,B,αr,βrは周波数偏差Δfを含む値であるので,周波数偏差Δfと誤差割合Errの関係を計算すると図5のようになる。この計算例における計算条件は,N=128,TS=1/(60Hz×128サンプル)=130.2[μs]である。図から分かるように±0.3Hzの範囲内では,周波数偏差Δfと誤差割合Errの関係は比例関係と見なすことができる。図5はr=0の場合を示したものであるが,rの値によって直線の傾きが変わるのみであり,比例関係は変わらない。 As shown in Equation 10, since A, B, α r , and β r are values including the frequency deviation Δf, the relationship between the frequency deviation Δf and the error rate Err is calculated as shown in FIG. The calculation conditions in this calculation example are N = 128, T S = 1 / (60 Hz × 128 samples) = 130.2 [μs]. As can be seen from the figure, within the range of ± 0.3 Hz, the relationship between the frequency deviation Δf and the error rate Err can be regarded as a proportional relationship. FIG. 5 shows the case where r = 0, but only the slope of the straight line changes depending on the value of r, and the proportionality does not change.
次に誤差割合Errの時間変化を計算した結果を図6に示す。図のようにErrの時間変化は振動的に変化するので,その振動周波数について説明する。数式13において,AとBは時間によって変化しない値である。そこで,(αr−βr)をθと表し,これを計算すると下記の式のようになる。 Next, FIG. 6 shows the result of calculating the time change of the error ratio Err. As shown in the figure, the time variation of Err changes in a vibration manner, so the vibration frequency will be described. In Equation 13, A and B are values that do not change with time. Therefore, (α r −β r ) is expressed as θ, and this is calculated as follows.
θ=αr−βr
=4π(f0+Δf)r・TS+2φ0−2π(f0+Δf)・(N−1)・TS (16)
この式において,第1項目中のr・TSは,r番目のデータをサンプリングした時の時間を表すので,これをtrと表記する。すなわち,第1項目は時間によって変化する項であり,第2項目と第3項目は時間によって変化しない項である。このことから,θ=ωtr+φとするとωとφはそれぞれ下記の式のように表すことができる。
θ = α r −β r
= 4π (f 0 + Δf) r · T S + 2φ 0 −2π (f 0 + Δf) · (N−1) · T S (16)
In this equation, r · T S in the first item represents the time when the r-th data is sampled, and is expressed as tr . That is, the first item is a term that changes with time, and the second item and the third item are terms that do not change with time. From this, if θ = ωt r + φ, ω and φ can be expressed by the following equations, respectively.
ω=4π(f0+Δf)=2π・2(f0+Δf)
φ=2φ0−2π(f0+Δf)・(N−1)・TS (17)
したがって,Errの振動分の周波数は,2(f0+Δf)=2fとなり,系統周波数の2倍の周波数となる。
ω = 4π (f 0 + Δf) = 2π · 2 (f 0 + Δf)
φ = 2φ 0 −2π (f 0 + Δf) · (N−1) · T S (17)
Therefore, the frequency of vibration of Err is 2 (f 0 + Δf) = 2f, which is twice the system frequency.
このように周波数偏差によって生じる誤差には,誤差の大きさが周波数偏差に比例し,誤差の振動分は系統周波数の2倍の周波数で変化するという性質がある。 As described above, the error caused by the frequency deviation has a property that the magnitude of the error is proportional to the frequency deviation, and the vibration of the error changes at twice the system frequency.
これらの誤差の性質を使って,その補正法を説明する。 The correction method is explained using the nature of these errors.
一つの電圧波形に対して,2つの異なる設定周波数でRDFT演算を同時に行う。この設定周波数をそれぞれ第1設定周波数f0a,第2設定周波数f0bとする。サンプリング数をNaとNbとすると第1設定周波数はf0a=1/(Na・TS)の関係となり,第2設定周波数はf0b=1/(Nb・TS)の関係となる。第1設定周波数f0aと第2設定周波数f0bは任意に選ぶことができるが,電力系統の周波数偏差が最大でも±0.3Hzであることを考慮して,電力系統の標準周波数の±0.4Hzを超えない程度に選ぶ。例えば,60Hzの系統の場合,第1設定周波数f0a=59.6[Hz],第2設定周波数f0b=60.4[Hz]というように選ぶ。そして下記の数式14によってRDFT演算を行うと,図7に示すように,それぞれの演算結果として複素数値VraとVrbが得られる。 For one voltage waveform, RDFT calculation is simultaneously performed at two different set frequencies. These set frequencies are defined as a first set frequency f 0a and a second set frequency f 0b , respectively. If the number of samplings is N a and N b , the first set frequency has a relationship of f 0a = 1 / (N a · T S ), and the second set frequency has a relationship of f 0b = 1 / (N b · T S ). It becomes. The first set frequency f 0a and the second set frequency f 0b can be selected arbitrarily, but considering that the frequency deviation of the power system is ± 0.3 Hz at the maximum, it is ± 0.4 Hz of the standard frequency of the power system Select so as not to exceed. For example, in the case of a 60 Hz system, the first setting frequency f 0a = 59.6 [Hz] and the second setting frequency f 0b = 60.4 [Hz] are selected. Then, when the RDFT operation is performed according to the following equation 14, complex values V ra and V rb are obtained as the respective operation results, as shown in FIG.
a:b≒Δfa:Δfb (18)
周波数偏差Δfa,Δfbは文献[1]に記載の方法によって求めることができる。
文献[1] 中野,他:「同期フェーザ計測に基づく実時間電力系統周波数検出」,
電気学会論文誌C, 122,12, pp2076-2082,2002
a : b ≒ Δf a : Δf b (18)
The frequency deviations Δf a and Δf b can be obtained by the method described in the document [1].
[1] Nakano, et al .: “Real-time power system frequency detection based on synchronous phasor measurement”,
IEEJ Transaction C, 122,12, pp2076-2082,2002
また,誤差の振動分の周波数は,設定周波数に因らず系統周波数の2倍であることから,VraとVrbに含まれる誤差の振動分の周波数は等しくなる。例えば,系統周波数f=60.2[Hz],実効値100.0[V]の交流電圧に対して,第1設定周波数f0a=59.6[Hz],第2設定周波数f0b=60.4[Hz]でRDFT演算を行った結果を図9に示す。VraとVrbの振動分の周波数はお互いに等しいことが分かる。また,この場合,
a:b≒Δfa:Δfb=(60.2−59.6):(60.2−60.4)=3:−1 (19)
となっている。したがって,下記の数式15のように,a:bを重み係数としてそれぞれの実効値を加重平均することにより,誤差を相殺し,誤差を減少した複素数値Vrpを得ることができる。
a: b≈Δf a : Δf b = (60.2−59.6) :( 60.2−60.4) = 3−1 (19)
It has become. Therefore, as shown in Equation 15 below, by calculating the weighted average of the respective effective values using a: b as weighting factors, it is possible to obtain a complex value V rp in which the error is canceled and the error is reduced.
周波数が変動している電力系統の電圧や電流の計測において,RDFT演算の連続性を失うことなく,簡単な四則演算による補正によって正確な実効値を求めることが可能となる。 In measuring the voltage and current of a power system whose frequency is fluctuating, it is possible to obtain an accurate effective value by correction by simple four arithmetic operations without losing the continuity of the RDFT operation.
提案法を実装した電力系統高調波解析装置を図10に示す。 Figure 10 shows a power system harmonic analyzer that implements the proposed method.
電圧入力ボックス1aには電圧変換器(PT)1を備え,DSPボード7の入力部にあるアナログ-ディジタルコンバータ(ADC)2の入力上限電圧を超えない値に降圧する。この例では,100[V]の交流電圧を1[V]の交流電圧に変換している。ADC2は,一定のサンプリング間隔でアナログデータをディジタルデータに変換している。この例で用いたADC2のサンプリング周波数は8[kHz]である。変換されたディジタルデータは,メモリ(RAM)4を経由してDSP3に取り込まれ,DSP3において上記で説明したRDFT演算と補正演算が行われる。そしてRAM4に保存された演算結果は,LANポート6を通してパソコン(PC)8へ転送され,PC8上で演算結果が表示される。 The voltage input box 1a includes a voltage converter (PT) 1 and steps down to a value that does not exceed the input upper limit voltage of the analog-digital converter (ADC) 2 in the input section of the DSP board 7. In this example, 100 [V] AC voltage is converted to 1 [V] AC voltage. The ADC 2 converts analog data into digital data at a constant sampling interval. The sampling frequency of ADC2 used in this example is 8 [kHz]. The converted digital data is taken into the DSP 3 via the memory (RAM) 4 and the above-described RDFT operation and correction operation are performed in the DSP 3. The calculation result stored in the RAM 4 is transferred to the personal computer (PC) 8 through the LAN port 6 and the calculation result is displayed on the PC 8.
このシステムを用いて波形発生器で電圧実効値100[V],周波数f=59.9[Hz]の波形を作成し,電圧入力ボックス1aにあるPT1の入力に入れた。設定周波数f0=60.15[Hz](=8[kHz]/133[サンプル])でRDFT演算を行った結果を図11に示す。この電圧波形の周波数と設定周波数に差があるので,演算結果に誤差が生じている。これに対し,第1設定周波数f0a=59.70[Hz](=8[kHz]/134[サンプル])と第2設定周波数f0b=60.15[Hz](=8[kHz]/133[サンプル])でRDFT演算を行い,上記に説明の方法で補正を行った結果を図12に示す。従来の方法に比べて大幅に誤差が低減できていることが分かる。 Using this system, a waveform generator with a voltage effective value of 100 [V] and a frequency of f = 59.9 [Hz] was created and input to the PT1 input in the voltage input box 1a. FIG. 11 shows the result of the RDFT calculation performed at the set frequency f 0 = 60.15 [Hz] (= 8 [kHz] / 133 [sample]). Since there is a difference between the frequency of the voltage waveform and the set frequency, an error occurs in the calculation result. On the other hand, the first set frequency f 0a = 59.70 [Hz] (= 8 [kHz] / 134 [sample]) and the second set frequency f 0b = 60.15 [Hz] (= 8 [kHz] / 133 [sample] FIG. 12 shows the result of performing the RDFT operation in step) and performing correction by the method described above. It can be seen that the error can be greatly reduced as compared with the conventional method.
ここで説明した誤差の補正方法は,電圧波形の基本波成分についてのものであるが,高調波成分も同じ方法で補正することができ,高い精度で実効値を求めることができる。また,電流波形についても電流変換器(CT)を用いてADCにデータを取り込むことができれば,求める実効値の大きさが変わるのみであり,同様の方法で誤差を補正することができる。 The error correction method described here is for the fundamental component of the voltage waveform, but the harmonic component can also be corrected by the same method, and the effective value can be obtained with high accuracy. If the current waveform can be taken into the ADC using the current converter (CT), only the magnitude of the effective value to be obtained can be changed, and the error can be corrected by the same method.
本実施形態において,2つの設定周波数に応じたsin関数のデータおよびcos関数のデータをあらかじめROMに記憶しておけば,DSP内で三角関数の演算を行うことなく,精度の高い実効値計算が可能になる。このため,DSPのプログラムを簡単にすることができ,サンプリング周期を短くして,高い周波数成分の計算が可能になる。 In this embodiment, if the sin function data and the cos function data corresponding to the two set frequencies are stored in the ROM in advance, high-accuracy RMS value calculation can be performed without performing trigonometric functions in the DSP. It becomes possible. For this reason, the DSP program can be simplified, the sampling cycle can be shortened, and high frequency components can be calculated.
1 電圧変換器(PT)
1a 電圧入力ボックス
2 アナログ-ディジタル変換器(ADC)
3 ディジタル・シグナル・プロセッサ(DSP)
4 メモリ(RAM)
5 メモリ(ROM)
6 LANポート
7 DSPボード
8 パソコン(PC)
1 Voltage converter (PT)
1a Voltage input box
2 Analog-to-digital converter (ADC)
3 Digital signal processor (DSP)
4 Memory (RAM)
5 Memory (ROM)
6 LAN port
7 DSP board
8 PC (PC)
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