JP2006094303A - Variable phase shifter - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a variable phase shifter having a large amount of phase shift in output voltage and a high stability during phase shift. <P>SOLUTION: At a variable phase shifter 10, a variable reactance circuit made of capacitors 30, 36, variable capacity diodes 32, 38, and inductors 34, 40 is connected electrically among a 0° terminal 14 and a 90° terminal 16 of a 90° hybrid coupler 20 and earth (GND). When a high frequency input signal Si is supplied to an input terminal 12, a high frequency output signal St is outputted from an output terminal 18. On this occasion, a control voltage Vc is impressed from a voltage control terminal 52 via the coils 46, 48 to variable capacity diodes 32, 38 to change the phase θ of the high frequency output signal St. <P>COPYRIGHT: (C)2006,JPO&NCIPI

Description

  The present invention relates to a variable phase shifter having a 90 ° hybrid coupler, which can increase the amount of change in the phase of an output signal output from the 90 ° hybrid coupler and stably change the phase. The present invention relates to a variable phase shifter.

  Conventionally, in a high-frequency wireless device, a distortion in an output signal of the power amplifier is compensated by arranging a variable phase shifter in front of the power amplifier (see Patent Document 1).

  As shown in FIG. 10, the conventional variable phase shifter 100 includes a 90 ° hybrid coupler 108 having four terminals (an input terminal 110, a 90 ° terminal 112, a 0 ° terminal 118, and an output terminal 126).

  A capacitor 106 is electrically connected between the input terminal 110 and the 90 ° hybrid coupler 108, and a capacitor 128 is electrically connected between the output terminal 126 and the 90 ° hybrid coupler 108.

  The cathode K1 of the variable capacitance diode 116 and the cathode K2 of the variable capacitance diode 122 are electrically connected via two coils 134 and 136. A voltage control terminal 132 is electrically connected between the coils 134 and 136, and a capacitor 138 is electrically connected between the voltage control terminal 132 and ground (GND).

  In this case, the capacitors 114 and 120 are capacitors having substantially the same capacitance value. The coils 134 and 136 are also coils having substantially the same inductance. Further, the variable capacitance diodes 116 and 122 are diodes having substantially the same electrical characteristics. Accordingly, a phase control circuit having substantially the same impedance is electrically connected between the 90 ° terminal 112 and the 0 ° terminal 118 and the ground.

  Next, the operation of the variable phase shifter 100 will be described.

  When the high frequency input signal Si is supplied to the input terminal 110, a high frequency output signal St having a phase θ different from that of the high frequency input signal Si is output from the output terminal 126. This phase θ is the phase θ of the phase control circuit electrically connected between the 90 ° terminal 112 and the 0 ° terminal 118 and the ground.

  In this case, when a low-frequency control voltage Vc is applied from the voltage control terminal 132 to the variable capacitance diodes 116 and 122, the junction capacitance C of the variable capacitance diodes 116 and 122 changes as the voltage value of the control voltage Vc changes. Therefore, the impedance and phase θ of the phase control circuit change. Therefore, the phase θ of the high frequency output signal St can be controlled to a predetermined value by changing the control voltage Vc.

JP 2001-285006 A

  When the junction capacitance C of the variable capacitance diodes 116 and 122 is changed by the control voltage Vc, the ideal variable range of the junction capacitance C is that the resonance between the coils 134 and 136 and the variable capacitance diodes 116 and 122 occurs. The range is from the capacitance value of the variable capacitance diodes 116 and 122 when the phase control circuit is in a short state to 0 pF which is the capacitance value of the variable capacitance diodes 116 and 122 when the phase control circuit is in an open state. That is, the ideal phase change amount of the phase θ ranges from a phase (0 °) where the impedance of the phase control circuit is only a resistance component to a phase (180 °) where the impedance of the phase control circuit is maximum. It is.

  However, in an actual high-frequency wireless device, a stray capacitance exists in a package in which the variable phase shifter 100 is accommodated or a chip configured with the variable phase shifter 100, and the reactance of this stray capacitance is included in the impedance. As a result, the phase change amount of the phase θ may be reduced.

  Therefore, in an actual wireless device, a plurality of variable phase shifters 100 are connected to increase the phase change amount of the phase θ to compensate for the decrease in the phase change amount. For example, if four variable phase shifters 100 having a phase change amount of 90 ° are connected in cascade, the wireless device can secure a phase change amount of 360 °. However, if a plurality of variable phase shifters 100 are mounted on a wireless device, there is a problem that the wireless device is increased in size.

  There is also a problem that even if the phase θ of the high-frequency output signal St is changed, the phase θ cannot be changed stably due to the stray capacitance described above.

  The present invention has been made in consideration of such problems, and provides a variable phase shifter capable of increasing the amount of phase change of an output signal and stably changing the phase of the output signal. The purpose is to do.

  A variable phase shifter according to the present invention is a variable phase shifter having at least one variable capacitance element, wherein an inductance component is connected to the variable capacitance element. Since the capacitance change due to the variable capacitance element and the phase amount of the inductance component are added, the change amount can be increased.

  When the 90 ° hybrid coupler having the input terminal, the output terminal, the 0 ° terminal, and the 90 ° terminal is provided, the first phase control circuit is electrically connected between the 0 ° terminal and the ground. And a second phase control circuit having substantially the same impedance as the first phase control circuit is electrically connected between the 90 ° terminal and the ground, and the first phase control circuit Includes a first variable capacitance element and a first inductor electrically connected to the first variable capacitance element, and the second phase control circuit includes a second variable capacitance element, You may make it have the 2nd inductor electrically connected to this 2nd variable capacitance element.

  In this case, the capacitances of the first and second variable capacitance elements are changed by the control voltage supplied to the first and second variable capacitance elements, and the output terminal is changed by the change in the capacitance. The phase of the output signal that is output from is changed.

  As described above, the first and second phase control circuits are configured by variable reactance circuits, and the phases of the first and second phase control circuits are the same as the phases of the first and second variable capacitance elements. The phase change range of the first and second phase control circuits is expanded, and the phase change amount of the output signal can be increased.

  Using the first and second variable capacitance diodes for the first and second variable capacitance elements, the control voltage is supplied to the first and second cathode terminals of the first and second variable capacitance diodes. It is preferable. In this case, the control voltage is a reverse bias voltage of the first and second variable capacitance diodes. By changing the reverse bias voltage, the junction capacitance of the first and second variable capacitance diodes can be changed.

  A specific circuit configuration of the first phase control circuit is that the first cathode terminal is electrically connected to the 0 ° terminal, the first anode terminal of the first variable capacitance diode, and the ground. The first inductor is electrically connected between the 90 ° terminal and the second cathode terminal is electrically connected to the 90 ° terminal. The second inductor is electrically connected, and the second inductor is electrically connected between the second anode terminal of the second variable capacitance diode and the ground.

  In this case, a first coupling capacitor is further electrically connected between the 0 ° terminal and the first cathode terminal, and further between the 90 ° terminal and the second cathode terminal. The second coupling capacitor may be electrically connected. Accordingly, the control voltage is prevented from entering the 90 ° hybrid coupler via the 0 ° terminal and the 90 ° terminal, and the influence of the control voltage on the output signal is suppressed. If the input signal supplied to the input terminal is a signal having a frequency higher than that of the control voltage, the above-described suppression effect becomes significant. Further, matching between the 90 ° hybrid coupler and the first variable capacitance element and matching between the 90 ° hybrid coupler and the second variable capacitance element can be achieved.

  Further, a specific circuit configuration for supplying the control voltage to the first and second cathode terminals is such that one end of a first coil is electrically connected to the first cathode terminal, and the second One end of a second coil is electrically connected to the cathode terminal of the first, and a voltage control terminal is electrically connected to the other end of the first and second coils, and the control voltage is supplied from the voltage control terminal to the cathode terminal. A circuit configuration may be adopted in which the first and second cathode terminals are supplied via the first and second coils. As a result, even if a high-frequency signal due to stray capacitance enters the first and second phase control circuits, the first and second coils function as a high resistance to the high-frequency signal. Is attenuated in the first and second coils. That is, it is possible to realize a variable phase shifter that is strong against high frequency noise and can stably change the phase of the output signal.

  Further, if a bypass capacitor is electrically connected between the voltage control terminal and the ground, the above-described high-frequency signal can be bypassed to the ground, so that the high-frequency signal can enter the voltage control terminal. It can be avoided.

  Further, a third coupling capacitor is electrically connected to the input terminal, a fourth coupling capacitor is electrically connected to the output terminal, and the input signal is passed through the third coupling capacitor. And the output signal may be output via the fourth coupling capacitor. In this case, it is possible to prevent a DC signal or a low frequency signal different from the input signal from passing. Further, matching between the input terminal and the external circuit connected to the input terminal and matching between the output terminal and the external circuit connected to the output terminal can be performed.

  In addition, a specific structure of the variable phase shifter according to the present invention is a 90 ° including an input terminal, an output terminal, a 0 ° terminal, and a 90 ° terminal in a dielectric substrate composed of a plurality of dielectric layers. A hybrid coupler, first and second inductors, and first and second coupling capacitors are formed, and the first and second variable capacitors are formed on a wiring pattern formed on the surface of the dielectric substrate. A diode is mounted, and a first phase control circuit including the first inductor, the first variable capacitance diode, and the first coupling capacitor is electrically connected between the 0 ° terminal and the ground. The second inductor, the second variable capacitance diode, and the second coupling capacitor between the 90 ° terminal and the ground, and the first phase control. Almost same as circuit A second phase control circuit having one impedance may be electrically connected.

  Another specific structure of the variable phase shifter according to the present invention includes an input terminal, an output terminal, a 0 ° terminal, and a 90 ° terminal on a wiring pattern of a circuit board constituted by a plurality of dielectric layers. The 90 ° hybrid coupler provided, the first and second variable capacitance diodes, and the first and second coupling capacitors are mounted, and the wiring pattern forms the first and second inductors, A first phase control circuit including the first inductor, the first variable capacitance diode, and the first coupling capacitor is electrically connected between the 0 ° terminal and the ground. Between the terminal and the ground, includes the second inductor, the second variable capacitance diode, and the second coupling capacitor, and substantially the same impedance as the first phase control circuit. A second phase control circuit having impedance may be electrically connected.

  Furthermore, each of the first and second inductors may be a variable inductor. Thereby, by adjusting the inductance length of each of the first and second inductors with a stub or the like, the phase change amount of the output signal can be adjusted to a desired characteristic, and variations between devices can be absorbed. Can be adjusted to a different standard (phase change amount).

  As described above, according to the variable phase shifter according to the present invention, the phase change amount of the output signal can be increased, and the phase of the output signal can be changed stably.

  Hereinafter, embodiments of a variable phase shifter according to the present invention will be described with reference to FIGS.

  As shown in FIG. 1, the variable phase shifter 10 according to the present embodiment includes a 90 ° hybrid coupler 20 having four terminals (an input terminal 12, a 0 ° terminal 14, a 90 ° terminal 16, and an output terminal 18). Have. The 90 ° hybrid coupler 20 is a hybrid coupler in which the input / output impedances of the four terminals 12, 14, 16, 18 described above are, for example, 50Ω.

  A capacitor 22 is electrically connected between the input terminal 12 and the 90 ° hybrid coupler 20, and a capacitor 26 is electrically connected between the output terminal 18 and the 90 ° hybrid coupler 20. A capacitor 30, a variable capacitance diode 32, and an inductor 34 are electrically connected between the 0 ° terminal 14 and ground (GND). A capacitor 36, a variable capacitance diode 38, and an inductor 40 are electrically connected between the 90 ° terminal 16 and ground (GND).

  In addition, coils 46 and 48 are connected in series between a connection point 42 between the capacitor 30 and the variable capacitance diode 32 and a connection point 44 between the capacitor 36 and the variable capacitance diode 38.

  Further, the connection point 50 between the coil 46 and the coil 48 and the voltage control terminal 52 are electrically connected. A capacitor 54 is electrically connected between the voltage control terminal 52 and the ground (GND).

  In this case, the capacitors 30 and 36 have substantially the same capacitance value. The coils 46 and 48 also have substantially the same inductance. Furthermore, the variable capacitance diodes 32 and 38 are diodes having substantially the same electrical characteristics. Furthermore, the inductors 34 and 40 also have substantially the same inductance. Thus, a variable reactance circuit having substantially the same reflection coefficient and reactance is electrically connected between the 0 ° terminal 14 and the 90 ° terminal 16 and the ground (GND).

  Next, the operation of the variable phase shifter 10 according to the present embodiment will be described.

  When a high frequency input signal Si is supplied to the input terminal 12, a high frequency output signal St is output to the output terminal 18. Further, the high-frequency signals S01 and S02 are generated at the 0 ° terminal 14 and the high-frequency signals S901 and S902 are generated at the 90 ° terminal 16 by the reflection coefficient described above.

  In this case, the high frequency signal S01 is a high frequency signal output from the 0 ° terminal 14, and the high frequency signal S02 is a high frequency signal input from the 0 ° terminal 14 to the 90 ° hybrid coupler 20. The high frequency signal S901 is a high frequency signal output from the 90 ° terminal 16, and the high frequency signal S902 is a high frequency signal input from the 90 ° terminal 16 to the 90 ° hybrid coupler 20.

  The voltage value V01 of the high frequency signal S01 is a voltage value that is 1 / √2 times the voltage value Vi of the high frequency input signal Si. The phase of the high frequency signal S01 is a phase delayed by -180 ° from the phase of the high frequency input signal Si.

  The voltage value V02 of the high-frequency signal S02 is a voltage value that is 1 / √2 times the voltage value Vi of the high-frequency input signal Si. The phase of the high-frequency signal S02 is a phase delayed by −180 ° from the phase θ of the series circuit composed of the variable capacitance diode 32, the inductor 34, and the coil 46.

  On the other hand, the voltage value V901 of the high-frequency signal S901 is a voltage value that is 1 / √2 times the voltage value Vi of the high-frequency input signal Si. The phase of the high frequency signal S901 is a phase delayed by −90 ° from the phase of the high frequency input signal Si.

  The voltage value V902 of the high-frequency signal S902 is a voltage value that is 1 / √2 times the voltage value of the high-frequency input signal Si. The phase of the high-frequency signal S902 is a phase that is delayed by −90 ° from the phase θ of the series circuit including the variable capacitance diode 38, the inductor 40, and the coil 48.

  Therefore, the high-frequency signals S01, S02, S901, and S902 generated at the 0 ° terminal 14 and the 90 ° terminal 16 have substantially the same voltage value, and the phase difference between the high-frequency signals S01 and S02 and the high-frequency signals S901 and S902. It can be seen that is 90 °.

  The high-frequency output signal St output from the output terminal 18 is a high-frequency signal generated when the high-frequency signal obtained by synthesizing the high-frequency signals S02 and S902 is totally reflected at the output terminal 18, and the voltage value Vi of the high-frequency input signal Si is It has substantially the same voltage value and a phase advanced by 90 ° from the phase θ.

  In the variable phase shifter 10 described above, when the control voltage Vc is applied from the voltage control terminal 52 to the variable capacitance diodes 32 and 38 via the coils 46 and 48, the junction capacitance C of the variable capacitance diodes 32 and 38 changes.

  Specifically, as shown in FIG. 2, when the voltage value of the control voltage Vc is increased, the junction capacitance C is decreased. As a result, the reactance (impedance) and phase θ of the variable reactance circuit including the coils 46 and 48, the variable capacitance diodes 32 and 38, and the inductors 34 and 40 change. That is, the phase θ can be changed by changing the control voltage Vc.

  The frequency of the control voltage Vc described above is lower than the frequencies of the high-frequency input signal Si, the high-frequency output signal St, and the high-frequency signals S01, S02, S901, and S902. At this time, the capacitor 54 functions as a bypass capacitor that prevents the leakage of the signal to the voltage control terminal 52 by bypassing the above-described high-frequency signal to the ground. The capacitors 30 and 36 function as coupling capacitors that prevent the control voltage Vc from flowing into the 90 ° hybrid coupler 20 via the 0 ° terminal 14 and the 90 ° terminal 16. Furthermore, the capacitors 22 and 26 function as coupling capacitors that block the passage of low-frequency signals such as the control voltage Vc or DC signals.

  Next, with respect to the variable phase shifter 10 (characteristic A) according to the present embodiment and the conventional variable phase shifter 100 (characteristic B), the change in the phase θ of the high-frequency output signal St with respect to the change in the control voltage Vc is shown in FIG. Show. Here, the inductors 34 and 40 of the variable phase shifter 10 are circuit elements whose electrical length L is L = λ / 8 (45 °) with respect to the wavelength λ of the high-frequency input signal Si.

  In the conventional variable phase shifter 100 (characteristic B), even when the control voltage Vc is changed from 0 to 25 V, the phase θ changes only from 0 ° to 150 °. That is, in order to obtain a phase change of 150 ° or more (150 ° to 180 °), it is necessary to connect another variable phase shifter 100 to the output terminal of the variable phase shifter 100. This may lead to an increase in the size of the wireless device in which the variable phase shifter 100 is mounted.

  On the other hand, in the variable phase shifter 10 according to the present embodiment, when the control voltage Vc is changed from 0 to 25 V, the phase θ can be changed in the range of 0 ° to 180 °. That is, one variable phase shifter 10 can cover a phase change of θ = 0 ° to 180 °. Such an increase in the phase change amount can be realized by providing the inductors 34 and 40 in the variable phase shifter 10 shown in FIG.

  That is, when Vc = 0, as shown in FIG. 2, the junction capacitance C of the variable capacitance diodes 32 and 38 is maximized and the reactance is minimized, and the control voltage Vc is applied to the inductors 34 and 40. Therefore, the reactance of the inductors 34 and 40 is also minimized. Thereby, the reactance (impedance of the phase control circuit) of the variable reactance circuit composed of the inductors 34 and 40 and the variable capacitance diodes 32 and 38 is minimized. Therefore, the phase θ in the variable phase shifter 10 when Vc = 0 is zero.

  When the voltage value of the control voltage Vc is increased, the junction capacitance C of the variable capacitance diodes 32 and 38 is decreased, and the reactance of the variable capacitance diodes 32 and 38 is increased. As a result, the reactance of the variable reactance circuit including the variable capacitance diodes 32 and 38, the inductors 34 and 40, and the coils 46 and 48 increases, and the phase θ of the high-frequency output signal St increases.

  Further, when Vc = 25 V, the junction capacitance C of the variable capacitance diodes 32 and 38 is minimized, and the reactance is maximized. Thereby, the reactance of the variable reactance circuit is maximized, and the phase θ of the high-frequency output signal St is also maximized (θ = 180 °).

  Thus, in the variable phase shifter 10 according to the present embodiment, the capacitors 30 and 36 and the variable capacitance diode 32 are provided between the 0 ° terminal 14 and 90 ° terminal 16 of the 90 ° hybrid coupler 20 and the ground (GND). , 38 and the inductors 34, 40 are electrically connected.

  In this case, when the control voltage Vc is supplied to the variable capacitance diodes 32 and 38 via the coils 46 and 48, the junction capacitance C of the variable capacitance diodes 32 and 38 changes, and the phase θ of the high frequency output signal St changes. Although the inductors 34 and 40 are connected in series with the variable capacitance diodes 32 and 38, the phase amount of the phase θ can be increased.

  Further, since the control voltage Vc is supplied to the variable capacitance diodes 32 and 38 via the coils 46 and 48, even if a high frequency signal generated by, for example, a stray capacitance enters the variable phase shifter 10, the coil 46, 48 functions as a high resistance to the high-frequency signal. Thereby, the high frequency signal is attenuated, and the phase change of the phase θ can be stably performed.

  If these inductors 34 and 40 are variable inductors, even if the phase change amount of the phase θ is reduced by the stray capacitance, the phase change amount can be reduced only by changing the inductance of the inductors 34 and 40. Can be compensated. Therefore, the phase θ characteristic (phase characteristic) can be stabilized, and the variable phase shifter 10 having a desired phase characteristic can be realized.

  Next, specific examples (first and second specific examples) of the variable phase shifter 10 according to the present embodiment will be described with reference to FIGS. Components similar to those described in FIGS. 1 to 3 are described with the same reference numerals.

  In the variable phase shifter 10A according to the first specific example, as shown in FIG. 4, a plurality of wiring patterns are formed on a dielectric substrate 60A, and variable capacitance diodes 32 and 38 and coils 46 and 48 are formed on the wiring patterns. Is mounted, and circuit elements other than the elements described above are formed in the dielectric substrate 60A.

  Surface ground electrodes 64a to 64d are formed on the first to fourth side surfaces 62a to 62d, which are the surfaces of the dielectric substrate 60A. Further, the input electrode 66 and the output electrode 68 are formed on the first side face 62a, and the control voltage electrodes 70 are formed on the third side face 62c at two positions with the surface ground electrode 64c interposed therebetween. The surface ground electrodes 64a to 64d, the input electrode 66, the output electrode 68, and the control voltage electrode 70 extend from the first to fourth side surfaces 62a to 62d to the upper surface 62e and the bottom surface 62f. A surface ground electrode 64e is formed on the entire bottom surface 62f.

  Terminals 72a to 72h are formed in parallel on the upper surface 62e at predetermined intervals without directly contacting the surface ground electrodes 64a to 64d, the input electrode 66, the output electrode 68, and the control voltage electrode 70. . The variable capacitance diodes 32 and 38 and the coils 46 and 48 are mounted on the upper surface 62e having the terminals 72a to 72h as described above. In this case, the cathodes K1 and K2 (see FIG. 1) of the variable capacitance diodes 32 and 38 are connected to the terminals 72a and 72d, and the anodes A1 and A2 (see FIG. 1) are connected to the terminals 72e and 72h. The coils 46 and 48 are connected to terminals 72b, 72c, 72f and 72g.

  In the variable phase shifter 10A according to the first specific example, as shown in FIG. 5, a plurality of dielectric layers (S1 to S10) are stacked and baked and integrated to form the dielectric substrate 60A. .

  The dielectric substrate 60A is configured by stacking a first dielectric layer S1 to a tenth dielectric layer S10 in order from the top. These first to tenth dielectric layers S1 to S10 are composed of one or a plurality of layers.

  In the dielectric substrate 60A, a first pattern 74a is formed in the fourth dielectric layer S4, and a second pattern 74b is formed in the fifth dielectric layer S5. Each of the first and second patterns 74a and 74b has a substantially U-shaped shape in which the start point and the end point of the wiring pattern are provided near the first side face 62a. The 90 ° hybrid coupler 20 is configured by the first and second patterns 74a and 74b.

  Regarding the first and second patterns 74a and 74b, the starting point refers to the tip of the wiring pattern near the second side surface 62b. The end point is the end of the wiring line near the fourth side surface 62d.

  The fifth and seventh dielectric layers S5 and S7 are electrically connected to the input electrode 66 from the position close to the first side surface 62a and from the position close to the second side surface 62b. Capacitor electrodes 76a and 76b are formed. The capacitor electrode 76a is formed so as not to be in direct contact with the second pattern 74b.

  On the other hand, in the fourth and sixth dielectric layers S4, S6, a capacitor electrode 76c, which is close to the first side surface 62a and from the position close to the second side surface 62b toward the third side surface 62c, 76d is formed to face the capacitor electrodes 76a and 76b. The capacitor electrode 76c is formed so as not to be in direct contact with the first pattern 74a.

  As shown in FIGS. 5 and 6, the capacitor electrodes 76c and 76d are electrically connected via a via hole 78a. Further, the capacitor electrode 76c and the input terminal 12 which is the starting point of the second pattern 74b are electrically connected through a via hole 78b. Therefore, the capacitor 22 is constituted by the capacitance formed between the capacitor electrodes 76a and 76c and the capacitance formed between the capacitor electrodes 76b and 76d.

  Further, the fifth and seventh dielectric layers S5 and S7 are electrically connected to the output electrode 68 from the position close to the first side face 62a and close to the fourth side face 62d toward the output electrode 68. Capacitor electrodes 76e and 76f that are electrically connected are formed. The capacitor electrode 76e is formed so as not to be in direct contact with the second pattern 74b.

  On the other hand, the fourth and sixth dielectric layers S4 and S6 are provided with capacitor electrodes 76g from the position close to the first side face 62a and close to the fourth side face 62d toward the third side face 62c, 76h is formed to face the capacitor electrodes 76e and 76f. Further, the capacitor electrode 76g is electrically connected to the output terminal 18 which is the end point of the second pattern 74b. The capacitor electrodes 76g and 76h are electrically connected via a via hole 78c. Therefore, the capacitor 26 is constituted by the capacitance formed between the capacitor electrodes 76e and 76g and the capacitance formed between the capacitor electrodes 76f and 76h.

  An inner layer ground electrode 64f is formed on the eighth dielectric layer S8. The inner layer ground electrode 64f is formed in a substantially cross shape, and has a portion where no electrode is formed at the center thereof. The inner layer ground electrode 64f and the surface ground electrodes 64a and 64c are directly connected. The inner layer ground electrode 64f and the surface ground electrodes 64b and 64d are electrically connected through four via holes 78d to 78g.

  Capacitor electrodes 76i are formed on the ninth dielectric layer S9. The capacitor electrode 76i is formed in a substantially cross shape facing the inner-layer ground electrode 64f so as not to contact the surface ground electrodes 64a to 64d, and a part of the wiring pattern is formed toward the third side surface 62c. The two control voltage electrodes 70 are electrically connected. Thereby, the voltage control terminal 52 is formed. Capacitance is formed between the capacitor electrode 76 i and the inner layer ground electrode 64 f and between the capacitor electrode 76 i and the surface ground electrode 64 e, thereby forming the capacitor 54.

  A connection electrode 80 is formed in the center of the second dielectric layer S2. The connection electrode 80 and the capacitor electrode 76i are electrically connected via a via hole 78h that passes through a portion of the inner layer ground electrode 64f where no electrode is formed. The connection electrode 80 and the terminal 72f are electrically connected through a via hole 78i, and the connection electrode 80 and the terminal 72g are electrically connected through a via hole 78j. As a result, the connection electrode 80 forms the connection point 50.

  In the second dielectric layer S2, a capacitor electrode 76j is formed near the first side face 62a and slightly closer to the center than the second side face 62b. On the other hand, in the third dielectric layer S3, a capacitor electrode 76k is formed closer to the first side face 62a and slightly closer to the center than the second side face 62b. A capacitor 30 is formed between the capacitor electrode 76j and the capacitor electrode 76k.

  The capacitor electrode 76j and the terminal 72a are electrically connected by a via hole 78k, and the capacitor electrode 76j and the terminal 72b are electrically connected by a via hole 78l. The capacitor electrode 76k and the 0 ° terminal 14 that is the starting point of the first pattern 74a are electrically connected by a via hole 78m.

  Further, a capacitor electrode 76l is formed in the second dielectric layer S2 near the first side face 62a and slightly closer to the center than the fourth side face 62d. On the other hand, in the third dielectric layer S3, a capacitor electrode 76m is formed near the first side face 62a and slightly closer to the center than the fourth side face 62d. A capacitor 36 is formed between the capacitor electrode 76l and the capacitor electrode 76m.

  The capacitor electrode 76l and the terminal 72c are electrically connected by a via hole 78n, and the capacitor electrode 76l and the terminal 72d are electrically connected by a via hole 78o. Further, the capacitor electrode 76m and the 90 ° terminal 16 which is the end point of the second pattern 74b are electrically connected by a via hole 78p.

  Furthermore, the wiring pattern of the inductors 34 and 40 is formed on the second dielectric layer S2 from the surface ground electrode 64c formed on the third side surface 62c toward the center of the second dielectric layer S2. ing. The wiring patterns of the inductors 34 and 40 have a substantially J-shape with the tips curved toward the second and fourth side faces 62b and 62d. The tip of the inductor 34 and the terminal 72e are electrically connected via a via hole 78q, and the tip of the inductor 40 and the terminal 72h are electrically connected via a via hole 78r.

  In the variable phase shifter 10A according to the first specific example, if each wiring pattern is formed by a known pattern processing method in the first to ninth dielectric layers S1 to S9 of the dielectric substrate 60A, Circuit constants (capacitance, inductance) can be configured with high accuracy. Thereby, the phase change range and phase change amount of the phase θ of the high-frequency output signal St can be set with higher accuracy.

  In addition, since the variable capacitance diodes 32 and 38 and the coils 46 and 48 are mounted on the dielectric substrate 60A, replacement is easy when the design is changed.

  Next, in the variable phase shifter 10B according to the second specific example, as shown in FIGS. 7 and 8, a wiring pattern is formed on the dielectric substrate 60B, and the circuit diagram of FIG. The circuit element is different from the variable phase shifter 10A according to the first specific example in that the circuit element is mounted.

  Specifically, as shown in FIG. 9, the dielectric substrate 60B has first to fourth side surfaces 82a to 82d, and a surface ground electrode 64g having a substantially H shape so as to substantially cover the entire upper surface 82. Is formed.

  That is, the wiring pattern 86a of the surface ground electrode 64g is formed from the second side surface 82b to the fourth side surface 82d of the dielectric substrate 60B at the center of the upper surface 84 of the dielectric substrate 60B, and both ends of the wiring pattern 86a. Four wiring patterns 86b to 86e are formed from the first to the third and second side surfaces 82a and 82c. At the tips of the wiring patterns 86b to 86e, one or more grounding terminals 88a are provided so as to protrude outward from the first and third side surfaces 82a and 82c.

  Further, one wiring pattern 86f is formed from the wiring pattern 86a toward the third side surface 82c, and three tips for grounding 88a are provided protruding from the third side surface 82c at the tip thereof. Yes. On the other hand, one wiring pattern 86g slightly protruding from the wiring pattern 86a toward the first side surface 82a is formed on the opposite side of the wiring pattern 86f.

  Of the wiring pattern 86a, wiring patterns 86h and 86i extend from the second and fourth side surfaces 82b and 82d toward the first side surface 82a. The wiring patterns 86h and 86i have a substantially J-shape that is curved so that the tips thereof face each other.

  A wiring pattern 86b and a wiring pattern 86j formed extending from the wiring pattern 86a are arranged in parallel on the side of the wiring pattern 86h. The wiring patterns 86b and 86j function as shield electrodes for the wiring pattern 86h serving as the inductor 34.

  On the other hand, on the side of the wiring pattern 86i, a wiring pattern 86c and a wiring pattern 86k formed extending from the wiring pattern 86a are arranged in parallel. The wiring patterns 86c and 86k function as shield electrodes of the wiring pattern 86i that becomes the inductor 40.

  Wiring patterns 86l and 86m are formed on the upper surface 84 of the dielectric substrate 60B so as to be sandwiched between the wiring patterns 86d and 86f. The wiring pattern 86l is formed toward the third side surface 82c, and a terminal 88b protruding outward is provided at the tip. On the other hand, the wiring pattern 86m is formed closer to the wiring pattern 86f.

  Further, wiring patterns 86n and 86o are formed on the upper surface 84 of the dielectric substrate 60B so as to be sandwiched between the wiring patterns 86e and 86f. The wiring pattern 86n is formed toward the third side surface 82c, and a terminal 88 protruding outward is provided at the tip. On the other hand, the wiring pattern 86o is formed closer to the wiring pattern 86f.

  Furthermore, wiring patterns 86p to 86t are formed on the upper surface 84 of the dielectric substrate 60B so as to be sandwiched between the wiring patterns 86b and 86c. The wiring pattern 86p is a substantially T-shaped wiring pattern formed to face the first side surface 82a so as not to directly contact the grounding wiring pattern 86g, and a terminal 88 protruding outward is formed at the tip of the wiring pattern 86p. Is provided. The wiring pattern 86q is formed so as to be sandwiched between the wiring patterns 86g and 86j. The wiring pattern 86r is formed so as to be sandwiched between the wiring patterns 86g and 86k. The wiring patterns 86s and 86t are formed so as to sandwich the wiring pattern 86p.

  Further, wiring patterns 86u and 86v serving as grounds are formed at positions closer to the first side surface 82a than the wiring patterns 86s and 86t, and a grounding terminal 88a is formed outward from the wiring patterns 86u and 86v. Has been.

  In the variable phase shifter 10B described above, as shown in FIGS. 7 and 8, the circuit element shown in FIG. 1 is mounted on the dielectric substrate 60B.

  That is, the 90 ° hybrid coupler 20 is joined to the input terminal 12 and the wiring pattern 86m, the 0 ° terminal 14 and the wiring pattern 86q, the 90 ° terminal 16 and the wiring pattern 86r, and the output terminal 18 and the wiring pattern 86o. The hybrid coupler 20 is mounted on the dielectric substrate 60B. As a mounting method, a known mounting method such as soldering can be used.

  The capacitor 22 is mounted between the wiring patterns 86l and 86m, and the capacitor 26 is mounted between the wiring patterns 86n and 86o. The capacitor 30 is mounted between the wiring patterns 86q and 86s, and the coil 46 is mounted between the wiring patterns 86q and 86p. A capacitor 54 is mounted between the wiring patterns 86g and 86p. A coil 48 is mounted between the wiring patterns 86r and 86p, and a capacitor 36 is mounted between the wiring patterns 86r and 86t. The variable capacitance diode 32 is mounted between the wiring patterns 86h and 86s, and the variable capacitance diode 38 is mounted between the wiring patterns 86i and 86t.

  With the mounting described above, when the high frequency input signal Si is input from the terminal 88b of the wiring pattern 86l, the high frequency output signal St having the phase θ is output from the terminal 88b of the wiring pattern 86n. In order to change the phase θ, the control voltage Vc may be applied from the terminal 88b of the wiring pattern 86p.

  In the variable phase shifter 10B according to the second specific example, as in the variable phase shifter 10A according to the first specific example, all circuit elements are configured by lumped constant circuit elements, so that circuit design is easy. Thus, the phase change amount of the phase θ can be easily expanded.

  In particular, since all the circuit elements are mounted on one dielectric substrate 60B, the circuit elements can be easily replaced and the design can be easily changed. Also, compared to the variable phase shifter 10A according to the first specific example, in the variable phase shifter 10B according to the second specific example, the wiring patterns 86h and 86i which are the inductors 34 and 40 are provided on the upper surface 84 of the dielectric substrate 60B. Is exposed. Therefore, when it is desired to change the change range of the phase θ, it can be realized by changing the inductance by changing the width and length of the wiring patterns 86h and 86i.

  For example, if the width is reduced by cutting the side portions of the wiring patterns 86h and 86i, the inductances of the inductors 34 and 40 are reduced. Thereby, since the impedance of the inductors 34 and 40 changes, the change range of the phase θ shown in FIG. 2 can be easily changed. Further, as a result of mounting the variable phase shifter 10B on the wireless device, even if stray capacitance such as the electrostatic capacitance of the package is generated, thereby affecting the change range of the phase θ, the wiring of the inductors 34 and 40 The phase change amount of the phase θ can be compensated by appropriately changing the shapes of the patterns 86h and 86i.

  Of course, the variable phase shifter according to the present invention is not limited to the above-described embodiment, and various configurations can be adopted without departing from the gist of the present invention.

1 is a circuit diagram showing a variable phase shifter according to a first embodiment. FIG. It is a characteristic view which shows the change of the junction capacitance of a variable capacitance diode. It is a characteristic view which shows the phase change of the output voltage when a control voltage is changed. It is a whole perspective view of the variable phase shifter concerning the 1st example. It is a disassembled perspective view of the variable phase shifter which concerns on a 1st specific example. It is sectional drawing of the variable phase shifter which concerns on a 1st specific example. It is a whole perspective view of the variable phase shifter which concerns on a 2nd example. It is a top view of the variable phase shifter which concerns on a 2nd specific example. It is a top view which shows the dielectric material board of the variable phase shifter which concerns on a 2nd example. It is a circuit diagram which shows the conventional variable phase shifter.

Explanation of symbols

DESCRIPTION OF SYMBOLS 10 ... Variable phase shifter 12 ... Input terminal 14 ... 0 degree terminal 16 ... 90 degree terminal 18 ... Output terminal 20 ... Hybrid coupler 22, 26, 30, 36, 54 ... Capacitor 32, 38 ... Variable capacity diode 34, 40 ... Inductor 42, 44, 50 ... connection point 46, 48 ... coil 52 ... voltage control terminal

Claims (13)

In a variable phase shifter having at least one variable capacitance element,
An inductance component is connected to the variable capacitor. A variable phase shifter. The variable phase shifter according to claim 1, wherein
A 90 ° hybrid coupler with an input terminal, an output terminal, a 0 ° terminal and a 90 ° terminal;
A first phase control circuit is electrically connected between the 0 ° terminal and the ground,
A second phase control circuit having substantially the same impedance as that of the first phase control circuit is electrically connected between the 90 ° terminal and the ground.
The first phase control circuit has a first variable capacitance element and a first inductor electrically connected to the first variable capacitance element,
The second phase control circuit includes a second variable capacitance element and a second inductor electrically connected to the second variable capacitance element. The variable phase shifter according to claim 2, wherein
The capacitances of the first and second variable capacitance elements change according to the control voltage supplied to the first and second variable capacitance elements,
The variable phase shifter characterized in that the phase of the output signal output from the output terminal changes due to the change in the capacitance. The variable phase shifter according to claim 2 or 3,
The first and second variable capacitance elements are first and second variable capacitance diodes;
The variable phase shifter, wherein the control voltage is supplied to first and second cathode terminals of the first and second variable capacitance diodes. The variable phase shifter according to claim 4, wherein
The first cathode terminal is electrically connected to the 0 ° terminal, and the first inductor is electrically connected between the first anode terminal of the first variable capacitance diode and the ground. Connected,
The second cathode terminal is electrically connected to the 90 ° terminal, and the second inductor is electrically connected between the second anode terminal of the second variable capacitance diode and the ground. A variable phase shifter characterized by being connected. The variable phase shifter according to claim 5, wherein
A first coupling capacitor is further electrically connected between the 0 ° terminal and the first cathode terminal,
A variable phase shifter characterized in that a second coupling capacitor is further electrically connected between the 90 ° terminal and the second cathode terminal. The variable phase shifter according to any one of claims 4 to 6,
One end of a first coil is electrically connected to the first cathode terminal;
One end of a second coil is electrically connected to the second cathode terminal;
A voltage control terminal is electrically connected to the other ends of the first and second coils,
The variable phase shifter, wherein the control voltage is supplied from the voltage control terminal to the first and second cathode terminals via the first and second coils. The variable phase shifter according to claim 7, wherein
A variable phase shifter, wherein a bypass capacitor is electrically connected between the voltage control terminal and the ground. The variable phase shifter according to any one of claims 3 to 8,
The variable phase shifter, wherein the input signal supplied to the input terminal is a signal having a frequency higher than that of the control voltage. The variable phase shifter according to claim 9, wherein
A third coupling capacitor is electrically connected to the input terminal,
A fourth coupling capacitor is electrically connected to the output terminal,
The input signal is supplied via the third coupling capacitor;
The variable phase shifter, wherein the output signal is output through the fourth coupling capacitor. The variable phase shifter according to claim 1, wherein
Having a dielectric substrate composed of a plurality of dielectric layers;
A 90 ° hybrid coupler having an input terminal, an output terminal, a 0 ° terminal and a 90 ° terminal, a first and a second inductor, and a first and a second coupling capacitor in the dielectric substrate. Formed,
The first and second variable capacitance diodes are mounted on a wiring pattern formed on the dielectric substrate surface,
A first phase control circuit including the first inductor, the first variable capacitance diode, and the first coupling capacitor is electrically connected between the 0 ° terminal and the ground,
Between the 90 ° terminal and the ground, includes the second inductor, the second variable capacitance diode, and the second coupling capacitor, and is substantially the same as the first phase control circuit. A variable phase shifter characterized in that a second phase control circuit having the following impedance is electrically connected. The variable phase shifter according to claim 1, wherein
A circuit board composed of a plurality of dielectric layers;
A 90 ° hybrid coupler having an input terminal, an output terminal, a 0 ° terminal, and a 90 ° terminal, a first and a second variable capacitance diode, and a first and a second cup on the wiring pattern of the circuit board; Ring capacitor is mounted,
First and second inductors are formed by the wiring pattern,
A first phase control circuit including the first inductor, the first variable capacitance diode, and the first coupling capacitor is electrically connected between the 0 ° terminal and the ground,
Between the 90 ° terminal and the ground, includes the second inductor, the second variable capacitance diode, and the second coupling capacitor, and is substantially the same as the first phase control circuit. A variable phase shifter characterized in that a second phase control circuit having the following impedance is electrically connected. The variable phase shifter according to any one of claims 1 to 12,
The variable phase shifter, wherein the first and second inductors are variable inductors.

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