JP2005260475A - Despread demodulator and spread spectrum radio receiver - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a despread demodulator and a spread spectrum radio receiver which have low voltage and low power consumption. <P>SOLUTION: The back diffusion demodulator has sample and hold circuits 100, 101 for sample-holding an inputted spread signal alternately per sampling interval ΔT, a subtractor 102 for obtaining a difference signal between a result of sample-holding by the circuit 100 and a result of sample-holding by the circuit 101, an A/D converter 103 for sampling the difference signal per ΔT to convert it to a digital signal, a polarity converter 104 for inverting the polarity of the difference signal digitized by the A/D converter 103 per 2×ΔT, and a despread processor 105 for applying despread processing to the output signal from the polarity converter 104 to demodulate the data signal. <P>COPYRIGHT: (C)2005,JPO&NCIPI

Description

  The present invention relates to spread spectrum wireless communication that spreads and transmits a desired signal by an operation using a spread code, and despreads the received spread signal by an operation using a spread code and extracts the desired signal. In particular, the present invention relates to a configuration of a despreading demodulator and a spread spectrum radio receiver using the same.

  FIG. 10 shows the configuration of a despreading demodulator as the first prior art. A spread spectrum radio transmitter (not shown) generates a spread signal obtained by spreading the data signal, and transmits this spread signal. The spread signal transmitted from the spread spectrum radio transmitter is received by an antenna (not shown) of the spread spectrum radio receiver, converted into a baseband signal by an RF signal processing unit (not shown), and then the despread demodulator of FIG. Is input. The A / D converter 301 of the despreading demodulator converts the input spread signal into a digital signal, and the despreading demodulator 302 demodulates the data signal by performing a despreading process by digital signal processing.

FIG. 11 shows the configuration of a spread spectrum radio receiver which is the second prior art. A spread signal in the radio frequency band transmitted from the spread spectrum radio transmitter is received by an antenna (not shown) of the spread spectrum radio receiver and input to the frequency conversion mixer 402 in FIG.
The 0/90 ° phase shifter 401 generates two local signals LO-I and LO-Q having a phase difference of 90 ° from the local signal LO having the same frequency as the carrier wave. The frequency conversion mixer 402 multiplies the radio frequency band spread signal RF and the two local signals LO-I and LO-Q, and performs direct conversion to generate two orthogonal spread signals IF-I and IF-Q. Do. The low-pass filters 403 and 404 remove unnecessary band signals from the spread signals IF-I and IF-Q, respectively.

A / D converters 405 and 406 convert the spread signals IF-I and IF-Q output from the low-pass filters 403 and 404, respectively, into digital signals. The phase correction processor 407 outputs an addition signal obtained by adding the output signals of the A / D converters 405 and 406, and at the same time, an addition signal so that the phase difference between the spread signal RF and the local signal LO is equivalent to a zero state. Correct the phase. The despreading processor 408 performs despreading processing by digital processing on the output signal of the phase correction processor 407 and demodulates the data signal. The despreading demodulator shown in FIG. 10 and the spread spectrum radio communication receiver shown in FIG. 11 are described in Non-Patent Document 1, for example.

The applicant has not yet found prior art documents related to the present invention by the time of filing other than the prior art documents specified by the prior art document information described in this specification.
Marubayashi Gen, Nakagawa Masao, Kawano Ryuji, “Spread Spectrum Communication and its Applications”, IEICE, 2000, pp. 121-122, ISBN 4-88552-153-X

  In wireless communication using spread spectrum, since the channel band is wide, an interference signal often exists in the same channel band. In the conventional despreading demodulator and spread spectrum radio receiver shown in FIGS. 10 and 11, only the desired signal is extracted by despreading processing. For this reason, the accuracy of the A / D converters 301, 405, and 406 is required to be 6 bits or more. Since it is difficult to operate such a high-precision A / D converter at a high speed and a low voltage, it has been difficult to realize a despreading demodulator and a spread spectrum radio receiver with a low voltage and a low power consumption. .

  The present invention has been made in view of the above points, and a despreading demodulator and a spread spectrum radio receiver that alleviate the bit accuracy required for an A / D converter and operate at low voltage and low power consumption. Is to contribute to the realization of

The despreading demodulator of the present invention includes a first sample and hold circuit and a second sample and hold circuit that alternately sample and hold an input spread signal every sampling interval ΔT, and the first sample and hold circuit. A subtractor that obtains a difference signal between the result of sample holding in step 2 and the result of sample holding by the second sample and hold circuit, an A / D converter that samples the difference signal every ΔT and converts it into a digital signal, A polarity converter for inverting the polarity of the difference signal digitized by the A / D converter every 2 × ΔT, and a despreading process for performing a despreading process on the output signal of the polarity converter and demodulating the data signal It has a container.
In one configuration example of the despreading demodulator of the present invention, the despreading processor performs the despreading process using a spreading code that has been code-converted corresponding to the difference signal.
Further, in one configuration example of the despreading demodulator of the present invention, the despreading processor is configured such that the sampling interval ΔT and the spreading code period Δt satisfy Δt = a × ΔT (a is a natural number of 2 or more). The despreading process is performed on the result of adding the digitized a difference signals output from the polarity converter.

The despreading demodulator of the present invention includes a first sample and hold circuit and a second sample and hold circuit that alternately sample and hold the input spread signal at every sampling interval ΔT, and the first sample and hold circuit. A subtractor that obtains a difference signal between the result of holding the sample by the hold circuit and the result of holding the sample by the second sample and hold circuit, and an A / D converter that samples the difference signal every ΔT and converts it into a digital signal A polarity converter for inverting the polarity of the difference signal digitized by the A / D converter every 2 × ΔT, an integrator for integrating the output signal of the polarity converter, and an output signal of the integrator And a despreading processor for demodulating the data signal.
In one configuration example of the despreading demodulator of the present invention, the despreading processor uses a pseudo-spreading code in which one code is added to the true spreading code used for generating the spread signal in the transmitter. The despreading process is performed, and the sum of the pseudo-spreading codes is zero.
In one configuration example of the despreading demodulator of the present invention, the despreading processor performs the despreading process using a Manchester type spreading code.

The spread spectrum radio receiver according to the present invention includes a frequency conversion mixer that converts an input spread signal in a radio frequency band into two spread signals that are orthogonal in an intermediate frequency band, and a first output from the frequency conversion mixer. The first sample and hold circuit and the second sample and hold circuit that alternately sample and hold the spread signal at every sampling interval ΔT, and the second spread signal output from the frequency conversion mixer at every sampling interval ΔT A third sample hold circuit and a fourth sample hold circuit that alternately hold samples; a result of sample holding by the first sample hold circuit; and a result of sample holding by the second sample hold circuit; The first subtractor for obtaining the difference signal of the signal and the result of the sample holding by the third sample / hold circuit. A second subtractor that obtains a difference signal between the result and the result of the sample holding by the fourth sample and hold circuit, and the difference signal output from the first subtracter is sampled every ΔT to obtain a digital signal A first A / D converter to convert;
A second A / D converter that samples the differential signal output from the second subtracter every ΔT and converts it into a digital signal, an output signal of the first A / D converter, and the second A Having a phase correction processor that outputs an addition signal obtained by adding the output signal of the / D converter, and a despreading processor that despreads the data signal by performing despreading processing on the output signal of the phase correction processor It is.

Further, in one configuration example of the spread spectrum radio receiver of the present invention, the despreading processing unit includes a polarity converter that inverts the polarity of the output signal of the phase correction processor every 2 × ΔT, and the difference signal. It comprises a despreading processor that performs a despreading process on the output signal of the polarity converter using the corresponding spread code.
In one configuration example of the spread spectrum radio receiver according to the present invention, the despreading processor satisfies the sampling interval ΔT and the spread code period Δt satisfy Δt = a × ΔT (a is a natural number of 2 or more). In this case, the despreading process is performed on the result of adding a digitized difference signals output from the polarity converter.
In one configuration example of the spread spectrum radio receiver according to the present invention, the despreading processing unit includes a polarity converter for inverting the polarity of the output signal of the phase correction processor every 2 × ΔT, and the polarity converter Are integrated with each other and a despreading processor that despreads the output signal of the integrator and demodulates the data signal.
Further, in one configuration example of the spread spectrum radio receiver of the present invention, the despreading processor adds a pseudo spread code obtained by adding one code to the true spread code used for generating the spread signal in the transmitter. The despreading process is performed using the pseudo spread code, and the sum of the pseudo spread codes is zero.
Moreover, in one configuration example of the spread spectrum radio receiver of the present invention, the despreading processor performs the despreading process using a Manchester type spreading code.

  According to the present invention, the spread signal is alternately sampled and held by the two sample and hold circuits, and the difference signal of the outputs of the two sample and hold circuits is converted into a digital signal by the A / D converter. If the spread signal is sampled and held at a sufficiently small ΔT interval, the amplitude of the differential signal can be greatly reduced. As a result, the accuracy required for the A / D converter for A / D converting the difference signal can be greatly reduced, and the power supply voltage required for the circuit operation of the despreading demodulator and the spread spectrum radio receiver can be greatly reduced. Can do. As a result, in the present invention, the power consumption of the despreading demodulator and the spread spectrum radio receiver can be significantly reduced.

[First Embodiment]
FIG. 1 is a block diagram showing a configuration of a despreading demodulator in a spread spectrum radio receiver according to the first embodiment of the present invention.
The despreading demodulator of the present embodiment includes a first sample and hold circuit 100, a second sample and hold circuit 101, a subtractor 102, an A / D converter 103, a polarity converter 104, a difference A mold despreading processor 105.

A spread spectrum radio transmitter (not shown) generates a spread signal obtained by spreading the data signal, and transmits this spread signal. The spread signal transmitted from the spread spectrum radio transmitter is received by an antenna (not shown) of the spread spectrum radio receiver, converted into a baseband signal by an RF signal processing unit (not shown), and then the despread demodulator of FIG. Is input.
The first sample-and-hold circuit 100 and the second sample-and-hold circuit 101 sample-hold the input spread signals in synchronization with the first clock f1 and the second clock f2, respectively.

FIG. 2 shows signal waveform examples of the first clock f1 and the second clock f2 used in the present embodiment. In FIG. 2, “S” indicates the timing at which the sample and hold circuits 100 and 101 sample the spread signal, and “H” indicates the period during which the sampled spread signal is held.
When the period of the first clock f1 and the second clock f2 is T, the first clock f1 and the second clock f2 are the first sample and hold circuit 100, the second sample and hold circuit 101, Are set to alternately sample every ΔT (ΔT = T / 2). That is, the first clock f1 and the second clock f2 are signals having the same frequency and a phase difference of 180 °.

The subtracter 102 outputs a difference signal between the output of the first sample and hold circuit 100 and the output of the second sample and hold circuit 101.
The A / D converter 103 receives a third clock f3 that is synchronized with the first clock f1 and the second clock f2 and has a frequency twice as high. That is, the period of the third clock f3 is ΔT. The A / D converter 103 samples the difference signal output from the subtractor 102 in synchronization with the third clock f3 and converts it into a digital signal.

  FIG. 3A shows an example of the waveform of the spread signal at point A in FIG. 1, and FIG. 3B shows an example of the waveform of the difference signal at point B in FIG. In the example of FIG. 3A, the spread signal is a signal represented by sin (2πft) of amplitude 1 and frequency f. The spread signal is sampled alternately every ΔT by the first sample and hold circuit 100 and the second sample and hold circuit 101, and the result obtained by holding the sample by the first sample and hold circuit 100 and the second sample and hold circuit. When the difference signal from the result of the sample holding by the circuit 101 is obtained, the amplitude b of this difference signal is 2πf × ΔT.

  Therefore, if the diffusion signal is sampled and held at a sufficiently small ΔT interval so that 2πf × ΔT <1, the amplitude of the differential signal can be greatly reduced. As a result, in this embodiment, the accuracy required for the A / D converter 103 for A / D converting the difference signal can be greatly reduced, and the power supply voltage required for the circuit operation of the despreading demodulator can be greatly reduced. be able to.

  The polarity of the difference signal output from the subtracter 102 is inverted every ΔT because the first sample-and-hold circuit 100 and the second sample-and-hold circuit 101 alternately sample every ΔT. Therefore, the polarity converter 104 inverts the polarity of the difference signal digitized by the A / D converter 103 every period T in order to align the polarities of the difference signals. Thereby, the polarity of the differential signal output from the polarity converter 104 is unified to either positive or negative.

The differential despreading processor 105 performs differential despreading processing by digital processing on the output signal of the polarity converter 104 and demodulates the data signal. The differential despreading process by the differential despreading processor 105 will be described below.
When the code length is m, the despreading process using the spread signal S _k (k = 1, 2, 3,..., M) and the spread code C _k can be expressed as the following equation.

In Expression (1), P is a signal resulting from the despreading process. The spreading code C _k is the same as the code used to generate the spread signal S _k in the transmitter.
At this time, assuming that the differential signal output from the polarity converter 104 is ΔS _i , the calculation of Expression (1) can be expressed as the following expression.

Therefore, by using a new spreading code D _k that has been code-converted corresponding to the difference signal, despreading processing using the difference signal ΔS _i as input becomes possible. However, in Equation (2), the first term in the third row from the top is approximately zero.
As described above, according to the present embodiment, the power supply voltage necessary for the circuit operation of the despreading demodulator can be greatly reduced, and thereby the power consumption of the despreading demodulator can be greatly reduced. .

[Second Embodiment]
Next, a second embodiment of the present invention will be described. In the first embodiment, the sampling interval ΔT of the spread signal by the first sample and hold circuit 100 and the second sample and hold circuit 101 and the spread spectrum chip interval (the period of the spread code D _k used in the despread demodulator) Although the case where Δt is equal is shown, the sampling interval ΔT can be made smaller than the spread spectrum chip interval Δt.

For example, in the case of Δt = a × ΔT, the result of adding a (a is a natural number of 2 or more) difference signals is obtained as ΔSS _i as shown in the following equation. This addition process may be performed by the differential despreading processor 105 shown in FIG.

Then, the despreading process using the addition result ΔSS _i and the spreading code D _k can be expressed by the following equation.

  According to the present embodiment, the bit interval required for the A / D converter 103 can be reduced as compared with the first embodiment by making the sampling interval ΔT smaller than the spread spectrum chip interval Δt.

[Third Embodiment]
Next, a third embodiment of the present invention will be described. FIG. 4 is a block diagram showing the configuration of the despreading demodulator in the spread spectrum radio receiver according to the third embodiment of the present invention. The same components as those in FIG. 1 are denoted by the same reference numerals.
The despreading demodulator of the present embodiment includes a first sample and hold circuit 100, a second sample and hold circuit 101, a subtractor 102, an A / D converter 103, a polarity converter 104, an integration And an approximate despreading processor 107.

The operations of the first sample and hold circuit 100, the second sample and hold circuit 101, the subtractor 102, the A / D converter 103, and the polarity converter 104 are the same as those in the first embodiment.
Also in the present embodiment, the amplitude of the differential signal can be significantly reduced by holding the spread signal at a sufficiently small ΔT interval that satisfies 2πf × ΔT <1, and this is necessary for the A / D converter 103. The accuracy can be greatly reduced, and the power supply voltage required for the circuit operation of the despreading demodulator can be greatly reduced.

  The present embodiment is characterized in that the difference signal is returned to the spread signal by integrating the digitized difference signal output from the polarity converter 104 by digital processing in the integrator 106. However, if the differential signal includes a DC offset, an overflow occurs in the integration process. This overflow of integration processing can be solved by subtraction after integration.

  For this reason, in the present embodiment, an approximate despreading process is performed on the digitized spread signal output from the integrator 106 by a digital process to demodulate the data signal. Specifically, the approximate despreading processor 107 performs despreading processing using the following approximate expression, and solves the overflow problem by setting the sum of pseudo-spreading codes used for this despreading processing to zero. Yes.

In Equation (5), S _k (k = 1, 2, 3,..., M) is a spread signal output from the integrator 106, and C _k is a true signal used to generate the spread signal in the transmitter. Spreading code. Further, .SIGMA.C _k in the second term on the right side S _n .SIGMA.C _k of formula (5) is one code was added to the true spread signal C _k. As a result, the sum of the pseudo spread code composed of the true spread signal C _k and the added code ΣC _k becomes zero. In Equation (5), _Sn is an arbitrary spread signal, and may be any one of the spread signals S _k (that is, n is any value from 1 to m), or from the spread signal S _k . may be a spread signal received before, may be a spread signal received later than spread signal S _k.
Thus, in this embodiment, the same effect as that of the first embodiment can be obtained.

[Fourth Embodiment]
Next, a fourth embodiment of the present invention will be described. FIG. 5 is a block diagram showing the configuration of the despreading demodulator in the spread spectrum radio receiver according to the fourth embodiment of the present invention. The same components as those in FIGS. 1 and 4 are given the same reference numerals. is there.
The despreading demodulator of the present embodiment includes a first sample and hold circuit 100, a second sample and hold circuit 101, a subtractor 102, an A / D converter 103, a polarity converter 104, an integration And a despreading processor 108.

The operations of the first sample and hold circuit 100, the second sample and hold circuit 101, the subtractor 102, the A / D converter 103, the polarity converter 104, and the integrator 106 are the same as those of the third embodiment.
Also in the present embodiment, the amplitude of the differential signal can be significantly reduced by holding the spread signal at a sufficiently small ΔT interval that satisfies 2πf × ΔT <1, and this is necessary for the A / D converter 103. The accuracy can be greatly reduced, and the power supply voltage required for the circuit operation of the despreading demodulator can be greatly reduced.

In this embodiment, as in the third embodiment, the integrator 106 performs integration processing on the digitized difference signal output from the polarity converter 104, thereby converting the difference signal into a spread signal. return. At this time, the overflow of the integration process that becomes a problem in the third embodiment is solved by using a Manchester type spreading code in the despreading processor 108. As shown in FIG. 6, in the Manchester type spreading code, since one code is composed of “1” and “−1”, the sum of the spreading codes becomes zero, and the overflow problem does not occur.
Thus, in this embodiment, the same effect as that of the first embodiment can be obtained.

[Fifth Embodiment]
Next, a fifth embodiment of the present invention will be described. FIG. 7 is a block diagram showing a configuration of a spread spectrum radio receiver according to the fifth embodiment of the present invention.
The spread spectrum radio receiver according to the present embodiment includes a 0/90 ° phase shifter 201, a frequency conversion mixer 202, a first low-pass filter (hereinafter referred to as LPF) 203, and a second low-pass filter 204. , First sample and hold circuit 205, second sample and hold circuit 206, third sample and hold circuit 207, fourth sample and hold circuit 208, first subtractor 209, 2 subtractor 210, first A / D converter 211, second A / D converter 212, phase correction processor 213, and despreading processing unit 214.

  A spread spectrum radio transmitter (not shown) generates a spread signal obtained by spreading the data signal, and transmits this spread signal. The spread signal in the radio frequency band transmitted from the spread spectrum radio transmitter is received by an antenna (not shown) of the spread spectrum radio receiver and input to the frequency conversion mixer 202 in FIG.

The 0/90 ° phase shifter 201 generates two local signals LO-I and LO-Q having a phase difference of 90 ° from the local signal LO having the same frequency as the carrier wave.
The frequency conversion mixer 202 multiplies the spread signal RF in the radio frequency band and the two local signals LO-I and LO-Q to generate direct conversion for generating two orthogonal spread signals IF-I and IF-Q. Do.

The first and second LPFs 203 and 204 remove unnecessary band signals from the spread signals IF-I and IF-Q, respectively.
The first sample and hold circuit 205 and the second sample and hold circuit 206 hold samples of the spread signal IF-I alternately every ΔT in synchronization with the first clock f1 and the second clock f2, respectively. . On the other hand, the third sample-and-hold circuit 207 and the fourth sample-and-hold circuit 208 sample the spread signal IF-Q alternately every ΔT in synchronization with the first clock f1 and the second clock f2, respectively. Hold.

The first subtractor 209 outputs a difference signal between the output of the first sample and hold circuit 205 and the output of the second sample and hold circuit 206, and the second subtractor 210 outputs the third sample A difference signal between the output of the hold circuit 207 and the output of the fourth sample and hold circuit 208 is output.
The first and second A / D converters 211 and 212 sample the differential signals output from the subtracters 209 and 210, respectively, in synchronization with the third clock f3 and convert them into digital signals.

The phase correction processor 213 outputs an addition signal obtained by adding the output signals of the A / D converters 211 and 212, and at the same time, an addition signal so that the phase difference between the spread signal RF and the local signal LO is equivalent to a zero state. Correct the phase.
As the configuration of the despreading processing unit 214, the polarity converter 104 and the differential despreading processor 105 of FIG. 1 described in the first and second embodiments may be used, or the third embodiment The polarity converter 104, the integrator 106, and the approximate despreading processor 107 of FIG. 4 described in the embodiment may be used, or the polarity converter 104 and the integrator of FIG. 5 described in the fourth embodiment. 106 and a despreading processor 108 may be used.

  Also in the present embodiment, the amplitude of the differential signal can be greatly reduced by sampling and holding the spread signal at a sufficiently small ΔT interval that satisfies 2πf × ΔT <1, thereby allowing the A / D converters 211 and 212 to The required accuracy can be greatly reduced, and the power supply voltage required for the circuit operation of the spread spectrum radio transmitter can be greatly reduced.

  FIG. 8 is a circuit diagram showing a configuration example of the frequency conversion mixer 202. The spread signal RF +, RF−, the local signal LO-I, and the local signal LO-Q having a phase difference of 90 ° with respect to the local signal LO-I are input to the frequency conversion mixer 202 in a differential format. Signal. Similarly, the spread signal IF-I in the intermediate frequency band output from the frequency conversion mixer 202 and the spread signal IF-Q having a phase difference of 90 ° with respect to the spread signal IF-I are differential signals.

  Frequency conversion mixer 202 has P-channel MOS transistors Q1 and Q2 constituting a differential circuit in which spread signals RF + and RF- are input to the gate, and local signal LO-I is input to the gate via capacitors C1 and C2. N-channel MOS transistors Q3 and Q4 constituting a differential circuit, and N-channel MOS transistors Q5 and Q6 constituting a differential circuit in which a local signal LO-I is inputted to the gate through capacitors C1 and C2; N-channel MOS transistors Q7 and Q8 constituting a differential circuit in which a local signal LO-Q is input to the gate through capacitors C3 and C4, and a local signal LO-Q is input to the gate through capacitors C3 and C4. N-channel MOS transistors Q9 and Q10 constituting a differential circuit to be operated, and a power source as a source The voltage VDD is supplied, the gate and drain are connected to the drains of the transistors Q3 and Q5 and the output terminal of the diffusion signal IF-I, the power supply voltage VDD is supplied to the source, and the gate and drain are the transistors P-channel MOS transistor Q12 connected to the drains of Q4 and Q6 and the output terminal of diffusion signal IF-I, the power supply voltage VDD is supplied to the source, and the gate and drain are the drains of transistors Q7 and Q9 and diffusion signal IF-Q P-channel MOS transistor Q13 connected to the output terminal of the transistor, and a P-channel MOS transistor whose power source voltage VDD is supplied to the source and whose gate and drain are connected to the drains of the transistors Q8 and Q10 and the output terminal of the diffusion signal IF-Q Q14 and power supply at one end Capacitor C5 to which VDD is supplied and the other end is connected to the sources of transistors Q1 and Q2, and one end is connected to the drain of transistor Q2 and the sources of transistors Q3, Q4, Q7, and Q8, and the other end is grounded C6, one end connected to the drain of the transistor Q1 and the sources of the transistors Q5, Q6, Q9, and Q10, and the other end connected to the ground, the coil L1 connected in parallel with the capacitor C5, and the capacitor C6 in parallel , A coil L3 connected in parallel with the capacitor C7, a resistor R1 for applying a bias voltage LObias to the gates of the transistors Q3 and Q6, and a resistor R2 for applying a bias voltage LObias to the gates of the transistors Q4 and Q5 To the gates of the transistors Q7 and Q10 The resistor R3 for providing the bias voltage LObias and the resistor R4 for applying the bias voltage LObias to the gates of the transistors Q8 and Q9 are configured.

  With the above configuration, the frequency conversion mixer 202 multiplies the spread signals RF + and RF− and the local signal LO-I, and outputs the spread signal IF-I as a multiplication result in the voltage mode, and also spreads the signals RF + and RF. -Is multiplied by the local signal LO-Q, and the multiplication result IF-Q is output in the voltage mode. Thus, frequency conversion mixer 202 performs current-voltage conversion, but uses diode-connected P-channel MOS transistors Q11, Q12, Q13, and Q14 as the mixer load. As a result, since the current signal is non-linearly voltage-converted, the output diffusion signals IF-I and IF-Q are not saturated even when the levels of the diffusion signals RF + and RF- are large, and are large even during low-voltage operation. A dynamic range can be secured.

  FIG. 9 is a circuit diagram showing a configuration example of the subtracter 209 or 210. In FIG. 9, IN1 + and IN1- are differential signals output from the first sample and hold circuit 205 or the third sample and hold circuit 207, and IN2 + and IN2- are the second sample and hold signals. This is a differential signal output from the hold circuit 206 or the fourth sample and hold circuit 208. OUT + and OUT− are differential differential signals output from the subtracter 209 or 210.

  The subtracters 209 and 210 are differential circuits in which the power supply voltage VDD is supplied to the sources and the output signals IN1 + and IN1− of the first sample and hold circuit 205 or the third sample and hold circuit 207 are input to the gates. The power supply voltage VDD is supplied to the P-channel MOS transistors Q15 and Q16 and the source, and the output signals IN2 + and IN2- of the second sample and hold circuit 206 or the fourth sample and hold circuit 208 are input to the gate. P-channel MOS transistors Q17 and Q18 constituting a differential circuit, a resistor R5 having one end connected to the drains of the transistors Q15 and Q18 and the output terminal of the differential signal OUT +, and the other end grounded, and one end transistors Q16 and Q17 And the other end of the differential signal OUT−. Consists of the land has been resistance R6 Metropolitan.

  With the above configuration, the subtracter 209 outputs the difference signals OUT + and OUT− between the output signals IN1 + and IN1− of the first sample and hold circuit 205 and the output signals IN2 + and IN2− of the second sample and hold circuit 206. Similarly, the subtractor 210 outputs difference signals OUT + and OUT− between the output signals IN1 + and IN1− of the third sample and hold circuit 207 and the output signals IN2 + and IN2− of the fourth sample and hold circuit 208. Is output.

  The subtracters 209 and 210 perform voltage-current conversion for correcting the nonlinearity of current-voltage conversion of the frequency conversion mixer 202, perform subtraction in the current mode to obtain a differential signal, and then convert the differential signal to voltage. Is output. Since the difference signal is converted into a voltage after subtraction, the dynamic range after voltage conversion can be secured large without any problem.

  The present invention can be applied to wireless communication in which digital signals are transmitted and received by electromagnetic waves.

It is a block diagram which shows the structure of the despreading demodulator in the spread spectrum radio | wireless receiver of the 1st Embodiment of this invention. FIG. 2 is a signal waveform diagram of a first clock and a second clock used in the despread demodulator of FIG. 1. It is a wave form diagram of a spread signal and a difference signal in a despread demodulator of a 1st embodiment of the present invention. It is a block diagram which shows the structure of the de-spreading demodulator in the spread-spectrum radio receiver of the 3rd Embodiment of this invention. It is a block diagram which shows the structure of the de-spreading demodulator in the spread-spectrum radio receiver of the 4th Embodiment of this invention. FIG. 6 is a waveform diagram of a Manchester type spreading code used in the despreading demodulator of FIG. 5. It is a block diagram which shows the structure of the spread spectrum radio | wireless receiver used as the 5th Embodiment of this invention. It is a circuit diagram which shows the structural example of the frequency conversion mixer in the spread spectrum radio | wireless receiver of the 5th Embodiment of this invention. It is a circuit diagram which shows the structural example of the subtractor in the spread spectrum radio | wireless receiver of the 5th Embodiment of this invention. It is a block diagram which shows the structure of the despreading demodulator which is a 1st prior art. It is a block diagram which shows the structure of the spread spectrum radio | wireless receiver which is a 2nd prior art.

Explanation of symbols

DESCRIPTION OF SYMBOLS 100 ... 1st sample hold circuit, 101 ... 2nd sample hold circuit, 102 ... Subtractor, 103 ... A / D converter, 104 ... Polarity converter, 105 ... Differential type de-spreading processor, 106 ... Integration 107 ... Approximate despreading processor 108 ... Despreading processor 201 ... 0/90 ° phase shifter 202 ... Frequency conversion mixer 203,204 ... Low pass filter 205,206,207,208 ... Sample Hold circuit, 209, 210 ... subtractor, 211, 212 ... A / D converter, 213 ... phase correction processor, 214 ... despreading processing unit.

Claims (12)

A first sample-and-hold circuit and a second sample-and-hold circuit that alternately sample and hold the input spread signal every sampling interval ΔT;
A subtractor for obtaining a difference signal between the result of sample holding by the first sample and hold circuit and the result of sample holding by the second sample and hold circuit;
An A / D converter that samples the differential signal every ΔT and converts it into a digital signal;
A polarity converter for inverting the polarity of the difference signal digitized by the A / D converter every 2 × ΔT;
A despreading demodulator comprising a despreading processor that despreads the output signal of the polarity converter and demodulates the data signal. The despreading demodulator according to claim 1,
The despreading demodulator performs the despreading process using a spreading code that is code-converted corresponding to the difference signal. The despreading demodulator according to claim 1,
When the sampling interval ΔT and the spreading code period Δt satisfy Δt = a × ΔT (where a is a natural number of 2 or more), the despreading processor outputs a digitized number a output from the polarity converter. The despreading demodulator performs the despreading process on the result obtained by adding the difference signals. A first sample-and-hold circuit and a second sample-and-hold circuit that alternately sample and hold the input spread signal every sampling interval ΔT;
A subtractor for obtaining a difference signal between the result of sample holding by the first sample and hold circuit and the result of sample holding by the second sample and hold circuit;
An A / D converter that samples the differential signal every ΔT and converts it into a digital signal;
A polarity converter for inverting the polarity of the difference signal digitized by the A / D converter every 2 × ΔT;
An integrator for integrating the output signal of the polarity converter;
A despreading demodulator comprising a despreading processor that despreads the output signal of the integrator and demodulates the data signal. The despread demodulator according to claim 4,
The despreading processor performs the despreading process using a pseudo-spreading code obtained by adding one code to a true spreading code used for generating the spread signal in the transmitter, and the pseudo-spreading code A despread demodulator characterized in that the sum of is zero. The despread demodulator according to claim 4,
The despreading demodulator performs the despreading process using a Manchester type spreading code. A frequency conversion mixer that converts the spread signal of the input radio frequency band into two orthogonal spread signals of the intermediate frequency band;
A first sample-and-hold circuit and a second sample-and-hold circuit that alternately sample and hold the first spread signal output from the frequency conversion mixer at every sampling interval ΔT;
A third sample and hold circuit and a fourth sample and hold circuit that alternately sample and hold the second spread signal output from the frequency conversion mixer at every sampling interval ΔT;
A first subtractor for obtaining a difference signal between the result of sample holding by the first sample and hold circuit and the result of sample holding by the second sample and hold circuit;
A second subtractor for obtaining a difference signal between the result of sample holding by the third sample and hold circuit and the result of sample holding by the fourth sample and hold circuit;
A first A / D converter that samples the differential signal output from the first subtractor every ΔT and converts it into a digital signal;
A second A / D converter that samples the differential signal output from the second subtractor every ΔT and converts it into a digital signal;
A phase correction processor that outputs an addition signal obtained by adding the output signal of the first A / D converter and the output signal of the second A / D converter;
A spread spectrum radio receiver comprising: a despreading processing unit for performing a despreading process on an output signal of the phase correction processor and demodulating a data signal. The spread spectrum radio receiver according to claim 7,
The despreading processing unit uses a polarity converter that inverts the polarity of the output signal of the phase correction processor every 2 × ΔT, and a spreading code that is code-converted corresponding to the difference signal. A spread spectrum radio receiver comprising a despreading processor that performs a despreading process on an output signal. The spread spectrum radio receiver according to claim 8,
When the sampling interval ΔT and the spreading code period Δt satisfy Δt = a × ΔT (where a is a natural number of 2 or more), the despreading processor outputs a digitized number a output from the polarity converter. A spread spectrum radio receiver characterized in that the despreading process is performed on the result of adding the difference signals. The spread spectrum radio receiver according to claim 7,
The despreading processing unit includes a polarity converter for inverting the polarity of the output signal of the phase correction processor every 2 × ΔT, an integrator for integrating the output signal of the polarity converter, and an output of the integrator A spread spectrum radio receiver comprising a despreading processor that despreads a signal and demodulates a data signal. The spread spectrum radio receiver of claim 10.
The despreading processor performs the despreading process using a pseudo-spreading code obtained by adding one code to a true spreading code used for generating the spread signal in the transmitter, and the pseudo-spreading code A spread spectrum radio receiver characterized in that the sum of is zero. The spread spectrum radio receiver of claim 10.
The spread spectrum radio receiver characterized in that the despreading processor performs the despreading process using a Manchester type spreading code.

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