JP2003229738A - Analog phase shifter - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide an analog phase shifter with a small shape, a wide band, a low loss and a low power consumption to be used in the microwave band. <P>SOLUTION: The analog phase shifter is provided with a polyphase filter means 2 to distribute high-frequency differential input signals V<SB>in</SB>'/V<SB>in</SB>at phase differences -90°, 0°, 90° and 180° to four high-frequency signals A<SB>i</SB>, B<SB>i</SB>, C<SB>i</SB>and D<SB>i</SB>with an equal amplitude, four variable attenuators 4a to 4d to set amplitudes of the four high-frequency signals A<SB>i</SB>, B<SB>i</SB>, C<SB>i</SB>and D<SB>i</SB>each independently and an output terminal 5 to achieve an in-phase synthesis of the amplitude-set high- frequency signals A<SB>o</SB>, B<SB>o</SB>, C<SB>o</SB>and D<SB>o</SB>. <P>COPYRIGHT: (C)2003,JPO

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an analog type phase shifter used in a microwave band, having a small size, a wide band, low loss and low power consumption.

[0002]

2. Description of the Related Art FIG. 12 shows, for example, "" An Octav.
e Band Analog Phase Shift
er ”, 1989 IEEE MTT-S Diges
t, LL-4, pp. 1051-1054 "is a configuration diagram showing a conventional analog type phase shifter reported in FIG.
In FIG. 2, 1 is an input terminal, 12 is an RC filter, 121a, 121b, 121c, 121d are resistors, 122a, 122b are capacitors, and 1
3a and 13b are differential amplifiers, and 10a, 10b and 1
0c and 10d are variable gain amplifiers, and 5 is an output terminal.

Next, the operation will be described. Input terminal 1
The high-frequency signal V _in input from the three filters constituting the RC filter 12, that is, the capacitor 122.
a and a high-pass filter in which a resistor 121c whose one side is grounded are connected in parallel, a low-pass filter in which a resistor 121a and a resistor 121b whose one side is grounded are connected in parallel, a capacitor 122b and a resistor 1 whose one side is grounded 1
4 with a high-pass filter in which 21d is connected in parallel
The signals are distributed and passed through the differential amplifier 13a and the differential amplifier 13b to be distributed to four high frequency signals A _i , B _i , C _i and D _i having phase differences of 0 °, 90 °, 180 ° and −90 °. It

High-frequency signals A _i , B _i
C _i and D _i are variable gain amplifiers 10a, 10b and 10
c and 10d, the amplitudes of the four high-frequency signals A _o , B _o ,
After C _o and D _o are in-phase combined, an output signal V _out is obtained from the output terminal 5.

FIG. 13 shows a high frequency signal as a vector.
It is a figure. High frequency signal V input from input terminal 1
_inIs an RC filter 12 and differential amplifiers 13a and 13b
Therefore, the phase difference is 0 °, 90 °, 180 °, −9, respectively.
4 high frequency signals A with 0 ° _i, B_i, C_i, D_i
Will be distributed to. The high-frequency signal distributed by 4 is increased by the variable gain.
Set to any amplitude with the width devices 10a, 10b, 10c, 10d.
4 high-frequency signals A whose amplitude is set_o，
B_o, C_o, D_oAre in-phase combined and output signal V_outTo
obtain. For example, the output signal V of FIG._outIncrease the variable gain
The amplitudes of the width devices 10b and 10c are set to zero, and the variable gain amplifier 10
The amplitudes of a and 10d are set to certain values, and
Four high-frequency signal output signals A whose width is set_o, B_o, C
_o, D_oIs the case of in-phase synthesis.

[0006]

Since the conventional analog type phase shifter is constructed as described above, there are three filters forming an RC filter for dividing the input signal into four, and
Since two differential amplifiers are used, there is a problem that it is difficult to miniaturize them.

Further, the conventional analog type phase shifter uses an RC filter and a differential amplifier to divide the input signal into four, so that there is a problem that electric power for driving it is required. It was

Further, in the conventional analog type phase shifter, RC
Since the filter is used, it is necessary to provide a grounding wiring and a pad in the filter, which causes a problem that the circuit wiring and the arrangement are complicated.

Further, in the conventional analog type phase shifter, RC
Since the filter is used, it is necessary to provide a grounding wire and a pad in the filter, which makes it difficult to reduce the size.

The present invention has been made to solve the above problems, and an object thereof is to obtain an analog type phase shifter having a small size, low power consumption, and simple circuit wiring and arrangement.

[0011]

SUMMARY OF THE INVENTION An analog type phase shifter according to the present invention provides a high frequency differential input signal with a phase difference of 0 °, 90 °.
It has a polyphase filter means for distributing four high frequency signals of 180 °, 180 °, -90 ° and equal amplitude, and an output means for independently setting the amplitudes of the four high frequency signals and performing in-phase synthesis. is there.

In the analog type phase shifter according to the present invention, the output means comprises four variable attenuators for independently setting the amplitudes of the four high frequency signals and an output terminal for performing in-phase synthesis of the high frequency signals for which the amplitudes have been set. It will be.

In the analog type phase shifter according to the present invention, the output means comprises four variable gain amplifiers for independently setting the amplitudes of the four high frequency signals, and an output terminal for in-phase combining the high frequency signals for which the amplitudes have been set. It will be.

In the analog type phase shifter according to the present invention, the output means sets the amplitudes of the four high frequency signals independently of each other to generate the positive phase high frequency signal and the negative phase high frequency signal. And a positive phase output terminal for in-phase synthesizing the high-frequency signal of the positive phase for which the amplitude is set, and a negative-phase output terminal for in-phase synthesizing the high-frequency signal of the reverse phase for which the amplitude is set.

In the analog type phase shifter according to the present invention, the output means sets the amplitudes of the four high frequency signals independently of each other to generate the positive phase high frequency signal and the negative phase high frequency signal. An amplifier, a positive phase output terminal for in-phase synthesizing a positive phase high frequency signal whose amplitude is set, and an opposite phase output terminal for in-phase synthesizing an amplitude set negative phase high frequency signal.

In the analog type phase shifter according to the present invention, the output means has the phase difference of 0 ° and 1 among the four high frequency signals.
Two differential 0-π phase modulators that phase-modulate two sets of high-frequency differential signals consisting of a high-frequency signal of 80 ° and a high-frequency signal of which the phase difference is −90 ° and 90 ° at 0 ° and 180 °, Two differential variable attenuators for independently setting the amplitudes of two sets of phase-modulated high-frequency differential signals to generate a positive-phase high-frequency signal and a negative-phase high-frequency signal, and an amplitude-set positive-phase high-frequency signal It is composed of a positive-phase output terminal for in-phase synthesizing signals, and an opposite-phase output terminal for in-phase synthesizing a high-frequency signal of opposite phase whose amplitude is set.

In the analog type phase shifter according to the present invention, the output means has phase differences of 0 ° and 1 among the four high frequency signals.
Two differential 0-π phase modulators that phase-modulate two sets of high-frequency differential signals consisting of a high-frequency signal of 80 ° and a high-frequency signal of which the phase difference is −90 ° and 90 ° at 0 ° and 180 °, Two differential variable gain amplifiers for independently setting the amplitudes of two sets of phase-modulated high-frequency differential signals to generate a positive-phase high-frequency signal and a negative-phase high-frequency signal, and an amplitude-set positive-phase high-frequency signal It is composed of a positive-phase output terminal for in-phase synthesizing signals, and an opposite-phase output terminal for in-phase synthesizing a high-frequency signal of opposite phase whose amplitude is set.

The analog type phase shifter according to the present invention further has a bias circuit having a temperature compensation function.

The analog type phase shifter according to the present invention further comprises input means for generating a high frequency differential input signal from a single phase high frequency signal and supplying it to the polyphase filter means.

In the analog type phase shifter according to the present invention, the input means is a 180 ° distributor.

In the analog type phase shifter according to the present invention, the input means is an active balun.

In the analog type phase shifter according to the present invention, the polyphase filter means comprises a polyphase filter in which resistors and capacitors are alternately arranged and are connected in a ring shape.

In the analog type phase shifter according to the present invention, the polyphase filter means is formed by connecting two stages of polyphase filters in which resistors and capacitors are alternately arranged and are connected in a ring shape.

An analog type phase shifter according to the present invention has input means for generating four high frequency signals whose amplitudes are set from a high frequency differential input signal, and polyphase means for in-phase combining the four high frequency signals. Is.

In the analog type phase shifter according to the present invention, the input means sets the amplitudes of two sets of high frequency signals composed of the high frequency differential input signals independently of each other to set the positive phase high frequency differential signal and the negative phase high frequency signal. Two differential variable gain amplifiers that generate a differential signal, and two differential 0-π that phase-modulates a positive-phase high-frequency differential signal and a negative-phase high-frequency differential signal at 0 ° and 180 °.
It is composed of a phase modulator.

In the analog type phase shifter according to the present invention, the input means sets the amplitudes of two sets of high frequency signals, which are high frequency differential input signals, independently of each other, and sets the positive phase high frequency differential signal and the negative phase high frequency signal. Two differential variable attenuators for generating a differential signal, a positive phase high frequency differential signal and a negative phase high frequency differential signal
It consists of two differential 0-π phase modulators that perform phase modulation at ° and 180 °.

The analog type phase shifter according to the present invention further has a bias circuit having a temperature compensation function.

In the analog type phase shifter according to the present invention, the polyphase filter means comprises a polyphase filter in which resistors and capacitors are alternately arranged and are connected in a ring shape.

In the analog type phase shifter according to the present invention, the polyphase filter means is formed by connecting two stages of polyphase filters in which resistors and capacitors are alternately arranged and are annularly connected.

[0030]

BEST MODE FOR CARRYING OUT THE INVENTION An embodiment of the present invention will be described below. Embodiment 1. 1 is a block diagram showing an analog type phase shifter according to Embodiment 1 of the present invention. In Figure 1,
1a, 1b is a high-frequency signal V _in, / V _in (here, "/
“X” represents an inverted signal of the signal X. That is, / V _in represents an inverted signal of the signal V _in (a signal having a 180 ° phase difference). Hereinafter, the symbol “/” will be used in the present specification to express the same meaning. ) Is a differential input terminal. A polyphase filter 2 receives the high frequency signals V _in and / V _{in and} outputs four high frequency signals A _i , B _i , C _i and D _i . 3a, 3b, 3c and 3d are output terminals of the polyphase filter 2. Reference numerals 4a, 4b, 4c and 4d are variable attenuators which receive the high frequency signals A _i , B _i , C _i and D _{i respectively and} output the high frequency signals A _o , B _o , C _o and D _o . _{Reference numeral} 5 is an output terminal for the high frequency signal V _out . In addition,
The four output terminals 3a, 3b of the polyphase filter 2,
4 high-frequency signals A _i output from 3c and 3d,
B _i , C _i , and D _i have a phase difference of 0 °, 90 °, and 18 respectively.
It is 0 °, −90 °, and has the same amplitude.

FIG. 2 is a diagram showing a configuration example of the polyphase filter 2 shown in FIG. 1. In FIG. 2, 1a and 1b are provided.
Is an input terminal, 21a, 21b, 21c and 21d are resistors, 22a, 22b, 22c and 22d are capacitors and 3a, 3b, 3c and 3d are output terminals.

Next, the structure will be described. In the polyphase filter 2 shown in FIG. 2, 4 having the same resistance value
One resistor 21a, 21b, 21c, 21d and four capacitors 22a, 22b, 22c, which have the same capacitance value,
22d has resistors and capacitors alternately arranged and is connected in series in a ring shape. Resistor 21a and capacitor 2
The connecting point of 2a and the connecting point of the resistor 21b and the capacitor 22b are connected to the positive phase input terminal 1a of the differential input terminal, and the connecting point of the resistor 21d and the capacitor 22d and the connecting point of the resistor 21c and the capacitor 22c are different. It is connected to the input terminal 1b of the opposite phase of the dynamic input terminal. The connection point of the resistor 21d and the capacitor 22c is connected to the output terminal 3b, the connection point of the resistor 21b and the capacitor 22a is connected to the output terminal 3a, and the connection point of the resistor 21a and the capacitor 22d is connected to the output terminal 3c. The connection point of the resistor 21c and the capacitor 22b is connected to the output terminal 3d.

Differential signal input from the input terminals 1a and 1b
Issue V_in, / V_inIndicates a phase difference of 0 °, 90 °, 180 °, −
High frequency signal A with 90 ° and equal amplitude_i, B_i，
C_i, D _iOutput terminals 3a, 3d, 3
It is output from b and 3c.

Next, the operation will be described. The high frequency signals V _in and / V _in input from the differential input terminals 1a and 1b are
The phase difference is 0 °, 9 after being divided into four by the polyphase filter 2.
Four high frequency signals A _i , B _i , C _i and D _{i of} 0 °, 180 ° and −90 ° and of equal amplitude are output from the output terminals 3a and 3.
It is output from d, 3b and 3c. The four high frequency signals A _i , B _i , C _i and D _i are respectively supplied to the variable attenuators 4a and 4a.
b, 4c, are input to 4d, each independently and optionally is amplitude setting, four amplitude setting high frequency signal _{A o, B o, C o} , is output as D _o. The four amplitude-set high frequency signals A _o , B _o , C _o and D _o are in-phase combined to obtain an output signal V _out from the output terminal 5.

FIG. 3 is a diagram for explaining the operation in the circuit configuration of FIG. 1 and shows the amplitude and phase of each signal. In FIG. 3, V _in is an input signal, V _out is an output signal, and A _i , B _i , C _i , and D _i are the input signal V _in when the polyphase filter 2 has a phase difference of 0 °, 90 °, 180 °,
The output signals are −90 ° and are equally divided into four, and A _o , B _o , C _o , and D _o are four high-frequency signals A _i ,
B _i , C _i , and D _i are high-frequency signals whose amplitude is arbitrarily set by the variable attenuator 4.

High-frequency signals A _o and B with four amplitude settings
_{Since the} amplitudes of _o , C _o , and D _o are independently set, the output signal V _out can be a vector whose end point is an arbitrary point within the shaded area in FIG. Further, the variable attenuator 4 controls the amplitudes of the four signals A _o , B _o , C _o , and D _o so that the amplitude of V _out becomes constant, and the in-phase synthesis is performed to thereby perform a 360 ° phase variable analog. Obtain a phase shifter.

For example, in the output signal V _out of FIG. 3, the amplitudes of the high frequency signals C _o and D _o output by the variable attenuators 4b and 4d are set to zero, and the high frequency signal A output by the variable attenuators 4a and 4c.
_By setting the amplitudes of _o and B _o to certain values, the high frequency signal A _o ,
This is the case where B _o , C _o , and D _o are in-phase synthesized.

As described above, in the analog type phase shifter of the first embodiment, the high frequency differential input signals V _in and / V _in have the phase difference of 0 °, 90 °, 180 ° and −90 °, and , A polyphase filter means 2 for distributing four high-frequency signals A _i , B _i , C _i , D _i of equal amplitude, and four high-frequency signals A _i , B _i , C _i , D _i are independently set in amplitude. And output means 4a-4d, 5 for performing in-phase synthesis.

The analog type phase shifter of the first embodiment is
Output means 4 a to 4 d, 5 are four high-frequency signals A _i, B
_From the four variable attenuators 4a to 4d for independently setting the amplitudes of _i , C _i , and D _i, and the output terminal 5 for in-phase combining the high-frequency signals A _o , B _o , C _o , and D _o with the set amplitude. It will be.

The analog type phase shifter of the first embodiment is
The polyphase filter means 2 comprises the polyphase filter 2 in which resistors 21a to 21d and capacitors 22a to 22d are alternately arranged and are connected in a ring shape.

As described above, according to the first embodiment, the input differential signal is supplied to the polyphase filter 2,
The phase difference is 0 °, 90 °, 180 °, -90 °, and
Since the configuration is such that the equal amplitude can be divided into four, the effect of miniaturizing the analog type phase shifter can be obtained.

According to the first embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since it is composed of only ~ 22d, it is possible to obtain the effect of reducing the power consumption of the analog type phase shifter.

According to the first embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since 22d are connected in series in a ring shape, wiring and pads for grounding are not required, and the circuit wiring and arrangement of the analog type phase shifter can be simplified.

Embodiment 2. 4 is a block diagram showing an analog type phase shifter according to Embodiment 2 of the present invention. In FIG. 4, the same reference numerals as those in FIG. 1 indicate the same or corresponding portions, and the description thereof will be omitted. 6 outputs are inputted high-frequency signal V _in differential signal V _'in, / V' a _in 180
° It is a distributor. Reference numeral 61 is an input terminal of the 180 ° distributor 6.

Next, the operation will be described. 180 ° distributor (passive balun) 6 single-phase input high frequency signal V phases from _in the 180 ° different differential signal V _'in,
/ V ' _in is generated and output. At this time, the differential signal V '
Any phase may be used for the high frequency signal V _in as long as _in and / V ′ _in are 180 ° out of phase with each other. For example, the differential signal V _'in a high-frequency signal V
When having a 0 ° phase relative _in the differential signal /
V ′ _in has a phase of 180 ° with respect to the high frequency signal V _in , and when the differential signal V ′ _in has a phase of 90 ° with respect to the high frequency signal V _in , the differential signal / V ′ _in Has a phase of −90 ° with respect to the high frequency signal V _in . Also, 180 °
The distributor (passive balun) 6, a differential signal V _'in, /
The amplitude of V _'in becomes that as compared to the high-frequency signal V _in of the input single-phase attenuated.

The differential signal V _'in, / V' _in each polyphase filter and second differential input terminals 1a, is supplied to 1b. Since the following operation is the same as that of the first embodiment, the description is omitted.

The vector-synthesizing analog phase shifter of the second embodiment has a 180 ° distributor 6 arranged in front of the polyphase filter 2 of the first embodiment as shown in FIG. Embodiment 4 and Embodiment 5 described later
18 before the polyphase filter 2 of the seventh embodiment and the polyphase filter 11 of the eighth embodiment.
The 0 ° distributor 6 may be arranged.

As described above, in the analog type phase shifter according to the second embodiment, the high frequency differential input signals V _in and / V _in have the phase difference of 0 °, 90 °, 180 °, -90 °, and , A polyphase filter means 2 for distributing four high-frequency signals A _i , B _i , C _i , D _i of equal amplitude, and four high-frequency signals A _i , B _i , C _i , D _i are independently set in amplitude. And output means 4a-4d, 5 / 8a-8d, 5 for performing in-phase synthesis
a, 5b / 10'a to 10'd, 5a, 5b / 9a, 9
b, 8a, 8b, 5a, 5b / 9a, 9b, 10'a,
10'b, 5a, 5b.

The analog type phase shifter of the second embodiment is
Output means 4 a to 4 d, 5 are four high-frequency signals A _i, B
_From the four variable attenuators 4a to 4d for independently setting the amplitudes of _i , C _i , and D _i, and the output terminal 5 for in-phase combining the high-frequency signals A _o , B _o , C _o , and D _o with the set amplitude. It will be.

The analog type phase shifter of the second embodiment is
The output means 8a to 8d, 5a, 5b independently set the amplitudes of the four high frequency signals A _i , B _i , C _i , D _i , respectively, and positive phase high frequency signals A _o , B _o , C _o , D _o. And four differential variable attenuators 8a to 8d for generating high-frequency signals / A _o , / B _o , / C _o , / D _o of opposite phase, and high-frequency signals A _o and B _{o of} positive phase whose amplitude is set. , _Co and _Do in-phase combined output terminal 5a and amplitude-set opposite phase high frequency signals / _Ao , / _Bo , / _Co and / _Do in-phase combined output It is composed of a terminal 5b.

The analog type phase shifter of the second embodiment is
Output means 10'a~10'd, 5a, 5b are four high-frequency signals _{A i, B i, C i} , a high-frequency signal of positive phase and amplitude independently set the _{D i A o, B o,} C _o, D _o and reverse phase high-frequency signal _{/ a o, / B o,} / C o, / D o 4 one differential variable gain amplifier 10'a~10'd for generating
And the positive-phase high-frequency signals A _o , B _o with amplitude set,
A positive phase output terminal 5a for in-phase combining C _o and D _o and a high frequency signal / A _o , / B _o , / of the opposite phase whose amplitude is set.
And an output terminal 5b of the opposite phase for in-phase combining C _o and / D _o .

The analog type phase shifter of the second embodiment is
Four output means 9a, 9b, 8a, 8b, 5a, 5b
High frequency signal A_i, B_i, C_i, D_iPhase difference of 0
° and 180 ° high frequency signal A_i, C_iAnd the phase difference is −
90 ° and 90 ° high frequency signals B_i, D_iConsists of
Phase modulation of two high frequency differential signals at 0 ° and 180 °
Two differential 0-π phase modulators 9a, 9b
Two sets of modulated high frequency differential signals (A '_i, C '_i, And
B '_i, D ’_iOr / A '_i, / C '_i,and/
B ’_i, / D '_i), The amplitude is set independently for each phase
High frequency signal (A '_o , B ’_o Or / A '_o , / B '
_o ) And a high-frequency signal (C ′) of opposite phase_o , D ’_o Or /
C ’_o , / D '_o ) Generating two differential variable attenuators 8
a, 8b and a high-frequency signal (A ′) of a positive phase whose amplitude is set.
_o , B ’_o Or / A '_o , / B ' _o ) In-phase synthesis
Positive phase output terminal 5a and opposite phase high frequency with amplitude set
Signal (C '_o , D ’_o Or / C '_o , / D '_o ) Same
It is composed of an output terminal 5b of opposite phase for phase combination.

The analog type phase shifter of the second embodiment is
Output means 9a, 9b, 10'a, 10'b, 5a, 5b
But four high-frequency signals A _i, B _i, C _i, a high-frequency signal phase difference is 0 ° and 180 ° of the D _i A _i, C _i and the phase difference is -90 ° and 90 ° RF signal B _i , D _i , two differential 0-π phase modulators 9a and 9b for phase-modulating two high-frequency differential signals at 0 ° and 180 °.
And two pairs of phase-modulated high-frequency differential signals (A ′ _i ,
_C'i , and _B'i , D' _i or / _A'i , / C '
_i , and / B ' _i , / D' _i ) are set to have independent amplitudes, and a positive phase high frequency signal (A ' _o , B' _o or /
_A'o , / _B'o ) and a high frequency signal of opposite phase ( _C'o ,
D _'o or _{/ C' o, / D '} o) to generate two differential variable gain amplifier 10'a, 10'b and, amplitude set positive phase high frequency signal (A' _o, B _'o Or / A ' _o ,
/ B ' _o ) in-phase output terminal 5a for in-phase synthesis and anti-phase high-frequency signal (C' _o , D' _o or / C ' _o , / D' _o ) for in-phase synthesis in which the amplitude is set. Output terminal 5
and b.

The analog type phase shifter of the second embodiment is
Bias circuits 101a and 101 having a temperature compensation function
b, 101c, 101d are further included.

The analog type phase shifter of the second embodiment is
High frequency differential from the high-frequency signal V _in the single-phase input signal V _'in,
/ V 'and generates _in those further comprising an input unit 6 for supplying the polyphase filtering means.

The analog type phase shifter of the second embodiment is
The input means 6 comprises a 180 ° distributor 6.

The analog type phase shifter of the second embodiment is
The polyphase filter means 2 comprises the polyphase filter 2 in which resistors 21a to 21d and capacitors 22a to 22d are alternately arranged and are connected in a ring shape.

As described above, according to the second embodiment, the input differential signal is input to the polyphase filter 2,
The phase difference is 0 °, 90 °, 180 °, -90 °, and
Since the configuration is such that the equal amplitude can be divided into four, the effect of miniaturizing the analog type phase shifter can be obtained.

According to the second embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since it is composed of only ~ 22d, it is possible to obtain the effect of reducing the power consumption of the analog type phase shifter.

According to the second embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since 22d are connected in series in a ring shape, wiring and pads for grounding are not required, and the circuit wiring and arrangement of the analog type phase shifter can be simplified.

According to the second embodiment, the 180 ° distributor 6 is provided in the preceding stage of the polyphase filter 2 so that the input single-phase high-frequency signal is supplied to the polyphase filter 2 as a high-frequency differential signal. Therefore, it is possible to obtain the effect that a high-frequency input signal that is not differential can be used.

Embodiment 3. 5 is a block diagram showing an analog type phase shifter according to a third embodiment of the present invention. In FIG. 5, the same reference numerals as those in FIG. 1 indicate the same or corresponding portions, and thus the description thereof will be omitted. 7 differential signal V _'in, / V' is inputted high-frequency signal V _in is active balun for outputting _in, 71 denotes an input terminal of the active balun.

Next, the operation will be described. Active bar
Run 7 is the input single-phase high-frequency signal V_inFrom each other
A differential signal V ′ having a phase difference of 180 °_in, / V '_inProduces
Output. High frequency signal V_inAnd the differential signal V '_in, /
V '_inThe phase relationship of the 180 ° distributor of the second embodiment
It is similar to the case of 6. Also, with Active Balun 7
Is the differential signal V '_in, / V ' _inThe amplitude of the
Phase high frequency signal V_inWas amplified with a predetermined gain compared to
Will be

[0064] Differential signal V _'in, / V' _in each polyphase filter and second differential input terminals 1a, is supplied to 1b. Since the following operation is the same as that of the first embodiment, the description is omitted.

The vector-synthesizing analog phase shifter of the third embodiment has an active balun 7 arranged before the polyphase filter 2 of the first embodiment as shown in FIG. 5, which will be described later. The active balun 7 may be arranged before the polyphase filter 2 of the fourth, fifth, and seventh embodiments and the polyphase filter 11 of the eighth embodiment.

As described above, in the analog type phase shifter of the third embodiment, the high frequency differential input signals V _in and / V _in have the phase difference of 0 °, 90 °, 180 ° and −90 °, and , A polyphase filter means 2 for distributing four high-frequency signals A _i , B _i , C _i , D _i of equal amplitude, and four high-frequency signals A _i , B _i , C _i , D _i are independently set in amplitude. And output means 4a-4d, 5 / 8a-8d, 5 for performing in-phase synthesis
a, 5b / 10'a to 10'd, 5a, 5b / 9a, 9
b, 8a, 8b, 5a, 5b / 9a, 9b, 10'a,
10'b, 5a, 5b.

The analog type phase shifter of the third embodiment is
Output means 4 a to 4 d, 5 are four high-frequency signals A _i, B
_From the four variable attenuators 4a to 4d for independently setting the amplitudes of _i , C _i , and D _i, and the output terminal 5 for in-phase combining the high-frequency signals A _o , B _o , C _o , and D _o with the set amplitude. It will be.

The analog type phase shifter of the third embodiment is
The output means 8a to 8d, 5a, 5b independently set the amplitudes of the four high frequency signals A _i , B _i , C _i , D _i , respectively, and positive phase high frequency signals A _o , B _o , C _o , D _o. And four differential variable attenuators 8a to 8d for generating high-frequency signals / A _o , / B _o , / C _o , / D _o of opposite phase, and high-frequency signals A _o and B _{o of} positive phase whose amplitude is set. , _Co and _Do in-phase combined output terminal 5a and amplitude-set opposite phase high frequency signals / _Ao , / _Bo , / _Co and / _Do in-phase combined output It is composed of a terminal 5b.

The analog type phase shifter of the third embodiment is
Output means 10'a~10'd, 5a, 5b are four high-frequency signals _{A i, B i, C i} , a high-frequency signal of positive phase and amplitude independently set the _{D i A o, B o,} C _o, D _o and reverse phase high-frequency signal _{/ a o, / B o,} / C o, / D o 4 one differential variable gain amplifier 10'a~10'd for generating
And the positive-phase high-frequency signals A _o , B _o with amplitude set,
A positive phase output terminal 5a for in-phase combining C _o and D _o and a high frequency signal / A _o , / B _o , / of the opposite phase whose amplitude is set.
And an output terminal 5b of the opposite phase for in-phase combining C _o and / D _o .

The analog type phase shifter of the third embodiment is
Four output means 9a, 9b, 8a, 8b, 5a, 5b
High frequency signal A_i, B_i, C_i, D_iPhase difference of 0
° and 180 ° high frequency signal A_i, C_iAnd the phase difference is −
90 ° and 90 ° high frequency signals B_i, D_iConsists of
Phase modulation of two high frequency differential signals at 0 ° and 180 °
Two differential 0-π phase modulators 9a, 9b
Two sets of modulated high frequency differential signals (A '_i, C '_i, And
B '_i, D ’_iOr / A '_i, / C '_i,and/
B ’_i, / D '_i), The amplitude is set independently for each phase
High frequency signal (A '_o , B ’_o Or / A '_o , / B '
_o ) And a high-frequency signal (C ′) of opposite phase_o , D ’_o Or /
C ’_o , / D '_o ) Generating two differential variable attenuators 8
a, 8b and a high-frequency signal (A ′) of a positive phase whose amplitude is set.
_o , B ’_o Or / A '_o , / B ' _o ) In-phase synthesis
Positive phase output terminal 5a and opposite phase high frequency with amplitude set
Signal (C '_o , D ’_o Or / C '_o , / D '_o ) Same
It is composed of an output terminal 5b of opposite phase for phase combination.

The analog type phase shifter of the third embodiment is
Output means 9a, 9b, 10'a, 10'b, 5a, 5b
But four high-frequency signals A _i, B _i, C _i, a high-frequency signal phase difference is 0 ° and 180 ° of the D _i A _i, C _i and the phase difference is -90 ° and 90 ° RF signal B _i , D _i , two differential 0-π phase modulators 9a and 9b for phase-modulating two high-frequency differential signals at 0 ° and 180 °.
And two pairs of phase-modulated high-frequency differential signals (A ′ _i ,
_C'i , and _B'i , D' _i or / _A'i , / C '
_i , and / B ' _i , / D' _i ) are set to have independent amplitudes, and a positive phase high frequency signal (A ' _o , B' _o or /
_A'o , / _B'o ) and a high frequency signal of opposite phase ( _C'o ,
D _'o or _{/ C' o, / D '} o) to generate two differential variable gain amplifier 10'a, 10'b and, amplitude set positive phase high frequency signal (A' _o, B _'o Or / A ' _o ,
/ B ' _o ) in-phase output terminal 5a for in-phase synthesis and anti-phase high-frequency signal (C' _o , D' _o or / C ' _o , / D' _o ) for in-phase synthesis in which the amplitude is set. Output terminal 5
and b.

The analog type phase shifter of the third embodiment is
Bias circuits 101a and 101 having a temperature compensation function
b, 101c, 101d are further included.

The analog type phase shifter of the third embodiment is
High frequency differential from the high-frequency signal V _in the single-phase input signal V _'in,
/ V 'and generates _in those further comprising an input unit 7 for supplying the polyphase filtering means.

The analog type phase shifter of the third embodiment is
The input means 7 comprises an active balun 7.

The analog type phase shifter of the third embodiment is
The polyphase filter means 2 comprises the polyphase filter 2 in which resistors 21a to 21d and capacitors 22a to 22d are alternately arranged and are connected in a ring shape.

As described above, according to the third embodiment, the input differential signal is input to the polyphase filter 2,
The phase difference is 0 °, 90 °, 180 °, -90 °, and
Since the configuration is such that the equal amplitude can be divided into four, the effect of miniaturizing the analog type phase shifter can be obtained.

According to the third embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since it is composed of only ~ 22d, it is possible to obtain the effect of reducing the power consumption of the analog type phase shifter.

According to the third embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since 22d are connected in series in a ring shape, wiring and pads for grounding are not required, and the circuit wiring and arrangement of the analog type phase shifter can be simplified.

According to the third embodiment, the active balun 7 is provided in the preceding stage of the polyphase filter 2 so that the input single-phase high-frequency signal is supplied to the polyphase filter 2 as a high-frequency differential signal. An effect that a high frequency input signal that is not differential can be used is obtained.

According to the third embodiment, since the active balun 7 is provided with a gain, it is possible to reduce the loss of the analog type phase shifter.

Fourth Embodiment 6 is a block diagram of an analog type phase shifter according to Embodiment 4 of the present invention. In FIG. 6, the same reference numerals as those in FIG. 1 indicate the same or corresponding portions, and the description thereof will be omitted. 8a is a high frequency signal A _i , C
It is a differential variable attenuator which receives _i (/ A _i ) and outputs differential signals A _o and / A _o . 8b is a high frequency signal C _i , A
It is a differential variable attenuator that receives _i (/ C _i ) and outputs differential signals C _o and / C _o . 8c is a high frequency signal B _i , D
It is a differential variable attenuator which receives _i (/ B _i ) and outputs differential signals B _o and / B _o . 8d is a high frequency signal D _i , B
It is a differential variable attenuator that receives _i (/ D _i ) and outputs differential signals D _o and / D _o . Reference numeral 5a is a positive phase output terminal, and 5b is a negative phase output terminal.

Next, the operation will be described. Polyphase
The operation of the filter 2 is the same as that of the first embodiment.
The description is omitted. The differential variable attenuator 8a is input
High frequency signal A_i, C_i(/ A_i) Amplitude is set arbitrarily
Differential signal A_o, / A_oIs generated and output. Differential variable
The attenuator 8b receives the input high frequency signal C_i, A_i(/ C
_i) Of the differential signal C_o, / C_oLive
Generate and output. The differential variable attenuator 8c receives the input high
Frequency signal B_i, D_i(/ B_i) Amplitude is set arbitrarily
Differential signal B_o, / B _oIs generated and output. Differential variable reduction
The attenuator 8d receives the input high frequency signal D_i, B _i(/
D_i) Is set to any value and the differential signal D_o, / D_oTo
Generate and output.

Of the differential signals output by the differential variable attenuators 8a to 8d, positive phase high frequency signals A _o , B _o ,
C _o and D _o are combined in phase to obtain the output signal V _out from the positive phase output terminal 5a. Of the differential signals output by the differential variable attenuators 8a to 8d, the high frequency signal of the opposite phase /
A _o , / B _o , / C _o and / D _o are in-phase combined to obtain an output signal / V _out from the output terminal 5b in anti-phase.

The positive-phase output signal V _out is generated in the same manner as the description given for the first embodiment with reference to FIG. 3, and the negative-phase output signal / V _out is the same as the positive-phase output signal V _out. Will be generated.

As described above, in the analog type phase shifter according to the fourth embodiment, the high frequency differential input signals V _in and / V _in have the phase differences of 0 °, 90 °, 180 ° and −90 °, and , A polyphase filter means 2 for distributing four high-frequency signals A _i , B _i , C _i , D _i of equal amplitude, and the four high-frequency signals A _i , B _i , C _i , D _i independently of each other in amplitude. It has output means 8a to 8d, 5a and 5b for setting and in-phase combining.

The analog type phase shifter of the fourth embodiment is
The output means 8a to 8d, 5a, 5b independently set the amplitudes of the four high frequency signals A _i , B _i , C _i , D _i , respectively, and positive phase high frequency signals A _o , B _o , C _o , D _o. And four differential variable attenuators 8a to 8d for generating high-frequency signals / A _o , / B _o , / C _o , / D _o of opposite phase, and high-frequency signals A _o and B _{o of} positive phase whose amplitude is set. , C _o, D _o the positive phase output terminals 5a and amplitude set reversed phase phase combining high-frequency signal _{/ a o, / B o,} / C o, of the reverse-phase in-phase synthesizing / D _o output terminal 5b and.

The analog type phase shifter of the fourth embodiment is
The polyphase filter means 2 comprises the polyphase filter 2 in which resistors 21a to 21d and capacitors 22a to 22d are alternately arranged and are connected in a ring shape.

As described above, according to the fourth embodiment, the input differential signal is converted by the polyphase filter 2 into
The phase difference is 0 °, 90 °, 180 °, -90 °, and
Since the configuration is such that the equal amplitude can be divided into four, the effect of miniaturizing the analog type phase shifter can be obtained.

According to the fourth embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since it is composed of only ~ 22d, it is possible to obtain the effect of reducing the power consumption of the analog type phase shifter.

According to the fourth embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since 22d are connected in series in a ring shape, wiring and pads for grounding are not required, and the circuit wiring and arrangement of the analog type phase shifter can be simplified.

According to the fourth embodiment, the phase difference output from the polyphase filter 2 is 0 °, 90 °, 180 °.
4 high-frequency signals of
Since the two differential variable attenuators 8a to 8d independently and arbitrarily set the amplitudes to perform in-phase synthesis, a high frequency differential output signal can be obtained from the output terminals 5a and 5b.
Even if the interface (either single-phase or differential) of the devices connected before and after the phase shifter is different, the effect of matching with these devices can be obtained.

Embodiment 5. 7 is a block diagram showing an analog type phase shifter according to a fifth embodiment of the present invention. Figure 7
In FIG. 1, the same reference numerals as those in FIG. 9a is a high frequency signal A _i ,
C _i is input a high frequency signal A _'i, C' _i or radio frequency signal / A _'i, / C' differential 0-[pi phase modulator for outputting a _i. 9b receives the high frequency signals B _i and D _{i, and} receives the high frequency signals B ′ _i and D ′ _i or the high frequency signals / B ′ _i ,
It is a differential 0-π phase modulator that outputs / D ′ _i . 8a
Is a high frequency signal A ′ _i , C ′ _i or a high frequency signal /
_A'i , / C ' _i are input and high frequency signals _A'o , C'
_This is a differential variable attenuator that outputs _o or high frequency signals / A ' _o and / C' _o . 8b is a high-frequency signal B _'i, D' _i or radio frequency signals _{/ B 'i, / D'} i is the input frequency signal differential signal B _'o, D' _o or high-frequency signal /
This is a differential variable attenuator that outputs _B'o and / D' _o . 5
Reference numeral a is a positive-phase output terminal, and reference numeral 5b is a negative-phase output terminal.

Next, the operation will be described. The operation of the polyphase filter 2 is the same as that of the first embodiment, and therefore its explanation is omitted. The differential 0-π phase modulator 9a performs 0 phase modulation and π phase modulation according to a control signal (not shown). That is, when 0 phase modulation is performed, the phases of the input high frequency signals A _i and C _i are left unchanged and high frequency signals A ′ _i and C ′ _i are generated and output.
When performing π phase modulation, input high-frequency signal A
High-frequency signal with the phase of _i , C _i shifted by 180 °
_A'i and / _C'i are generated and output. Similarly to the differential 0-π phase modulator, the differential 0-π phase modulator 9b also performs 0 phase modulation or π phase modulation on the input high frequency signals B _i and D _i to generate a high frequency signal B ′. _i , D ′ _i or high frequency signals / B ′ _i , / D ′ _i are generated and output.

The differential variable attenuator 8a receives the input high frequency signals _A'i , _C'i (or the high frequency signals / ' _Ai , /
If the amplitude of _C'i ) is set arbitrarily, the high frequency signal _A'o ,
_C'o (or high-frequency signals / _A'o , / _C'o ) is generated and output. The differential variable attenuator 8b receives the input high frequency signals _B'i , D' _i (or the high frequency signals / ' _Bi , /
If the amplitude of D' _i ) is arbitrarily set, the high frequency signal _B'o ,
D' _o (or high frequency signal / B ' _o , / D' _o ) is generated and output.

The high frequency signals _A'o , _B'o (or the high frequency signal /
_A'o , / _B'o ) are in-phase combined and output in positive phase 5
Obtain the output signal V _out from a. Differential variable attenuator 8a,
Frequency signal C _'o, D' output by 8b _o (or high-frequency signal _{/ C 'o, / D'} o) to obtain an output signal V _'out from the output terminal 5b of the opposite phase is phase synthesis.

The positive-phase output signal V _out is generated in the same manner as the description given for the first embodiment with reference to FIG. 3, and the negative-phase output signal V ′ _out is the same as the positive-phase output signal V _out. Will be generated. However, in the fifth embodiment, the positive-phase output signal V _out is represented as a vector having the end point in the first quadrant or the third quadrant of FIG. 3, and the negative-phase output signal V ' _out will be represented as a vector with endpoints in the second or fourth quadrant of FIG. Furthermore, by setting the attenuation rate of each of the differential variable attenuators 8a and 8b to the same value when the 0 phase modulation is performed by the differential 0-π phase modulators 9a and 9b and when the π phase modulation is performed. , the output signal V _'out of the reverse phase inverted signal / V _out next to the output signal V _out of _the positive phase, the differential variable attenuator 8
By changing the attenuation rate of each of a and 8b, the amplitude and the phase of the output signal _V'out of the opposite phase are changed to the output signal _Vout of the positive phase.
Can be set independently of.

As described above, in the analog type phase shifter of the fifth embodiment, the high frequency differential input signals V _in and / V _in have the phase difference of 0 °, 90 °, 180 ° -90 °, and Polyphase filter means 2 for distributing four high-frequency signals A _i , B _i , C _i , D _i of equal amplitude, and four high-frequency signals A _i ,
It has output means 9a, 9b, 8a, 8b, 5a, 5b for independently setting the amplitudes of B _i , C _i and D _i and performing in-phase synthesis.

The analog type phase shifter of the fifth embodiment is
Four output means 9a, 9b, 8a, 8b, 5a, 5b
High frequency signal A_i, B_i, C_i, D_iPhase difference of 0
° and 180 ° high frequency signal A_i, C_iAnd the phase difference is −
90 ° and 90 ° high frequency signals B_i, D_iConsists of
Phase modulation of two high frequency differential signals at 0 ° and 180 °
Two differential 0-π phase modulators 9a, 9b
Two sets of modulated high frequency differential signals (A '_i, C '_i, And
B '_i, D ’_iOr / A '_i, / C '_i,and/
B ’_i, / D '_i), The amplitude is set independently for each phase
High frequency signal (A '_o , B ’_o Or / A '_o , / B '
_o ) And a high-frequency signal (C ′) of opposite phase_o , D ’_o Or /
C ’_o , / D '_o ) Generating two differential variable attenuators 8
a, 8b and a high-frequency signal (A ′) of a positive phase whose amplitude is set.
_o , B ’_o Or / A '_o , / B ' _o ) In-phase synthesis
Positive phase output terminal 5a and opposite phase high frequency with amplitude set
Signal (C '_o , D ’_o Or / C '_o , / D '_o ) Same
It is composed of an output terminal 5b of opposite phase for phase combination.

The analog type phase shifter of the fifth embodiment is
The polyphase filter means 2 comprises the polyphase filter 2 in which resistors 21a to 21d and capacitors 22a to 22d are alternately arranged and are connected in a ring shape.

As described above, according to the fifth embodiment, the input differential signal is input to the polyphase filter 2,
The phase difference is 0 °, 90 °, 180 °, -90 °, and
Since the configuration is such that the equal amplitude can be divided into four, the effect of miniaturizing the analog type phase shifter can be obtained.

According to the fifth embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since it is composed of only ~ 22d, it is possible to obtain the effect of reducing the power consumption of the analog type phase shifter.

According to the fifth embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since 22d are connected in series in a ring shape, wiring and pads for grounding are not required, and the circuit wiring and arrangement of the analog type phase shifter can be simplified.

According to the fifth embodiment, the phase differences output from the polyphase filter 2 are 0 °, 90 °, 180 °.
Four high-frequency signals with the same amplitude at
Since two differential 0-π phase modulators 9a and 9b are used to perform phase modulation at 0 ° or 180 °, respectively,
By using the two differential variable attenuators 8a and 8b, a high frequency differential output signal can be obtained from the output terminals 5a and 5b, and the interface of devices connected before and after the phase shifter (single phase and differential Even if any one of them is different, the effect of matching with these devices can be obtained.

Sixth Embodiment 8 is a block diagram showing an analog type phase shifter according to a sixth embodiment of the present invention. In FIG. 8, the same reference numerals as those in FIGS. 1 and 5 indicate the same or corresponding portions, and the description thereof will be omitted. 10a, 1
0b, 10c and 10d are high frequency signals A _i , B _i and C, respectively.
_i , D _i are input and high frequency signals A _o , B _o , C _o , D
It is a variable gain amplifier that outputs _o .

Next, the operation will be described. The operation of the active balun 7 is the same as that of the third embodiment, and the operation of the polyphase filter 2 is the same as that of the first embodiment, so the description thereof will be omitted. The four high frequency signals A _i , B _i , C _i and D _i are respectively supplied to the variable gain amplifier 10
a, 10b, 10c, are input to 10d, each independently and optionally is amplitude setting, four amplitude setting high frequency signal _{A o, B o, C o} , is output as D _o. Four
High-frequency signals A _o , B _o , C _o , and D _{o with} two amplitude settings
Are in-phase combined to obtain an output signal V _out from the output terminal 5.

The positive-phase output signal V _out is generated in the same manner as the description given for the first embodiment with reference to FIG.

The vector synthesis type analog phase shifter of the sixth embodiment is obtained by replacing the variable attenuators 4a-4d of the third embodiment with variable gain amplifiers 10a-10d as shown in FIG. The variable attenuators 4a to 4d of the first and second embodiments are replaced by the variable gain amplifiers 10a to 10a.
It may be replaced with 0d.

As described above, in the analog type phase shifter of the sixth embodiment, the high frequency differential input signals V _in and / V _in have the phase differences of 0 °, 90 °, 180 ° and −90 °, and , A polyphase filter means 2 for distributing four high-frequency signals A _i , B _i , C _i , D _i of equal amplitude, and four high-frequency signals A _i , B _i , C _i , D _i are independently set in amplitude. And output means 10a to 10d, 5 for performing in-phase synthesis.

The analog type phase shifter of the sixth embodiment is
Output means 10 a to 10 d, 5 are four high-frequency signals _{A i, B i, C i} , and four variable gain amplifier 10 a to 10 d for amplitude setting independently the D _i, amplitude setting high frequency signal A _o, B _o, in which C _o, and an output terminal 5 for phase combining a D _o.

The analog type phase shifter of the sixth embodiment is
Bias circuits 101a and 101 having a temperature compensation function
b, 101c, 101d are further included.

The analog type phase shifter of the sixth embodiment is
High frequency differential from the high-frequency signal V _in the single-phase input signal V _'in,
It further comprises input means 6/7 for generating / V ' _in and supplying it to the polyphase filter means.

The analog type phase shifter of the sixth embodiment is
The input means 7 comprises an active balun 7.

The analog type phase shifter of the sixth embodiment is
The polyphase filter means 2 comprises the polyphase filter 2 in which resistors 21a to 21d and capacitors 22a to 22d are alternately arranged and are connected in a ring shape.

As described above, according to the sixth embodiment, the input differential signal is input to the polyphase filter 2,
The phase difference is 0 °, 90 °, 180 °, -90 °, and
Since the configuration is such that the equal amplitude can be divided into four, the effect of miniaturizing the analog type phase shifter can be obtained.

According to the sixth embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since it is composed of only ~ 22d, it is possible to obtain the effect of reducing the power consumption of the analog type phase shifter.

According to the sixth embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since 22d are connected in series in a ring shape, wiring and pads for grounding are not required, and the circuit wiring and arrangement of the analog type phase shifter can be simplified.

According to the sixth embodiment, the active balun 7 is provided in the preceding stage of the polyphase filter 2 so that the input single-phase high-frequency signal is supplied to the polyphase filter 2 as a high-frequency differential signal. An effect that a high frequency input signal that is not differential can be used is obtained.

According to the sixth embodiment, since the active balun 7 is provided with a gain, the effect of reducing the loss of the analog type phase shifter can be obtained.

According to the sixth embodiment, since the high frequency signal output from the polyphase filter 2 is amplified by using the variable gain amplifiers 10a to 10d, it is possible to reduce the loss of the analog type phase shifter. Is obtained.

Seventh Embodiment 9 is a block diagram showing an analog type phase shifter according to a seventh embodiment of the present invention. In FIG. 9, the same reference numerals as those in FIGS. 1 and 7 indicate the same or corresponding portions, and the description thereof will be omitted. 10'a high frequency signal A _'i, C' _i or radio frequency signal / A _'i,
It is a differential variable gain amplifier which receives / C ' _{i and} outputs high frequency signals _A'o , _C'o or high frequency signals / A' _o , / C ' _o . 10'b high-frequency signal B _'i, D' _i or radio frequency signals _{/ B 'i, / D'} i is the input frequency signal differential signal B _'o, D' _o or high-frequency signal /
The differential variable gain amplifier outputs _B'o and / D' _o . Reference numerals 101a and 101b are bias circuits having a temperature compensation function. In FIG. 9, the differential variable gain amplifier 1
Although 0'a and 10'b are used, the differential variable attenuators 8a and 8b shown in FIG. 7 may be used.

Next, the operation will be described. In the seventh embodiment, the differential variable attenuators 8a and 8b in the fifth embodiment shown in FIG.
It is replaced with 0'b and bias circuits 101a and 101b having a temperature compensation function are added. The operation of the polyphase filter 2 is the same as that of the first embodiment, and the operation of the differential 0-π phase modulators 9a and 9b is the same as that of the fifth embodiment, so the description thereof will be omitted.

[0122] Differential variable gain amplifier 10'a is inputted high-frequency signal A _'i, C' _i (or high-frequency signal / 'A
_i , / C ' _i ) amplitude is arbitrarily set and high frequency signal A'
_o , _C'o (or high frequency signals / A ' _o , / C' _o ) are generated and output. Differential variable gain amplifier 10'b is input high-frequency signal B _'i, D' _i (or high-frequency signals _{/ 'B i, / D'} i) high-frequency signal B _'o and amplitude arbitrarily set in, D' _o (or high frequency signal / B ' _o , / D'
_o ) is generated and output.

Bias circuit 101 having temperature compensation function
a and 101b are differential variable gain amplifiers 10'a and 1 ', respectively.
The temperature characteristic of 0'b is compensated to eliminate the gain change due to the temperature change.

The positive-phase output signal V _out and the negative-phase output signal _V'out are obtained in the same manner as in the fifth embodiment shown in FIG. 7, and the positive-phase output terminal 5a and the negative-phase output terminal 5a are obtained, respectively. It is output from the output terminal 5b.

The vector synthesis type analog phase shifter according to the seventh embodiment has the differential variable attenuators 8a and 8b according to the fifth embodiment as shown in FIG.
10'b is replaced with bias circuits 101a and 101b having a temperature compensation function. The differential variable attenuators 8a to 8d of the fourth embodiment shown in FIG. 6 are used as a differential variable gain amplifier. It may be replaced with a bias circuit having a temperature compensation function. The vector-synthesizing analog phase shifter of the seventh embodiment may be the variable gain amplifiers 10a to 10d of the sixth embodiment to which a bias circuit having a temperature compensation function is added. Furthermore, the vector synthesis type analog phase shifter of the seventh embodiment is the variable attenuator 4 of the first, second and third embodiments.
a to 4d are variable gain amplifiers 10a to 10 of the sixth embodiment.
Instead of d, a bias circuit having a temperature compensation function may be added.

As described above, in the analog type phase shifter of the seventh embodiment, the high frequency differential input signals V _in and / V _in have the phase differences of 0 °, 90 °, 180 ° and −90 °, and , A polyphase filter means 2 for distributing four high-frequency signals A _i , B _i , C _i , D _i of equal amplitude, and four high-frequency signals A _i , B _i , C _i , D _i are independently set in amplitude. And in-phase synthesizing output means 9a, 9b, 10'a, 10 '
b, 5a, 5b.

The analog type phase shifter of the seventh embodiment is
Output means 9a, 9b, 10'a, 10'b, 5a, 5b
But four high-frequency signals A _i, B _i, C _i, a high-frequency signal phase difference is 0 ° and 180 ° of the D _i A _i, C _i and the phase difference is -90 ° and 90 ° RF signal B _i , D _i , two differential 0-π phase modulators 9a and 9b for phase-modulating two high-frequency differential signals at 0 ° and 180 °.
And two pairs of phase-modulated high-frequency differential signals (A ′ _i ,
_C'i , and _B'i , D' _i or / _A'i , / C '
_i , and / B ' _i , / D' _i ) are set to have independent amplitudes, and a positive phase high frequency signal (A ' _o , B' _o or /
_A'o , / _B'o ) and a high frequency signal of opposite phase ( _C'o ,
D _'o or _{/ C' o, / D '} o) to generate two differential variable gain amplifier 10'a, 10'b and, amplitude set positive phase high frequency signal (A' _o, B _'o Or / A ' _o ,
/ B ' _o ) in-phase output terminal 5a for in-phase synthesis and anti-phase high-frequency signal (C' _o , D' _o or / C ' _o , / D' _o ) for in-phase synthesis in which the amplitude is set. Output terminal 5
and b.

The analog type phase shifter of the seventh embodiment is
Bias circuits 101a and 101 having a temperature compensation function
b, 101c, 101d are further included.

The analog type phase shifter of the seventh embodiment is
The polyphase filter means 2 comprises the polyphase filter 2 in which resistors 21a to 21d and capacitors 22a to 22d are alternately arranged and are connected in a ring shape.

As described above, according to the seventh embodiment, the input differential signal is supplied to the polyphase filter 2,
The phase difference is -90 °, 0 °, 90 °, 180 °, and
Since the configuration is such that the equal amplitude can be divided into four, the effect of miniaturizing the analog type phase shifter can be obtained.

According to the seventh embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since it is composed of only ~ 22d, it is possible to obtain the effect of reducing the power consumption of the analog type phase shifter.

According to the seventh embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since 22d are connected in series in a ring shape, wiring and pads for grounding are not required, and the circuit wiring and arrangement of the analog type phase shifter can be simplified.

According to the seventh embodiment, the phase difference output from the polyphase filter 2 is 0 °, 90 °, 180 °.
Four high-frequency signals with the same amplitude at
Since two differential 0-π phase modulators 9a and 9b are used to perform phase modulation at 0 ° or 180 °, respectively,
A high frequency differential output signal can be obtained from the output terminals 5a and 5b by using the two differential variable gain amplifiers 10'a and 10'b, and the interface (single phase) of the devices connected before and after the phase shifter can be obtained. And any of the differentials are different, the effect of matching with these devices can be obtained.

According to the seventh embodiment, the high frequency signal output from the polyphase filter 2 is amplified by using the differential variable gain amplifiers 10'a and 10'b. Therefore, the analog type phase shifter is used. It is possible to obtain the effect of reducing the loss.

According to the seventh embodiment, since the bias circuits 101a and 101b having the temperature compensating function are added, the effect that the temperature characteristic of the analog type phase shifter can be compensated can be obtained.

Eighth Embodiment 10 is a block diagram showing an analog type phase shifter according to Embodiment 8 of the present invention.
In FIG. 10, the same reference numerals as those in FIGS. 1 and 6 indicate the same or corresponding portions, and the description thereof will be omitted. Reference numeral 11 denotes a two-stage polyphase filter which receives the high-frequency signals V _in and / V _{in and} outputs four high-frequency signals A _i , B _i , C _i and D _i , and may be a polyphase filter having two or more stages. Reference numeral 10'a is a differential variable gain amplifier which receives the high frequency signals A _i and C _i (/ A _i ) and outputs the differential signals A _o and / A _o . 10'b is a high frequency signal C _i , A _i (/
It is a differential variable gain amplifier that receives C _i ) and outputs differential signals C _o and / C _o . 10'c is a high frequency signal B _i ,
The differential variable gain amplifier receives D _i (/ B _i ) and outputs differential signals B _o and / B _o . High-frequency signals D _i , B _i (/ D _i ) are input to 10 ′ d to obtain differential signals D _o , /
It is a differential variable degain amplifier that outputs D _o . 101
Reference numerals a, 101b, 101c and 101d are bias circuits having a temperature compensation function.

Next, the structure will be described. The two-stage polyphase filter 11 has a configuration in which the polyphase filter 2 shown in FIG. 2 is connected in two stages. That is, FIG.
Of the output terminals of the first-stage polyphase filter having the configuration of the polyphase filter 2 of FIG. 2 (the output terminals 3a and 3b in FIG. 2) that output a high-frequency signal of 0 ° phase and a high-frequency signal of 180 ° phase. 2) is connected to the positive-phase input terminal and the negative-phase input terminal (input terminal 1a and input terminal 1b in FIG. 2) of the second-stage polyphase filter, respectively. Two-stage polyphase filter 1
1 has the configuration of the polyphase filter 2 of FIG.
Phase 90 of the output terminals of the polyphase filter in the second stage
Output terminals for outputting a high-frequency signal of 90 degrees and a high-frequency signal of -90 degrees (the output terminal 3d and the output terminal 3 of FIG. 2).
It may have a configuration in which c) is connected to the positive-phase input terminal and the negative-phase input terminal (the input terminal 1a and the input terminal 1b in FIG. 2) of the second-stage polyphase filter, respectively.

Next, the operation will be described. The high frequency signals V _in and / V _in input from the differential input terminals 1a and 1b are
It is divided into four by the two-stage polyphase filter 11 and has no phase difference.
4 degrees of equal amplitude at °, 90 °, 180 °, -90 °
Two high frequency signals A _i , B _i , C _i and D _i are output terminals 3
It is output from a, 3d, 3b and 3c.

The differential variable gain amplifier 10'a sets the amplitudes of the input high frequency signals A _i and C _i (/ A _i ) to generate differential signals A _o and / A _o and outputs them. To do. The differential variable gain amplifier 10'b is configured to receive the input high frequency signal C _i ,
The amplitude of A _i (/ C _i ) is arbitrarily set and the differential signal C _o ,
/ C _o is generated and output. Differential variable gain amplifier 10 '
c sets the amplitudes of the input high frequency signals B _i and D _i (/ B _i ) arbitrarily and generates and outputs differential signals B _o and / B _o . The differential variable gain amplifier 10′d arbitrarily sets the amplitudes of the input high frequency signals D _i and B _i (/ D _i ) to generate and output differential signals D _o and / D _o .

Bias circuit 101 having temperature compensation function
The a, 101b, 101c and 101d function to compensate the temperature characteristics of the differential variable gain amplifiers 10'a, 10'b, 10'c and 10'd, respectively, so as to eliminate the gain change due to the temperature change.

Of the differential signals output by the differential variable gain amplifiers 10'a to 10'd, the positive phase high frequency signals A _o , B _o , C _o and D _o are in-phase combined and the positive phase output terminal. Obtain the output signal V _out from 5a. Differential variable gain amplifier of a reverse phase of the output differential signals by 10'a~10'd frequency signal _{/ A o, / B o,} / C o, / D o is the reverse phase are phase synthesized output Output signal from terminal 5b / V
get _out

The positive phase output signal V _out is generated in the same manner as the description given for the first embodiment with reference to FIG. 3, and the negative phase output signal / V _out is the same as the positive phase output signal V _out. Will be generated.

The analog type phase shifter of the eighth embodiment is
As shown in FIG. 10, the polyphase filter 2 and the differential variable attenuators 8a to 8d of the fourth embodiment are replaced by a two-stage polyphase filter 11 and a differential variable gain amplifier 10 '.
The bias circuits 101a to 101d having a temperature compensation function are added instead of a to 10'd, and the polyphase filter 2 of Embodiments 1 to 7 is replaced by two.
It may be replaced with the multi-stage polyphase filter 11. Further, in the eighth embodiment, the two-stage polyphase filter 11 shown in FIG. 10 may be replaced with the polyphase filter 2.

As described above, in the analog type phase shifter of the eighth embodiment, the high frequency differential input signals V _in and / V _in have the phase difference of 0 °, 90 °, 180 °, -90 °, and , Polyphase filter means 11 for distributing four high-frequency signals A _i , B _i , C _i , and D _i of equal amplitude, and four high-frequency signals A
Output means 4a to 4d, 5 / 10a to 10d for performing in-phase synthesis by setting amplitudes of _i , B _i , C _i , and D _i independently of each other.
5 / 8a to 8d, 5a, 5b / 10'a to 10'd, 5
a, 5b / 9a, 9b, 8a, 8b, 5a, 5b / 9
a, 9b, 10'a, 10'b, 5a, 5b.

The analog type phase shifter of the eighth embodiment is
Output means 4 a to 4 d, 5 are four high-frequency signals A _i, B
_From the four variable attenuators 4a to 4d for independently setting the amplitudes of _i , C _i , and D _i, and the output terminal 5 for in-phase combining the high-frequency signals A _o , B _o , C _o , and D _o with the set amplitude. It will be.

The analog type phase shifter of the eighth embodiment is
Output means 10 a to 10 d, 5 are four high-frequency signals _{A i, B i, C i} , and four variable gain amplifier 10 a to 10 d for amplitude setting independently the D _i, amplitude setting high frequency signal A _o, B _o, in which C _o, and an output terminal 5 for phase combining a D _o.

The analog type phase shifter of the eighth embodiment is
The output means 8a to 8d, 5a, 5b independently set the amplitudes of the four high frequency signals A _i , B _i , C _i , D _i , respectively, and positive phase high frequency signals A _o , B _o , C _o , D _o. And four differential variable attenuators 8a to 8d for generating high-frequency signals / A _o , / B _o , / C _o , / D _o of opposite phase, and high-frequency signals A _o and B _{o of} positive phase whose amplitude is set. , C _o, D _o the positive phase output terminals 5a and amplitude set reversed phase phase combining high-frequency signal _{/ a o, / B o,} / C o, of the reverse-phase in-phase synthesizing / D _o output terminal 5b and.

The analog type phase shifter of the eighth embodiment is
Output means 10'a~10'd, 5a, 5b are four high-frequency signals _{A i, B i, C i} , a high-frequency signal of positive phase and amplitude independently set the _{D i A o, B o,} C _o, D _o and reverse phase high-frequency signal _{/ a o, / B o,} / C o, / D o 4 one differential variable gain amplifier 10'a~10'd for generating
And the positive-phase high-frequency signals A _o , B _o with amplitude set,
A positive phase output terminal 5a for in-phase combining C _o and D _o and a high frequency signal / A _o , / B _o , / of the opposite phase whose amplitude is set.
And an output terminal 5b of the opposite phase for in-phase combining C _o and / D _o .

The analog type phase shifter of the eighth embodiment is
Four output means 9a, 9b, 8a, 8b, 5a, 5b
High frequency signal A_i, B_i, C_i, D_iPhase difference of 0
° and 180 ° high frequency signal A_i, C_iAnd the phase difference is −
90 ° and 90 ° high frequency signals B_i, D_iConsists of
Phase modulation of two high frequency differential signals at 0 ° and 180 °
Two differential 0-π phase modulators 9a, 9b
Two sets of modulated high frequency differential signals (A '_i, C '_i, And
B '_i, D ’_iOr / A '_i, / C '_i,and/
B ’_i, / D '_i), The amplitude is set independently for each phase
High frequency signal (A '_o , B ’_o Or / A '_o , / B '
_o ) And a high-frequency signal (C ′) of opposite phase_o , D ’_o Or /
C ’_o , / D '_o ) Generating two differential variable attenuators 8
a, 8b and a high-frequency signal (A ′) of a positive phase whose amplitude is set.
_o , B ’_o Or / A '_o , / B ' _o ) In-phase synthesis
Positive phase output terminal 5a and opposite phase high frequency with amplitude set
Signal (C '_o , D ’_o Or / C '_o , / D '_o ) Same
It is composed of an output terminal 5b of opposite phase for phase combination.

The analog type phase shifter of the eighth embodiment is
Output means 9a, 9b, 10'a, 10'b, 5a, 5b
But four high-frequency signals A _i, B _i, C _i, a high-frequency signal phase difference is 0 ° and 180 ° of the D _i A _i, C _i and the phase difference is -90 ° and 90 ° RF signal B _i , D _i , two differential 0-π phase modulators 9a and 9b for phase-modulating two high-frequency differential signals at 0 ° and 180 °.
And two pairs of phase-modulated high-frequency differential signals (A ′ _i ,
_C'i , and _B'i , D' _i or / _A'i , / C '
_i , and / B ' _i , / D' _i ) are set to have independent amplitudes, and a positive phase high frequency signal (A ' _o , B' _o or /
_A'o , / _B'o ) and a high frequency signal of opposite phase ( _C'o ,
D _'o or _{/ C' o, / D '} o) to generate two differential variable gain amplifier 10'a, 10'b and, amplitude set positive phase high frequency signal (A' _o, B _'o Or / A ' _o ,
/ B ' _o ) in-phase output terminal 5a for in-phase synthesis and anti-phase high-frequency signal (C' _o , D' _o or / C ' _o , / D' _o ) for in-phase synthesis in which the amplitude is set. Output terminal 5
and b.

The analog type phase shifter of the eighth embodiment is
Bias circuits 101a and 101 having a temperature compensation function
b, 101c, 101d are further included.

The analog type phase shifter of the eighth embodiment is
High frequency differential from the high-frequency signal V _in the single-phase input signal V _'in,
It further comprises input means 6/7 for generating / V ' _in and supplying it to the polyphase filter means.

The analog type phase shifter of the eighth embodiment is
The input means 6 comprises a 180 ° distributor 6.

The analog type phase shifter of the eighth embodiment is
The input means 7 comprises an active balun 7.

The analog type phase shifter of the eighth embodiment is
The polyphase filter means 2 comprises the polyphase filter 2 in which resistors 21a to 21d and capacitors 22a to 22d are alternately arranged and are connected in a ring shape.

The analog type phase shifter of the eighth embodiment is
The polyphase filter means 11 is composed of a polyphase filter 2 in which resistors and capacitors are alternately arranged and are connected in a ring, and two stages are connected.

As described above, according to the eighth embodiment, the input differential signal is input to the two-stage polyphase filter 1.
1, the phase difference is 0 °, 90 °, 180 °, -90 °,
Moreover, since it is configured such that it can be divided into four equal amplitudes, the effect of miniaturizing the analog type phase shifter can be obtained.

According to the eighth embodiment, since the two-stage polyphase filter 11 is composed of only the resistors 21a to 21d and the capacitors 22a to 22d, it is possible to reduce the power consumption of the analog type phase shifter. can get.

According to the eighth embodiment, the two-stage polyphase filter 11 includes the resistors 21a to 21d and the capacitor 2.
Since 2a to 22d are connected in series in a ring shape, wiring for grounding and a pad are not required, and an effect that circuit wiring and arrangement of the analog type phase shifter can be simplified can be obtained.

According to the eighth embodiment, the phase difference output from the two-stage polyphase filter 11 is 0 °, 90 °,
Four high frequency signals of 180 ° and −90 ° and equal amplitude are supplied to four differential variable gain amplifiers 10′a, 10′b, 1
Since the amplitudes are independently and arbitrarily set at 0'c and 10'd and in-phase synthesis is performed, a high frequency differential output signal can be obtained from the output terminals 5a and 5b, and they are connected before and after the phase shifter. Even if the interfaces of the devices (single-phase or differential) are different, the effect of matching with these devices can be obtained.

According to the eighth embodiment, the high frequency signal output from the two-stage polyphase filter 11 is amplified by using the differential variable gain amplifiers 10'a, 10'b, 10'c and 10'd. As a result, the effect of reducing the loss of the analog type phase shifter can be obtained.

According to the eighth embodiment, the bias circuits 101a, 101b, 101c having the temperature compensation function,
Since 101d is added, the effect of compensating the temperature characteristic of the analog type phase shifter can be obtained.

According to the eighth embodiment, since the polyphase filter is multi-staged and the two-stage polyphase filter 11 is used, a wide band characteristic can be obtained and the analog phase shifter can be widened. can get.

Ninth Embodiment 11 is a block diagram showing an analog type phase shifter according to a ninth embodiment of the present invention.
11, the same reference numerals as those in FIGS. 1, 7 and 9 indicate the same or corresponding portions, and thus the description thereof will be omitted.
In FIG. 11, the differential variable gain amplifiers 10′a and 10 ′ are shown.
b and a bias circuit 101a having a temperature compensation function,
Although 101b is used, instead of them, only the differential variable gain amplifiers 10'a and 10'b may be used, or the differential variable attenuators 8a and 8b may be used.

Next, the operation will be described. RF signal V _in input from the differential input terminal 1a is supplied to the input terminal of the negative phase of the differential variable gain amplifier 10'a positive phase input terminal and a differential variable gain amplifier 10'b, differential input Terminal 1
The high frequency signal / V _in input from b is supplied to the negative phase input terminal of the differential variable gain amplifier 10'a and the positive phase input terminal of the differential variable gain amplifier 10'b.

The differential variable gain amplifier 10'a arbitrarily sets the amplitudes of the input high frequency signals V _in and / V _in to generate and output the high frequency signals A _i and / A _i . The differential variable gain amplifier 10'b receives the input high frequency signals / V _in , V _in.
Of the high frequency signals B _i and / B _i are generated and output.

Bias circuit 101 having temperature compensation function
a and 101b are differential variable gain amplifiers 10'a and 1 ', respectively.
The temperature characteristic of 0'b is compensated to eliminate the gain change due to the temperature change.

Differential 0-π phase modulator 9a performs 0 phase modulation and π phase modulation in accordance with a control signal (not shown). That is, in the case of performing 0 phase modulation, the phases of the input high frequency signals A _i and / A _i are maintained and the high frequency signals A ′ _i and / A ′ _i are generated and output. When performing π phase modulation, the input high frequency signal A _i ,
High-frequency signal / A ' _i by shifting the phase of / A _i by 180 °,
_A'i is generated and output. Differential 0-π phase modulator 9b
Similarly to the differential 0-π phase modulator, 0 phase modulation or π phase modulation is performed on the input high frequency signals B _i and / B _i to generate high frequency signals B ′ _i and / B ′ _i or high frequency signals. The signals / B ′ _i and B ′ _i are generated and output.

High frequency signal A '_i, / A '_i, B ’_i, /
B ’_i(Or high frequency signal / A '_i, A ’_i, /
B ’_i, B ’_i) Is the output end of the polyphase filter 2
It is input to the children 3a, 3b, 3c, 3d. Form of this implementation
In state 9, the output end of the polyphase filter 2 shown in FIG.
Input using the children 3a, 3b, 3c, 3d as input terminals
Terminals 1a and 1b are used as output terminals 5a and 5b
It Input high frequency signal A ' _i, / A '_i, B ’_i，
/ B '_i(Or high frequency signal / A '_i, A ’_i, / B '
_i, B ’_i) Is synthesized by the polyphase filter 2,
Output signal V from output terminals 5a and 5b_out , / V_out (Ma
Or output signal / V_out , V_out ) Get.

In the ninth embodiment, the polyphase filter 2 is used as shown in FIG. 11, but a multistage polyphase filter may be used.

As described above, the analog of the ninth embodiment is obtained.
High-speed differential input signal V_in, / V_inShake
4 high-frequency signals (A_i, / A_i, B_i，
/ B _iOr / A_i, A_i, / B_i, B_i) Is generated
Input means 10'a, 10'b, 9a, 9b / 8a, 8
b, 9a, 9b and four high frequency signals (A_i, / A_i，
B_i, / B_iOr / A_i, A_i, / B_i, B_i) Same
With polyphase means 2/11 for phase synthesis
is there.

The analog type phase shifter of the ninth embodiment is
The input means 10'a, 10'b, 9a, 9b have two sets of high-frequency signals (V _in , V _in , / V _in) , which are high-frequency differential input signals.
_in , / V _in and / V _in , V _in ) are independently set to generate positive phase high frequency differential signals A _i and / A _i and negative phase high frequency differential signals B _i and / B _i . The two differential variable gain amplifiers 10a and 10b, which are set to 0, and the high-frequency differential signals A _i and / A _{i of} positive phase and the high-frequency differential signals B _i and / B _i of negative phase are set to 0
It is composed of two differential 0-π phase modulators 9a and 9b which perform phase modulation at 90 ° and 180 °.

The analog type phase shifter of the ninth embodiment is
The input means 8a, 8b, 9a, 9b are two sets of high frequency signals (V _in , / V _{in) which} are high frequency differential input signals V _in , / V _in.
in and / V _in , V _in ) are independently set in amplitude to generate a positive phase high frequency differential signal A _i , / A _i and a negative phase high frequency differential signal B _i , / B _i. Dynamic variable attenuator 8
a and 8b, two differential 0-π phases for phase-modulating the positive-phase high-frequency differential signals A _i and / A _i and the negative-phase high-frequency differential signals B _i and / B _i at 0 ° and 180 ° It is composed of modulators 9a and 9b.

The analog type phase shifter of the ninth embodiment is
Bias circuits 101a and 101b having a temperature compensation function
Is further included.

The analog type phase shifter of the ninth embodiment is
The polyphase filter means 2 comprises the polyphase filter 2 in which resistors 21a to 21d and capacitors 22a to 22d are alternately arranged and are connected in a ring shape.

The analog type phase shifter of the ninth embodiment is
The polyphase filter means 11 includes resistors 21a to 21d.
And the capacitors 22a to 22d are alternately arranged and are composed of the polyphase filter 2 which is connected in a loop and is connected in two stages.

As described above, according to the ninth embodiment, since the polyphase filter 2 is used to synthesize four high-frequency signals in-phase, the analog phase shifter can be miniaturized. .

According to the ninth embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since it is composed of only ~ 22d, it is possible to obtain the effect of reducing the power consumption of the analog type phase shifter.

According to the ninth embodiment, the polyphase filter 2 includes resistors 21a to 21d and a capacitor 22a.
Since 22d are connected in series in a ring shape, wiring and pads for grounding are not required, and the circuit wiring and arrangement of the analog type phase shifter can be simplified.

According to the ninth embodiment, since the input high frequency signal is amplified by using the differential variable gain amplifiers 10'a and 10'b, the loss of the analog type phase shifter can be reduced. The effect is obtained.

According to the ninth embodiment, since the bias circuits 101a and 101b having the temperature compensating function are added, it is possible to obtain the effect of compensating the temperature characteristic of the analog type phase shifter.

According to the ninth embodiment, since the polyphase filter is multi-staged and the two-stage polyphase filter 11 is used, wide band characteristics can be obtained and the analog phase shifter can be widened in band. can get.

[0183]

As described above, according to the present invention, the input differential signal is processed by the polyphase filter so that the phase difference is zero.
At 90 °, 90 °, 180 °, -90 °, and with equal amplitude 4
Since it is configured to be distributed, there is an effect that the analog type phase shifter can be downsized.

According to the present invention, the active balun is provided in the preceding stage of the polyphase filter to supply the input single-phase high-frequency signal to the polyphase filter as a high-frequency differential signal. There is an effect that a signal can be used, and since the active balun is provided with a gain, there is an effect that the analog type phase shifter can have a low loss.

According to the present invention, the phase difference output from the polyphase filter is 0 °, 90 °, 180 °, -90.
Since four high-frequency signals of the same amplitude and the same amplitude are independently and arbitrarily set by the four differential variable attenuators to perform in-phase synthesis, a high-frequency differential output signal can be obtained from the output terminal. Even if the interfaces of the devices connected before and after the phase shifter (either single-phase or differential) are different, matching with these devices can be achieved.

According to the present invention, the phase difference output from the polyphase filter is 0 °, 90 °, 180 °, -90.
Since four high-frequency signals of the same amplitude and the same amplitude are independently and arbitrarily set by the four differential variable gain amplifiers to perform in-phase synthesis, a high-frequency differential output signal can be obtained from the output terminal. There is an effect that can be obtained, and since the four high frequency signals are amplified by using the differential variable gain amplifier, there is an effect that the loss of the analog type phase shifter can be reduced.

According to the present invention, the phase difference output from the polyphase filter is 0 °, 90 °, 180 °, -90.
4 high frequency signals of equal amplitude at 0 ° or 180 ° by two differential 0-π phase modulators, respectively.
Since it is designed to perform phase modulation, it is possible to obtain a high-frequency differential output signal from the output terminals by using two variable attenuators, and to interface the devices (single phase and differential) connected before and after the phase shifter. If any) is different, the effect of matching with these devices can be obtained.

According to the present invention, the phase difference output from the polyphase filter is 0 °, 90 °, 180 °, -90.
4 high frequency signals of equal amplitude at 0 ° or 180 ° by two differential 0-π phase modulators, respectively.
Since the phase modulation is performed in two, there is an effect that a high frequency differential output signal can be obtained from the output terminal by using two variable gain amplifiers, and the high frequency signal output from the polyphase filter is obtained. Since the amplification is performed by using, there is an effect that the loss of the analog type phase shifter can be reduced.

According to the present invention, since the bias circuit having the temperature compensating function is added, the temperature characteristic of the analog type phase shifter can be compensated.

According to the present invention, the input means is provided before the polyphase filter so that the input single-phase high-frequency signal is supplied to the polyphase filter as a high-frequency differential signal. There is an effect that a signal can be used.

According to the present invention, since the active balun is given a gain, there is an effect that the analog type phase shifter can have a low loss.

According to the present invention, since the polyphase filter is composed only of resistors and capacitors, there is an effect that the power consumption of the analog type phase shifter can be reduced, and the polyphase filter has an annular resistor and capacitor. Since it is connected in series, the ground wiring and pad are not required, and the circuit wiring and arrangement of the analog type phase shifter can be simplified.

According to the present invention, since the polyphase filter is multistage and the two-stage polyphase filter is used, wide band characteristics can be obtained and the analog type phase shifter can have a wide band.

According to the present invention, since the four high-frequency signals are combined in phase by using the polyphase filter, the analog type phase shifter can be miniaturized.

According to the present invention, since the input high frequency signal is amplified by using the differential variable gain amplifier, there is an effect that the loss of the analog type phase shifter can be reduced.

[Brief description of drawings]

FIG. 1 is a configuration diagram showing an analog type phase shifter according to a first embodiment of the present invention.

FIG. 2 is a diagram showing a configuration example of a polyphase filter shown in FIG.

FIG. 3 is a diagram illustrating an operation in the circuit configuration of FIG.

FIG. 4 is a configuration diagram showing an analog type phase shifter according to a second embodiment of the present invention.

FIG. 5 is a configuration diagram showing an analog type phase shifter according to a third embodiment of the present invention.

FIG. 6 is a configuration diagram showing an analog type phase shifter according to a fourth embodiment of the present invention.

FIG. 7 is a configuration diagram showing an analog type phase shifter according to a fifth embodiment of the present invention.

FIG. 8 is a configuration diagram showing an analog type phase shifter according to a sixth embodiment of the present invention.

FIG. 9 is a configuration diagram showing an analog type phase shifter according to a seventh embodiment of the present invention.

FIG. 10 is a configuration diagram showing an analog type phase shifter according to an eighth embodiment of the present invention.

FIG. 11 is a configuration diagram showing an analog type phase shifter according to a ninth embodiment of the present invention.

FIG. 12 is a configuration diagram showing a conventional analog type phase shifter.

FIG. 13 is a diagram showing a high-frequency signal as a vector.

[Explanation of symbols]

1a, 1b input terminal, 2 polyphase filter, 3
a to 3d polyphase filter output terminals, 4a to 4d
Variable attenuator, 5, 5a, 5b output terminal, 6180 °
Distributor, 7 active baluns, 8a-8d differential variable attenuator, 9a, 9b differential 0-π phase modulator, 10a-
10d variable gain amplifier, 10'a to 10'd differential variable gain amplifier, 11 two-stage polyphase filter, 12
RC filter, 13a, 13b Differential amplifier, 21a
-21d resistance, 22a-22d capacitor, 61
Input terminal of 180 ° distributor, input terminal of 71 active balun, 101a to 101d bias circuit having temperature compensation function, 121a to 121d resistor, 122a to
122d capacitor.

   ─────────────────────────────────────────────────── ─── Continued front page    (72) Inventor Akira Funakoshi             2-3 2-3 Marunouchi, Chiyoda-ku, Tokyo             Inside Ryo Electric Co., Ltd.

Claims (19)

[Claims] 1. A high-frequency differential input signal having a phase difference of 0 °, 90
It has a polyphase filter means for distributing into four high frequency signals of 180 °, 180 °, -90 ° and equal amplitude, and an output means for independently setting the amplitudes of the four high frequency signals and performing in-phase synthesis. An analog type phase shifter. 2. The output means comprises four variable attenuators for independently setting the amplitudes of the four high frequency signals, and an output terminal for in-phase combining the high frequency signals for which the amplitudes have been set. 1. The analog type phase shifter described in 1. 3. The output means comprises four variable gain amplifiers for independently setting the amplitudes of the four high frequency signals, and an output terminal for in-phase combining the high frequency signals for which the amplitudes have been set. 1. The analog type phase shifter described in 1. 4. The output means includes four differential variable attenuators for independently setting the amplitudes of the four high-frequency signals to generate a positive-phase high-frequency signal and a negative-phase high-frequency signal, and the amplitude-adjusted positive differential attenuator. 2. The analog phase shifter according to claim 1, comprising a positive-phase output terminal for in-phase combining high-frequency signals of the same phase and an opposite-phase output terminal for in-phase combining of the high-frequency signals of the opposite phase whose amplitude is set. vessel. 5. The output means includes four differential variable gain amplifiers for independently setting the amplitudes of the four high frequency signals to generate a positive phase high frequency signal and a negative phase high frequency signal, and the amplitude set positive differential gain amplifier. 2. The analog phase shifter according to claim 1, comprising a positive-phase output terminal for in-phase combining high-frequency signals of the same phase and an opposite-phase output terminal for in-phase combining of the high-frequency signals of the opposite phase whose amplitude is set. vessel. 6. The output means outputs two sets of high frequency differential signals composed of high frequency signals having a phase difference of 0 ° and 180 ° and high frequency signals having a phase difference of −90 ° and 90 ° among the four high frequency signals. 0 ° and 180
Two differential 0-π phase modulators that perform phase modulation at °, and the amplitudes of the above two sets of high-frequency differential signals that have been phase-modulated are independently set to generate a positive-phase high-frequency signal and a negative-phase high-frequency signal. Two differential variable attenuators, a positive-phase output terminal for in-phase synthesizing the positive-phase high-frequency signal whose amplitude is set, and a negative-phase output terminal for in-phase synthesizing the opposite-phase high-frequency signal whose amplitude is set. The analog type phase shifter according to claim 1, wherein the analog type phase shifter comprises: 7. The output means outputs two sets of high frequency differential signals composed of high frequency signals having a phase difference of 0 ° and 180 ° and high frequency signals having a phase difference of −90 ° and 90 ° among the four high frequency signals. 0 ° and 180
Two differential 0-π phase modulators that perform phase modulation at °, and the amplitudes of the above two sets of high-frequency differential signals that have been phase-modulated are independently set to generate a positive-phase high-frequency signal and a negative-phase high-frequency signal. Two differential variable gain amplifiers, a positive phase output terminal for in-phase synthesizing the amplitude-set positive phase high frequency signal, and an opposite phase output terminal for in-phase synthesizing the amplitude set negative phase high frequency signal. The analog type phase shifter according to claim 1, wherein the analog type phase shifter comprises: 8. The analog type phase shifter according to claim 3, further comprising a bias circuit having a temperature compensation function. 9. The method according to claim 1, further comprising input means for generating a high frequency differential input signal from a single phase high frequency signal and supplying the high frequency differential input signal to the polyphase filter means. An analog type phase shifter described in paragraph. 10. The analog type phase shifter according to claim 9, wherein the input means comprises a 180 ° distributor. 11. The analog type phase shifter according to claim 9, wherein the input means comprises an active balun. 12. The polyphase filter means comprises a polyphase filter in which resistors and capacitors are alternately arranged and are connected in a ring shape, according to any one of claims 1 to 11. Analog type phase shifter. 13. The polyphase filter means comprises a polyphase filter in which resistors and capacitors are alternately arranged and which are connected in an annular shape and which are connected in two stages. An analog type phase shifter described in any one of 1. 14. An analog phase shifter comprising: an input means for generating four high frequency signals whose amplitudes are set from a high frequency differential input signal; and a polyphase means for in-phase combining the four high frequency signals. vessel. 15. The two differences in which the input means independently sets the amplitudes of two sets of high frequency signals composed of high frequency differential input signals to generate a positive phase high frequency differential signal and a negative phase high frequency differential signal. Dynamic variable gain amplifier, and two differential 0-π for phase-modulating the positive phase high frequency differential signal and the negative phase high frequency differential signal at 0 ° and 180 °.
15. The analog type phase shifter according to claim 14, comprising a phase modulator. 16. A difference between two sets in which the input means independently sets the amplitudes of two sets of high-frequency signals composed of high-frequency differential input signals to generate a positive-phase high-frequency differential signal and a negative-phase high-frequency differential signal. Dynamic variable attenuator, and two differential 0-π for phase-modulating the positive phase high frequency differential signal and the negative phase high frequency differential signal at 0 ° and 180 °.
15. The analog type phase shifter according to claim 14, comprising a phase modulator. 17. The analog type phase shifter according to claim 15, further comprising a bias circuit having a temperature compensation function. 18. The polyphase filter means comprises a polyphase filter in which a resistor and a capacitor are alternately arranged and are connected in a ring shape, according to any one of claims 14 to 17. Analog type phase shifter. 19. The polyphase filter means is formed by connecting two stages of polyphase filters in which resistors and capacitors are alternately arranged and are connected in a ring shape. An analog type phase shifter described in any one of 1.