JP2003115783A - Method for estimating transmission path characteristic of reception signal and cdma receiver - Google Patents

Abstract

PROBLEM TO BE SOLVED: To improve the precision of reception processing using a pilot symbol without increasing the rate of the number of pilot symbols, or increasing the transmission power of the pilot symbol, or using any temporary judgement data. SOLUTION: A TFCI included in a control channel is decoded (including error correction) by a decoding part 108, and re-encoded by a re-encoding data generating part 112, and the re-encoded data are used as already known bits in the same way as pilot symbols, and the transmission path characteristics of the next frame are estimated by transmission path characteristic estimating parts 103-1-103-N, and synchronism detection is operated.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a method of estimating propagation path characteristics of a received signal and a CDMA receiver.

[0002]

2. Description of the Related Art In mobile communication, fluctuations in channel characteristics due to fading occur as communication terminals move in an environment where multipaths are formed. When receiving and demodulating data symbols in such a situation, pilot symbols transmitted together with the data symbols are received and demodulated, the channel characteristics are estimated using this pilot symbol, and the data symbol is estimated by the estimated value of the channel characteristics. Synchronous detection techniques that compensate for phase fluctuations and amplitude fluctuations due to fading are widely used.

At this time, if the estimation of the transmission path (propagation path) characteristics is not accurate, the reliability of the demodulated signal is rather lowered.

In order to improve the accuracy of propagation path characteristics,
Increasing the transmission power of the pilot channel or increasing the number of pilot symbols to be averaged is effective, but in the former case, there is a problem that interference with the data channel increases, and in the latter case However, there is a problem that the estimation accuracy is rather lowered in a situation where the fluctuation of the propagation path characteristics is large due to fading, and both measures have limitations.

Therefore, in recent years, a method has been proposed in which information data is tentatively determined and the tentative determination data is used as known data in the same manner as pilot symbols to be used for estimating channel characteristics (Japanese Patent Laid-Open No. Hei 10 (1999) -135242). 11-355
849, JP 2001-53644, etc.).

In the method of using the temporary decision data symbol as the known bit, the received signal is delayed by a delay circuit,
Alternatively, while accumulating in the memory, synchronous detection is performed on the information data included in the received signal to obtain provisional determination data, and the provisional determination data is used as a known symbol similar to the pilot signal to perform synchronous detection, etc. I do.

As the name implies, the provisional determination data is provisional decoded data that is not regular decoded data, that is, decoded data that has not undergone error correction processing. If error correction processing is performed, the accuracy of the decoded data is improved, but since the time required for that processing is long, there is no room for error correction for real-time reception processing, and temporary judgment data is used. Is.

[0008]

In the method using the provisional decision data, the estimation accuracy of the channel characteristic is deteriorated when the provisional decision data has an error. That is, when the error rate of the provisional determination is large, the use of the provisional determination data rather deteriorates the estimation accuracy of the channel characteristics, so that stable reliability may not be expected.

The present invention has been made in view of such a problem, and an object thereof is to increase the ratio of the number of pilot symbols, to increase the transmission power of pilot symbols, and to further determine the provisional decision data. It is to provide a receiving device that can perform reception processing (estimation of channel characteristics, creation of delay profile, etc.) with high accuracy without using pilot symbols, and improve reception quality and measurement accuracy.

[0010]

According to the present invention, the control information is not officially determined, but attention is paid to control information in which redundant bits are added to ensure high decoding accuracy, and the control information is officially decoded. Then, the decoded signal is encoded again. Then, the re-encoded data is used as a known symbol like the pilot symbol.

Since the control information is described, for example, in units of blocks of a predetermined length in the transport channel, the contents of the control information in one block are the same. If one block has a size including a plurality of frames, it means that the control information is the same over a plurality of transmission frames.

In this case, when the control information contained in the first frame is officially decoded and re-encoded, the re-encoded data cannot be used for the receiving process for the first frame. , It is possible to use it for the reception processing of the next frame in terms of time.

Therefore, for the second and subsequent frames contained in one block, the receiving process is performed using the re-encoded data of the immediately preceding frame.

Since the control information plays an important role in performing accurate reception on the receiving side, redundant bits are added to increase the number of bits, or special encoding is performed, fading, etc. Resistance to. Therefore, the accuracy of the control information encoded through the error correction processing is high. Furthermore, the reliability is significantly higher than that of the provisional judgment data in which error correction is not performed.

Data that is normally decoded with a high degree of reliability and then encoded again is also highly reliable. By using this re-encoded data as a known bit in the reception process of the next frame, the accuracy is improved as compared with the reception process using only the pilot symbol.

Further, by utilizing the fact that the control information has the same contents over a plurality of frames, the re-encoded data obtained by performing the decoding / re-encoding in the immediately preceding frame is used in the next frame. It is possible to use an extremely rational method that is useful for reception processing, and unlike the method that uses temporary judgment data, there is no need to delay the original received signal or store it in memory, and it has an extremely efficient configuration. can do.

[0017]

BEST MODE FOR CARRYING OUT THE INVENTION First, W-based on the 3GPP specifications.
The configuration of the physical layer of the CDMA system will be described.

Data for each service such as voice, packet data and FAX is sent to the transport channel. The transport channel is a channel provided from the physical layer to the MAC sublayer, and generally, a plurality of types of transport channels are used to transmit data having different characteristics and transmission forms on the physical layer.

The data rates and error correction methods of these transport channels are usually different methods, multiplexed as needed, and then transmitted on one or more physical channels.

A combination of transport channels for high data rate services and low data rate services can also be multiplexed onto multiple physical channels, and this flexibility allows a large number of different data rates. Transport channels (services) can be efficiently assigned to physical channels.

Number of bits per block of a plurality of transmitted transport channels, transmission cycle of one block (TTI: Transmission Time Interval, TTI is a time length that is an integral multiple of a frame), number of CRC bits for error detection, error For transport format information such as correction method and rate match parameters, TFCI (transport format combination)
indicator) to the receiving side.

The TFCI is data in which transport format information represented by a maximum of 10 bits is encoded into 30 bits, and normally, 2 bits are transmitted to each slot for each frame. Here, since the transport format information is the same in the minimum TTI of a plurality of transport channels, the contents of the TFCI of each frame in the TTI are also the same.

In the present invention, focusing on this point, the minimum TTI
The TFCI included in is decoded and re-encoded, and is used as a known bit like a pilot symbol to estimate a propagation path (line).

FIG. 11A is a diagram showing a frame structure of an uplink physical channel (DPDCH, DPCCH).

Physical channel DPDCH (Dedicated Physical)
Data Channel) includes data after the information data of the transport channel has been subjected to channel codec such as error correction coding and rate matching.

On the other hand, the physical channel DPCCH (Dedicated Phy
sical Control Channel) has a pilot symbol, T
It includes control data such as FCI symbols, TPC symbols, and FBI symbols. Then, these are multiplexed and transmitted.

When the minimum 1 unit (minimum TTI) of the transmission cycle of the transport channel corresponds to 4 frames,
The TFCI data (normally 30 bits) of each frame of frame # 0 to frame # 3 is the same.

Therefore, as shown in FIGS. 11A and 11B, the second and subsequent frames (frame # 1 to frame # 3) within the minimum TTI are TFCI information 1 decoded in the immediately preceding frame.
The 0-bit is decoded, and the re-encoded TFCI re-encoded data is used as a known bit like the pilot symbol to perform a receiving process such as a channel characteristic estimating process. By this means, the same improvement effect as when the pilot symbols are increased by the amount of TFCI encoded data is obtained.

As shown at the bottom of FIG. 11 (a),
For frame # 0, within the period from time t1 to t3, TF
The CI is decoded and re-encoded, and the characteristic of the propagation path is estimated using the re-encoded data as a known bit in the period (time t3 to t5) of the next frame # 1. Hereinafter, similarly, by using the re-encoded data of TFCI of frames # 1 and # 2, for receiving the next frames # 2 and # 3,
Estimate the propagation path characteristics.

A concrete timing example of each processing is shown in FIG.
It shows in (b). When the TFCI decoding timing of each frame is t1, t3, t5, t7 ..., The re-encoded data (R0-R3 ...) Is delayed for a while and then recoded at times t2, t4, t.
6, reception processing of the next frame using the immediately preceding re-encoded data (estimation of channel characteristics / coherent detection)
I do.

Here, "re-encoded data" is data obtained by re-encoding the received encoded data, which has been decoded through error correction. The “coded data” referred to here is data in which redundant bits are added to information data according to a predetermined rule, like the control information TFCI.

In the TFCI, redundant bits are added to the information data represented by a maximum of 10 bits in accordance with a predetermined rule to make it 3
This is encoded data extended to 0 bits, and originally, if error correction is performed and decoding is performed on the receiving side, information data can be restored with high reliability.

Since re-encoded data of control information such as TFCI is re-encoded high-precision decoded data after error correction, provisional decision data (data without quality check before error correction) ), The reliability is much higher. Therefore, by using this re-encoded data as a known bit and using it for the receiving process of the next frame,
The accuracy is improved as compared with the reception processing using only pilot symbols.

As described above, the TFCI is described in units of blocks of a predetermined length in the transport channel, so that the contents of the control information in one block are the same. If one block has a size including a plurality of frames, it may be transmitted over a plurality of transmission frames.
The control information is the same.

When the TFCI included in the first frame is officially decoded and re-encoded, the re-encoded data cannot be used in the reception process for the first frame, but the next frame Can be sufficiently used in time. Paying attention to this point, the tentative decision data can be obtained by using a very rational method in which the re-encoded data obtained by performing the decoding / re-encoding in the immediately preceding frame is used for the receiving process of the next frame. Like the method used, delaying the original received signal,
Extremely efficient processing can be performed without the need to temporarily store in the memory.

In the case of the present invention, it is only necessary to add to the normal structure a structure for performing TFCI re-encoding processing, and a small structure can be added.

Here, the TFCI acquired by the simulation
BE of re-encoded data (data after error correction) and TFCI temporary judgment data (data before quality check by error correction)
R characteristic and BLE of transport channel information data
The R characteristic is shown in FIG.

In FIG. 12, the horizontal axis is Eb-N0 and the vertical axis is the error rate. Generally, BLER = 10 ^-2 of transport channel information data for which communication quality is considered good.
Comparing the BER characteristics of the TFCI re-encoded data and the TFCI tentative decision data in the vicinity, because of the coding gain, the TFCI re-encoded data has a BE of about 5 dB at Eb-N0 than the TFCI tentative decision data.
It can be seen that the R characteristics are good and the reliability is high.

Thus, the error rate is low and the reliability is high.
TFCI re-encoded data from the second frame onward within the minimum TTI,
By using it for reception processing as well as pilot symbols,
From the second frame onward within the minimum TTI, pilot symbols are
The same improvement effect as when increasing the TFCI encoded data is obtained.

Embodiments of the present invention will be described below with reference to the drawings.

(Embodiment 1) FIG.1 is a block diagram showing a configuration of a CDMA receiving apparatus according to Embodiment 1 of the present invention.

In the figure, the receiving apparatus 100 of the present embodiment has a synchronizing section 101 and despreading sections 102-1 to 102-1.
2-N, a synchronous detection unit 105- that includes propagation path estimation units 103-1 to 103-N and multiplication units 104-1 to 104-N.
1 to 105-N and the pilot pattern generation unit 106
And a rake combining unit 107, a decoding unit 108, a re-encoding unit 109, a re-encoded data output unit 110, and a re-encoded data generation unit 112 including a minimum TTI in-frame number measurement unit 111. Has been done.

The synchronization section 101 calculates the synchronization timing for despreading the received signal and outputs the synchronization timing to the despreading sections 102-1 to 102-N.

The despreading units 102-1 to 102-N output the correlation signal between the received signal and the spread code at each synchronization timing.

The propagation path estimation units 103-1 to 103-N are
It estimates the channel characteristics received in each path using pilot symbols and TFCI re-encoded data.

The multiplying units 104-1 to 104-N multiply the complex conjugate of the estimated value of the propagation path characteristic output from the propagation path estimating units 103-1 to 103-N, and the fading fluctuation received in each path. To output a correlation signal in which

The synchronous detection units 105-1 to 105-N include the propagation path estimation units 103-1 to 103-N and the multiplication unit 104-.
1 to 104-N, the estimated value of the propagation path characteristic is calculated from the correlation signal after despreading, and the correlation signal in which the fading fluctuation received in each path is compensated is output.

The pilot pattern generating section 106 has its bit pattern preliminarily decided between transmission and reception.
This is to generate a known pilot bit pattern.

The rake combiner 107 is for adding in-phase the correlation signals of the fingers after synchronous detection and combining them.

The decoding section 108 decodes the TFCI encoded data after Rake combining and outputs the TFCI decoded data, and comprises an error correction section 350. This decoding process is performed when TFCI encoded data for one frame is received (when TFCI of slot # 14 is received (see FIG. 11).
(See (a) and (b))), and is performed in a frame cycle.

The re-encoding unit 109 outputs the TFCI re-encoded data obtained by re-encoding the TFCI decoded data decoded by the decoding unit 108.
10 is to output the TFCI re-encoded data calculated in the previous frame by the re-encoded data output unit 110 to the channel estimation units 103-1 to 103-N in the second and subsequent frames within the minimum TTI. .

The minimum TTI frame number measuring unit 111 measures the current frame number when the first frame number in the minimum TTI is 0, and outputs it to the re-encoded data output unit 110. Here, the minimum TTI is a time period during which the transmitted TFCI data is the same.

The operation of such a configuration will be described. Despreading sections 102-1 to 102-N output the correlation signal between the received signal and the spreading code at the synchronization timing set by synchronization section 101. The synchronous detection units 105-1 to 105-N are
The propagation path characteristics are estimated and the fading fluctuation received in each path is compensated. Here, the propagation path estimation units 103-1 to 103
-N, using pilot symbols and TFCI re-encoded data output from re-encoded data generation section 112,
Estimate the channel characteristics.

The rake combiner 107 is a synchronous detector 105.
-1 to 105-N combine the correlation signals of the fingers after the synchronous detection.

As described above, the receiving apparatus 10 of the present embodiment
According to 0, in the frame where the TFCI data is the same as the previous frame, the TFCI calculated in the previous frame has high reliability.
The re-encoded data was used for the estimation processing of the channel characteristics as well as the pilot symbols. By this means, it is possible to increase the average number of symbols in the calculation of the propagation path characteristic estimation value, and to calculate a more accurate propagation path characteristic estimation value in which the influence of noise and interference is reduced.

An outline of the procedure for estimating the propagation path characteristic of the CDMA received signal is shown in FIG.

That is, decoding processing including error correction is performed on control information having the same contents over a plurality of frames and having redundant bits added to enable error correction (step 10). .

Next, the decoded data after error correction is encoded again (step 12). Then, the channel characteristic of the received signal is estimated using the re-encoded data as known bits (step 14).

The specific procedure is as shown in FIG.

That is, first, the uplink DPDCH
The transmission cycle (TTI: Transmission Time Interval) of one block of each transport channel multiplexed in (Dedicated Physical Data Channel) is n (n is 2).
DPCCH (Dedicated Physical Control Channel) of the received signal when the frame is equivalent to the above integer) frame
Included in TFCI (Transport Format Combination I
(ndicator) is decoded at intervals corresponding to one frame to obtain information data (step 20).

Next, the information data obtained by decoding is re-encoded to obtain re-encoded data (step 22).

Next, with respect to each of the second frame to the nth frame in the transmission cycle (TTI) of one block, the re-encoded data of the frame immediately before the frame is used as the known bit to estimate the propagation path characteristic. Is performed (step 24).

(Embodiment 2) FIG.2 is a block diagram showing a configuration of a CDMA receiving apparatus according to Embodiment 2 of the present invention. However, in the second embodiment shown in FIG. 2, parts corresponding to the respective parts of the first embodiment in FIG. 1 are designated by the same reference numerals, and description thereof will be omitted.

The receiving apparatus 200 shown in this figure is a despreading section 102 which is a component of the receiving apparatus 100 of the first embodiment.
-1 to 102-N and the pilot pattern generator 106
In addition to the Rake combining unit 107, the decoding unit 108, and the re-encoded data generation unit 112, the synchronization timing determination unit 2
01, a synchronization unit 2 including a delay profile calculation unit 202
03 and synchronous detection units 204-1 to 204-N.

The synchronization timing determining section 201 obtains the timing when the correlation value takes the maximum value from the delay profile and determines it as the synchronization timing. The delay profile calculation unit 202 calculates a delay profile which is a correlation power characteristic of each spread timing between the spread code and the received signal (pilot symbol, TFCI symbol).

The synchronization unit 203 is a synchronization timing determination unit 2
01 and delay profile calculation unit 202.

Synchronous detection sections 204-1 to 204-N calculate the estimated value of the propagation path characteristic from the despread correlation signal using pilot symbols, and obtain the correlation signal in which the fading fluctuation received by each path is compensated. It is what is output.

The operation of such a configuration will be described.

Delay profile calculating section 202 uses the pilot symbols and the TFCI re-encoded data output from re-encoded data generating section 112 to match the quadrants of the received signal and adds the plurality of symbols in phase to add noise. The delay profile is calculated by reducing the influence of interference.

The synchronization timing determination unit 201 obtains the timing when the correlation value of the delay profile output from the delay profile calculation unit 202 takes the maximum value, determines it as the synchronization timing, and despreads the units 102-1 to 102-1.
Output to 102-N. Despreading units 102-1 to 102-
N outputs the correlation signal between the received signal and the spread code at the synchronization timing output from the synchronization timing determination unit 201. The rake combiner 107 includes synchronous detectors 204-1 and 204-2.
The correlation signal of each finger after synchronous detection outputted from 04-N is synthesized.

As described above, the receiving device 20 of the present embodiment
According to 0, in the frame where the TFCI data is the same as the previous frame, the TFCI calculated in the previous frame has high reliability.
The re-encoded data was used for the delay profile calculation process in the same manner as the pilot symbol.

As a result, the average number of symbols can be increased in the calculation of the delay profile, and a more accurate delay profile in which the influence of noise and interference is reduced can be calculated.

(Embodiment 3) FIG.3 is a block diagram showing the configuration of a receiving apparatus according to Embodiment 3 of the present invention.
However, in the third embodiment shown in FIG. 3, parts corresponding to the respective parts of the second embodiment in FIG. 2 are denoted by the same reference numerals, and description thereof will be omitted.

The receiving apparatus 300 shown in this figure is a despreading section 102 which is a component of the receiving apparatus 200 of the second embodiment.
-1 to 102-N and the pilot pattern generator 106
, Rake combining section 107, decoding section 108, re-encoded data generation section 112, and synchronous detection sections 204-1 to 20-20.
In addition to 4-N, an early-late calculation unit 301 and a synchronization unit 303 including a synchronization timing determination unit 302 are provided.

Early-Late calculating section 301 outputs pilot symbols and TF output from re-encoded data generating section 112.
Using the CI re-encoded data, the power was calculated by averaging multiple symbols of the correlation signal between the early signal and the spread code.
The rly average correlation power and the late average correlation power obtained by averaging a plurality of symbols of the correlation signal between the late signal and the spread code to calculate the power are output, and the difference between them, the Early-Late correlation value difference, is output. Here, the EALRY signal is a signal obtained by delaying the phase of the received signal (pilot symbol, TFCI symbol) by 1/2 chip from the current synchronization timing,
The Late signal is a signal obtained by advancing the phase of the received signal (pilot symbol, TFCI symbol) by 1/2 chip from the current synchronization timing.

The synchronization timing determination unit 302 uses the Early-La
The Early-Late correlation value difference output from the te calculation unit 301 is compared with a preset threshold value, and the current synchronization timing is finely adjusted according to the comparison result.

That is, if the Early-Late correlation value difference exceeds the threshold value and is “positive”, the timing is delayed, and if the Early-Late correlation value difference exceeds the threshold value and is “negative”. Advance the timing. If the threshold value is not exceeded, the synchronization timing is unchanged.

The synchronizing section 303 is an Early-Late calculating section 301.
And the synchronization timing determination unit 302.

The operation of such a configuration will be described.

Early-Late calculation section 301 outputs pilot symbols and TF output from re-encoded data generation section 112.
Using the CI re-encoded data, the power was calculated by averaging multiple symbols of the correlation signal between the early signal and the spread code.
The rly average correlation power and the late average correlation power obtained by averaging a plurality of symbols of the correlation signal between the late signal and the spread code are calculated, and the difference between them is output as the Early-Late correlation value difference. By averaging using multiple symbols,
It reduces the effects of noise and interference.

The synchronization timing determination unit 302 uses the Early-La
The current synchronization timing is finely adjusted using the Early-Late correlation value difference output from the te calculating unit 301 and the preset threshold, and the synchronization timing after the fine adjustment is despreading unit 102-
1 to 102-N.

Despreading sections 102-1 to 102-N output the correlation signal between the received signal and the spreading code at the synchronization timing output from synchronization timing determining section 302.

The rake combiner 107 includes a synchronous detector 204
As described above, according to the receiving apparatus 300 of the present embodiment, in the frame in which the TFCI data is the same as the previous frame, the correlation signals of the fingers after the synchronous detection output from -1 to 204-N are combined. The TFCI re-encoded data with high reliability calculated in the previous frame was used for the calculation process of the Early-Late correlation value difference similarly to the pilot symbol.

With this, in the calculation of the early-LATE correlation value difference, the average number of symbols can be increased, and the more accurate early-late correlation value difference in which the influence of noise and interference is reduced can be calculated.

(Embodiment 4) FIG.4 is a block diagram showing a configuration of a receiving apparatus according to Embodiment 4 of the present invention.
However, in the fourth embodiment shown in FIG. 4, parts corresponding to the respective parts of the first to second embodiments shown in FIG. 1 are designated by the same reference numerals, and description thereof will be omitted.

The receiving apparatus 400 shown in this figure is a synchronization unit 101 which is a component of the receiving apparatus 100 of the first embodiment.
, Despreading sections 102-1 to 102-N, pilot pattern generating section 106, rake combining section 107, decoding section 108, re-encoded data generating section 112, and receiving apparatus 200 according to the second embodiment. Detection unit 20 which is a component of
In addition to 4-1 to 204-N, quadrant matching section 401-1 to
401-N and RSSI calculation part 402 are comprised.

The quadrant matching units 401-1 to 401-N are
The pilot pattern is used to match the quadrants of the received pilot symbols, and the TFCI re-encoded data output from the re-encoded data generation unit 112 is used to adjust the quadrants of the received TFCI symbols. Then, it outputs the received pilot symbol and the received TFCI symbol in the quadrant.

The RSSI calculation section 402 is a quadrant matching section 401.
The received pilot symbols and the received TFCI symbols in which the quadrants of the fingers output from -1 to 401-N are aligned are in-phase added over a plurality of symbols to obtain an averaged average symbol. The power of the average symbol of each finger is taken and combined to calculate RSSI (received power of desired wave).

The operation of such a configuration will be described.

Despreading sections 102-1 to 102-N output the correlation signal between the received signal and the spreading code at the synchronization timing output from synchronization section 101. Quadrant matching section 401-
1 to 401-N are for adjusting the quadrants of the received pilot symbols using the pilot pattern, and for adjusting the quadrants of the received TFCI symbols using the TFCI re-encoded data output from the re-encoded data generation unit 112. . Then, the received pilot symbol and the received TFCI in the quadrant are combined.
The symbol is output to RSSI calculation section 402.

RSSI calculation section 402 performs in-phase addition on the received pilot symbols and the received TFCI symbols in the same quadrant over a plurality of symbols, and outputs RSSI (desired wave received power) for which power has been obtained.

As described above, the receiving device 40 of the present embodiment
According to 0, in the frame where the TFCI data is the same as the previous frame, the TFCI calculated in the previous frame has high reliability.
The re-encoded data was used for the RSSI (desired wave received power) calculation process as well as the pilot symbols.

As a result, in the measurement of the desired wave reception power, the average number of symbols can be increased, and more accurate RSSI (desired wave reception power) in which the influence of noise and interference is reduced can be calculated.

(Embodiment 5) FIG.5 is a block diagram showing the configuration of a receiving apparatus according to Embodiment 5 of the present invention.
However, in the fifth embodiment shown in FIG. 5, parts corresponding to the respective parts of the fourth embodiment in FIG. 4 are designated by the same reference numerals, and description thereof will be omitted.

The receiving apparatus 500 shown in this figure is a synchronization unit 101 which is a component of the receiving apparatus 400 of the fourth embodiment.
, Despreading sections 102-1 to 102-N, pilot pattern generating section 106, rake combining section 107, decoding section 108, re-encoded data generating section 112, and coherent detection sections 204-1 to 204. -N and quadrant matching unit 401-1
.About.401-N and an ISSI calculation unit 502 in addition to the RSSI calculation unit 501.

The RSSI calculation unit 501 includes a quadrant matching unit 401.
-1 to 401-N, the received pilot symbols in which the quadrants of each finger are aligned and the received TFCI symbol are in-phase added over a plurality of symbols, and the average symbol is output.

ISSI calculation section 502 obtains an average deviation amount obtained by averaging the deviation amounts of the received pilot symbol and the received TFCI symbol over a plurality of symbols from the average symbol of each finger calculated by RSSI calculation section 501.

The ISSI (interference wave reception power) is calculated by obtaining the power of the average deviation amount of each finger and combining them.

The operation of such a configuration will be described.

Despreading sections 102-1 to 102-N output the correlation signal between the received signal and the spreading code at the synchronization timing output from synchronization section 101.

The quadrant matching units 401-1 to 401-N are
The pilot pattern is used to match the quadrants of the received pilot symbols, and the TFCI re-encoded data output from the re-encoded data generation unit 112 is used to adjust the quadrants of the received TFCI symbols. Then, it outputs the received pilot symbol and the received TFCI symbol in the quadrant to RSSI calculation section 501 and ISSI calculation section 502.

The ISSI calculator 502 averages the deviations of the received pilot symbols and the received TFCI symbols, which have the same quadrant of each finger, from the average symbol of each finger output from the RSSI calculator 501 over a plurality of symbols. Find the amount. ISSI (interference wave reception power) is calculated by calculating the average deviation power of each finger
To calculate.

As described above, the receiving device 50 of the present embodiment
According to 0, in the frame where the TFCI data is the same as the previous frame, the TFCI calculated in the previous frame has high reliability.
The re-encoded data was used for ISSI (interference wave received power) calculation processing as well as pilot symbols.

As a result, in the measurement of the interference wave reception power, the average number of symbols can be increased, and more accurate ISSI (interference wave reception power) in which the influence of noise and interference is reduced can be calculated.

(Embodiment 6) FIG.6 is a block diagram showing the configuration of a receiving apparatus according to Embodiment 6 of the present invention.
However, in the sixth embodiment shown in FIG. 6, parts corresponding to the respective parts of the fifth embodiment in FIG. 5 are designated by the same reference numerals, and description thereof will be omitted.

The receiving apparatus 600 shown in this figure is a synchronization unit 101 which is a component of the receiving apparatus 500 of the fifth embodiment.
, Despreading sections 102-1 to 102-N, pilot pattern generating section 106, rake combining section 107, decoding section 108, re-encoded data generating section 112, and coherent detection sections 204-1 to 204. -N and quadrant matching unit 401-1
˜401-N, an ISSI calculation unit 502, an RSSI calculation unit 601, and an SIR calculation unit 602.

The RSSI calculation unit 601 includes a quadrant matching unit 401.
-1 to 401-N, the received pilot symbols in which the quadrants of each finger are aligned and the received TFCI symbol are in-phase added over a plurality of symbols, and the average symbol is output. Further, the power of the average symbol of each finger is obtained, and the combined RSSI (received power of desired wave) is output.

The SIR calculating section 602 calculates the RSSI (desired wave received power) output from the RSSI calculating section 601 and the ISSI calculating section 5
SIR (reception power of desired wave to reception power of interference wave), which is a ratio with ISSI (interference wave reception power) output from 02, is calculated and output.

The operation of such a configuration will be described.

The RSSI calculation unit 601 has a quadrant matching unit 401.
The received pilot symbols and the received TFCI symbols in which the quadrants of the fingers output from -1 to 401-N are aligned are in-phase added over a plurality of symbols to obtain an averaged average symbol. The power of the average symbol of each finger is taken and combined to calculate RSSI (received power of desired wave).

The SIR calculating section 602 calculates the RSSI (desired wave received power) output from the RSSI calculating section 601 and the ISSI calculating section 5
SIR (reception power of desired wave to reception power of interference wave), which is a ratio with ISSI (interference wave reception power) output from 02, is calculated and output.

As described above, the receiving device 60 of the present embodiment
According to 0, in the frame where the TFCI data is the same as the previous frame, the TFCI calculated in the previous frame has high reliability.
The re-encoded data was used for the calculation process of SIR (reception power of desired wave to reception power of interference wave) similarly to the pilot symbol.

As a result, in the measurement of the desired wave reception power to the interference wave reception power ratio, it is possible to increase the average number of symbols and reduce the influence of noise and interference.
R (reception power of desired wave to reception power of interference wave) can be calculated.

(Embodiment 7) FIG.7 is a block diagram showing the configuration of a receiving apparatus according to Embodiment 7 of the present invention.
However, in the seventh embodiment shown in FIG. 7, parts corresponding to the respective parts in the first embodiment shown in FIG. 1 are designated by the same reference numerals, and description thereof will be omitted.

The receiving apparatus shown in this figure has a pilot pattern generating section 106, a rake combining section 107, and a decoding section 108, which are components of receiving apparatus 100 of the first embodiment.
And the re-encoded data generation unit 112, in addition to the PhyCH BER
The measuring unit 701 is provided.

The Physical CH BER measuring unit 701 measures the physical channel bit error rate (BER). Specifically, the bit error rate of pilot symbols and TFCI symbols within a certain section is measured.

The operation of such a configuration will be described.

PhyCH BER measuring section 701 bit-matches the received pilot symbol output from rake combining section 107 with the pilot pattern output from pilot pattern generating section 106 to obtain the number of error bits of the received pilot symbol.

Also, the received TFCI symbol output from rake combining section 107 and the TFCI re-encoded data output from re-encoded data generating section 112 are bit-matched and received.
Find the number of error bits in the TFCI symbol. By dividing the sum of the error bits of the received pilot symbols and the received TFCI symbols calculated in this way by the total number of pilot symbols and TFCI symbols used for bit matching, the physical channel
Measure the BER.

As described above, the receiving device 70 of the present embodiment
According to 0, in the frame where the TFCI data is the same as the previous frame, the TFCI calculated in the previous frame has high reliability.
The recoded data was used for physical channel BER measurement as well as pilot symbols. As a result, in the physical channel BER measurement, it is possible to increase the number of samples when obtaining the BER, and it is possible to measure a more accurate physical channel BER in which the influence of noise and interference is reduced.

(Embodiment 8) FIG.8 is a block diagram showing a configuration of a receiving apparatus according to Embodiment 8 of the present invention.
However, in the eighth embodiment shown in FIG. 8, parts corresponding to the respective parts of the first embodiment in FIG. 1 are designated by the same reference numerals, and description thereof will be omitted.

The receiving apparatus shown in this figure has a pilot pattern generating section 106, a rake combining section 107, and a decoding section 108, which are components of receiving apparatus 100 of the first embodiment.
And a re-encoded data generation unit 112, and a synchronization determination unit 801.

The synchronization determination unit 801 determines whether the current synchronization is maintained or out of synchronization. Specifically, the determination is performed by comparing the number of bit errors of the pilot symbol and the TFCI symbol with a preset number of allowable error bits.

The operation of such a configuration will be described.

The synchronization determination unit 801 is the rake synthesis unit 107.
The received pilot symbol output from the pilot pattern and the pilot pattern output from the pilot pattern generation unit 106 are bit-matched to obtain the error bit number of the received pilot symbol. Also, bit matching is performed with the received TFCI symbol output from the Rake combining unit 107 and the TFCI re-encoded data output from the re-encoded data generation unit 112,
Determine the number of error bits in the received TFCI symbol. The sum of the error bit numbers of the received pilot symbol and the received TFCI symbol calculated in this way is compared with a preset allowable error bit number to determine the synchronization state.

That is, if the number of error-allowed bits is less than the allowable number of bits, it is determined to be in the synchronization holding state. At this time, in order to reduce the influence of noise and interference, the comparison result may be provided with front protection and rear protection.

As described above, the receiving apparatus 80 of the present embodiment
According to 0, in the frame where the TFCI data is the same as the previous frame, the TFCI calculated in the previous frame has high reliability.
The re-encoded data was used for synchronization judgment as well as the pilot symbol.

As a result, it is possible to increase the number of samples when obtaining the number of error bits in the synchronization determination, and it is possible to perform more accurate synchronization determination in which the influence of noise and interference is reduced.

(Embodiment 9) FIG. 9 is a block diagram showing the configuration of a receiving apparatus according to Embodiment 9 of the present invention.
However, in the ninth embodiment shown in FIG. 9, parts corresponding to those in the first to second embodiments shown in FIG. 1 are designated by the same reference numerals, and the description thereof will be omitted.

The receiving apparatus 900 shown in this figure is a synchronization unit 101 which is a component of the receiving apparatus 200 of the second embodiment.
, Despreading sections 102-1 to 102-N, which are components of receiving apparatus 200 of Embodiment 2, pilot pattern generating section 106, rake combining section 107, and decoding section 10.
8, the re-encoded data generation unit 112, and the synchronous detection unit 20
In addition to 4-1 to 204-N, the frequency offset detection unit 9
01 and 01.

The frequency offset detector 901 uses the AFC
(Automatic Frequency control
(ol: automatic frequency control), the amount of deviation (frequency offset value) between the reference clock frequency on the transmission side and the reference clock frequency on the reception side, which cannot be completely corrected, is detected.

When there is a frequency offset, the phase of the received signal rotates at a substantially constant phase rotation speed with respect to the measurement time. Therefore, in the frequency offset value detection, an average symbol obtained by averaging the received pilot symbol and the received TFCI symbol over a plurality of symbols is calculated for each certain fixed interval, and the phase change amount of the average symbol is calculated, and further, it is measured between fingers, This is averaged in a certain section, converted into a frequency offset value, and output.

The operation of such a configuration will be described.

Frequency offset detecting section 901 matches the quadrant of the received pilot symbol of each finger using the pilot pattern. Also, the TFCI re-encoded data output from the re-encoded data generation unit 112 is used for reception.
Match the quadrants of the TFCI symbol.

Then, the received pilot symbols and the received TFCI symbols in the quadrant are added in-phase over a plurality of symbols to obtain an average symbol. This average symbol is calculated for each fixed interval, and the amount of phase change in the fixed interval of the average symbol is obtained.

By averaging the amount of phase change calculated at each finger at fixed intervals, and further averaging it over a fixed interval, the amount of phase change in which noise and interference waves have been reduced is obtained and converted to a frequency offset value. And output.

As described above, the receiving device 90 of the present embodiment
According to 0, in the frame where the TFCI data is the same as the previous frame, the TFCI calculated in the previous frame has high reliability.
The re-encoded data was used to detect the frequency offset as well as the pilot symbols.

As a result, in the frequency offset detection, it is possible to increase the average number of symbols, and it is possible to detect a more accurate frequency offset in which the influence of noise and interference is reduced.

(Embodiment 10) FIG.10 is a block diagram showing the configuration of a receiving apparatus according to Embodiment 10 of the present invention. However, in the tenth embodiment shown in FIG. 10, parts corresponding to the respective parts of the ninth embodiment in FIG. 9 are designated by the same reference numerals, and description thereof will be omitted.

The receiving apparatus 1000 shown in this figure is a synchronization unit 101 which is a component of the receiving apparatus 900 of the ninth embodiment.
, Despreading sections 102-1 to 102-N, pilot pattern generating section 106, rake combining section 107, decoding section 108, re-encoded data generating section 112, and coherent detection sections 204-1 to 204. -N, in addition to the frequency offset detection unit 901, a fading frequency detection unit 1001
It is configured with.

The fading frequency detector 1001 detects the fading frequency received by the received signal.

The received signal undergoes phase rotation at a substantially constant speed due to frequency offset and random phase change due to fading. Therefore, based on the frequency offset amount output from the frequency offset detection unit 901, the phase change amount obtained by subtracting the constant speed rotation due to the frequency offset is averaged, converted into a fading frequency, and output.

The operation of such a configuration will be described.

Fading frequency detecting section 1001 matches the quadrant of the received pilot symbol of each finger using the pilot pattern. Also, the TFCI re-encoded data output from the re-encoded data generation unit 112 is used to match the quadrants of the received TFCI symbols.

Then, the received pilot symbols and the received TFCI symbols in the quadrant are added in-phase over a plurality of symbols to obtain an average symbol. This average symbol is calculated for each fixed interval, and the phase change amount of the average symbol is obtained. Then, based on the frequency offset amount output from the frequency offset detection unit 901, the phase change amount due to fading is obtained by subtracting the constant speed rotation amount due to the frequency offset, and by averaging the phase change amount between fingers in a constant section. , The amount of phase change due to fading with reduced noise and interference waves can be obtained.

The phase change amount due to the averaged fading is converted into a fading frequency and output.

As described above, the receiving apparatus 10 of the present embodiment
According to 00, in the frame where the TFCI data is the same as the previous frame, the TF calculated in the previous frame has high reliability.
CI re-encoded data was used to detect fading frequency as well as pilot symbols. By this means, in fading frequency detection, it is possible to increase the average number of symbols, and it is possible to detect a more accurate fading frequency with reduced effects of noise and interference.

The same effect can be obtained with a mobile station apparatus characterized by including the receiving apparatus according to any of Embodiments 1 to 10 above.

Further, the same effect can be obtained by a base station apparatus characterized by including the receiving apparatus according to any of the above-mentioned first to tenth embodiments.

Further, the same effect can be obtained also in a mobile communication system characterized by including the receiving apparatus described in any of the above-mentioned first to tenth embodiments.

Further, the receiving method in the receiving device of any of the above first to tenth embodiments may be used. For example, the receiving method in the receiving apparatus 100 according to the first embodiment is as follows.

That is, the received encoded data is decoded at every fixed time to obtain information data, this information data is re-encoded to calculate re-encoded data, which is within an integer multiple of the fixed time. After the second fixed time, the re-encoded data calculated in the immediately previous fixed time is output,
This output re-encoded data is used to calculate an estimated value of a channel characteristic using a pilot symbol, and a received signal is synchronously detected based on the estimated value of the channel characteristic.

Further, the operation of the receiving device according to any of the first to tenth embodiments may be recorded in the recording medium as a program. For example, the receiving device 1 according to the first embodiment
The program at 00 has the following procedure.

A decoding procedure for decoding the received coded data for each predetermined section to obtain information data, and a re-encoded data calculation procedure for re-encoding the decoded information data to calculate re-encoded data And a re-encoded data output procedure for outputting the re-encoded data calculated in the immediately preceding predetermined period after the second predetermined period within the integral multiple time period of the predetermined period, and the re-encoded data output A channel estimation procedure for calculating an estimated value of the channel characteristic using the pilot symbol and a synchronous detection procedure for synchronously detecting the received signal based on the estimated value of the channel characteristic.

[0155]

As described above, according to the present invention,
Various receiving processes using the pilot symbols can be performed more accurately than before without increasing the ratio of the number of pilot symbols, increasing the transmission power of the pilot symbols, and using the temporary determination data.

[Brief description of drawings]

FIG. 1 is a block diagram showing a configuration of a CDMA receiving apparatus according to Embodiment 1 of the present invention.

FIG. 2 is a block diagram showing a configuration of a CDMA receiving apparatus according to Embodiment 2 of the present invention.

FIG. 3 is a block diagram showing a configuration of a CDMA receiving apparatus according to Embodiment 3 of the present invention.

FIG. 4 is a block diagram showing a configuration of a CDMA receiving apparatus according to Embodiment 4 of the present invention.

FIG. 5 is a block diagram showing a configuration of a CDMA receiving apparatus according to Embodiment 5 of the present invention.

FIG. 6 is a block diagram showing a configuration of a CDMA receiving apparatus according to Embodiment 6 of the present invention.

FIG. 7 is a block diagram showing the configuration of a CDMA receiving apparatus according to Embodiment 7 of the present invention.

FIG. 8 is a block diagram showing the configuration of a CDMA receiving apparatus according to Embodiment 8 of the present invention.

FIG. 9 is a block diagram showing the configuration of a CDMA receiving apparatus according to Embodiment 9 of the present invention.

FIG. 10 is a block diagram showing a configuration of a CDMA receiving apparatus according to Embodiment 10 of the present invention.

FIG. 11 (a) Uplink physical channel (DPDC
H, DPCCH) frame structure (b) Decoding, re-encoding, and channel characteristics estimation timing example

FIG. 12 TFCI re-encoded data (data after error correction)
And TFCI provisional judgment data (data before quality check by error correction) BER characteristics and BLER characteristics of transport channel information data

FIG. 13 is a flowchart showing an example of a procedure for estimating propagation path characteristics of a received signal.

FIG. 14 is a flowchart showing a specific example of the procedure for estimating the propagation path characteristics of a received signal.

[Explanation of symbols]

100 CDMA receiver 101 synchronization unit 102-1 to 102-N despreading unit 103-1 to 103-N Channel estimation unit 104-1 to 104-N Multiplier 105-1 to 105-N Synchronous detection unit 106 Pilot pattern generator 107 Lake Synthesizer 108 Decoding unit 109 re-encoding unit 110 Re-encoded data output unit 111 Minimum TTI frame number measurement unit 112 Re-encoded Data Generation Unit 350 Error correction unit

Continued front page    (72) Inventor Daisuke Yamada             3-1, Tsunashima-Higashi 4-chome, Kohoku-ku, Yokohama-shi, Kanagawa             Matsushita Communication Industry Co., Ltd. F term (reference) 5K014 AA01 BA06 GA01 HA05                 5K022 EE02 EE13 EE22 EE32 EE36                 5K047 AA03 BB01 GG34 HH15 LL15                       MM03 MM12

Claims (17)

[Claims] 1. A method of receiving a signal of a CDMA communication system and estimating a propagation path characteristic of the received signal, wherein the contents are the same over a plurality of frames, and redundant bits are added. For control information that is error-correctable, a step of performing decoding processing including error correction, a step of re-encoding the decoded data after error correction, and a step of re-encoding the data as known bits And a step of estimating the propagation path characteristic of the received signal using the method, and a method of estimating the propagation path characteristic of the received signal. 2. A method of receiving a signal of a CDMA communication system conforming to IMT2000 and estimating a propagation path characteristic of the received signal, the method comprising: uplink DPDCH (Dedicated Physical Data Ch
transmission period (TTI: Transmission Time Int) of one block of each transport channel multiplexed in an annel)
erval) corresponds to n (n is an integer of 2 or more) frames, DPCCH (Dedicated Physic) of the received signal.
TFCI (Transport) included in al Control Channel
Format Combination Indicator) to obtain information data by decoding at intervals corresponding to one frame; step of re-encoding the information data obtained by decoding to obtain re-encoded data; transmission cycle of the one block For each of the second frame to the nth frame in (TTI), a step of estimating the propagation path characteristic using the re-encoded data of the immediately preceding frame as a known bit is included. Method for estimating propagation path characteristics of received signal. 3. A CDMA receiving apparatus which receives a signal of a CDMA communication system and estimates the propagation path characteristic of the received signal, wherein the contents are the same over a plurality of frames and a redundant bit is added. For the control information that has been error corrected, a decoding unit that performs a decoding process that includes error correction, a re-encoding unit that re-encodes the decoded data after error correction, and a re-encoding And a detection section for performing detection using the estimated propagation path characteristics, the propagation path characteristic estimator for estimating the propagation path characteristics of the received signal using the data CDMA receiver. 4. A CDMA receiving device for receiving a signal of a CDMA communication system conforming to IMT2000 and estimating a propagation path characteristic of the received signal, wherein each transformer is multiplexed on a DPDCH (Dedicated Physical Data Channel). The transmission cycle (TTI: Transmission Time Interval) of one block of the port channel is n
(N is an integer equal to or greater than 2) frames, DPCCH (Dedicated Physical control C) of the received signal
TFCI (Transport Format Combi) included in hannel
nation indicator) at intervals corresponding to one frame to obtain information data, a re-encoding unit for re-encoding the information data obtained by decoding to obtain re-encoded data, A channel characteristic estimation unit that performs channel characteristic estimation processing using the re-encoded data of the immediately preceding frame as known bits for each of the second frame to the nth frame within the transmission period (TTI) of the block. A CDMA receiving apparatus comprising: a detection unit that performs detection using the estimated propagation path characteristics. 5. Decoding means for decoding the received encoded data for each predetermined section to obtain information data, and re-encoded data calculation for re-encoding the decoded information data to calculate re-encoded data. Means within a period of n times the predetermined section (n is an integer of 2 or more),
In the second to n-th predetermined sections, re-encoded data output means for outputting the re-encoded data calculated in the immediately preceding predetermined section, and the re-encoded data output is known in the same manner as pilot symbols. A re-encoded data utilization unit that performs reception processing by using as a signal, and a CDMA reception device. 6. The propagation according to claim 5, wherein the recoded data utilizing means calculates an estimated value of a channel characteristic using pilot symbols and recoded data output from the recoded data output means. A CDMA receiving apparatus comprising: a path estimating unit; and a synchronous detecting unit that synchronously detects a received signal based on the estimated value of the propagation path characteristic. 7. The delay code calculation means according to claim 5, wherein the recoded data utilization means calculates a delay profile using pilot symbols and recoded data output from the recoded data output means. And a synchronization timing determining means for determining a synchronization timing based on the delay profile. 8. The recoded data utilizing means according to claim 5, wherein the recoded data utilizing means uses the pilot symbol and the recoded data output from the recoded data output means to receive a received signal for a predetermined time from a synchronization timing. Early correlation value averaging means for averaging the correlation value between the phase advanced signal and the spread code, and the re-encoded data output from the pilot symbol and the re-encoded data output means, the synchronization timing To average the correlation value between the late signal and the spread code in which the phase of the received signal is delayed by the same time as the Early signal
Late correlation value averaging means, Early-Late correlation value difference calculating means for calculating the correlation power difference between the averaged Early correlation value and the averaged Late correlation value, and the Early-Late correlation value difference A CDMA receiving apparatus comprising: a tracking unit that compares a predetermined threshold value and finely adjusts the synchronization timing based on the result. 9. The desired wave reception unit according to claim 5, wherein the recoded data utilization unit calculates a desired wave reception power using pilot symbols and recoded data output from the recoded data output unit. A CDMA receiving apparatus comprising power calculation means. 10. The interference wave reception unit according to claim 5, wherein the recoded data utilization unit calculates an interference wave reception power using pilot symbols and recoded data output from the recoded data output unit. A CDMA receiving apparatus comprising power calculation means. 11. The desired wave reception unit according to claim 5, wherein the recoded data utilization unit calculates a desired wave reception power using pilot symbols and recoded data output from the recoded data output unit. Power calculation means, interference wave reception power calculation means for calculating interference wave reception power using pilot symbols and re-encoded data output from the re-encoded data output means, the desired wave reception power and the interference From received power of desired wave to desired power of received power to received power of interference wave (SIR)
And a SIR calculating means for calculating. 12. The bit error rate (BER) of a physical channel signal according to claim 5, wherein the recoded data utilizing means uses pilot symbols and recoded data output from the recoded data output means. A CDMA receiving device comprising a physical channel BER measuring means for calculating 13. The recoded data utilizing means according to claim 5, wherein the current synchronization can be maintained or lost by using the pilot symbol and the recoded data output from the recoded data output means. A CDMA receiving apparatus, characterized in that it comprises a synchronization determining means for determining whether or not there is any. 14. The recoded data utilizing means according to claim 5, wherein the reference clock frequencies of the transmitting side and the receiving side are determined using pilot symbols and recoded data output from the recoded data output means. A CDMA receiver comprising a frequency offset detecting means for detecting a frequency offset value caused by a shift. 15. The fading cycle detection means according to claim 5, wherein the recoded data utilizing means detects a fading cycle using pilot symbols and recoded data output from the recoded data output means. A CDMA receiver comprising: 16. A mobile station device equipped with the CDMA receiving device according to claim 3. 17. A base station device equipped with the CDMA receiver according to claim 3. Description: