JP2002095264A - Pwm inverter - Google Patents
Pwm inverterInfo
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- JP2002095264A JP2002095264A JP2000281125A JP2000281125A JP2002095264A JP 2002095264 A JP2002095264 A JP 2002095264A JP 2000281125 A JP2000281125 A JP 2000281125A JP 2000281125 A JP2000281125 A JP 2000281125A JP 2002095264 A JP2002095264 A JP 2002095264A
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- inverter
- wiring
- inductance
- parallel circuit
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Abstract
Description
【０００１】[0001]
【発明の属する技術分野】本発明は、運転周波数範囲の
広い電動機駆動用の電圧形ＰＷＭインバータの出力電流
の検出によって過負荷保護等を行うＰＷＭインバータに
係り、特に負荷電流を検出するためのインバータと電動
機の配線回路に関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a PWM inverter for performing overload protection by detecting an output current of a voltage-type PWM inverter for driving a motor having a wide operating frequency range, and more particularly to an inverter for detecting a load current. And the wiring circuit of the motor.
【０００２】[0002]
【従来の技術】電圧形ＰＷＭインバータで、誘導電動機
やダンパ巻線付き永久磁石電動機を運転する場合のシス
テム構成を図５に示す。同図の制御装置は、マイクロコ
ンピュータやロジックＩＣを用いたディジタル回路で構
成され、電圧と周波数の制御には三角波と正弦波の比較
方式とする場合である。2. Description of the Related Art FIG. 5 shows a system configuration when an induction motor or a permanent magnet motor with a damper winding is operated by a voltage-type PWM inverter. The control device shown in the figure is configured by a digital circuit using a microcomputer or a logic IC, and the voltage and frequency are controlled by a method of comparing a triangular wave and a sine wave.
【０００３】同図において、順変換回路１には直流電力
を得、電圧形にされる逆変換回路（インバータ）２によ
って周波数及び電圧の比（Ｖ／ｆ）を一定にした交流出
力を得、電動機３を駆動する。In FIG. 1, DC power is obtained from a forward conversion circuit 1, and an AC output having a constant frequency / voltage ratio (V / f) is obtained by a voltage-converted inverter (inverter) 2. The electric motor 3 is driven.
【０００４】制御装置は、周波数設定信号からＶ／ｆ設
定回路４により一定比にした電圧設定値を得、位相積分
回路５により位相設定値を得、三相正弦波発生部６では
位相設定値に応じた周波数で一定振幅の三相正弦波を発
生し、乗算器７1〜７3では三相正弦波にそれぞれ電圧設
定値を乗じることによりその振幅を調節し、コンパレー
タ回路８により三角波発生回路９からの三角波（キャリ
ア信号）との大小を比較し、コンパレータ回路８にはＰ
ＷＭ波形のゲート信号を得、これらゲート信号はデット
タイム作成回路１０により互いに同時ＯＮを無くしたＰ
ＷＭ波形を得、逆変換回路２の各スイッチング素子ＴＵ
〜ＴＺのゲートドライブ信号を得る。The control device obtains a voltage set value at a fixed ratio from a frequency set signal by a V / f setting circuit 4, obtains a phase set value by a phase integrator circuit 5, and a three-phase sine wave generator 6 generates a phase set value. the three-phase sine wave of constant amplitude occurs at a frequency corresponding to the multiplier 7 1-7 to 3 in the three-phase sine wave by each multiplying the voltage set value by adjusting the amplitude, the triangular wave generating circuit by the comparator circuit 8 9 is compared with the triangular wave (carrier signal) from
Gate signals having WM waveforms are obtained, and these gate signals are output by the dead time generation circuit 10 to P
WM waveform is obtained, and each switching element TU of the inverse conversion circuit 2 is obtained.
To TZ are obtained.
【０００５】このようなＶ／ｆ一定制御方式で単純に運
転する場合でも、ＰＷＭインバータや電動機の過負荷保
護等の目的で出力電流を検出することが一般的である。
運転周波数範囲の広い電動機駆動用のＰＷＭインバータ
では、直流分の検出も可能なホール素子を用いた電流検
出器をインバータ出力端に設け、出力電流の基本波成分
を比較的低速なＡ／Ｄ変換器で取り込むことができるよ
うにサンプルアンドホールド回路１１1〜１１3を用意
し、三角波発生回路９からの三角波の頂点（山ｏｒ谷）
のタイミングをサンプリングタイミングとして各相の出
力電流をサンプリングし、各サンプリング値はＡ／Ｄ変
換器１２により次の三角波頂点が来る前までにＡ／Ｄ変
換を実行する。[0005] Even in the case of simple operation using such a constant V / f control method, it is common to detect an output current for the purpose of protecting an overload of a PWM inverter or a motor.
In a PWM inverter for driving a motor having a wide operating frequency range, a current detector using a Hall element capable of detecting a direct current component is provided at an output terminal of an inverter, and a fundamental wave component of an output current is converted into an A / D signal at a relatively low speed. providing a sample-and-hold circuits 11 1 to 11 3 to be able to capture in vessels, the apex of the triangular wave from the triangular wave generating circuit 9 (peaks or troughs)
The output current of each phase is sampled using the timing of (1) as a sampling timing, and the A / D converter 12 executes A / D conversion of each sampled value before the next triangular wave peak.
【０００６】この電流検出方法は、Ｔｕ，Ｔｖ，Ｔｗの
上側３素子が全ＯＮ状態か、Ｔｘ，Ｔｙ、Ｔｚの下側３
素子が全ＯＮ状態となる、出力電圧が零の状態の電流値
を取り込もうとするもので、出力電流経路にインバータ
直流電圧源が入らないため、スイッチングに伴う電流の
脈動成分が小さく、基本波成分を良好に抽出することが
可能である。図６にインバータ出力電流波形と線間電圧
波形および三角波と相電流との関係を示す。[0006] This current detection method is based on whether the upper three elements of Tu, Tv and Tw are all in the ON state or the lower three elements of Tx, Ty and Tz.
In order to take in the current value in the state where the output voltage is zero, in which all the elements are in the ON state. Since the inverter DC voltage source does not enter the output current path, the pulsating component of the current due to switching is small, and the fundamental wave component. Can be satisfactorily extracted. FIG. 6 shows the relationship between the inverter output current waveform, the line voltage waveform, and the triangular wave and the phase current.
【０００７】[0007]
【発明が解決しようとする課題】図６の波形は、インバ
ータ出力端と電動機３との間に配線がないか、もしくは
極端に短い配線での波形を示すものであるが、実際には
インバータ出力端と電動機を接続する配線にはインダク
タンス（Ｌ0）と浮遊容量（Ｃ0）が存在し、インバータ
素子のスイッチングによる電圧変化でＬＣ共振現象が発
生し、図７にシミュレーション波形を示すように、電動
機端子間に高いサージ電圧を印加させたり、インバータ
出力電流にサージ電流が重畳してしまい、三角波の頂点
タイミンゲで電流をサンプリングしているにもかかわら
ず、基本波成分の抽出を困難にする場合がある。The waveform in FIG. 6 shows a waveform with no wiring between the inverter output terminal and the motor 3 or with extremely short wiring. There is an inductance (L 0 ) and a stray capacitance (C 0 ) in the wiring connecting the end and the motor, and an LC resonance phenomenon occurs due to a voltage change due to the switching of the inverter element, as shown in a simulation waveform in FIG. When a high surge voltage is applied between the motor terminals or a surge current is superimposed on the inverter output current, making it difficult to extract the fundamental wave component even though the current is sampled at the apex of the triangular wave. There is.
【０００８】サージ電圧やサージ電流の大きさは、イン
バータ素子のスイッチング速度や配線条件などによって
異なるが、配線が長い（Ｌ0，Ｃ0とも大）ほど大きくな
る。図７は４００Ｖ系インバータを想定した波形であ
り、三角波キャリア周波数：６ｋＨｚ、線路インダクタ
ンスＬ0：２１.６μＨ、線路浮遊容量Ｃ0：２０ｎＦ、
線路直流抵抗Ｒ0：１３０ｍΩとする場合である。The magnitude of the surge voltage or surge current varies depending on the switching speed of the inverter element, the wiring conditions, and the like, but increases as the wiring length increases (both L 0 and C 0 increase). FIG. 7 shows a waveform assuming a 400 V inverter, a triangular wave carrier frequency: 6 kHz, a line inductance L 0 : 21.6 μH, a line stray capacitance C 0 : 20 nF,
This is the case where the line DC resistance R 0 is 130 mΩ.
【０００９】本発明の目的は、キャリア信号になる三角
波の頂点で電流サンプリングを行うのに、配線インダク
タンスと浮遊容量の影響を少なくして出力電流の基本波
成分を抽出できるようにしたＰＷＭインバータを提供す
ることにある。SUMMARY OF THE INVENTION An object of the present invention is to provide a PWM inverter capable of extracting a fundamental wave component of an output current by reducing the influence of wiring inductance and stray capacitance to perform current sampling at a peak of a triangular wave serving as a carrier signal. To provide.
【００１０】[0010]
【課題を解決するための手段】本発明は、インバータ出
力端と電動機との間の配線にＬfとＲfのＬ−Ｒ並列回路
を挿入し、高周波成分をＲf側に流すことで配線のイン
ダクタンスＬ0と浮遊容量Ｃ0で構成される直列共振回路
の減衰率を大きくし、これによりインバータ出力電流に
含まれるＬＣ共振によるサージ電流の割合を小さくする
ことで、基本波電流成分を良好に抽出できるようにした
もので、以下の構成を特徴とする。According to the present invention, an LR parallel circuit of Lf and Rf is inserted into a wiring between an inverter output terminal and a motor, and a high-frequency component is caused to flow to the Rf side. The fundamental wave current component can be improved by increasing the attenuation rate of the series resonance circuit composed of the inductance L 0 and the stray capacitance C 0 of the inverter circuit, thereby reducing the ratio of the surge current due to LC resonance included in the inverter output current. And is characterized by the following configuration.
【００１１】ＰＷＭ波形でゲート制御される電圧形イン
バータから配線を通して電動機に電流を供給し、前記配
線に設けた電流検出器の検出電流からＰＷＭ波形のキャ
リア信号になる三角波の頂点でサンプリングして出力電
流を検出するＰＷＭインバータであって、前記配線の各
相にインダクタンスＬfと抵抗ＲfのＬ−Ｒ並列回路をそ
れぞれ挿入し、前記Ｌ−Ｒ並列回路のインダクタンスＬ
fと抵抗Ｒfは、前記配線のインダクタンスＬ0と浮遊容
量Ｃ0で構成される直列共振回路の減衰率を大きくする
定数にした構成を特徴とする。A current is supplied to the motor from a voltage source inverter gate-controlled by a PWM waveform through a wiring, and is sampled and output at a vertex of a triangular wave which becomes a carrier signal of a PWM waveform from a detection current of a current detector provided on the wiring. a PWM inverter for detecting a current, the insert respectively the L-R parallel circuit of an inductance L f and resistor R f in each phase of the wire, the inductance L of the L-R parallel circuit
f and the resistor Rf are characterized in that they are constants that increase the attenuation factor of the series resonance circuit composed of the inductance L 0 of the wiring and the stray capacitance C 0 .
【００１２】また、前記Ｌ−Ｒ並列回路の定数は、Ｒf
＝Ｚ0＝√（Ｌ0／Ｃ0）、Ｌf≧２＊Ｌ0としたことを特
徴とする。The constant of the LR parallel circuit is R f
= Z 0 = √ (L 0 / C 0 ), and L f ≧ 2 * L 0 .
【００１３】また、前記Ｌ−Ｒ並列回路のインダクタン
スＬf側の電流を検出し、インバータの基本波電流成分
を抽出する構成を特徴とする。Further, the invention is characterized in that a current on the inductance Lf side of the LR parallel circuit is detected and a fundamental wave current component of the inverter is extracted.
【００１４】また、前記Ｌ−Ｒ並列回路のインダクタン
スＬfの鉄心にホール素子を組込み、電流検出器と兼用
した構成を特徴とする。Further, incorporation of the Hall element in the core of inductance L f of the L-R parallel circuit, and wherein the configuration in which also serves as a current detector.
【００１５】[0015]
【発明の実施の形態】図１は、本発明の実施形態を示す
システム構成図である。同図が図５と異なる部分は、逆
変換回路２の出力端と電動機３の配線接続回路の各相に
リアクトルＬ fと抵抗ＲfのＬ−Ｒ並列回路１３をそれぞ
れ直列に挿入した点にある。FIG. 1 shows an embodiment of the present invention.
It is a system configuration diagram. 5 is different from FIG.
Each phase of the output terminal of the conversion circuit 2 and the wiring connection circuit of the motor 3
Reactor L fAnd resistance RfLR parallel circuit 13
Are inserted in series.
【００１６】上記の構成において、電動機が接続されて
いない場合の配線路は、簡単なＬＣＲ直列回路で表現で
き、一般には抵抗分Ｒ0は、線路の特性インピーダンス
Ｚ0＝√（Ｌ0／Ｃ0）と比較して十分小さいため、イン
バータ素子のスイッチングによる電圧変化でＬＣＲ直列
回路は減衰率の小さな振動的応答を示す。In the above configuration, the wiring path when no motor is connected can be represented by a simple LCR series circuit. In general, the resistance R 0 is equal to the characteristic impedance Z 0 = √ (L 0 / C 0 ), the LCR series circuit shows an oscillating response with a small damping rate due to a voltage change due to the switching of the inverter element.
【００１７】そこで、本実施形態では、インバータ出力
部分にＬ−Ｒ並列回路を挿入し、周波数の高い成分をＲ
f側に流すことでＬ0，Ｃ0と構成される直列共振回路の
減衰率を大きくし、インバータ出力電流に含まれるＬＣ
共振によるサージ電流の割合を小さくするものである。Therefore, in the present embodiment, an LR parallel circuit is inserted in the output portion of the inverter, and the high frequency component is reduced to R
By flowing to the f side, the attenuation factor of the series resonance circuit composed of L 0 and C 0 is increased, and LC included in the inverter output current is increased.
This is to reduce the ratio of surge current due to resonance.
【００１８】定数設定は、Ｒf＝Ｚ0＝√（Ｌ0／Ｃ0）、
Ｌf≧２＊Ｌ0とし、完全に振動を抑制することはできな
いが、Ｒfでの損失をＰrf＝Ｃ0＊（Ｖdc／ｓｑｒｔ
（３）） 2＊２＊ｆc（ただし、Ｖdc：インバータ直流電
圧［Ｖ］、ｆc＝キャリア周波数［Ｈｚ］）程度に抑え
ることができる経済的な設定とする。The constant setting is Rf= Z0= √ (L0/ C0),
Lf≧ 2 * L0And vibration cannot be completely suppressed.
But RfLoss at Prf= C0* (Vdc/ Sqrt
(3)) Two* 2 * fc(However, Vdc: Inverter DC power
Pressure [V], fc= Carrier frequency [Hz])
An economic setting that can be used.
【００１９】図２は、本実施形態を４００Ｖ系インバー
タに適用した場合のシミュレーション波形を示し、図７
に比べてサージ電流を大幅に低減でき、出力電流の検出
が容易になる。FIG. 2 shows simulation waveforms when this embodiment is applied to a 400 V inverter.
, The surge current can be greatly reduced and the output current can be easily detected.
【００２０】図３は、本発明の他の実施形態を示し、同
図が図１と異なる部分は各相電流検出器をＬ−Ｒ並列回
路１３のインダクタンスＬfを通した電流のみを検出す
る酔う回路接続した点にある。[0020] Figure 3 shows another embodiment of the present invention, the portion drawing differs from that of Figure 1 only detects current through the inductance L f of the phase current detector L-R parallel circuit 13 It is at the point where the intoxicated circuit is connected.
【００２１】本実施形態によれば、Ｌf側に流れる電流
のみを検出し、サージ電流成分を検出しにくい構成とし
ており、電流検出を一層容易にする。図４に４００Ｖ系
インバータに適用した場合のＬf、Ｒfおよびインバータ
の出力電流波形を示し、Ｒfに流れるサージ電流成分を
取り除いた電流検出が可能となる。According to the present embodiment, only the current flowing to the Lf side is detected, and the surge current component is hardly detected, so that the current detection is further facilitated. FIG. 4 shows L f , R f and the output current waveform of the inverter when applied to a 400 V inverter, and it is possible to detect a current from which a surge current component flowing through R f has been removed.
【００２２】なお、図３に示す実施形態において、Ｌf
の鉄心にホール素子を組込み、電流検出器と兼用する構
成とすることができる。In the embodiment shown in FIG. 3, L f
A Hall element may be incorporated in the iron core of the above, so that the Hall element is used also as a current detector.
【００２３】[0023]
【発明の効果】以上のとおり、本発明によれば、以下の
効果がある。As described above, according to the present invention, the following effects can be obtained.
【００２４】１）インバータ出力部分にＬ−Ｒ並列回路
を挿入し、高周波成分をＲf側に流すことで配線のイン
ダクタンスＬ0と浮遊容量Ｃ0で構成される直列共振回路
の減衰率を大きくし、これによりインバータ出力電流に
含まれるＬＣ共振によるサージ電流の割合を小さくする
ことで、キャリア信号になる三角波の頂点で電流サンプ
リングを行う電圧形ＰＷＭインバータで基本波電流成分
を良好に抽出することができる。1) An LR parallel circuit is inserted in the inverter output portion, and a high frequency component is caused to flow to the Rf side to increase the attenuation factor of the series resonance circuit composed of the wiring inductance L 0 and the stray capacitance C 0. By reducing the ratio of the surge current due to LC resonance included in the inverter output current, a voltage-type PWM inverter that performs current sampling at the apex of a triangular wave serving as a carrier signal can favorably extract a fundamental wave current component. Can be.
【００２５】２）同時に、モータ端子間のサージ電圧を
抑制することができる。2) At the same time, a surge voltage between the motor terminals can be suppressed.
【００２６】３）Ｌ−Ｒ回路のＬfの鉄心にホール素子
を組込み、電流検出器と兼用すれば、インバータ装置の
コストダウンが可能となる。3) If a Hall element is incorporated in the Lf core of the LR circuit and used as a current detector, the cost of the inverter device can be reduced.
【図１】本発明の実施形態を示すシステム構成図。FIG. 1 is a system configuration diagram showing an embodiment of the present invention.
【図２】実施形態における各部波形図。FIG. 2 is a waveform diagram of each part in the embodiment.
【図３】本発明の他の実施形態を示すシステム構成図。FIG. 3 is a system configuration diagram showing another embodiment of the present invention.
【図４】他の実施形態における各部波形図。FIG. 4 is a waveform diagram of each part according to another embodiment.
【図５】従来のＰＷＭインバータのシステム構成図。FIG. 5 is a system configuration diagram of a conventional PWM inverter.
【図６】インバータの出力端と電動機間の配線がない場
合の各部波形図。FIG. 6 is a waveform diagram of each part when there is no wiring between the output terminal of the inverter and the motor.
【図７】インバータの出力端と電動機間の配線がある場
合の各部波形図。FIG. 7 is a waveform diagram of each part when there is a wiring between the output terminal of the inverter and the motor.
２…逆変換回路 ３…電動機 ９…三角波発生回路 １１1〜１１3…サンプルアンドホールド回路 １２…Ａ／Ｄ変換器 １３…Ｌ−Ｒ並列回路2. Inverse conversion circuit 3. Electric motor 9. Triangular wave generation circuit 11 1 to 11 3. Sample and hold circuit 12. A / D converter 13. LR parallel circuit
フロントページの続き Ｆターム(参考） 5H007 AA04 BB06 CA01 CB05 CC12 DA05 DB01 DC02 EA02 FA01 FA03 5H576 BB05 CC05 DD02 DD04 DD07 EE04 EE15 GG04 HA02 HB02 JJ03 JJ08 JJ16 JJ22 JJ29 LL22 MM04 Continued on front page F-term (reference)
Claims (4)
ンバータから配線を通して電動機に電流を供給し、前記
配線に設けた電流検出器の検出電流からＰＷＭ波形のキ
ャリア信号になる三角波の頂点でサンプリングして出力
電流を検出するＰＷＭインバータであって、 前記配線の各相にインダクタンスＬfと抵抗ＲfのＬ−Ｒ
並列回路をそれぞれ挿入し、 前記Ｌ−Ｒ並列回路のインダクタンスＬfと抵抗Ｒfは、
前記配線のインダクタンスＬ0と浮遊容量Ｃ0で構成され
る直列共振回路の減衰率を大きくする定数にした構成を
特徴とするＰＷＭインバータ。1. A current is supplied to a motor through a wiring from a voltage-source inverter gate-controlled by a PWM waveform, and sampling is performed at a vertex of a triangular wave which becomes a carrier signal of a PWM waveform from a detection current of a current detector provided on the wiring. a PWM inverter for detecting an output current Te, L-R of the inductance L f and resistor R f in each phase of the wiring
A parallel circuit inserted respectively, the inductance L f and resistor R f of the L-R parallel circuit,
A PWM inverter characterized in that a constant is set to increase a damping rate of a series resonance circuit constituted by the wiring inductance L 0 and the stray capacitance C 0 .
＝√（Ｌ0／Ｃ0）、Ｌ f≧２＊Ｌ0としたことを特徴とす
る請求項１に記載のＰＷＭインバータ。2. The constant of the LR parallel circuit is Rf= Z0
= √ (L0/ C0), L f≧ 2 * L0The feature is that
The PWM inverter according to claim 1.
f側の電流を検出し、インバータの基本波電流成分を抽
出する構成を特徴とする請求項１または２に記載のＰＷ
Ｍインバータ。3. An inductance L of the LR parallel circuit.
3. The PW according to claim 1, wherein a current on the f side is detected and a fundamental current component of the inverter is extracted.
M inverter.
fの鉄心にホール素子を組込み、電流検出器と兼用した
構成を特徴とする請求項３に記載のＰＷＭインバータ。4. An inductance L of the LR parallel circuit.
4. The PWM inverter according to claim 3, wherein a Hall element is incorporated in the iron core of f and also serves as a current detector.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2000281125A JP2002095264A (en) | 2000-09-18 | 2000-09-18 | Pwm inverter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2000281125A JP2002095264A (en) | 2000-09-18 | 2000-09-18 | Pwm inverter |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JP2002095264A true JP2002095264A (en) | 2002-03-29 |
Family
ID=18765830
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP2000281125A Pending JP2002095264A (en) | 2000-09-18 | 2000-09-18 | Pwm inverter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP2002095264A (en) |
Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2005020419A1 (en) * | 2003-08-25 | 2005-03-03 | Mitsubishi Denki Kabushiki Kaisha | Controller for power converter |
| JP2006020430A (en) * | 2004-07-02 | 2006-01-19 | Hitachi Industrial Equipment Systems Co Ltd | Power converter, motor, motor drive system and maintenance method thereof |
| JP2006230169A (en) * | 2005-02-21 | 2006-08-31 | Toshiba Corp | Controller for synchronous machine |
| JP2007124762A (en) * | 2005-10-26 | 2007-05-17 | Fuji Electric Systems Co Ltd | Current detecting circuit in voltage converter |
| JP2010017077A (en) * | 2009-10-19 | 2010-01-21 | Hitachi Industrial Equipment Systems Co Ltd | Motor, motor driving system, and maintenance method of motor driving system |
| CN108684212A (en) * | 2016-08-30 | 2018-10-19 | 富士电机株式会社 | Surge restraint circuit and Driven by inverter motor system |
-
2000
- 2000-09-18 JP JP2000281125A patent/JP2002095264A/en active Pending
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2005020419A1 (en) * | 2003-08-25 | 2005-03-03 | Mitsubishi Denki Kabushiki Kaisha | Controller for power converter |
| US7426122B2 (en) | 2003-08-25 | 2008-09-16 | Mitsubishi Denki Kabushiki Kaisha | Power-converter control apparatus employing pulse width modulation and adjusting duration of a zero-voltage vector |
| JP2006020430A (en) * | 2004-07-02 | 2006-01-19 | Hitachi Industrial Equipment Systems Co Ltd | Power converter, motor, motor drive system and maintenance method thereof |
| US7663337B2 (en) | 2004-07-02 | 2010-02-16 | Hitachi Industrial Equipment System Co. | Frequency converter, motor, motor drive system and maintenance method for motor drive system |
| JP4557616B2 (en) * | 2004-07-02 | 2010-10-06 | 株式会社日立産機システム | Power converter |
| JP2006230169A (en) * | 2005-02-21 | 2006-08-31 | Toshiba Corp | Controller for synchronous machine |
| JP2007124762A (en) * | 2005-10-26 | 2007-05-17 | Fuji Electric Systems Co Ltd | Current detecting circuit in voltage converter |
| JP2010017077A (en) * | 2009-10-19 | 2010-01-21 | Hitachi Industrial Equipment Systems Co Ltd | Motor, motor driving system, and maintenance method of motor driving system |
| JP4558089B2 (en) * | 2009-10-19 | 2010-10-06 | 株式会社日立産機システム | Motor and motor drive system |
| CN108684212A (en) * | 2016-08-30 | 2018-10-19 | 富士电机株式会社 | Surge restraint circuit and Driven by inverter motor system |
| CN108684212B (en) * | 2016-08-30 | 2020-07-21 | 富士电机株式会社 | Surge suppression circuit and inverter drive motor system |
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