JP2001352759A - Pwm rectifier - Google Patents
Pwm rectifierInfo
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- JP2001352759A JP2001352759A JP2000171648A JP2000171648A JP2001352759A JP 2001352759 A JP2001352759 A JP 2001352759A JP 2000171648 A JP2000171648 A JP 2000171648A JP 2000171648 A JP2000171648 A JP 2000171648A JP 2001352759 A JP2001352759 A JP 2001352759A
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- value
- capacitor
- pwm rectifier
- reactor
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Abstract
Description
【発明の詳細な説明】DETAILED DESCRIPTION OF THE INVENTION
【０００１】[0001]
【発明の属する技術分野】この発明は、スイッチングア
ーム複数組を並列接続してなるＰＷＭ整流器と、該ＰＷ
Ｍ整流器の出力の両端に接続される直流コンデンサと、
該直流コンデンサのいずれか一端に接続される直流リア
クトルと、制御回路とから構成されたＰＷＭ整流装置に
関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a PWM rectifier comprising a plurality of sets of switching arms connected in parallel,
A DC capacitor connected across the output of the M rectifier;
The present invention relates to a PWM rectifier including a DC reactor connected to one end of the DC capacitor and a control circuit.
【０００２】[0002]
【従来の技術】図９は、この種のＰＷＭ整流装置の従来
例を示す回路構成図であり、１はスター結線の三相交流
電源、２はＰＷＭ整流装置、３はＰＷＭ整流装置２を直
流電源とする負荷を示す。2. Description of the Related Art FIG. 9 is a circuit diagram showing a conventional example of this type of PWM rectifier. Reference numeral 1 denotes a star-connected three-phase AC power supply; 2, a PWM rectifier; Indicates the load used as the power supply.
【０００３】このＰＷＭ整流装置２は８組のスイッチン
グアームからなるＰＷＭ整流器１１と、交流リアクトル
１２〜１４と、直流コンデンサ１５と、直流リアクトル
１６と、三相交流電源１のＲ相の相電圧（ＶR ）を検出
する交流電圧検出器１７と、三相交流電源１のＳ相の相
電圧（ＶS ）を検出する交流電圧検出器１８と、三相交
流電源１のＴ相の相電圧（ＶT ）を検出する交流電圧検
出器１９と、三相交流電源１のＲ相の相電流（ＩR ）を
検出する交流電流検出器２０と、三相交流電源１のＴ相
の相電流（ＩT ）を検出する交流電流検出器２１と、直
流コンデンサ１５の両端電圧（ＶC ）を検出する直流電
圧検出器２２と、前記検出器１７〜２２それぞれの検出
値に基づいてＰＷＭ整流器１１を構成するそれぞれのＩ
ＧＢＴ（ＲU ，ＲX ，ＲV ，ＲY ，ＳU ，ＳX ，ＳV ，
ＳY ，ＴU ，ＴX ，ＴV，ＴY ）をオン，オフ制御する
制御回路３０とから構成されている。The PWM rectifier 2 includes a PWM rectifier 11 having eight sets of switching arms, AC reactors 12 to 14, a DC capacitor 15, a DC reactor 16, and a phase voltage of the R-phase of the three-phase AC power supply 1 ( V R ), an AC voltage detector 18 for detecting the S- phase voltage (V S ) of the three-phase AC power supply 1, and a T-phase voltage (T S ) of the three-phase AC power supply 1. VT ), an AC current detector 20 for detecting the R- phase current (IR) of the three-phase AC power supply 1, and a T-phase current (T) of the three-phase AC power supply 1. an AC current detector 21 for detecting the I T), a DC voltage detector 22 for detecting the voltage across the DC capacitor 15 (V C), the PWM rectifier 11 based on a detection value of each of the detectors 17 to 22 Each of the constituent I
GBT (R U , R X , R V , R Y , S U , S X , S V ,
S Y , T U , T X , T V , and T Y ).
【０００４】図１０は図９に示した制御回路３０の詳細
回路構成図であり、この制御回路３０には電圧調節器３
１と、極性反転器３２と、ベクトル演算器３３と、２相
／３相変換器３４と、Ｒ相電流調節器３５と、Ｔ相電流
調節器３６と、加算演算器３７〜４０と、キャリア比較
器４１と、ゲート駆動回路４２とを備えている。FIG. 10 is a detailed circuit diagram of the control circuit 30 shown in FIG.
1, a polarity invertor 32, a vector calculator 33, a two-phase / three-phase converter 34, an R-phase current regulator 35, a T-phase current regulator 36, addition operators 37 to 40, a carrier A comparator 41 and a gate drive circuit 42 are provided.
【０００５】図９に示した従来のＰＷＭ整流装置２の動
作を、図１０に示した制御回路３０のいずれも周知の技
術で形成された制御要素を参照しつつ、以下に説明す
る。[0005] The operation of the conventional PWM rectifier 2 shown in FIG. 9 will be described below with reference to control elements formed by well-known techniques in any of the control circuits 30 shown in FIG.
【０００６】このＰＷＭ整流装置２は三相交流電源１の
各相の交流電圧から任意の値の直流電圧に変換して負荷
３に供給し、その際に、三相交流電源１から見た基本波
力率をほぼ「１．０」にすることができる可逆の整流装
置である。The PWM rectifier 2 converts the AC voltage of each phase of the three-phase AC power supply 1 into a DC voltage having an arbitrary value and supplies the DC voltage to the load 3. This is a reversible rectifier capable of reducing the wave power factor to approximately “1.0”.
【０００７】すなわち、直流コンデンサ１５の両端電圧
に対する電圧指令値（ＶC *）と直流電圧検出器２２で検
出した直流コンデンサ１５の両端電圧（ＶC ）との偏差
を零にする調節演算を電圧調節器３１で行ない、電圧調
節器３１で得た調節演算値に極性反転器３２を介するこ
とにより、有効電流指令値を得る。ここで、極性反転器
３２は、後述のＲ相電流調節器３５およびＴ相電流調節
器３６での電流調節演算の際の極性を合わせるために設
けられている。That is, an adjustment operation for zeroing the deviation between the voltage command value (V C * ) for the voltage across the DC capacitor 15 and the voltage (V C ) across the DC capacitor 15 detected by the DC voltage detector 22 is performed by a voltage An effective current command value is obtained by the adjustment operation value obtained by the voltage adjuster 31 via the polarity inverter 32. Here, the polarity inverter 32 is provided in order to match the polarity at the time of the current adjustment calculation in the R-phase current adjuster 35 and the T-phase current adjuster 36 described later.
【０００８】ベクトル演算器３３では一方の入力である
前記有効電流指令値と、他方の入力である無効電流指令
値とのベクトル演算を行ない、２相（例えば、ｄ−ｑ
軸）の電流指令値を得る。このとき、上述の如く、三相
交流電源１から見た基本波力率を「１．０」にするため
に、前記無効電流指令値を「０」に設定している。The vector operation unit 33 performs a vector operation of the effective current command value as one input and the reactive current command value as the other input, and performs two-phase (for example, dq
Axis) current command value. At this time, as described above, the reactive current command value is set to "0" in order to set the fundamental wave power factor viewed from the three-phase AC power supply 1 to "1.0".
【０００９】２相／３相変換器３４では前記２相の電流
指令値から３相の電流指令値を得ているが、この制御回
路３０ではその内、Ｒ相の電流指令値（ＩR *）とＴ相の
電流指令値（ＩT *）とを利用している。[0009] Although the current command value of the two-phase / three-phase converter 34 in the two-phase to obtain a current command value of three-phase, of which the control circuit 30, the current command value of R-phase (I R * ) And the T-phase current command value ( IT * ).
【００１０】Ｒ相電流調節器３５では前記Ｒ相の電流指
令値（ＩR *）と、交流電流検出器２０で検出されたＲ相
の相電流（ＩR ）との偏差を零にする調節演算を行な
い、その演算結果をＲ相の電圧指令値（ＶR *）として出
力する。同様に、Ｔ相電流調節器３６では前記Ｔ相の電
流指令値（ＩT *）と、交流電流検出器２１で検出された
Ｔ相の相電流（ＩT ）との偏差を零にする調節演算を行
ない、その演算結果をＴ相の電圧指令値（ＶT *）として
出力する。また、加算演算器３７では電圧指令値
（ＶR *）と電圧指令値（ＶT *）とからＳ相の電圧指令値
（ＶS *）を得ている。[0010] adjusted R-phase current regulator 35 that the current command value of the R-phase in the (I R *), to zero the deviation between the detected R-phase phase current (I R) in an alternating current detector 20 performs computation, and outputs the result of operation voltage command value of R-phase as (V R *). Similarly, the T-phase current adjuster 36 adjusts the deviation between the T-phase current command value ( IT * ) and the T-phase current ( IT ) detected by the AC current detector 21 to zero. The calculation is performed, and the calculation result is output as a T-phase voltage command value ( VT * ). Further, to obtain voltage command values of S phase (V S *) from the adders 37 in the voltage command value (V R *) a voltage command value (V T *).
【００１１】加算演算器３８では前記Ｒ相の電圧指令値
（ＶR *）と交流電圧検出器１７で検出されたＲ相の相電
圧（ＶR ）との加算演算からＲ相の通流率指令値
（λR ）を得ている。同様に、加算演算器３９では前記
Ｓ相の電圧指令値（ＶS *）と交流電圧検出器１８で検出
されたＳ相の相電圧（ＶS ）との加算演算からＳ相の通
流率指令値（λS ）を得ている。また、加算演算器４０
では前記Ｔ相の電圧指令値（ＶT *）と交流電圧検出器１
９で検出されたＴ相の相電圧（ＶT ）との加算演算から
Ｔ相の通流率指令値（λT ）を得ている。[0011] adding calculator 38 voltage command value of the R phase at (V R *) and an AC voltage detector detected phase voltage of the R phase at 17 (V R) and the duty ratio of the R-phase from the addition operation The command value (λ R ) has been obtained. Similarly, the addition calculator 39 calculates the S-phase conduction ratio from the addition calculation of the S-phase voltage command value (V S * ) and the S-phase phase voltage (V S ) detected by the AC voltage detector 18. The command value (λ S ) has been obtained. Further, the addition arithmetic unit 40
In the above, the T-phase voltage command value (V T * ) and the AC voltage detector 1
The T-phase conduction ratio command value (λ T ) is obtained from the addition operation with the T-phase phase voltage (V T ) detected in 9.
【００１２】キャリア比較器４１では前記通流率指令値
（λR ），通流率指令値（λS ），通流率指令値
（λT ）と、例えば三角波状のキャリアとのＰＷＭ演算
を行ない、これらの演算結果にゲート駆動回路４２を介
することによりＰＷＭ整流器１１を構成するそれぞれの
ＩＧＢＴ（ＲU ，ＲX ，ＲV ，ＲY ，ＳU ，ＳX ，
ＳV，ＳY ，ＴU ，ＴX ，ＴV ，ＴY ）を前記通流率指
令値に対応した通流率λ（λ＝オン期間／（オン期間＋
オフ期間））でオン、又はオフさせている。The carrier comparator 41 performs a PWM operation on the duty ratio command value (λ R ), the duty ratio command value (λ S ), the duty ratio command value (λ T ) and, for example, a triangular carrier. The IGBTs (R U , R X , R V , R Y , S U , S X , and IGBT) constituting the PWM rectifier 11 by passing these calculation results through the gate drive circuit 42.
S V , S Y , T U , T X , T V , T Y ) are converted to a duty ratio λ (λ = ON period / (ON period +
In the off period)), it is turned on or off.
【００１３】[0013]
【発明が解決しようとする課題】図９に示した従来のＰ
ＷＭ整流装置２において、直流リアクトル１６は、例え
ば負荷３に短絡が発生したときにこの短絡電流の電流変
化率（ｄｉ／ｄｔ）によるＰＷＭ整流装置２の破損を防
止するためなどに設けられているが、上述の従来の制御
回路３０では、単に直流コンデンサ１５の両端電圧を所
望の値にする制御を行っていることから、負荷３の電流
の変動に伴って、負荷３の両端電圧が直流リアクトル１
６に起因して、若干変動するという難点があった。The conventional P shown in FIG.
In the WM rectifier 2, the DC reactor 16 is provided, for example, to prevent damage to the PWM rectifier 2 due to a current change rate (di / dt) of the short-circuit current when a short circuit occurs in the load 3. However, in the above-described conventional control circuit 30, since the voltage between both ends of the DC capacitor 15 is simply controlled to a desired value, the voltage between both ends of the load 3 is changed according to the fluctuation of the current of the load 3. 1
6, there was a problem that it fluctuated slightly.
【００１４】この発明の目的は上記問題点を解消し、負
荷の両端電圧の変動を抑制したＰＷＭ整流装置を提供す
ることにある。An object of the present invention is to solve the above problems and to provide a PWM rectifier which suppresses fluctuations in the voltage across the load.
【００１５】[0015]
【課題を解決するための手段】この第１の発明は、スイ
ッチングアーム複数組を並列接続してなるＰＷＭ整流器
と、該ＰＷＭ整流器の出力の両端に接続される直流コン
デンサと、該直流コンデンサのいずれか一端に接続され
る直流リアクトルと、制御回路とから構成されたＰＷＭ
整流装置において、前記制御回路では、前記直流リアク
トルの他端と前記直流コンデンサの他端との間に接続さ
れる負荷への電圧指令値と、前記直流コンデンサの両端
電圧から前記直流リアクトルの電圧降下分を減算した演
算値との偏差を零にする調節演算を行ない、前記調節演
値を有効電流指令値とした電流の調節演算により前記そ
れぞれのスイッチングアームのスイッチング素子をオ
ン，オフ制御することを特徴とする。According to a first aspect of the present invention, there is provided a PWM rectifier comprising a plurality of sets of switching arms connected in parallel, a DC capacitor connected to both ends of an output of the PWM rectifier, and a DC capacitor. PWM comprising a DC reactor connected to one end and a control circuit
In the rectifier, in the control circuit, a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor, and a voltage drop of the DC reactor from a voltage across the DC capacitor. Performing an adjustment operation to reduce the deviation from the operation value obtained by subtracting the minute to zero, and performing on / off control of the switching elements of the respective switching arms by current adjustment operation using the adjustment performance value as an effective current command value. Features.
【００１６】第２の発明は前記ＰＷＭ整流装置におい
て、前記制御回路では、前記直流リアクトルの他端と前
記直流コンデンサの他端との間に接続される負荷への電
圧指令値と、該負荷の両端電圧との偏差を零にする第１
の調節演算を行ない、前記負荷の両端電圧から前記直流
リアクトルの電圧降下分を減算した演算値と、前記第１
の調節演算値との加算演算を行ない、前記加算演算値と
前記直流コンデンサの両端電圧との偏差を零にする第２
の調節演算を行ない、前記第２の調節演算値を有効電流
指令値とした電流の調節演算により前記それぞれのスイ
ッチングアームのスイッチング素子をオン，オフ制御す
ることを特徴とする。According to a second aspect of the present invention, in the PWM rectifier, in the control circuit, a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor; The first to make the deviation from the voltage between both ends zero
And a calculation value obtained by subtracting the voltage drop of the DC reactor from the voltage across the load,
And a second operation for reducing the deviation between the added operation value and the voltage across the DC capacitor to zero.
And performing on / off control of the switching elements of the respective switching arms by a current adjustment operation using the second adjustment operation value as an effective current command value.
【００１７】第３の発明は前記ＰＷＭ整流装置におい
て、前記制御回路では、前記直流リアクトルの他端と前
記直流コンデンサの他端との間に接続される負荷への電
圧指令値と、前記直流コンデンサの両端電圧から前記直
流リアクトルの電圧降下分を減算した演算値との偏差を
零にする調節演算を行ない、前記調節演算値と、前記Ｐ
ＷＭ整流器の出力電力値との加算値を有効電流指令値と
した電流の調節演算により前記それぞれのスイッチング
アームのスイッチング素子をオン，オフ制御することを
特徴とする。According to a third aspect of the present invention, in the PWM rectifier, in the control circuit, a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor; An adjustment operation is performed to make a deviation from an operation value obtained by subtracting the voltage drop of the DC reactor from the voltage between both ends of the DC reactor zero, and the adjustment operation value and the P
The switching element of each of the switching arms is controlled to be on and off by a current adjustment calculation using an added value with the output power value of the WM rectifier as an effective current command value.
【００１８】第４の発明は前記ＰＷＭ整流装置におい
て、前記制御回路では、前記直流リアクトルの他端と前
記直流コンデンサの他端との間に接続される負荷への電
圧指令値と、該負荷の両端電圧との偏差を零にする第１
の調節演算を行ない、前記負荷の両端電圧から前記直流
リアクトルの電圧降下分を減算した演算値と、前記第１
の調節演算値との加算演算を行ない、前記加算演算値と
前記直流コンデンサの両端電圧との偏差を零にする第２
の調節演算を行ない、前記第２の調節演算値と、前記Ｐ
ＷＭ整流器の出力電力値との加算値を有効電流指令値と
した電流の調節演算により前記それぞれのスイッチング
アームのスイッチング素子をオン，オフ制御することを
特徴とする。According to a fourth aspect of the present invention, in the PWM rectifier, in the control circuit, a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor; The first to make the deviation from the voltage between both ends zero
And an operation value obtained by subtracting the voltage drop of the DC reactor from the voltage across the load, and the first
And a second operation for reducing the deviation between the added operation value and the voltage across the DC capacitor to zero.
Of the second adjustment calculation value and P
The switching element of each of the switching arms is controlled to be on and off by a current adjustment calculation using an added value with the output power value of the WM rectifier as an effective current command value.
【００１９】第５の発明は前記ＰＷＭ整流装置におい
て、前記制御回路では、前記直流リアクトルの他端と前
記直流コンデンサの他端との間に接続される負荷への電
圧指令値と、前記直流コンデンサの両端電圧から前記直
流リアクトルの電圧降下分を減算した演算値との偏差を
零にする調節演算を行ない、前記調節演算値を有効電流
指令値とした電流の調節演算により前記それぞれのスイ
ッチングアームのスイッチング素子の通流率指令値を求
め、該それぞれの通流率指令値を前記直流コンデンサの
両端電圧で除算演算し、この除算演算結果を新たな通流
率指令値として前記スイッチングアームのスイッチング
素子をオン，オフ制御することを特徴とする。According to a fifth aspect of the present invention, in the PWM rectifier, in the control circuit, a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor; An adjustment operation is performed to reduce the deviation from an operation value obtained by subtracting the voltage drop of the DC reactor from the voltage between both ends of the switching arm to zero, and the adjustment operation of the respective switching arms is performed by adjusting the current using the adjustment operation value as an effective current command value. A duty ratio command value of a switching element is obtained, each of the duty ratio command values is divided by a voltage across the DC capacitor, and the result of the division operation is set as a new duty ratio command value as a switching element of the switching arm. Is turned on and off.
【００２０】第６の発明は前記ＰＷＭ整流装置におい
て、前記制御回路では、前記直流リアクトルの他端と前
記直流コンデンサの他端との間に接続される負荷への電
圧指令値と、該負荷の両端電圧との偏差を零にする第１
の調節演算を行ない、前記負荷の両端電圧から前記直流
リアクトルの電圧降下分を減算した演算値と、前記第１
の調節演算値との加算演算を行ない、前記加算演算値と
前記直流コンデンサの両端電圧との偏差を零にする第２
の調節演算を行ない、前記第２の調節演算値を有効電流
指令値とした電流の調節演算により前記それぞれのスイ
ッチングアームのスイッチング素子の通流率指令値を求
め、該それぞれの通流率指令値を前記直流コンデンサの
両端電圧で除算演算し、この除算演算結果を新たな通流
率指令値として前記スイッチングアームのスイッチング
素子をオン，オフ制御することを特徴とする。According to a sixth aspect of the present invention, in the PWM rectifier, in the control circuit, a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor; The first to make the deviation from the voltage between both ends zero
And an operation value obtained by subtracting the voltage drop of the DC reactor from the voltage across the load, and the first
And a second operation for reducing the deviation between the added operation value and the voltage across the DC capacitor to zero.
Of the switching element of each of the switching arms by current adjustment calculation using the second adjustment calculation value as an effective current command value, and calculating the respective duty ratio command values. Is divided by the voltage across the DC capacitor, and the result of the division operation is used as a new duty ratio command value to turn on and off the switching element of the switching arm.
【００２１】第７の発明は前記ＰＷＭ整流装置におい
て、前記制御回路では、前記直流リアクトルの他端と前
記直流コンデンサの他端との間に接続される負荷への電
圧指令値と、前記直流コンデンサの両端電圧から前記直
流リアクトルの電圧降下分を減算した演算値との偏差を
零にする調節演算を行ない、前記調節演算値と、前記Ｐ
ＷＭ整流器の出力電力値との加算値を有効電流指令値と
した電流の調節演算により前記それぞれのスイッチング
アームのスイッチング素子の通流率指令値を求め、該そ
れぞれの通流率指令値を前記直流コンデンサの両端電圧
で除算演算し、この除算演算結果を新たな通流率指令値
として前記スイッチングアームのスイッチング素子をオ
ン，オフ制御することを特徴とする。According to a seventh aspect of the present invention, in the PWM rectifier, in the control circuit, a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor; An adjustment operation is performed to make a deviation from an operation value obtained by subtracting the voltage drop of the DC reactor from the voltage between both ends of the DC reactor zero, and the adjustment operation value and the P
A duty ratio command value of the switching element of each of the switching arms is obtained by a current adjustment calculation using an added value with the output power value of the WM rectifier as an effective current command value. A division operation is performed by a voltage between both ends of the capacitor, and the result of the division operation is set as a new duty ratio command value to control on / off of the switching element of the switching arm.
【００２２】第８の発明は前記ＰＷＭ整流装置におい
て、前記制御回路では、前記直流リアクトルの他端と前
記直流コンデンサの他端との間に接続される負荷への電
圧指令値と、該負荷の両端電圧との偏差を零にする第１
の調節演算を行ない、前記負荷の両端電圧から前記直流
リアクトルの電圧降下分を減算した演算値と、前記第１
の調節演算値との加算演算を行ない、前記加算演算値と
前記直流コンデンサの両端電圧との偏差を零にする第２
の調節演算を行ない、前記第２の調節演算値と、前記Ｐ
ＷＭ整流器の出力電力値との加算値を有効電流指令値と
した電流の調節演算により前記それぞれのスイッチング
アームのスイッチング素子の通流率指令値を求め、該そ
れぞれの通流率指令値を前記直流コンデンサの両端電圧
で除算演算し、この除算演算結果を新たな通流率指令値
として前記スイッチングアームのスイッチング素子をオ
ン，オフ制御することを特徴とする。According to an eighth aspect of the present invention, in the PWM rectifier, in the control circuit, a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor; The first to make the deviation from the voltage between both ends zero
And an operation value obtained by subtracting the voltage drop of the DC reactor from the voltage across the load, and the first
And a second operation for reducing the deviation between the added operation value and the voltage across the DC capacitor to zero.
Of the second adjustment calculation value and P
A duty ratio command value of the switching element of each of the switching arms is obtained by a current adjustment calculation using an added value with the output power value of the WM rectifier as an effective current command value. A division operation is performed by a voltage between both ends of the capacitor, and the result of the division operation is set as a new duty ratio command value to control on / off of the switching element of the switching arm.
【００２３】この発明によれば、従来の制御回路に前記
直流リアクトルの電圧降下分を補償する制御機能を付加
することにより、前記負荷の電流の変動に伴う該負荷の
両端電圧の変動を抑制している。According to the present invention, the control function for compensating for the voltage drop of the DC reactor is added to the conventional control circuit, thereby suppressing the fluctuation of the voltage between both ends of the load due to the fluctuation of the load current. ing.
【００２４】[0024]
【発明の実施の形態】図１はこの発明の第１の実施の形
態を示すＰＷＭ整流装置の回路構成図であり、図９に示
した従来例回路と同一機能を有するものには同一符号を
付している。FIG. 1 is a circuit diagram of a PWM rectifier according to a first embodiment of the present invention, in which components having the same functions as those of the conventional circuit shown in FIG. It is attached.
【００２５】すなわち、図１に示した回路構成が図９に
示した回路構成と異なる点は、直流リアクトル１６から
負荷３への経路に負荷３の電流（ＩL ）を検出する直流
電流検出器２３が挿設され、また、従来の制御回路３０
に代えて制御回路５０，６０，７０のいずれかを備えて
いることである。That is, the point that the circuit configuration shown in FIG. 1 is different from the circuit configuration shown in FIG. 9 is that a DC current detector for detecting a current (I L ) of the load 3 in a path from the DC reactor 16 to the load 3. 23, and the conventional control circuit 30
Instead of the control circuit 50, 60, or 70.
【００２６】図２は、この発明の第１の実施例としての
図１に示した制御回路５０の詳細回路構成図であり、図
１０に示した従来例回路と同一機能を有するものには同
一符号を付して、ここでは重複する説明を省略する。FIG. 2 is a detailed circuit diagram of the control circuit 50 shown in FIG. 1 as a first embodiment of the present invention. The same circuit as that of the conventional circuit shown in FIG. The reference numerals are attached, and the duplicate description is omitted here.
【００２７】すなわち、図２に示した制御回路５０が図
１０に示した制御回路３０と異なる点は、電圧調節器３
１に代えて、電圧降下演算器５１と、加算演算器５２
と、電圧調節器５３とを備えていることである。That is, the difference between the control circuit 50 shown in FIG. 2 and the control circuit 30 shown in FIG.
1, a voltage drop calculator 51 and an addition calculator 52
And a voltage regulator 53.
【００２８】先ず、電圧降下演算器５１では直流電流検
出器２３で得られる検出値（ＩL）を負荷３に流入する
方向を正極性として、直流リアクトル１６のインダクタ
ンス分を「Ｌ」とし、抵抗分を「Ｒ」とすると、 直流リアクトル１６の両端電圧＝Ｌ・〔ｄ（ＩL ）／ｄ
ｔ〕＋Ｒ・ＩL で表される電圧降下分を求めている。First, in the voltage drop calculator 51, the direction in which the detection value (I L ) obtained by the DC current detector 23 flows into the load 3 is set to a positive polarity, the inductance of the DC reactor 16 is set to “L”, and the resistance is set to “L”. Assuming that the minute is “R”, the voltage across the DC reactor 16 = L · [d (I L ) / d
seeking a voltage drop represented by t] + R · I L.
【００２９】従って、加算演算器５２では直流電圧検出
器２２で得られた検出値（ＶC ）から前記電圧降下分を
減算した負荷３の両端電圧の演算値を求めている。Therefore, the addition calculator 52 calculates the calculated value of the voltage across the load 3 by subtracting the voltage drop from the detection value (V C ) obtained by the DC voltage detector 22.
【００３０】さらに、電圧調節器５３は負荷３の電圧調
節動作を行なうべく、負荷３の両端電圧の指令値
（ＶL *）と前記演算値との偏差を零にする調節演算を行
ない、この調節演算結果に極性反転器３２を介すること
により、ベクトル演算器３３への有効電流指令値を得て
いる。Further, the voltage adjuster 53 performs an adjustment operation to make the deviation between the command value (V L * ) of the voltage between both ends of the load 3 and the operation value zero in order to perform the voltage adjustment operation of the load 3. An effective current command value to the vector calculator 33 is obtained by passing the adjustment calculation result through the polarity inverter 32.
【００３１】その結果、この制御回路５０によれば、負
荷３の電流（ＩL ）の変動に伴い、直流リアクトル１６
に起因する負荷３の両端電圧の変動を、効果的に抑制す
ることができる。[0031] Consequently, according to the control circuit 50, along with the variation of the load 3 of the current (I L), DC reactor 16
The fluctuation of the voltage between both ends of the load 3 due to the above can be effectively suppressed.
【００３２】図３は、この発明の第２の実施例としての
図１に示した制御回路６０の詳細回路構成図であり、図
２に示した実施例回路と同一機能を有するものには同一
符号を付して、ここでは重複する説明を省略する。FIG. 3 is a detailed circuit configuration diagram of a control circuit 60 shown in FIG. 1 as a second embodiment of the present invention, and those having the same functions as those of the embodiment circuit shown in FIG. The reference numerals are attached, and the duplicate description is omitted here.
【００３３】すなわち、図３に示した制御回路６０が図
２に示した制御回路５０と異なる点は、負荷電力演算器
６１と、加算演算器６２とが付加されていることであ
る。That is, the control circuit 60 shown in FIG. 3 differs from the control circuit 50 shown in FIG. 2 in that a load power calculator 61 and an addition calculator 62 are added.
【００３４】負荷電力演算器６１では直流電圧検出器２
２で得られた検出値（ＶC ）と、直流電流検出器２３で
得られた検出値（ＩL ）とを乗算演算することにより、
ＰＷＭ整流器１１が出力電力の瞬時値を求めている。The load power calculator 61 includes a DC voltage detector 2
2 and the detection value (I L ) obtained by the DC current detector 23 by multiplying the detection value (V C ) obtained in
The PWM rectifier 11 determines the instantaneous value of the output power.
【００３５】従って、前述の電圧調節器５３の調節演算
結果と前記出力電力の瞬時値とを加算演算器６２で加算
し、この加算値に極性反転器３２を介することにより、
ベクトル演算器３３の有効電流指令値を得ている。Therefore, the result of the adjustment operation of the voltage adjuster 53 and the instantaneous value of the output power are added by the addition operation unit 62, and the added value is passed through the polarity inverter 32.
The effective current command value of the vector calculator 33 is obtained.
【００３６】その結果、この制御回路６０によれば、負
荷３の電流（ＩL ）の変動に伴い、直流リアクトル１６
に起因する負荷３の両端電圧の変動を、よりダイナミッ
クに抑制することができる。As a result, according to the control circuit 60, the DC reactor 16 is controlled by the fluctuation of the current (I L ) of the load 3.
, The fluctuation of the voltage between both ends of the load 3 can be more dynamically suppressed.
【００３７】図４は、この発明の第３の実施例としての
図１に示した制御回路７０の詳細回路構成図であり、図
２に示した実施例回路と同一機能を有するものには同一
符号を付して、ここでは重複する説明を省略する。FIG. 4 is a detailed circuit configuration diagram of a control circuit 70 shown in FIG. 1 as a third embodiment of the present invention. The same circuit as that of the embodiment shown in FIG. The reference numerals are attached, and the duplicate description is omitted here.
【００３８】すなわち、図４に示した制御回路７０が図
２に示した制御回路５０と異なる点は、除算演算器７１
〜７３が付加されていることである。That is, the difference between the control circuit 70 shown in FIG. 4 and the control circuit 50 shown in FIG.
To 73 are added.
【００３９】除算演算器７１では加算演算器３８で得ら
れるＲ相の通流率指令値（λR ）を直流電圧検出器２２
で得られる検出値（ＶC ）で除算演算し、この演算値を
キャリア比較４１への新たなＲ相の通流率指令値として
いる。同様に、除算演算器７２では加算演算器３９で得
られるＳ相の通流率指令値（λS ）を前記検出値
（Ｖ C ）で除算演算し、この演算値をキャリア比較４１
への新たなＳ相の通流率指令値としている。また、除算
演算器７３では加算演算器４０で得られるＴ相の通流率
指令値（λT ）を前記検出値（ＶC ）で除算演算し、こ
の演算値をキャリア比較４１への新たなＴ相の通流率指
令値としている。The division operation unit 71 obtains the value obtained by the addition operation unit 38.
R-phase duty ratio command value (λR) To the DC voltage detector 22
The detection value (VC) And divide the result by
As a new R-phase duty ratio command value for carrier comparison 41
I have. Similarly, the division operation unit 72 obtains the value obtained by the addition operation unit 39.
S phase duty ratio command value (λS) Is the detected value
(V C), And the calculated value is compared with the carrier comparison 41.
To the new S-phase conduction ratio command value. Also division
In the operation unit 73, the conduction ratio of the T phase obtained by the addition operation unit 40
Command value (λT) With the detected value (VC).
The calculated value of is used as a new conductivity index of the T phase to the carrier comparison 41.
It has been set as the limit price.
【００４０】その結果、この制御回路７０によれば、コ
ンデンサ１５の両端電圧の変動をフイードフォワード的
に補正しつつ、負荷３の電流（ＩL ）の変動に伴い、直
流リアクトル１６に起因する負荷３の両端電圧の変動
を、より高速に抑制することができる。As a result, according to the control circuit 70, the fluctuation of the voltage across the capacitor 15 is corrected in a feed-forward manner, and the fluctuation of the current (I L ) of the load 3 is caused by the DC reactor 16. The fluctuation of the voltage between both ends of the load 3 can be suppressed more quickly.
【００４１】図５はこの発明の第２の実施の形態を示す
ＰＷＭ整流装置の回路構成図であり、図９に示した従来
例回路と同一機能を有するものには同一符号を付してい
る。FIG. 5 is a circuit diagram of a PWM rectifier according to a second embodiment of the present invention, in which components having the same functions as those of the conventional circuit shown in FIG. .
【００４２】すなわち、図５に示した回路構成が図９に
示した回路構成と異なる点は、直流リアクトル１６から
負荷３への経路に負荷３の電流（ＩL ）を検出する直流
電流検出器２３が挿設され、また、負荷３の両端電圧
（ＶL ）を検出する直流電圧検出器２４が付加され、従
来の制御回路３０に代えて制御回路８０を備えているこ
とである。That is, the circuit configuration shown in FIG. 5 is different from the circuit configuration shown in FIG. 9 in that a DC current detector for detecting a current (I L ) of load 3 in a path from DC reactor 16 to load 3. 23, a DC voltage detector 24 for detecting the voltage (V L ) across the load 3 is added, and a control circuit 80 is provided instead of the conventional control circuit 30.
【００４３】図６は、この発明の第４の実施例としての
図５に示した制御回路８０の詳細回路構成図であり、図
２に示した実施例回路と同一機能を有するものには同一
符号を付して、ここでは重複する説明を省略する。FIG. 6 is a detailed circuit diagram of a control circuit 80 shown in FIG. 5 according to a fourth embodiment of the present invention. The same circuit as that of the embodiment shown in FIG. The reference numerals are attached, and the duplicate description is omitted here.
【００４４】すなわち、図６に示した制御回路８０が図
２に示した制御回路５０と異なる点は、電圧調節器５３
に代えて、直流コンデンサ１５の電圧調節動作を行う従
来の電圧調節器３１が用いられ、さらに、電圧調節器８
１と、加算演算器８２とが付加されていることである。That is, the difference between the control circuit 80 shown in FIG. 6 and the control circuit 50 shown in FIG.
Is replaced with a conventional voltage regulator 31 for performing a voltage regulating operation of the DC capacitor 15,
1 and an adder 82 are added.
【００４５】先述の電圧調節器５３と同等の制御定数を
有する電圧調節器８１では負荷３への電圧指令値
（ＶL *）と直流電圧検出器２４で得られる検出値
（ＶL ）との偏差を零にする調節演算を行ない、この調
節演算値と前記検出値（ＶL ）との加算と、この加算値
から電圧降下演算器５１の演算値を減算する加算演算器
８２により、直流コンデンサ１６の両端電圧の指令値
（演算値）が得られる。In the voltage regulator 81 having the same control constant as the voltage regulator 53 described above, the voltage command value (V L * ) to the load 3 and the detection value (V L ) obtained by the DC voltage detector 24 are calculated. An adjustment operation for reducing the deviation to zero is performed. The addition of the adjustment operation value and the detection value (V L ) and the addition operation unit 82 for subtracting the operation value of the voltage drop operation unit 51 from the addition value result in a DC capacitor. Thus, a command value (computed value) of the voltage between both ends is obtained.
【００４６】従って、電圧調節器３１では前記指令値
（演算値）と直流電圧検出器２２で得られる検出値（Ｖ
C ）との偏差を零にする調節演算を行っている。Accordingly, in the voltage regulator 31, the command value (calculated value) and the detection value (V
C ) An adjustment operation is performed to make the deviation from zero.
【００４７】その結果、この制御回路８０によれば、負
荷３の電流（ＩL ）の変動に伴い、直流リアクトル１６
に起因する負荷３の両端電圧の変動を効果的に抑制しつ
つ、電圧調節器８１により定常的な負荷３の両端電圧
を、ほぼ一定値に維持することができる。As a result, according to the control circuit 80, the DC reactor 16 is controlled by the fluctuation of the current (I L ) of the load 3.
, The voltage regulator 81 can maintain the steady-state voltage across the load 3 at a substantially constant value while effectively suppressing fluctuations in the voltage across the load 3 due to the above.
【００４８】このとき、電圧調節器８１の応答速度は電
圧調節器３１の応答速度に比して遅く設定することが、
電圧調節器８１と電圧調節器３１との間の制御干渉を防
ぐために有効である。At this time, the response speed of the voltage regulator 81 may be set lower than the response speed of the voltage regulator 31.
This is effective for preventing control interference between the voltage regulator 81 and the voltage regulator 31.
【００４９】図７はこの発明の第３の実施の形態を示す
ＰＷＭ整流装置の回路構成図であり、図９に示した従来
例回路と同一機能を有するものには同一符号を付してい
る。FIG. 7 is a circuit diagram of a PWM rectifier according to a third embodiment of the present invention, in which components having the same functions as those of the conventional circuit shown in FIG. .
【００５０】すなわち、図７に示した回路構成が図９に
示した回路構成と異なる点は、ＰＷＭ整流器２５として
３組のスイッチングアームから構成され、直流リアクト
ル１６から負荷３への経路に負荷３の電流（ＩL ）を検
出する直流電流検出器２３が挿設され、また、従来の交
流電圧検出器１７〜１９に代えて、Ｒ−Ｓ相間の線間電
圧（ＶRS）を検出する交流電圧検出器２６と、Ｓ−Ｔ相
間の線間電圧（ＶST）を検出する交流電圧検出器２７
と、Ｔ−Ｒ相間の線間電圧（ＶTR）を検出する交流電圧
検出器２８と、制御回路３０に代えて制御回路９０を備
えていることである。また、デルタ結線の三相交流電源
６がこのＰＷＭ整流装置７への入力電源になっている。That is, the circuit configuration shown in FIG. 7 is different from the circuit configuration shown in FIG. 9 in that the PWM rectifier 25 is composed of three sets of switching arms, and the load 3 is provided on the path from the DC reactor 16 to the load 3. A DC current detector 23 for detecting the current (I L ) is inserted, and instead of the conventional AC voltage detectors 17 to 19, an AC for detecting a line voltage (V RS ) between the R and S phases is provided. A voltage detector 26 and an AC voltage detector 27 for detecting a line voltage (V ST ) between the ST and T phases.
And an AC voltage detector 28 for detecting a line voltage (V TR ) between the T and R phases, and a control circuit 90 in place of the control circuit 30. The delta-connected three-phase AC power supply 6 is the input power supply to the PWM rectifier 7.
【００５１】図８は、この発明の第５の実施例としての
図７に示した制御回路９０の詳細回路構成図であり、図
２に示した実施例回路と同一機能を有するものには同一
符号を付して、ここでは重複する説明を省略する。FIG. 8 is a detailed circuit configuration diagram of a control circuit 90 shown in FIG. 7 as a fifth embodiment of the present invention, and the same circuit having the same function as the embodiment circuit shown in FIG. The reference numerals are attached, and the duplicate description is omitted here.
【００５２】すなわち、図８に示した制御回路９０が図
２に示した制御回路５０と異なる点は、三相交流電源６
のそれぞれの線間電圧をそれぞれの相電圧に変換する相
電圧演算器９１が付加されていることである。That is, the control circuit 90 shown in FIG. 8 is different from the control circuit 50 shown in FIG.
Is added to the phase voltage calculator 91 for converting the respective line voltages into the respective phase voltages.
【００５３】なお、図示しないが図７に示した主回路構
成においても、先述の制御回路６０，７０，８０のいず
れかの制御機能を付加することができる。Although not shown, any of the control functions of the control circuits 60, 70, and 80 can be added to the main circuit configuration shown in FIG.
【００５４】[0054]
【発明の効果】この発明によれば、従来の制御回路に直
流リアクトルの電圧降下分を補償する制御機能を付加す
ることにより、負荷の電流の変動に伴う該負荷の両端電
圧の変動を抑制し、負荷短絡などに伴うＰＷＭ整流装置
の損傷を防止した動作信頼性の高いＰＷＭ整流装置を提
供することができる。According to the present invention, by adding a control function for compensating for the voltage drop of the DC reactor to the conventional control circuit, the fluctuation of the voltage across the load due to the fluctuation of the load current can be suppressed. In addition, it is possible to provide a highly reliable PWM rectifier that prevents damage to the PWM rectifier due to a load short circuit or the like.
【図１】この発明の第１の実施の形態を示すＰＷＭ整流
装置の回路構成図FIG. 1 is a circuit configuration diagram of a PWM rectifier showing a first embodiment of the present invention.
【図２】この発明の第１の実施例を示す図１の部分詳細
回路構成図FIG. 2 is a partial detailed circuit configuration diagram of FIG. 1 showing a first embodiment of the present invention;
【図３】この発明の第２の実施例を示す図１の部分詳細
回路構成図FIG. 3 is a partially detailed circuit configuration diagram of FIG. 1 showing a second embodiment of the present invention;
【図４】この発明の第３の実施例を示す図１の部分詳細
回路構成図FIG. 4 is a partial detailed circuit configuration diagram of FIG. 1 showing a third embodiment of the present invention;
【図５】この発明の第２の実施の形態を示すＰＷＭ整流
装置の回路構成図FIG. 5 is a circuit configuration diagram of a PWM rectifier showing a second embodiment of the present invention.
【図６】この発明の第４の実施例を示す図５の部分詳細
回路構成図FIG. 6 is a partial detailed circuit configuration diagram of FIG. 5 showing a fourth embodiment of the present invention;
【図７】この発明の第３の実施の形態を示すＰＷＭ整流
装置の回路構成図FIG. 7 is a circuit configuration diagram of a PWM rectifier showing a third embodiment of the present invention.
【図８】この発明の第５の実施例を示す図７の部分詳細
回路構成図FIG. 8 is a partial detailed circuit configuration diagram of FIG. 7 showing a fifth embodiment of the present invention.
【図９】従来例を示すＰＷＭ整流装置の回路構成図FIG. 9 is a circuit configuration diagram of a PWM rectifier showing a conventional example.
【図１０】図９の部分詳細回路構成図FIG. 10 is a partial detailed circuit configuration diagram of FIG. 9;
１…三相交流電源、２…ＰＷＭ整流装置、３…負荷、
４，５…ＰＷＭ整流装置、６…三相交流電源、７…ＰＷ
Ｍ整流装置、１１…ＰＷＭ整流器、１２〜１４…交流リ
アクトル、１５…直流コンデンサ、１６…直流リアクト
ル、１７〜１９…交流電圧検出器、２０，２１…交流電
流検出器、２２…直流電圧検出器、２３…直流電流検出
器、２４…直流電圧検出器、２５…ＰＷＭ整流器、２６
〜２８…交流電圧検出器、３０…制御回路、３１…電圧
調節器、３２…極性反転器、３３…ベクトル演算器、３
４…２相／３相変換器、３５…Ｒ相電流調節器、３６…
Ｓ相電流調節器、３７〜４０…加算演算器、４１…キャ
リア比較器、４２…ゲート駆動回路、５０…制御回路、
５１…電圧降下演算器、５２…加算演算器、５３…電圧
調節器、６０…制御回路、６１…乗算演算器、６２…加
算演算器、７０…制御回路、７１〜７３…除算演算器、
８０…制御回路、８１…電圧調節器、８２…加算演算
器、９０…制御回路、９１…相電圧演算器。1 ... three-phase AC power supply, 2 ... PWM rectifier, 3 ... load,
4, 5 PWM rectifier, 6 three-phase AC power supply, 7 PWM
M rectifier, 11 PWM rectifier, 12-14 AC reactor, 15 DC capacitor, 16 DC reactor, 17-19 AC voltage detector, 20, 21 AC current detector, 22 DC voltage detector , 23 ... DC current detector, 24 ... DC voltage detector, 25 ... PWM rectifier, 26
~ 28 ... AC voltage detector, 30 ... Control circuit, 31 ... Voltage regulator, 32 ... Polarity inverter, 33 ... Vector calculator, 3
4 ... 2 phase / 3 phase converter, 35 ... R phase current regulator, 36 ...
S-phase current controller, 37 to 40: addition arithmetic unit, 41: carrier comparator, 42: gate drive circuit, 50: control circuit,
51: voltage drop calculator, 52: addition calculator, 53: voltage regulator, 60: control circuit, 61: multiplication calculator, 62: addition calculator, 70: control circuit, 71 to 73: division calculator,
80: control circuit, 81: voltage regulator, 82: addition operator, 90: control circuit, 91: phase voltage operator.
Claims (8)
てなるＰＷＭ整流器と、該ＰＷＭ整流器の出力の両端に
接続される直流コンデンサと、該直流コンデンサのいず
れか一端に接続される直流リアクトルと、制御回路とか
ら構成されたＰＷＭ整流装置において、 前記制御回路では、 前記直流リアクトルの他端と前記直流コンデンサの他端
との間に接続される負荷への電圧指令値と、前記直流コ
ンデンサの両端電圧から前記直流リアクトルの電圧降下
分を減算した演算値との偏差を零にする調節演算を行な
い、 前記調節演値を有効電流指令値とした電流の調節演算に
より前記それぞれのスイッチングアームのスイッチング
素子をオン，オフ制御することを特徴とするＰＷＭ整流
装置。1. A PWM rectifier comprising a plurality of sets of switching arms connected in parallel, a DC capacitor connected to both ends of an output of the PWM rectifier, a DC reactor connected to one end of the DC capacitor, and a control unit. In the PWM rectifier, the control circuit includes: a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor; and a voltage across the DC capacitor. Performing an adjustment operation to reduce the deviation from the operation value obtained by subtracting the voltage drop of the DC reactor from the control element to zero, and performing the adjustment operation of the current using the adjustment performance value as an effective current command value to switch the switching element of each switching arm. A PWM rectifier characterized by on / off control.
てなるＰＷＭ整流器と、該ＰＷＭ整流器の出力の両端に
接続される直流コンデンサと、該直流コンデンサのいず
れか一端に接続される直流リアクトルと、制御回路とか
ら構成されたＰＷＭ整流装置において、 前記制御回路では、 前記直流リアクトルの他端と前記直流コンデンサの他端
との間に接続される負荷への電圧指令値と、該負荷の両
端電圧との偏差を零にする第１の調節演算を行ない、 前記負荷の両端電圧から前記直流リアクトルの電圧降下
分を減算した演算値と、前記第１の調節演算値との加算
演算を行ない、 前記加算演算値と前記直流コンデンサの両端電圧との偏
差を零にする第２の調節演算を行ない、 前記第２の調節演算値を有効電流指令値とした電流の調
節演算により前記それぞれのスイッチングアームのスイ
ッチング素子をオン，オフ制御することを特徴とするＰ
ＷＭ整流装置。2. A PWM rectifier comprising a plurality of sets of switching arms connected in parallel, a DC capacitor connected to both ends of an output of the PWM rectifier, a DC reactor connected to one end of the DC capacitor, and a control unit. In the PWM rectifier configured with a circuit, in the control circuit, a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor, a voltage across the load, Performs a first adjustment operation to reduce the deviation of the load to zero, performs an addition operation of an operation value obtained by subtracting the voltage drop of the DC reactor from the voltage across the load, and the first adjustment operation value, and performs the addition. A second adjustment operation is performed to make the deviation between the operation value and the voltage between both ends of the DC capacitor zero, and a current adjustment operation is performed by using the second adjustment operation value as an effective current command value. Serial turns on the switching element of the respective switching arms, P, characterized by off control
WM rectifier.
てなるＰＷＭ整流器と、該ＰＷＭ整流器の出力の両端に
接続される直流コンデンサと、該直流コンデンサのいず
れか一端に接続される直流リアクトルと、制御回路とか
ら構成されたＰＷＭ整流装置において、 前記制御回路では、 前記直流リアクトルの他端と前記直流コンデンサの他端
との間に接続される負荷への電圧指令値と、前記直流コ
ンデンサの両端電圧から前記直流リアクトルの電圧降下
分を減算した演算値との偏差を零にする調節演算を行な
い、 前記調節演算値と、前記ＰＷＭ整流器の出力電力値との
加算値を有効電流指令値とした電流の調節演算により前
記それぞれのスイッチングアームのスイッチング素子を
オン，オフ制御することを特徴とするＰＷＭ整流装置。3. A PWM rectifier comprising a plurality of sets of switching arms connected in parallel, a DC capacitor connected to both ends of an output of the PWM rectifier, a DC reactor connected to one end of the DC capacitor, and a control unit. In the PWM rectifier, the control circuit includes: a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor; and a voltage across the DC capacitor. And performing an adjustment operation to reduce the deviation from the operation value obtained by subtracting the voltage drop of the DC reactor from the current value to zero, and setting a current obtained by adding an adjustment value of the adjustment operation value and an output power value of the PWM rectifier to an effective current command value. A switching element of each of the switching arms is controlled to be turned on and off by an adjustment operation of the PWM rectifier.
てなるＰＷＭ整流器と、該ＰＷＭ整流器の出力の両端に
接続される直流コンデンサと、該直流コンデンサのいず
れか一端に接続される直流リアクトルと、制御回路とか
ら構成されたＰＷＭ整流装置において、 前記制御回路では、 前記直流リアクトルの他端と前記直流コンデンサの他端
との間に接続される負荷への電圧指令値と、該負荷の両
端電圧との偏差を零にする第１の調節演算を行ない、 前記負荷の両端電圧から前記直流リアクトルの電圧降下
分を減算した演算値と、前記第１の調節演算値との加算
演算を行ない、 前記加算演算値と前記直流コンデンサの両端電圧との偏
差を零にする第２の調節演算を行ない、 前記第２の調節演算値と、前記ＰＷＭ整流器の出力電力
値との加算値を有効電流指令値とした電流の調節演算に
より前記それぞれのスイッチングアームのスイッチング
素子をオン，オフ制御することを特徴とするＰＷＭ整流
装置。4. A PWM rectifier comprising a plurality of sets of switching arms connected in parallel, a DC capacitor connected to both ends of an output of the PWM rectifier, a DC reactor connected to one end of the DC capacitor, and a control unit. In the PWM rectifier configured with a circuit, in the control circuit, a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor, a voltage across the load, Performs a first adjustment operation to reduce the deviation of the load to zero, and performs an addition operation of an operation value obtained by subtracting a voltage drop of the DC reactor from a voltage across the load and the first adjustment operation value. A second adjustment operation is performed to make a deviation between an operation value and a voltage between both ends of the DC capacitor zero, and an added value of the second adjustment operation value and an output power value of the PWM rectifier is performed. Turning on the switching element of the respective switching arms by adjusting operation of current and active current command value, PWM rectifier, characterized in that the off control.
てなるＰＷＭ整流器と、該ＰＷＭ整流器の出力の両端に
接続される直流コンデンサと、該直流コンデンサのいず
れか一端に接続される直流リアクトルと、制御回路とか
ら構成されたＰＷＭ整流装置において、 前記制御回路では、 前記直流リアクトルの他端と前記直流コンデンサの他端
との間に接続される負荷への電圧指令値と、前記直流コ
ンデンサの両端電圧から前記直流リアクトルの電圧降下
分を減算した演算値との偏差を零にする調節演算を行な
い、 前記調節演算値を有効電流指令値とした電流の調節演算
により前記それぞれのスイッチングアームのスイッチン
グ素子の通流率指令値を求め、該それぞれの通流率指令
値を前記直流コンデンサの両端電圧で除算演算し、 この除算演算結果を新たな通流率指令値として前記スイ
ッチングアームのスイッチング素子をオン，オフ制御す
ることを特徴とするＰＷＭ整流装置。5. A PWM rectifier comprising a plurality of sets of switching arms connected in parallel, a DC capacitor connected to both ends of an output of the PWM rectifier, a DC reactor connected to one end of the DC capacitor, and a control unit. In the PWM rectifier, the control circuit includes: a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor; and a voltage across the DC capacitor. Performing an adjustment operation to reduce the deviation from the operation value obtained by subtracting the voltage drop of the DC reactor from the current value to zero, and performing the adjustment operation of the current using the adjustment operation value as an effective current command value, for the switching element of each switching arm. A duty ratio command value is obtained, and each of the duty ratio command values is divided by a voltage across the DC capacitor to calculate the duty ratio command value. The results on the switching elements of the switching arm as a new conduction ratio command value, PWM rectifier, characterized in that the off control.
てなるＰＷＭ整流器と、該ＰＷＭ整流器の出力の両端に
接続される直流コンデンサと、該直流コンデンサのいず
れか一端に接続される直流リアクトルと、制御回路とか
ら構成されたＰＷＭ整流装置において、 前記制御回路では、 前記直流リアクトルの他端と前記直流コンデンサの他端
との間に接続される負荷への電圧指令値と、該負荷の両
端電圧との偏差を零にする第１の調節演算を行ない、 前記負荷の両端電圧から前記直流リアクトルの電圧降下
分を減算した演算値と、前記第１の調節演算値との加算
演算を行ない、 前記加算演算値と前記直流コンデンサの両端電圧との偏
差を零にする第２の調節演算を行ない、 前記第２の調節演算値を有効電流指令値とした電流の調
節演算により前記それぞれのスイッチングアームのスイ
ッチング素子の通流率指令値を求め、該それぞれの通流
率指令値を前記直流コンデンサの両端電圧で除算演算
し、 この除算演算結果を新たな通流率指令値として前記スイ
ッチングアームのスイッチング素子をオン，オフ制御す
ることを特徴とするＰＷＭ整流装置。6. A PWM rectifier comprising a plurality of sets of switching arms connected in parallel, a DC capacitor connected to both ends of an output of the PWM rectifier, a DC reactor connected to one end of the DC capacitor, and a control unit. In the PWM rectifier configured with a circuit, in the control circuit, a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor, a voltage across the load, Performs a first adjustment operation to reduce the deviation of the load to zero, and performs an addition operation of an operation value obtained by subtracting a voltage drop of the DC reactor from a voltage across the load and the first adjustment operation value. A second adjustment operation is performed to make the deviation between the operation value and the voltage between both ends of the DC capacitor zero, and a current adjustment operation is performed by using the second adjustment operation value as an effective current command value. The duty ratio command values of the switching elements of the respective switching arms are obtained, the respective duty ratio command values are divided by the voltage across the DC capacitor, and the result of the division operation is used as a new duty ratio command value. A PWM rectifier, wherein on / off control of a switching element of the switching arm is performed.
てなるＰＷＭ整流器と、該ＰＷＭ整流器の出力の両端に
接続される直流コンデンサと、該直流コンデンサのいず
れか一端に接続される直流リアクトルと、制御回路とか
ら構成されたＰＷＭ整流装置において、 前記制御回路では、 前記直流リアクトルの他端と前記直流コンデンサの他端
との間に接続される負荷への電圧指令値と、前記直流コ
ンデンサの両端電圧から前記直流リアクトルの電圧降下
分を減算した演算値との偏差を零にする調節演算を行な
い、 前記調節演算値と、前記ＰＷＭ整流器の出力電力値との
加算値を有効電流指令値とした電流の調節演算により前
記それぞれのスイッチングアームのスイッチング素子の
通流率指令値を求め、該それぞれの通流率指令値を前記
直流コンデンサの両端電圧で除算演算し、 この除算演算結果を新たな通流率指令値として前記スイ
ッチングアームのスイッチング素子をオン，オフ制御す
ることを特徴とするＰＷＭ整流装置。7. A PWM rectifier comprising a plurality of sets of switching arms connected in parallel, a DC capacitor connected to both ends of an output of the PWM rectifier, a DC reactor connected to one end of the DC capacitor, and a control unit. In the PWM rectifier, the control circuit includes: a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor; and a voltage across the DC capacitor. And performing an adjustment operation to reduce the deviation from the operation value obtained by subtracting the voltage drop of the DC reactor from the current value to zero, and setting a current obtained by adding an adjustment value of the adjustment operation value and an output power value of the PWM rectifier to an effective current command value. The duty ratio command value of the switching element of each of the switching arms is obtained by the adjustment calculation of A PWM rectifier, wherein a division operation is performed by a voltage between both ends of a capacitor, and the result of the division operation is used as a new duty ratio command value to control ON / OFF of a switching element of the switching arm.
てなるＰＷＭ整流器と、該ＰＷＭ整流器の出力の両端に
接続される直流コンデンサと、該直流コンデンサのいず
れか一端に接続される直流リアクトルと、制御回路とか
ら構成されたＰＷＭ整流装置において、 前記制御回路では、 前記直流リアクトルの他端と前記直流コンデンサの他端
との間に接続される負荷への電圧指令値と、該負荷の両
端電圧との偏差を零にする第１の調節演算を行ない、 前記負荷の両端電圧から前記直流リアクトルの電圧降下
分を減算した演算値と、前記第１の調節演算値との加算
演算を行ない、 前記加算演算値と前記直流コンデンサの両端電圧との偏
差を零にする第２の調節演算を行ない、 前記第２の調節演算値と、前記ＰＷＭ整流器の出力電力
値との加算値を有効電流指令値とした電流の調節演算に
より前記それぞれのスイッチングアームのスイッチング
素子の通流率指令値を求め、該それぞれの通流率指令値
を前記直流コンデンサの両端電圧で除算演算し、 この除算演算結果を新たな通流率指令値として前記スイ
ッチングアームのスイッチング素子をオン，オフ制御す
ることを特徴とするＰＷＭ整流装置。8. A PWM rectifier comprising a plurality of sets of switching arms connected in parallel, a DC capacitor connected to both ends of an output of the PWM rectifier, a DC reactor connected to one end of the DC capacitor, and a control unit. In the PWM rectifier configured with a circuit, in the control circuit, a voltage command value to a load connected between the other end of the DC reactor and the other end of the DC capacitor, a voltage across the load, Performs a first adjustment operation to reduce the deviation of the load to zero, and performs an addition operation of an operation value obtained by subtracting a voltage drop of the DC reactor from a voltage across the load and the first adjustment operation value. A second adjustment operation is performed to make a deviation between an operation value and a voltage between both ends of the DC capacitor zero, and an added value of the second adjustment operation value and an output power value of the PWM rectifier is performed. A duty ratio command value of the switching element of each of the switching arms is obtained by an adjustment calculation of a current as an effective current command value, and each of the duty ratio command values is divided by a voltage across the DC capacitor to calculate the duty ratio command value. A PWM rectifier, wherein a switching result of the switching arm is turned on and off by using a calculation result as a new duty ratio command value.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2000171648A JP3821270B2 (en) | 2000-06-08 | 2000-06-08 | PWM rectifier |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2000171648A JP3821270B2 (en) | 2000-06-08 | 2000-06-08 | PWM rectifier |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JP2001352759A true JP2001352759A (en) | 2001-12-21 |
| JP3821270B2 JP3821270B2 (en) | 2006-09-13 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP2000171648A Expired - Fee Related JP3821270B2 (en) | 2000-06-08 | 2000-06-08 | PWM rectifier |
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| JP (1) | JP3821270B2 (en) |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2006094682A (en) * | 2004-09-27 | 2006-04-06 | Toshiba Mitsubishi-Electric Industrial System Corp | Power supply device |
| JP2011254645A (en) * | 2010-06-03 | 2011-12-15 | Fuji Electric Co Ltd | Power conversion equipment and power conversion system |
| CN102647097A (en) * | 2011-02-17 | 2012-08-22 | 富士电机株式会社 | Power supply device |
| JP2014124084A (en) * | 2012-12-20 | 2014-07-03 | Tdk Corp | Power factor improvement circuit |
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| JPH01227660A (en) * | 1988-03-04 | 1989-09-11 | Fuji Electric Co Ltd | Control system for semiconductor power converter device |
| JPH0684796U (en) * | 1993-05-19 | 1994-12-02 | ヤマハ株式会社 | Power supply |
| JPH07322629A (en) * | 1994-05-27 | 1995-12-08 | Meidensha Corp | Power rectifying device |
| JPH0819261A (en) * | 1994-06-24 | 1996-01-19 | Toyo Electric Mfg Co Ltd | Controller of current converter |
| JPH08214550A (en) * | 1995-02-01 | 1996-08-20 | Hitachi Ltd | Controller pwm converter |
| JPH09163752A (en) * | 1995-12-11 | 1997-06-20 | Fuji Electric Co Ltd | Pwm controlled self-excited rectifier |
| JPH1118433A (en) * | 1997-06-19 | 1999-01-22 | Hitachi Ltd | Pulse width modulating power converter |
| JPH11355909A (en) * | 1998-06-05 | 1999-12-24 | Toshiba Corp | Power converting device |
| JP2001314086A (en) * | 2000-04-28 | 2001-11-09 | Sanken Electric Co Ltd | Ac-dc converter |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH01227660A (en) * | 1988-03-04 | 1989-09-11 | Fuji Electric Co Ltd | Control system for semiconductor power converter device |
| JPH0684796U (en) * | 1993-05-19 | 1994-12-02 | ヤマハ株式会社 | Power supply |
| JPH07322629A (en) * | 1994-05-27 | 1995-12-08 | Meidensha Corp | Power rectifying device |
| JPH0819261A (en) * | 1994-06-24 | 1996-01-19 | Toyo Electric Mfg Co Ltd | Controller of current converter |
| JPH08214550A (en) * | 1995-02-01 | 1996-08-20 | Hitachi Ltd | Controller pwm converter |
| JPH09163752A (en) * | 1995-12-11 | 1997-06-20 | Fuji Electric Co Ltd | Pwm controlled self-excited rectifier |
| JPH1118433A (en) * | 1997-06-19 | 1999-01-22 | Hitachi Ltd | Pulse width modulating power converter |
| JPH11355909A (en) * | 1998-06-05 | 1999-12-24 | Toshiba Corp | Power converting device |
| JP2001314086A (en) * | 2000-04-28 | 2001-11-09 | Sanken Electric Co Ltd | Ac-dc converter |
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2006094682A (en) * | 2004-09-27 | 2006-04-06 | Toshiba Mitsubishi-Electric Industrial System Corp | Power supply device |
| JP2011254645A (en) * | 2010-06-03 | 2011-12-15 | Fuji Electric Co Ltd | Power conversion equipment and power conversion system |
| CN102647097A (en) * | 2011-02-17 | 2012-08-22 | 富士电机株式会社 | Power supply device |
| JP2012175714A (en) * | 2011-02-17 | 2012-09-10 | Fuji Electric Co Ltd | Power supply unit |
| JP2014124084A (en) * | 2012-12-20 | 2014-07-03 | Tdk Corp | Power factor improvement circuit |
Also Published As
| Publication number | Publication date |
|---|---|
| JP3821270B2 (en) | 2006-09-13 |
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