JP2001319797A - Light bulb type fluorescent lamp and lighting device - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a light bulb type fluorescent lamp and a lighting device using the light bulb form fluorescent lamp which has been improved so as not to yield a short life and malfunction when it is connected with a low frequency AC power supply via a light controller. SOLUTION: This device is equipped with a load circuit LD having and a resonance inductance L3 and resonance electrostatic capacitances C5, C6, which apply a smoothed direct voltage to both the first switching means Q1 and the second switching means Q2 that make switching alternately by a feedback type drive signal generating circuit FDG and that are connected in series, and which is actuated by a produced high-frequency current, and an inductor L2 is inserted in series between a rectification circuit FBR and a smoothing circuit C1, and is planned so that a high-frequency current directly flows from the rectification circuit FBR through at least a part of the resonance inductance L3 and the second switching means Q2, by connecting a high-frequency current passage HCP between a direct-current output of a rectification direct current power source and a load circuit LC via the one end inductor L2.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a bulb-type fluorescent lamp having improved lighting circuit means, and a lighting device using the same.

[0002]

2. Description of the Related Art A bulb-type fluorescent lamp has a structure in which a compact fluorescent lamp and its lighting circuit means are integrated. Since it is a light source having both high lamp efficiency and long life, which are characteristic features, and capable of achieving significant power saving, it is widely used in place of incandescent lamps.

[0003] In general, commercially available bulb-type fluorescent lamps are capable of operating a fluorescent lamp with high efficiency, and are required to be small and light in weight. It has an inverter. The high-frequency inverter converts the low-frequency AC into non-smooth DC once using a rectifier circuit and converts the non-smooth DC voltage from the non-smooth DC voltage using a smoothing capacitor to convert DC to high frequency. I am getting direct current. (Prior art 1) A circuit system for directly charging a smoothing capacitor with a non-smoothed DC voltage after rectification is referred to as a capacitor input system, and a bulb-type fluorescent lamp using this system performs dimming for the reason described later. Can not do.

On the other hand, recently, a dimmable bulb-type fluorescent lamp has been developed. This bulb-type fluorescent lamp uses a voltage doubler rectifier circuit and employs a special control IC, and monitors the power supply waveform to control the frequency, so that the phase can be controlled from the dimming phase of 90 to 180 °. Does not go off. (Prior art 2)

The prior art 1 has the advantage that the circuit configuration is simple and inexpensive.
Since the input current from the low-frequency AC power supply to the lighting circuit means is a charging current to the smoothing capacitor, the inflow period is short. Therefore, if the phase control type dimmer is turned on during the pause of the input current, the holding current cannot be secured, and the triac used as the phase control element is turned off. Cannot be maintained for half a cycle. As a result, the input current of the bulb-type fluorescent lamp increases and the life is shortened. In addition, there is a problem that the brightness flickers due to a malfunction.

On the other hand, the prior art 2 has a problem that the circuit configuration is complicated, the number of circuit components such as ICs is increased, the area of the wiring board is increased, and the bulb-type fluorescent lamp is enlarged. .

An object of the present invention is to provide a bulb-type fluorescent lamp improved so that short life and malfunction do not occur when connected to a low-frequency AC power supply via a dimmer, and a lighting device using the same. With the goal.

[0007]

According to a first aspect of the present invention, there is provided a light-bulb-shaped fluorescent lamp having a compact shape such that a bent discharge path is formed therein.
Including a phosphor layer disposed on the inner surface side of the translucent discharge vessel, a pair of electrodes sealed at both ends of the translucent discharge vessel, and mercury and a rare gas sealed inside the translucent discharge vessel A fluorescent lamp having an ionizing medium; an input terminal connected to a low-frequency AC power supply, a noise filter connected to the input terminal, a rectifier circuit having an AC input terminal connected to an output terminal side of the noise filter, and a non-smoothing DC of the rectifier circuit. A smoothing circuit for smoothing the output voltage, a first switching means and a second switching means connected in series so that a smoothed DC voltage of the smoothing circuit is applied, a resonance inductance and a resonance capacitance. The fluorescent lamp is operated in parallel with at least a part of the resonance capacitance while operating by high-frequency alternating current generated by alternate switching of the first and second switching means. A load circuit connected thereto, a feedback type drive signal generation circuit for feeding back a current flowing through the load circuit to form a drive signal for the first and second switching means, and between the DC output terminal of the rectified DC power supply and the smoothing circuit. And one end connected to the DC output end of the rectified DC power supply via the inductor and the other end passing through at least a part of the resonance inductance of the load circuit and the second switching means. Circuit means having a high-frequency current path connected to a load circuit so that the light flows directly from the rectifier circuit; a cover accommodating the lighting circuit means therein and supporting the fluorescent lamp; an input terminal of the lighting circuit means And a base provided at the base end of the cover.

<Regarding the Fluorescent Lamp> (Regarding the Translucent Discharge Vessel) The translucent discharge vessel has an outer diameter of 11 mm or less, preferably 8 to 11 mm, and more preferably 3 to 9 mm for further miniaturization. Are formed in a compact shape such that a bent discharge path is formed therein. For example, a single elongated glass tube is bent in a saddle shape, or a plurality of U-shaped glass tubes bent in a U-shape are connected by a connecting tube, and a portion of each U-shaped glass tube is placed on the circumference. By arranging or arranging the gaps formed between the U-shaped glass tubes back and forth so that they can be seen from one direction, and further by spirally winding the glass tubes, The light discharge vessel can be formed in a compact shape, and a discharge path bent inside can be formed. The connecting pipe can be formed by a blow-off method, or can be formed by glass welding using a separately prepared pipe.

Further, the outer diameter of the translucent discharge vessel can be freely selected within the above numerical range. However, if the outer diameter is less than 3 mm, the lamp current is excessively reduced, so that the desired lamp input can be reduced. In order to ensure this, it is necessary to compensate for the decrease in lamp current by increasing the discharge path length, making it impossible to reduce the size. In addition, since the lamp voltage increases along with this, the starting voltage also increases, the lighting circuit becomes large, and the cost increases. Conversely, if the outer diameter of the translucent discharge vessel exceeds 11 mm, the translucent discharge vessel becomes too large, making it difficult to obtain a compact fluorescent lamp. The inner diameter of the translucent discharge vessel is substantially proportional to the outer diameter, and is an average value obtained by subtracting twice the thickness of the translucent discharge vessel from the outer diameter.

Further, a seal portion, for example, a pinch seal portion is formed at at least both ends of the translucent discharge vessel, and if necessary, a pinch seal portion is formed in the middle in addition to this. For example, in the case where a plurality of U-shaped glass tubes are connected by a connecting tube to form a light-transmitting discharge vessel, a seal portion may be formed in the middle of the light-transmitting discharge vessel. That is, seal portions are formed at both ends of each U-shaped glass tube, and intermediate portions near the ends are connected to each other by a connection tube to form one bent discharge path.

On the other hand, the outer diameter of the length of the translucent discharge vessel, that is, the length of the discharge path formed between a pair of electrodes sealed at both ends of the translucent discharge vessel, that is, the discharge path length, is within the above range. Within this range, it can be set to 300 to 500 mm depending on the lamp power of the bulb-type fluorescent lamp.

The material of the translucent discharge vessel is not limited as long as it has the above-mentioned structure, but it can be generally made of glass. In this case, it is economical to use soft glass such as soda lime glass or lead glass as the glass, but if necessary, hard or semi-hard glass such as borosilicate glass can be used.

Further, the cross-sectional shape of the translucent discharge vessel is generally circular, but may be non-circular, for example, elliptical or any other cross-sectional shape, if necessary.

(Regarding Phosphor Layer) The phosphor layer is used for converting the wavelength of ultraviolet light generated by discharge into visible light in a desired wavelength range. The type of phosphor used is not limited, but a three-wavelength light-emitting phosphor is preferable because it can obtain excellent heat resistance and load characteristics and has excellent color rendering properties.

In the present invention, the phrase “the phosphor layer is disposed on the inner surface side of the translucent discharge vessel” means that the phosphor layer is directly formed on the inner face of the translucent discharge vessel. It means that it may be formed indirectly via a protective film, a reflective film, or the like.

Further, as the protective film, Al₂O₃Fine
A film configuration mainly composed of particles can be used. Crystal structure
The structure may be either β-form or α-form. However, α-form
Al ₂O₃By using a protective film made of
Light flux rising characteristics can be obtained.

(Electrode) A pair of electrodes are sealed at both ends of the light-transmitting discharge vessel via a seal portion, and the electrode structure may be any of a filament electrode and a ceramic electrode.

When the electrode is a filament electrode and the seal portion has a pinch seal structure, a bead mount structure is employed to prevent the shape of the filament from being disturbed at the time of sealing. Both ends can be pinch sealed.

When a ceramic electrode is used, the ceramic electrode has the following configuration. That is, the ceramic electrode is composed of a sintered body of a composite oxide or oxynitride,
A conductive substrate for supporting the sintered body.

The sintered body is composed of fine particles of a composite oxide or oxynitride containing an alkaline earth element and a transition metal element as main components and a porous aggregate thereof. In addition, the surfaces of the fine particles of the sintered body and the porous aggregate thereof can be coated with a carbide such as TaC and / or a nitride such as TiN. By forming these coatings on the surface, Ba
Has the effect of preventing the sputtering of thermionic emission materials. However, the thermionic emission material also has a function of assisting electric conduction when the temperature of the surface sintered body is low due to thermal diffusion from the inside.

The “conductive substrate” may be made of any material as long as it is a member having a suitable conductivity and supporting a sintered body. Or can be carried and carried in a cup-shaped body formed from a transition metal or the above sintered body.

(Ionizing Medium) The ionizing medium enclosed in the translucent discharge vessel contains mercury and a rare gas.

Since the temperature of the mercury is high during the operation of the bulb-type fluorescent lamp, the mercury is generally supplied by amalgam in order to optimally control the mercury vapor pressure at a high temperature. By using amalgam, it is possible to stably control the mercury vapor pressure even when the ambient temperature changes, and thus to obtain a stable light output. Further, by arranging the auxiliary amalgam in the vicinity of the electrode, mercury vapor can be supplied at the initial stage of lighting, and the luminous flux rising characteristics can be improved. In order to distinguish the former amalgam from the auxiliary amalgam, it is hereinafter referred to as "main amalgam".

The main amalgam emits mercury necessary for low-pressure mercury vapor discharge and supplies mercury vapor into the translucent discharge vessel, and is preferably housed in a thin tube. And the main amalgam is Bi-In-Hg, Bi-In-Sn-H.
In addition to the composition such as g, a material containing 4.5% by weight or more, preferably 6% by weight of mercury can be used in order to improve the light flux rising.

However, when the content of mercury reaches the above-mentioned content, care must be taken because mercury easily oozes out on the surface of the amalgam and causes stickiness. That is, when producing amalgam, it is possible to rapidly reduce the size of the crystal particles by cooling and to perform a non-sticky treatment on the surface of the amalgam.

The amount of the main amalgam to be enclosed is 40 to 1
About 20 mg is good.

Further, the main amalgam is preferably processed into particles of an appropriate size, and a plurality of particles are preferably enclosed in a capillary so that a required amount is enclosed.

Further, as the outer diameter of the light-transmitting discharge vessel becomes smaller, it takes more time for the mercury vapor pressure in the discharge space of the light-transmitting discharge vessel to be evenly distributed at the time of lighting. It can be supplied at a plurality of locations on the translucent discharge vessel.

The auxiliary amalgam is configured such that by placing an amalgam-forming metal, for example, indium In, at a required position, mercury moves in the translucent discharge vessel to form an amalgam. The amalgam-forming metal can be applied to a metal substrate such as stainless steel by vapor deposition or the like.

Further, when the auxiliary amalgam is arranged near the electrode, it can be supported by welding to the lead wire of the electrode. When the auxiliary amalgam is provided at a position remote from the electrode, the auxiliary amalgam can be supported by a member such as an appropriate lead wire having a base end sealed to the seal portion.

The rare gas can be filled with one or more of argon, krypton, xenon, neon and the like and mixed at a pressure of several thousand to several tens of thousands Pa.

<Lighting Circuit Means> In the present invention, the lighting circuit means is a circuit means for starting the fluorescent lamp and lighting it at a high frequency. And an input terminal, a noise filter, a rectifier circuit, a smoothing circuit, first and second switching means connected in series, a load circuit, a feedback drive signal generation circuit, a series circuit, and high-frequency current paths. It is configured with elements. And it is permitted to provide other configurations as needed. Note that the above circuit elements are generally mounted on a wiring board. In the present invention, “high frequency” refers to frequency 1
0 kHz or more, preferably at a frequency of 20 to 200
kHz.

The following is a description of each circuit element.

(Regarding the Input Terminal) The input terminal is used as lighting circuit means, and therefore does not necessarily have to be a base. For example, in the present invention, it is permissible that the bulb-type fluorescent lamp integrally has a function as a dimmer, but in such a case, it is possible to adjust the brightness between the base and the input terminal of the lighting circuit means. Optical circuit intervenes. Further, the input terminal does not have to have a terminal form.

(Regarding Noise Filter) The noise filter is interposed between the low-frequency AC power supply and the rectifier circuit, and the high-frequency noise generated by the high-frequency switching of the first and second switching means is transmitted to the low-frequency AC power supply. This is to prevent leakage. In general, it is constituted by an inductor connected in series between the low-frequency AC power supply and the rectifier circuit, and a capacitor connected in parallel to the low-frequency AC power supply. Also, if necessary, use a capacitor for the noise filter with a differentiator to prevent the input current from becoming zero due to vibration at the moment when the phase control element of the dimmer is turned on. Can be shared.

(Regarding Rectifier Circuit) A rectifier circuit is a means for converting low-frequency alternating current into direct current, and its AC input terminal is connected directly or indirectly through another noise component to a low-frequency alternating current through a noise filter. It is connected to an AC power supply and outputs a non-smooth DC to a DC output terminal, and can be arbitrarily adopted from rectification circuits of various circuit types as desired. For example, a bridge type full-wave rectifier circuit, a voltage doubler type full-wave rectifier circuit, a center tap type full-wave rectifier circuit, a half-wave rectifier circuit, or the like can be used.

(Smoothing Circuit) A smoothing circuit is a means for smoothing an unsmoothed DC voltage of a rectifier circuit. Generally, one or a plurality of electrolytic capacitors are provided depending on the circuit system of the rectifier circuit. Used to form a capacitor input system. For example, in the case of a voltage doubler rectifier circuit, two smoothing capacitors are used in series.
Further, a Schottney divided voltage type smoothing circuit may be configured by using two smoothing capacitors and two diodes.

(First and Second Switching Means) The first and second switching means are a pair of switching means for alternately turning on and off the half-bridge type inverter, and have the same polarity and complementary switching means. Either may be used. Further, either voltage-driven switching means such as a MOSFET or current-driven switching means such as a bipolar transistor may be used.

Since the FET is a voltage drive type switching means, it is easy to drive. Also, MOS
The FET is effective as a power switching means that is less restricted by a safe operation area. Further, the enhancement type MOSFET is easy as power-on processing, and is suitable as a power switching means. Furthermore, N-channel MOSFETs are advantageous because the current product lineup is abundant. However, a P-channel MOSFET can be used if desired. Further, by using an N-channel MOSFET for one switching means and using a P-channel MOSFET for the other switching means, the first and second switching means can be configured in a complementary manner.

By the way, the switching means is allowed to have a drive terminal. The drive is turned on when a drive signal of a predetermined polarity is supplied to the drive terminal. Enhancement type MOS
In a FET, when a gate voltage as a drive signal is applied between a gate as a drive terminal and a source, a channel is formed and the FET is turned on. Therefore, the off state is maintained when no gate voltage is applied.

"Connecting the first and second switching means in series so that the smoothing DC voltage of the smoothing circuit is applied" means that the first and second switching means are viewed from the smoothing circuit. Are connected in series, and other circuit components such as inductors and resistors may be interposed between the first and second switching means and the DC power supply. Further, a circuit component may be interposed between the first and second switching means.

(Regarding Load Circuit) The load circuit has at least a resonance inductance and a resonance capacitance. And it operates by the high frequency alternating current generated by the alternating switching of the first and second switching means. Then, the fluorescent lamp of the load is connected in parallel to at least a part of the capacitance of the load circuit.

The resonance inductance and the resonance capacitance can resonate with the high-frequency alternating current generated by the alternate switching of the first and second switching means. At least one of each of the resonance inductance and the resonance capacitance is connected to the load circuit, and if necessary, one or both of the resonance inductance and the resonance capacitance can be constituted by a plurality.

The resonant inductance is configured to act as a current limiting impedance for the fluorescent lamp to compensate for the negative characteristics of the load.

Further, when the resonance capacitance is composed of a plurality of capacitors, a part thereof can be made to act as a DC cut capacitor, and at least a part of the remainder can be made to act as a resonance voltage extracting capacitor. . Then, the fluorescent lamps can be connected in parallel so that the resonance voltage appearing between both ends of the resonance voltage extracting capacitor is applied to the fluorescent lamp.

(Return type drive signal generation circuit)
The feedback-type drive signal generation circuit is a circuit that generates and supplies a drive signal to the first and second switching means by feeding back a current flowing through the load circuit. Therefore, the lighting circuit means of the present invention constitutes a self-excited half-bridge type inverter.

Further, the feedback drive signal generation circuit can be constituted by adding a drive protection circuit, if necessary, with a feedback transformer and a drive resonance circuit. In such a configuration, first, the feedback transformer will be described.

In order to feed back the current flowing through the load circuit, the feedback transformer is formed by magnetically coupling a feedback winding to the resonance inductance of the load circuit, or an independent transformer is inserted in series with the resonance inductance. Can be arranged. When the feedback winding is magnetically coupled to the resonance inductance, a gap is generally provided in the magnetic circuit. Care must be taken in the winding position of the feedback winding on the magnetic circuit to obtain the desired characteristics. When an independent feedback transformer is inserted, any of a saturable configuration and an unsaturated configuration may be used. However, it should be noted that the saturable configuration is difficult to wind the winding, has large variations in characteristics, and is large. In contrast, the unsaturated configuration is
Since it is superior to other configurations, it will be described in detail below.

When using a feedback transformer in an unsaturated configuration, this transformer comprises at least a primary winding and a secondary winding, in order to drive the switching means a voltage proportional to the current flowing in the load circuit. Acts on the secondary winding. Therefore, the number of turns on the primary winding side is relatively small, so that the inductance of the primary winding is small and does not substantially contribute as resonance inductance. The “unsaturated configuration” refers to a configuration in which a core configured so as not to be substantially magnetically saturated is used or formed without using a core. Further, "configured so that the core is not saturated" means that the core has a substantially infinite gap length, such as a drum core or a rod core. A core having such characteristics can be realized by a drum core or a rod core.

The relationship between the primary winding and the secondary winding is as follows.
In addition to the primary winding being wound on the secondary winding, the secondary winding may be wound on the primary winding. Further, the primary winding and the secondary winding of the feedback transformer having the unsaturated configuration may be wound not only in the lap winding but also adjacently.
In this case, a winding frame can be used. Furthermore, the secondary winding may be single or multiple. For example, one secondary winding can be assigned to each of the first and second switching means, and a drive resonance circuit and a drive circuit can be further provided. However, even when a pair of secondary windings is provided, if a drive resonance circuit is formed by connecting a capacitance only to one of the secondary windings, the other secondary winding can be provided. Since this also induces a resonance output, there is no need to provide two drive resonance circuits.

Next, the drive resonance circuit will be described.

The drive resonance circuit is composed of an inductance viewed from the secondary winding side of the feedback transformer and a drive resonance capacitance. The resonance circuit in this case may be any of a parallel resonance circuit and a series resonance circuit. The drive resonance capacitance is determined by using a capacitor or the capacitance of the switching means, for example, MO
The capacitance between the gate and the source of the SFET can be used. The drive resonance circuit generates a resonance output having positive and negative polarities by resonance, and can supply the resonance output to the drive circuit.

If the first and second switching means have the same polarity, the resonance output of the drive resonance circuit must have a certain polarity with respect to one of the switching means in order to turn on and off each switching means alternately. , The polarity may be inverted and supplied to the other switching means. For this purpose, for example, the polarity can be easily inverted by using a transformer. On the other hand, when the first and second switching means are in a complementary relationship, the resonance output of the drive resonance circuit can be supplied to both switching means without reversing the polarity.

When the first and second switching means are of a voltage drive type, the drive circuit is configured to supply a drive voltage. In the case of a current drive type, a drive current is supplied.

Next, the drive protection circuit will be described.

In the case of using the voltage drive type switching means, a drive protection circuit may be added to the voltage clamp circuit if necessary in order to regulate the drive signal to a predetermined voltage. The drive protection circuit prevents an excessive voltage from being applied to the drive terminals of the first and second switching means, and may have any specific circuit configuration. For example, at least 2
One or more Zener diodes can be connected in series with opposite polarities to form a drive protection circuit. This drive protection circuit can perform a protection action on the positive and negative bipolar resonance voltages. When the complementary switching means is used, one drive protection circuit also exerts a gate protection action on both the first and second switching means. Further, the drive protection circuit can be configured by various similar circuit configurations without using a Zener diode as long as it is a constant voltage element. Furthermore, the number of constant voltage elements to be used may be determined according to the relationship between the constant voltage and the gate voltage.

Then, the voltage which becomes overvoltage with respect to the gate of the switching means is short-circuited and absorbed by the drive protection circuit, so that each gate of the first and second switching means has an appropriate value. Only voltage is applied. When an overvoltage is applied to the switching means, the switching means may be destroyed. Therefore, it is preferable to add a drive protection circuit.

<Regarding the Inductor> The inductor is inserted in series between the DC output terminal of the rectified DC power supply and the smoothing circuit so that a desired high-frequency current flows through a high-frequency current path described later. If necessary, a pair of diodes can be inserted at both ends of the inductor in the forward direction.

<Regarding the High-Frequency Current Path> One end of the high-frequency current path is connected to the DC output terminal of the rectified DC power supply via the inductor, and the other end has at least a part of the resonance inductance of the load circuit and the second switching. It is connected to the load circuit so that the high frequency current flows directly from the rectifier circuit through the means. And in the high-frequency current path,
Capacitors can be inserted in series.

<Regarding the Cover> The cover accommodates at least the lighting circuit means therein, supports the fluorescent lamp, and supports the base at the base end. Furthermore, in a bulb-type fluorescent lamp provided with a globe, the globe is fixed to the cover.

An auxiliary member, for example, a partition plate, can be used to house and fix the lighting circuit means inside the cover. That is, the wiring board can be housed in the cover by supporting the wiring board on the partition plate and mounting the partition plate on the cover so as to close the opening end of the cover. In this case, the partition plate can be further fixed to the cover together with the glove.
However, needless to say, the wiring board can be directly supported and stored in the cover.

A partition plate can also be used to support the fluorescent lamp on the cover. That is, the fluorescent lamp is supported by the partition plate, and the partition plate is fixed to the opening end of the cover. Thus, by attaching the partition plate to the opening end of the cover, it is possible to prevent unnecessary opening of the cover.

Further, the cover is preferably formed to be narrow from the middle portion to the base portion in order to support the base at the base end and to increase the adaptability to the lighting fixture for incandescent lamps.
However, the shape of the entire cover should be determined in consideration of the design as a compact fluorescent lamp. That is, it is natural that the shape of the cover differs greatly between the cover having the glove and the cover not having the glove and exposing the fluorescent lamp, mainly due to design considerations.

The shape of the cover should be different depending on the shape of the glove. For example, in the case of a G-shaped globe, the cover can be shaped like a portion of a sphere so that it cooperates with the glove to form a shape close to a G-shaped valve. Also, in the case of an A-shaped globe, the cover can be formed into a shape as close to an A-shaped valve as possible in cooperation with the glove.

<Regarding the Base> The base is a power receiving means and functions as a means for mechanically supporting the light bulb-shaped fluorescent lamp. A known base can be appropriately selected and used, but an E26 screw base, which is widely used as a bulb-type fluorescent lamp, is appropriate.

The means for supporting the base on the cover is not particularly limited, and may be supported by known supporting means, for example, mechanical fixing by a punch, ie, caulking.

<Regarding Other Configurations> 1. Differentiating Circuit In the capacitor input method, vibration occurs at the moment when a phase control element such as a thyristor of the dimmer is turned on, and the input current tends to instantaneously become zero. When such a state occurs, the phase control element is turned off because the holding current cannot be secured. As a result, the input current of the bulb-type fluorescent lamp increases, resulting in a shorter life or malfunction.

Therefore, a differentiating circuit can be added at a position on a circuit which affects the input terminal of the compact fluorescent lamp. The differentiating circuit can be constituted by a series circuit of a capacitor and a resistor, for example. Also, by inserting switch means in series in the differentiating circuit and controlling the switch means to turn on only during the off period of the dimmer, the power loss occurring in the differentiating circuit during the on period of the phase control element is reduced. can do.

2. Dimmer The dimmer is not generally used as a circuit element constituting a bulb-type fluorescent lamp, but is used by being buried in an indoor wall or built in a lighting fixture. In the above, if necessary, it is allowed to be incorporated in a bulb-type fluorescent lamp. The dimmer mainly includes a phase control element and an operation circuit for controlling the ON phase of the phase control element. The phase control element includes a non-contact switch element such as a thyristor such as a triac. The operation circuit supplies a conduction signal of a desired phase to a control terminal of the phase control element, and includes a phase shift circuit in which a variable resistor and a capacitor are connected in series, and a trigger element such as a diac. Further, a capacitor is connected in parallel with the phase control element so as to absorb noise generated by switching of the phase control element.

3. High-frequency output control means In order to properly control the high-frequency output of the load to the fluorescent lamp in accordance with the dimming phase of the dimmer of 0 to 90 °, high-frequency output control means is provided as necessary. be able to. That is, in the range of the dimming phase of the dimmer of 0 to 90 °,
Since the change in the charging voltage of the smoothing capacitor is small, the ratio of the actual dimming of the fluorescent lamp is small in spite of changing the dimming phase. Therefore, if it is desired to realize a large dimming ratio according to the dimming phase in this range, the operating frequencies of the first and second switching means may be changed according to the dimming phase. Since the load circuit includes a resonance inductance that acts as a current-limiting inductance of the fluorescent lamp, if the frequency of the high frequency generated by switching of the switching means is changed, the impedance of the current-limiting inductance changes, and the load of the fluorescent lamp is changed. Dimming is performed by changing the input power. To change the high frequency in accordance with the dimming phase, for example, an input voltage is detected, and the operating frequency of the first and second switching means is set to a substantially constant frequency during each half cycle in accordance with the detected voltage. Control so that Further, as another means, a pause period and an ON period of the input voltage are determined, and
The operating frequency in the pause interval is set high, and the frequency in the ON interval is set low. As a result, if the ON period increases and the dimming phase decreases, the high-frequency output increases. Conversely, if the ON period decreases and the dimming phase increases, the high-frequency output decreases.

<Operation of the Present Invention> When the base of the compact fluorescent lamp of the present invention is mounted on the lamp socket and a low-frequency AC power is applied, the low-frequency AC voltage is rectified via the input terminal and the noise filter. Applied to the circuit and rectified,
The non-smooth DC output voltage is smoothed by charging the smoothing circuit. The charging voltage of the smoothing circuit is
Even if a small amount of ripple is included when viewed from a low frequency, it may be regarded as constant when viewed from a high frequency.

The high frequency generated by the half-bridge type inverter operation by the alternating high frequency switching of the first and second switching means is applied to the load circuit. As a result, the load resonance circuit resonates with the high frequency and generates a sinusoidal high frequency vibration. In this case, the resonance voltage appearing across at least a part of the resonance capacitance is applied to the fluorescent lamp, and the starting of the fluorescent lamp can be promoted. Further, a filament heating circuit can be formed by connecting a capacitor of a load resonance circuit between the non-power supply side terminals of the pair of filament electrodes of the fluorescent lamp. When the fluorescent lamp is started, a lamp current flows through the fluorescent lamp via the resonance inductance of the load circuit, and the fluorescent lamp is turned on.

Further, in addition to the current which is converted to a high frequency via the above-mentioned smoothing circuit and supplied to the fluorescent lamp, the inductor and the second diode in the series circuit of the first diode, the inductor and the second diode A high-frequency current (hereinafter, referred to as “direct high-frequency current”) directly flows from the connection point to the load circuit via the high-frequency current path. That is, when the second switching means is turned on, the first diode of the series circuit, the inductor, the high-frequency current path, at least a part of the resonance inductance of the load circuit, the second switching means, and the rectifier circuit, from the positive electrode of the rectifier circuit. A high-frequency current flows directly through the path of the negative electrode. The direct high-frequency current flows through almost all the phase sections of the low-frequency AC voltage.

Therefore, even if the bulb-type fluorescent lamp is connected to a low-frequency AC power supply via a dimmer of a phase control type, a pause period occurs in the input current flowing from the base because the high-frequency current flows directly. As a result, the phase control element such as the triac of the dimmer does not undesirably turn off. For this reason, problems such as an increase in the input current of the bulb-type fluorescent lamp to shorten its life and a malfunction such as a flicker of brightness due to malfunction are not caused. However, as can be understood from the above description, the direct high-frequency current does not flow into the fluorescent lamp, and does not contribute to the light emission of the bulb-type fluorescent lamp. For this reason, it is desirable to set the circuit conditions so that the direct high-frequency current is as small as possible without impairing the operation of the dimmer, for example, about half or less of the input current of the bulb-type fluorescent lamp. When the smoothing circuit is of a capacitor input type, it is preferable that the high-frequency current is reduced directly so that the bulb-type fluorescent lamp basically operates at a low power factor.

According to a second aspect of the present invention, there is provided the light bulb-shaped fluorescent lamp according to the first aspect, wherein the feedback drive signal generating circuit is configured so that the primary winding is connected to the load circuit and the current flowing through the load circuit is reduced. A first and second transformer is formed by a transformer in an unsaturated configuration in which a proportional voltage is induced in the secondary winding, and a drive resonance capacitance and an inductance of the secondary winding of the transformer in the unsaturated configuration, and a resonance output. And a drive circuit for alternately driving the switching means.

The present invention defines a preferred configuration of a feedback drive signal generation circuit using a transformer having an unsaturated configuration.

That is, the transformer having the unsaturated configuration can be constituted by any one or a combination of the following.

1. The primary winding is connected to the load circuit, and a voltage proportional to the current flowing through the load circuit is induced in the secondary winding.

2. The primary winding is configured to have a negligible inductance as compared to the resonance inductance of the load circuit. One of the transformers with unsaturated configuration
The secondary winding has such a small inductance that it does not substantially contribute to the resonance inductance, and is arranged separately from the resonance inductance of the load circuit. Note that “negligible” means that the inductance is 2% of the resonance inductance of the load circuit.
%, Preferably 1% or less.

However, in the implementation of the circuit, it is desirable to dispose the transformer having the unsaturated configuration at a distance from the resonance inductance so as not to be affected by the resonance inductance of the load circuit. In this case, another kind of shielding effect is produced by interposing other circuit components such as a capacitor between the transformer having the unsaturated configuration and the resonance inductance, so that the resonance inductance is more effective in suppressing interference. It is.

3. The ratio Ln2 / Ln1 of the inductance Ln2 of the secondary winding to the inductance Ln1 of the primary winding is 10
It is configured to be 0 or more. With this configuration, the primary winding does not contribute to the resonance inductance of the load circuit, so that a voltage proportional to the current flowing through the load circuit can be induced in the secondary winding, and
It is possible to configure a drive resonance circuit that resonates the inductance Ln2 of the next winding with the capacitance and obtains a resonance output required for forming a drive signal. In contrast, 1
If the ratio Ln2 / Ln1 of the inductance Ln2 of the secondary winding to the inductance Ln1 of the secondary winding is less than 100, 1
Since the inductance Ln1 of the secondary winding is relatively large, in such a case, the inductance Ln1 of the primary winding starts to contribute as a resonance inductance, and thus a voltage proportional to the current flowing through the load circuit. 2
It cannot be induced in the next winding. Alternatively, since the inductance Ln2 of the secondary winding is small, the inductance required by the drive resonance circuit cannot be provided.

4. The ratio Ln2δ / Ln2 of the equivalent inductance Ln2δ existing in series with the secondary winding when the primary winding is short-circuited to the inductance Ln2 of the secondary winding is configured to be 0.5 or more. . The equivalent inductance Ln2δ existing in series with the secondary winding when the primary winding of the transformer having the unsaturated configuration is short-circuited indicates an inductance that contributes to configuring the drive resonance circuit together with the capacitance. The magnitude of the equivalent inductance Ln2δ is defined by the ratio Ln2δ / Ln2 to the inductance Ln2 of the secondary winding.

Thus, by providing any of the above-described configurations, it is possible to form a drive resonance circuit having a resonance frequency suitable for generating a high-frequency alternating current.

Next, the operation when the feedback drive signal generation circuit is constituted by a transformer having an unsaturated configuration and a drive resonance circuit will be described.

That is, a voltage proportional to the current flowing through the load circuit is induced in the secondary winding of the transformer having the unsaturated configuration. The drive resonance circuit resonates at the fundamental frequency of the voltage induced in the secondary winding of the unsaturated transformer. And
The resonance output of the drive resonance circuit is supplied to each switching means as a drive signal. As a result, the first and second switching means alternately switch on and off, operate as a half-bridge type inverter, and generate a high-frequency alternating current. In the above circuit operation, since the primary winding of the transformer having the unsaturated configuration is provided separately from the resonance inductance, a high voltage due to resonance of the load circuit is not applied. Therefore, high reliability can be obtained without imparting exceptionally high dielectric strength to the transformer having the unsaturated configuration. Also, unlike a supersaturated current transformer, in which the winding is difficult to form, the winding of the transformer is easy, so the cost can be kept low and the characteristics of the transformer are small. Is relatively easy and can be miniaturized.

In the bulb-type fluorescent lamp according to the third aspect of the present invention, in the bulb-type fluorescent lamp according to the first or second aspect, the load circuit includes a DC cut capacitor and a resonance voltage extracting capacitor having a resonance capacitance connected in series. And the fluorescent capacitance is connected in series, and the fluorescent lamp is connected in parallel to the resonance voltage extracting capacitor; the other end of the high-frequency current path is the midpoint of the resonance inductance of the load circuit. Is connected to the computer.

The “midpoint of the resonance inductance” is not limited to the center where the winding forming the inductance is divided into two. The other end of the high-frequency current path can be connected with the position at which the winding is divided at an appropriate ratio as the middle point.

Thus, in the present invention, the above structure can reduce the withstand voltage required for the capacitor inserted in the high-frequency current path.

A bulb-type fluorescent lamp according to a fourth aspect of the present invention is the bulb-type fluorescent lamp according to the first or second aspect, wherein the load circuit is a DC cut capacitor and a capacitor for extracting a resonance voltage having a resonance capacitance connected in series. And a fluorescent lamp is connected in parallel to the resonance voltage extracting capacitor; the other end of the high-frequency current path is connected to a connection point of the resonance inductance of the load circuit and the DC cut capacitor; It is characterized by.

In the present invention, since the other end of the high-frequency current path is connected to the connection point of the resonance inductance and the DC cut capacitor, it is not necessary to arrange a middle point in the resonance inductance. However, it is necessary to use a capacitor having a higher withstand voltage as compared with the configuration connected to the resonance inductance at the middle point in the high-frequency current path.

A bulb-type fluorescent lamp according to a fifth aspect of the present invention is the bulb-type fluorescent lamp according to the first or second aspect, wherein the load circuit is a DC cut capacitor and a capacitor for extracting a resonance voltage having a resonance capacitance connected in series. And a fluorescent lamp is connected in parallel to the resonance voltage extraction capacitor, and a resonance voltage extraction capacitor is connected between the resonance inductance and the DC cut capacitor; the other end of the high-frequency current path is Connected to the connection point of the resonance inductance of the load circuit and the capacitor for extracting the resonance voltage.

In the present invention, since the other end of the high-frequency current path is connected to the connection point of the resonance inductance and the capacitor for extracting the resonance voltage, it is not necessary to arrange a middle point in the resonance inductance. However, it is necessary to use a capacitor having a higher withstand voltage as compared with the configuration connected to the resonance inductance at the middle point in the high-frequency current path.

A lighting device according to a sixth aspect of the present invention comprises: a lighting device main body; and the bulb-type fluorescent lamp according to any one of claims 1 to 5 supported by the lighting device main body. And

In the present invention, the term “illumination device” is a broad concept including any device utilizing the light emission of a compact fluorescent lamp. For example, it includes a lighting fixture, an indicator light, and the like.

The lighting device main body refers to the remaining portion of the lighting device excluding the bulb-shaped fluorescent lamp.

[0096]

Embodiments of the present invention will be described below with reference to the drawings.

FIG. 1 shows a first embodiment of a compact fluorescent lamp of the present invention.
It is a partial sectional front view showing the embodiment.

FIG. 2 is a plan view of the glove as seen through.

FIG. 3 is an exploded perspective view.

In each figure, 1 is a fluorescent lamp, 2 is lighting circuit means, 3 is a cover, 4 is a base, 5 is a globe, and 6 is a partition plate.

[About Fluorescent Lamp 1] Fluorescent Lamp 1
Includes a light-transmitting discharge vessel 1a and an electrode 1b.

The translucent discharge vessel 1a has four outer diameters of 10 m.
The U-shaped glass tubes 1a1 of m are connected by three connecting tubes 1a2, and the U-shaped glass tubes 1a1 are formed so as to be equally distributed on the circumference.

Each U-shaped glass tube 1a1 has seal portions 1a3 formed at both ends thereof, and one thin tube 1a4 protrudes from one seal portion 1a3 to the outside.

The thin tube 1a4 communicates with the inside of the translucent discharge vessel 1a. The thin tube 1a4 is used for evacuating the inside of the translucent discharge container 1, storing main amalgam (not shown), and filling a rare gas.

The connection pipe 1a2 is formed by a blow-down method.

The phosphor layer is mainly composed of a three-wavelength light emitting phosphor, and is formed on the inner surface side of the translucent discharge vessel 1a via a protective film mainly composed of alumina fine particles (not shown). Have been.

The electrode 1b is constituted by a filament electrode. The electrode 1b is formed by coating a double coil made of a tungsten wire with an oxide of an electron emitting material made of an alkaline earth metal.

The main amalgam is contained in the thin tube 1a4 of the translucent discharge vessel 1. And the main amalgam,
Hg consists of 6% by weight of Bi-In-Hg, and encapsulates three particles having a particle size of about 2.5 mm.

The auxiliary amalgam (not shown) is formed by plating a thin plate of stainless steel with indium In, and is welded to the lead wire so as to be located near the main amalgam.

[Regarding Lighting Circuit Means 2] The lighting circuit means 2 is mainly composed of a half-bridge type inverter, although the details of its circuit configuration will be described later.
The fluorescent lamp 1 is energized and turned on, and is housed in a cover 3 described later. And the high frequency output end
It is connected to the fluorescent lamp 1 as required as described later.
The lighting circuit means 2 includes a wiring board 2a and a circuit component 2b mounted thereon. The main circuit component 2b is mounted on the lower surface of the wiring board 2a in the figure. On the other hand, since the circuit component 2b has an inverted truncated conical shape in the cavity inside the cover 3, the circuit component 2b has a generally inverted conical shape with the circuit component such as a tall capacitor as the apex. It is mounted on the wiring board 2a. A pair of switching means Q1 and Q2 is a drain-exposed molded package type MOSFE having a DIP terminal.
Consists of T.

[Cover 3] The cover 3 is formed by molding a white light-shielding heat-resistant synthetic resin into a cup-shaped cylinder. Then, the base end 3a is narrowed narrowly,
b is open and the inside forms a cavity for housing circuit components.

[Regarding the base 4] The base 4 is made of an E26 type screw base, and is attached to the base end 3a of the cover 3 by caulking with a punch. The input end of the lighting circuit means 2 is connected to the center contact of the base 4 and the base shell.

[Globe 5] The globe 5 has a milky white light diffusing property by applying light diffusing fine particles to the inner surface of a transparent glass bulb, and has an A-shape.
Siege. And the base end of the glove 5 is the cover 3
Glove 5 and cover 3
Form an envelope AJ.

[About the partition plate 6] The partition plate 6 supports the fluorescent lamp 1 and the wiring board 2a, and divides the inside of the envelope AJ into a light emitting room A and a lighting circuit storage room B.

The partition plate 6 has the following structure for supporting the fluorescent lamp 1 and the lighting circuit means 2 and fixing the same together with the globe 5 to the cover 3.

That is, the partition plate 6 is provided with a cylindrical portion 6a which is opened downward in the figure and whose top is closed, and a flange portion 6b which protrudes outside the cylindrical portion 6a. And the cylindrical part 6a
Of the translucent discharge vessel 1a of the fluorescent lamp 1
An insertion hole 6a2 for inserting the vicinity of the seal portion at both ends of the U-shaped glass tube 1a1 is formed, and the vicinity of the seal portion of the U-shaped glass tube 1a1 is inserted and bonded with a silicone adhesive (not shown). The fluorescent lamp 1 is supported and fixed on a partition plate 6.

The wiring board 2a is inserted and supported inside the lower end of the cylindrical portion 6a of the partition plate 6.

Furthermore, the flange 6b of the partition plate 6 is
The partition plate 6 is inserted into the cover 3 so as to be in contact with the inner surface near the opening, and is fixed with a silicone adhesive (not shown) with the open end of the glove 5 inserted into the open end of the cover 3 from above. Have been.

[Circuit Configuration of Lighting Circuit Means 2] FIG. 4 is a circuit diagram showing lighting circuit means and a dimmer according to the first embodiment of the bulb-type fluorescent lamp of the present invention.

FIG. 5 shows a first embodiment of the compact fluorescent lamp of the present invention.
FIG. 9 is a circuit diagram showing a dimmer combined with the embodiment.

In the figure, AS is a low-frequency AC power source, a,
b is an AC terminal, DM is a dimmer, c and d are input terminals, f is an overcurrent fuse, NF is a noise filter, FBR is a rectifier circuit, SC is a serial circuit, C1 is a smoothing circuit, Q1 and Q2.
Is a first and second switching means, LC is a load circuit, FDG is a feedback drive signal generation circuit, HCP is a high-frequency current path, ST is a start circuit, and Def is a differentiation circuit. Each of the above components will be described.

<Regarding the Low Frequency AC Power Supply AS> The low frequency AC power supply AS is a commercial 100 V AC power supply.

<About AC Terminals a and b>
b is an input terminal as a discharge lamp lighting device, which is connected to both poles of the low-frequency AC power supply AS.

<Regarding the dimmer DM> As shown in FIG. 5, the dimmer DM has terminals t1 and t2, and a triac TRI.
An AC, an operation circuit OC, and a capacitor C2 are provided. The terminal t1 is connected to the AC terminal a in FIG.
Terminal t2 is similarly connected to input terminal c. Further, a triac TRIAC and a capacitor C3 are connected in parallel between the terminals t1 and t2. The operation circuit OC includes a phase shift circuit PSC and a diac DIAC.
The phase shift circuit PSC includes a variable resistor R1 and a capacitor C
2 series circuits and triac TRIA
C connected in parallel, phase shift output terminal and TRIAC TRI
A diac DIAC is connected between the terminal and an AC trigger terminal. <Regarding Input Terminals c and d> The input terminals c and d constitute the input terminals of the lighting circuit means, and are shown in FIG.
Is connected to the base 4.

<Overcurrent fuse f> The overcurrent fuse f is formed of a pattern fuse integrally formed on a wiring board 2a on which the circuit component 2b of the lighting circuit means 2 shown in FIGS. 1 and 3 is mounted. AS to dimmer DM
When the input current flowing into the bulb-type fluorescent lamp through the over-current becomes overcurrent, it is protected from being blown and the circuit from burning.

<Regarding Noise Filter NF> The noise filter NF is composed of an inductor L1 inserted in series between the low-frequency AC power supply AS and the rectifier circuit FBR, and a line between the dimmer DM and the rectifier circuit FBR. A high-frequency noise generated by switching in the high-frequency inverter HFI is removed so as not to flow to the low-frequency AC power supply AS side.

<Regarding Rectifier Circuit FBR> Rectifier Circuit FB
R is a bridge-type full-wave rectifier circuit, and has an AC input terminal connected between the output terminals of the noise filter NF.

<Regarding Inductor L2> Inductor L
2 has a first diode D1 and an inductor L
The second and second diodes D2 are connected, and one end thereof is connected to the positive electrode of the DC output terminal of the rectifier circuit FBR via the first diode D1. The other end is connected via a second diode D2 to a connection point between a smoothing circuit C1 described later and the first switching means Q1.

<Regarding Smoothing Circuit C1> Smoothing Circuit C
1 comprises an electrolytic capacitor. One end is connected to a connection point between the series circuit SC and the first switching means Q1, and the other end is connected to the negative electrode of the DC output terminal of the rectifier circuit FBR.

<Regarding First and Second Switching Means> The first switching means Q1 is composed of an N-channel MOSFET. Then, the drain of the first switching means Q1 is connected to the positive electrode of the smoothing circuit C1. The second switching means Q2 is a P-channel type M
It consists of OSFET. Then, the source of the second switching means Q2 is connected to the source of the first switching means Q1, and the drain is connected to the negative electrode of the smoothing circuit C1, so that the first and second switching elements Q1,
Q2 is connected in series so that the smoothed DC voltage of the smoothing circuit C1 is applied.

<About Load Circuit LC> Load Circuit LC
Is the resonance inductance L3 and the DC cut capacitor C
5 and a series circuit of a resonance voltage extracting capacitor C6, and a second switching means Q2
Are connected in parallel. And DC cut capacitor C
5 and the resonance voltage extracting capacitor C6 constitute the resonance capacitance according to the present invention. However, since the DC cut capacitor C3 has a relatively large capacitance,
As the resonance capacitance, a capacitor 6 for extracting a resonance voltage
Acts dominantly.

The resonance voltage extracting capacitor C6
, A pair of filament electrodes E1 and E2 of the fluorescent lamp FL are interposed in the load circuit LC. Therefore, the resonance voltage extracting capacitor C6 forms the filament heating circuit FHC of the fluorescent lamp FL, and the fluorescent lamp FL is connected in parallel to the resonance voltage extracting capacitor C6. In addition, the fluorescent lamp FL
Is the configuration shown in FIGS.

The resonance inductance L3 provides a current limiting impedance to the fluorescent lamp FL constituting the load, and has a middle tap ct.

<Feedback Drive Signal Generation Circuit FDG> The feedback drive signal generation circuit FDG is composed of a feedback transformer NST having an unsaturated configuration, a drive resonance circuit DRC, and a drive protection circuit DP.

(Regarding Feedback Transformer NST in Unsaturated Configuration) The feedback transformer NST in the unsaturated configuration includes a core CO, a primary winding wp, and a secondary winding ws.

The core CO is constituted by a drum-shaped ferrite core, and is not saturated because the magnetic path is open.

The primary winding wp is formed by winding an insulated conductor 10 turns on the secondary winding ws. And one end is the one end of the secondary winding ws, that is, the first and second ends.
Are connected to the sources of the switching means Q1 and Q2, and the other end is connected to one end of the resonance inductance L3. Therefore, the primary winding wp is inserted in series with the load circuit LC. The inductance Ln1 of the primary winding wp was 2.1 μH, and the equivalent inductance Ln1δ existing in series equivalently with the primary winding wp when the secondary winding ws was short-circuited was 1.2 μH. .

The secondary winding ws is formed by winding an insulated conductor on a core for 270 turns. One end is connected to the sources of the first and second switching means Q1, Q2. The inductance Ln2 of the secondary winding ws was 1857 μH. Also, the primary winding wp
Was short-circuited, the equivalent inductance Ln2δ existing in series equivalently to the secondary winding ws was 1855 μH.

Therefore, the ratio Ln2 / Ln1 of the inductance Ln2 of the secondary winding ws to the inductance Ln1 of the primary winding wp is 884.

Also, the inductance Ln of the secondary winding ws
Ratio Ln2δ / Ln2 of equivalent inductance Ln2δ to 2
Is about 1.

The above inductances are values measured at a frequency of 1 kHz and a voltage of 1 V.

(Regarding Drive Resonant Circuit DRC) The drive resonant circuit DRC is a feedback transformer NST having an unsaturated configuration.
Is connected in parallel with the capacitor C7 forming the drive resonance capacitance, thereby forming the secondary winding ws.
This is a series resonance circuit formed by the inductance Ln2 of s and the drive resonance capacitance of the capacitor C7. That is, one end of the capacitor C7 is connected in parallel to the secondary winding ws. Then, the connection point of the high voltage of the capacitor C7 and the secondary winding ws is connected to the gates of the first and second switching means Q1 and Q2 via the capacitor C8, and the connection point on the low voltage side is connected to the first connection point. And the source of the second switching means Q1, Q2.

Thus, the feedback voltage induced in the secondary winding ws resonates in series in the drive resonance circuit DRC.

(Regarding Drive Protection Circuit DP) The drive protection circuit DP includes a pair of zener diodes ZD1,
The first and second switching means Q1 and Q2 are connected between the gate and source of the first and second switching means Q1 and Q2.

<Regarding High Frequency Current Path HCP> The high frequency current path HCP is connected between the connection point of the inductor L2 and the second diode D2 of the series circuit SC and the middle point ct of the resonance inductance L3, and connects the capacitor C8. Included in series.

<Regarding Startup Circuit ST> Startup circuit ST
Are resistors R4, R3 and capacitors C8, 2
It is constituted by a series circuit of the next winding ws and a resistor R5.

One end of the resistor R4 has a smoothing circuit C1.
And the other end is connected to the gate of the first switching means Q1. The resistor R5 is connected in parallel between the source and the drain of the second switching means Q2.

Therefore, the starting circuit ST is connected in series between the output terminals of the smoothing circuit C1.

<Regarding Differentiating Circuit Def> Differentiating Circuit De
f is a series circuit of a capacitor C9 and a resistor R6, and is connected across both lines on the DC output side of the rectifier circuit FBR. When the light is turned on via the dimmer, the input current is prevented from becoming zero due to vibration at the moment when the dimmer is turned on.

[Circuit Operation] First, the operation of the high-frequency inverter HFI when the dimmer DM is not connected will be described.

When the low-frequency AC power supply AS is turned on, the DC voltage smoothed by the smoothing circuit C1 is applied between the drain and source of the first and second switching means Q1, Q2 connected in series. However, the first and second switching means Q1, Q2 remain off because no gate voltage is applied.

The above DC voltage is also applied to the starter circuit ST at the same time, causing a voltage drop corresponding to each resistance value. As a result, the voltage drop of the capacitor C8 connected in parallel with the resistor R3 causes the first switching means Q1
Is applied between the gate and the source, and the charge is discharged between the gate and the source. Thereby, the first switching means Q1 is turned on with a channel formed. On the other hand, the second switching means Q2 maintains the off state because the voltage drop of the drive protection circuit DP is in the opposite direction.

Then, when the first switching means Q1 is turned on, the drain / source of the first switching means Q1 and the primary winding wp of the feedback transformer NST having an unsaturated configuration are connected from the positive electrode of the smoothing circuit C1. A current flows through the load circuit LC, that is, the resonance inductance L3, the DC cut capacitor C5, the capacitor C6, and the negative electrode path of the smoothing circuit C1 in series. At this time, the resonance inductance L3 of the load circuit LC, the series resonance circuit of the DC cut capacitor C5 and the capacitor C6 resonate, and the capacitor C
The terminal voltage of No. 6 increases and is charged.

In addition, since a current flows through the primary winding wp of the transformer NST having the unsaturated configuration, a voltage having a waveform proportional to the current waveform is induced in the secondary winding ws.

On the other hand, since the inductance Ln2 of the secondary winding ws of the unsaturated transformer NST forms the drive resonance circuit DRC with the capacitance of the capacitor C7, the induced voltage of the secondary winding ws Resonates. Then, the resonance voltage continuously applies a forward voltage between the gate and the source of the first switching means Q1 via the capacitor C8 to maintain the ON state.

On the other hand, since the resonance voltage is applied in the opposite direction between the gate and the source of the second switching means Q2, the second switching means Q2 remains in the off state.

However, since the polarity of the resonance voltage of the drive resonance circuit DRC is inverted next due to the vibration caused by the resonance, the gate-source voltage of the first switching means Q1 becomes a reverse voltage and turns off. Then, the voltage between the gate and the source of the second switching means Q2 becomes the polarity in the drive direction and turns on.

Therefore, the first switching means Q1
Is ON time of the capacitor C of the drive resonance circuit DRC.
7 and the feedback transformer N in the unsaturated configuration
It is determined by the inductance Ln2 of the secondary winding ws of ST.

When the first switching means Q1 is turned off, the electromagnetic energy stored in the resonance inductance L3 is released, and the direct current cut capacitor C5, the capacitor C6, and the parasitic diode of the second switching means Q2 are released from the resonance inductance L3. , Primary winding p of resonant transformer NST and resonance inductance L3
When the current becomes zero, the charge of the capacitor C6 is reduced by the DC cut capacitor C5, the resonance inductance L3, the primary winding wp of the unsaturated transformer NST, and 2 discharges the path of the switching means Q2 and the capacitor C6, and the current flows in the opposite direction. At this time, the voltage induced in the secondary winding ws of the feedback transformer NST having an unsaturated configuration is opposite to that described above, and this voltage resonates in the drive resonance circuit DRC, and the first voltage to which the resonance voltage is applied is applied. The switching means Q1 maintains the off state, and the second switching means Q2 maintains the on state.

However, when the resonance voltage of the drive resonance circuit DRC oscillates and the polarity is reversed, the first switching means Q1 is turned on again, and the second switching means Q2 is turned off.

As a result, after the electromagnetic energy stored in the resonance inductance L3 is released, a current flows from the positive electrode of the smoothing circuit C1 to the load circuit LC again as described first. Hereinafter, the operation described above is repeated to operate as a half-bridge type inverter.

When the resonance voltage of the drive resonance circuit DRC is applied between the gate and the source of the switching means Q1 and Q2, the overvoltage is generated in the drive protection circuit DP.
The gate is protected from overvoltage.

In the load circuit LC, when a current flows through the resonance capacitor C6 during the above operation, the current flows through the filament electrodes E1 and E2 of the fluorescent lamp FL and heats the filament electrodes E1 and E2.
1 and E2 are in a state of emitting thermoelectrons, and since a high voltage due to resonance is applied between the filament electrodes E1 and E2, the fluorescent lamp FL is started and turned on like an instant start.

When the fluorescent lamp is turned on, the voltage between the filament electrodes E1 and E2 becomes a lamp voltage that is about half of the DC voltage, so that the resonance of the capacitor C6 is alleviated. Primary winding wp
, Voltage induction proportional to the lamp current is continued.

Next, the operation of the high frequency current path HCP will be described. That is, in the above operation, when the second switching means Q2 is turned on, the first diode D1, the inductor L2, the high-frequency current path HCP, and the resonance inductance L are connected from the positive electrode of the DC output terminal of the rectifier circuit FBR.
3, the left part of the resonance inductance L3 in the drawing, the second switching means Q2, and the rectifier circuit F.
The high-frequency current flows directly through the path of the negative electrode at the DC output terminal of the BR. This direct high-frequency current flows through almost the entire period of the low-frequency AC voltage. An example of the electrical characteristics according to the present embodiment is shown below. Input power 16.4W, input current 0.19
On the other hand, in the case of a bulb-type fluorescent lamp employing a conventional capacitor input type lighting circuit means, the input current is a pulse-shaped charging current of the smoothing capacitor, A pause period occurs before and after the charging current.

Next, the dimming operation by the dimmer DM will be described.

During the rest period of the triac TRIAC of the dimmer DM, a low voltage proportional to the input impedance of the capacitor C2 and the compact fluorescent lamp is applied to the compact fluorescent lamp. In the lighting circuit means 2, the voltage in the pause period is rectified by the rectifier circuit FBR,
The half-bridge inverter is activated by applying the voltage smoothed by the smoothing circuit C1, and the high-frequency current is supplied for almost the entire period of the non-smooth DC voltage of the rectifier circuit FBR regardless of whether the dimmer DM is conductive or not. Passage HCP and second
, A relatively small value of a direct high-frequency current flows through the switching means Q2. In addition, it is possible to suppress a decrease in lamp efficiency due to a direct flow of a high-frequency current to about 2%.

On the other hand, in the dimmer DM, when the output voltage of the phase shift circuit PSC, that is, the terminal voltage of the capacitor C3 rises and the diac DIAC turns on, the gate current flows into the triac TRIAC and turns on. Then, by changing the value of the variable resistor R1 of the operation circuit OC, the phase shift is performed, the conduction phase of the triac TRIAC changes, and the conduction section changes. Since the high-frequency current in the bulb-type fluorescent lamp flows directly through the triac TRIAC during the ON period, a holding current can be secured during the ON period.

Hereinafter, the waveform of the direct high-frequency current in the dimming lighting state of the bulb-type fluorescent lamp will be described with reference to FIGS.

FIG. 6 shows a first embodiment of the compact fluorescent lamp of the present invention.
FIG. 9 is a waveform chart showing waveforms of an input voltage and an input current in an all-light state in the embodiment.

FIG. 7 shows a first embodiment of the compact fluorescent lamp of the present invention.
FIG. 13 is a waveform chart showing waveforms of an input voltage and an input current at a conduction angle of 90 ° in the embodiment.

FIG. 8 shows a first embodiment of the compact fluorescent lamp of the present invention.
FIG. 9 is a waveform chart showing waveforms of an input voltage and an input current near a dimming limit in the embodiment.

In each of the figures, V indicates an input voltage, and I indicates an input current. In addition, in the input current, Ic
Is a capacitor charging current, and Ih is a direct high-frequency current.

FIG. 9 shows a second embodiment of the compact fluorescent lamp of the present invention.
It is a circuit diagram showing lighting circuit means in the embodiment.

In the figure, the same parts as those in FIG. 4 are denoted by the same reference numerals, and description thereof will be omitted. The present embodiment is different in that the other end of the high-frequency current path HCP is connected to a connection point between the resonance inductance L3 of the load circuit LC and the DC cut capacitor C5.

FIG. 10 is a circuit diagram showing a third embodiment of a compact fluorescent lamp according to the present invention.

In the figure, the same parts as those in FIG. 4 are denoted by the same reference numerals, and the description is omitted. This embodiment differs from the first embodiment in the configuration of the smoothing circuit C1 '.

That is, the smoothing circuit C1 'is constituted by a Schottney voltage smoothing circuit and the drive protection circuit D
The connection position of ef is different. The Schottney component voltage smoothing circuit divides the smoothing capacitor into C11 and C12, connects them in series with the rectifier circuit FBR with the diode D5 and charges them, and connects the diodes D3 and D4 in series. The high frequency inverter HFI is connected in parallel to supply DC current,
This is a circuit configuration in which the withstand voltage of the smoothing capacitor is reduced. Then, a differentiating circuit Def is connected in parallel with the diode D5. The high-frequency inverter HFI can use the embodiment shown in FIGS. 4 and 9. However, if necessary, the high-frequency current path may not be provided. It should be noted that, in comparison with FIG. 1, illustration of components other than those described above is omitted.

Thus, according to the present embodiment, the breakdown voltage of the differentiating circuit Def can be reduced to half that of FIG.

FIG. 11 is a waveform chart showing the entire waveforms of the input voltage and the input current in the dimming state in the third embodiment of the bulb-type fluorescent lamp of the present invention.

FIG. 12 is an enlarged waveform diagram showing the main parts of the waveforms of the input voltage and the input current at the moment when the phase control element of the dimmer is turned on.

FIG. 13 is an enlarged waveform diagram showing the main parts of the waveforms of the input voltage and the current flowing through the differentiating circuit.

FIG. 14 is an enlarged waveform diagram showing the main parts of the waveforms of the input voltage and the input current at the moment when the phase control element of the dimmer of the comparative example is turned on.

In each figure, V is an input voltage waveform, I is an input current waveform, and Idef is a differential circuit current. Note that the comparative example does not include the differentiating circuit Def.

As can be understood from the figure, in this embodiment, the input current does not become zero at the moment when the dimmer is turned on, so that the dimmer does not malfunction. On the other hand, in the comparative example, since the input current is instantaneously zero at the same time, the dimmer is likely to malfunction.

FIG. 15 is a circuit diagram showing a bulb-type fluorescent lamp according to a fourth embodiment of the present invention.

In the figure, the same parts as those in FIG. 10 are denoted by the same reference numerals, and description thereof will be omitted.

The present embodiment is different in that the differentiating circuit Def has the same configuration as that of FIG.

FIG. 16 is a front view showing a wall-mounted lamp using a compact fluorescent lamp as an embodiment of the lighting device of the present invention.

In the figure, reference numeral 11 denotes a lighting device main body, and reference numeral 12 denotes a bulb-type fluorescent lamp.

The lighting device main body 11 is made of earthenware, has a hollow interior, an open lower surface, and a mounting portion formed on a side surface. Further, a lamp socket 11a is provided inside.

The bulb-type fluorescent lamp 12 is shown in FIGS.
The glove 5 and the cover 3 have a generally spherical shape, that is, a so-called G shape. Then, the base is inserted into the lighting device main body 11 from the lower surface thereof and screwed into the lamp socket 11a, whereby the light bulb shaped fluorescent lamp 12 is mounted on the lighting device main body 11.

[0193]

According to the first to fourth aspects of the present invention, a low-frequency AC is rectified by a rectifier circuit, a smoothed DC voltage is obtained by a smoothing circuit, and the first and second DC voltages are connected in series. Second
And a load circuit having at least a resonance inductance and a resonance capacitance operated by high-frequency alternating current generated by alternately switching by using a feedback drive signal generation circuit, and a rectifier circuit. Insert an inductor in series with the smoothing circuit, connect one end to the DC output terminal of the rectified DC power supply via the inductor, connect the other end to the load circuit, connect the high-frequency current path, and resonate. Since the high-frequency current flows directly from the rectifier circuit through at least a part of the inductance and the second switching means, the input current does not increase even when connected to the low-frequency AC power supply via the dimmer. Bulb-type fluorescent lamp that does not have a short life and does not cause flicker of brightness due to malfunction It is possible to provide a pump.

According to the second aspect of the present invention, the feedback drive signal generating circuit further includes the feedback transformer and the drive resonance circuit having an unsaturated configuration, so that the feedback transformer does not require a particularly high dielectric strength. , Characteristics are small,
Moreover, by using a small and inexpensive feedback transformer,
An inexpensive bulb-type fluorescent lamp can be provided.

According to the third aspect of the present invention, it is possible to provide a bulb-type fluorescent lamp in which the load circuit side of the high-frequency current path is connected to the midpoint of the resonance inductance.

According to the invention of claim 4, it is possible to provide a bulb-type fluorescent lamp in which the load circuit side of the high-frequency current path is connected to the connection point of the resonance inductance and the DC cut capacitor.

According to the fifth aspect of the present invention, it is possible to provide a bulb-type fluorescent lamp in which the load circuit side of the high-frequency current path is connected to a connection point of a resonance inductance and a capacitor for extracting a resonance voltage.

According to the invention of claim 6, it is possible to provide a lighting device having the effects of claims 1 to 5.

[Brief description of the drawings]

FIG. 1 is a partial cross-sectional front view showing a first embodiment of a bulb-type fluorescent lamp of the present invention.

FIG. 2 is a plan view of the same glove.

FIG. 3 is an exploded perspective view of the same.

FIG. 4 is a circuit diagram showing lighting circuit means and a dimmer in the first embodiment of the bulb-type fluorescent lamp of the present invention.

FIG. 5 is a circuit diagram showing a dimmer combined with the first embodiment of the bulb-type fluorescent lamp of the present invention.

FIG. 6 is a waveform chart showing input voltage and input current waveforms in an all-light state in the first embodiment of the bulb-type fluorescent lamp of the present invention.

FIG. 7 is a waveform chart showing input voltage and input current waveforms at a conduction angle of 90 ° in the bulb-type fluorescent lamp according to the first embodiment of the present invention.

FIG. 8 is a waveform chart showing input voltage and input current waveforms near the dimming limit in the first embodiment of the bulb-type fluorescent lamp of the present invention.

FIG. 9 is a circuit diagram showing lighting circuit means in a bulb-type fluorescent lamp according to a second embodiment of the present invention.

FIG. 10 is a circuit diagram showing a third embodiment of the bulb-type fluorescent lamp of the present invention. Similarly, a waveform diagram showing the voltage of the secondary winding under the rated load.

FIG. 11 is a waveform diagram showing the entire waveforms of the input voltage and the input current in the dimming state in the third embodiment of the bulb-type fluorescent lamp of the present invention.

FIG. 12 is an enlarged waveform diagram showing a main part of the waveforms of the input voltage and the input current at the moment when the phase control element of the dimmer is turned on.

FIG. 13 is an enlarged waveform diagram showing a main part of a waveform of a current flowing through an input voltage and an impedance adjustment circuit in the same manner.

FIG. 14 is an enlarged waveform diagram showing a main part of the waveforms of the input voltage and the input current at the moment when the phase control element of the dimmer of the comparative example is turned on.

FIG. 15 is a circuit diagram showing a fourth embodiment of a compact fluorescent lamp according to the present invention;

FIG. 16 is a front view showing a wall-mounted lamp using a bulb-type fluorescent lamp as one embodiment of the lighting device of the present invention.

[Explanation of symbols]

 AS: low frequency AC power supply a: AC terminal b: AC terminal c: input terminal d: input terminal DM: dimmer f: overcurrent fuse NF: noise filter FBR: rectifying circuit Def: differentiating circuit L2: inductor C1: smoothing Q1 ... first switching means Q2 ... second switching means ST ... start circuit FDG ... feedback type drive signal generation circuit NST ... unsaturated feedback transformer CO ... &#9; core wp ... primary winding ws: Secondary winding DRC: Drive resonance circuit DP: Drive protection circuit DC2: Second drive circuit LC: Load circuit L3: Resonance inductance ct: Middle point C5: DC cut capacitor C6: Capacitor for extracting resonance voltage DP: Drive Protection circuit FL: fluorescent lamp E1: filament electrode E2: filament electrode

 ──────────────────────────────────────────────────続 き Continued on the front page F term (reference) 3K072 AA02 BA03 CA03 DB03 EA06 FA05 GA02 GB12 GC02 HA05 3K098 CC07 CC22 CC40 DD20 DD21 DD35 EE13 GG02 5C039 EB11

Claims (6)

[Claims] A light-transmitting discharge vessel formed in a compact shape such that a bent discharge path is formed therein; a phosphor layer disposed on an inner surface side of the light-transmitting discharge vessel; A fluorescent lamp including a pair of electrodes sealed at both ends of a light-emitting discharge vessel, and an ionization medium containing mercury and a rare gas sealed inside the light-transmitting discharge vessel; an input terminal connected to a low-frequency AC power supply , A noise filter connected to the input terminal, a rectifier circuit having an AC input terminal connected to the output terminal side of the noise filter, a smoothing circuit for smoothing a non-smoothed DC output voltage of the rectifier circuit, a smoothed DC voltage of the smoothing circuit , A first switching means and a second switching means connected in series such that a voltage is applied to the first switching means and the second switching means. A load circuit that is operated by the generated high-frequency alternating current and is connected in parallel with the fluorescent lamp to at least a part of the resonance capacitance; a current flowing through the load circuit is fed back to drive the first and second switching means; A feedback drive signal generating circuit, an inductor inserted in series between the DC output terminal of the rectifier circuit and the smoothing circuit, and one end connected to the DC output terminal of the rectified DC power supply via the inductor. Lighting circuit means having a high-frequency current path connected to the load circuit so that the other end passes through at least a part of the resonance inductance of the load circuit and the second switching means so that the high-frequency current flows directly from the rectified DC power supply; A cover for accommodating the lighting circuit means therein and supporting the fluorescent lamp; connecting to an input end of the lighting circuit means, Compact fluorescent lamp, characterized in that it comprises a; and the cap disposed at the proximal end of the chromatography. 2. A feedback drive signal generating circuit comprising: a transformer having an unsaturated configuration in which a primary winding is connected to a load circuit and a voltage proportional to a current flowing through the load circuit is induced in the secondary winding; A drive circuit formed by a drive resonance capacitance and an inductance of a secondary winding of a transformer having an unsaturated configuration, and a drive circuit for alternately driving the first and second switching means by a resonance output. Item 7. A bulb-type fluorescent lamp according to Item 1. 3. A load circuit comprising a DC cut capacitor and a resonance voltage extracting capacitor having a resonance capacitance connected in series, and a fluorescent lamp connected in parallel to the resonance voltage extracting capacitor. ;
The high-frequency current path is connected at the other end to the midpoint of the resonance inductance of the load circuit.
Or the bulb-type fluorescent lamp according to 2. 4. A load circuit comprising a DC cut capacitor and a resonance voltage extracting capacitor having a resonance capacitance connected in series, and a fluorescent lamp connected in parallel to the resonance voltage extracting capacitor. ;
3. The light bulb-shaped fluorescent lamp according to claim 1, wherein the other end of the high-frequency current path is connected to a connection point of a resonance inductance of a load circuit and a DC cut capacitor. 5. A load circuit comprising a DC cut capacitor and a resonance voltage extracting capacitor having a resonance capacitance connected in series, a fluorescent lamp connected in parallel to the resonance voltage extracting capacitor, and a resonance inductance and a DC voltage. A resonance voltage extracting capacitor is connected between the cut capacitors; the other end of the high-frequency current path is connected to a connection point of the resonance inductance of the load circuit and the resonance voltage extracting capacitor. The bulb-type fluorescent lamp according to claim 1 or 2, 6. A lighting device comprising: a lighting device main body; and the bulb-type fluorescent lamp according to claim 1 supported by the lighting device main body.