JP2001231286A - Dc brushless motor system - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a DC brushless motor system capable of rationally transferring from a start of an inverter to an ordinary operation. SOLUTION: The DC brushless motor system drives an inverter by a position detection signal Su1 obtained by detecting a rotary position of a rotor to operate a motor. It is controlled in response to the number of the detection signals obtained after starting the position detection mask time tf for specifying the detection of the detection signal. A communication delay time tg for specifying a communication time point Ut continued to the detection signal is controlled similarly corresponding to the number of the detection signals. An increasing ratio of a drive frequency of the inverter is controlled to a larger increasing ratio than that when ordinarily operated and controlled. These correspondence and the increasing ratio are suitably combined, and conducted only during a period from the start of the mask time tf to the arrival of the rotor at a predetermined rotational speed. Since the control corresponding to the number of the detection signal from the start of the mask time is conducted, even if a load of the rotor is changed in a pulsating manner on the way, it can be early transferred to the stationary operation.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a D brushless motor in which the drive of an inverter circuit is controlled by a position detection signal obtained by detecting the position of a rotor of a DC brushless motor.
The present invention relates to a C brushless motor device.

[0002]

2. Description of the Related Art As a configuration of such a DC brushless motor device, for example, a configuration as shown in FIG.
No. 2378 discloses this. In FIG.
The power supply unit 1 is a DC power supply, and is a part that obtains a bus voltage Dcc of an inverter circuit 2 for obtaining a pulse modulation voltage described later. For example, the DC power supply is obtained by rectifying and smoothing an AC power supply.

The inverter circuit 2 controls a plurality of phases, for example, a U-phase, a V-phase, and a W-phase by controlling transistors TrU to Trz, for example, a power transistor and an IGBT element by a drive signal from a drive circuit 4. Generates a three-phase pulse width modulation voltage, and applies it to each of the stator windings 3U, 3V, 3W of the DC brushless motor 3 to generate a rotating magnetic field, thereby rotating the rotor 3R. Although not shown, the rotor 3R is provided with a plurality of magnetized magnetized poles, for example, two pairs of N poles and S poles.

The transistor TrU by the drive circuit 4
7 is driven as shown in [Transistor drive waveform] in FIG. 7, where a fine pulse waveform portion is a chopped pink portion, a U-phase terminal R, a V-phase terminal S, and a W-phase terminal. The voltage output to T appears as, for example, a waveform before the voltage division of the [terminal voltage division waveform] in FIGS. 7 and 8.

Here, since the U-phase, V-phase and W-phase are alternating current,
When viewed in time series, U-phase → V-phase → W-phase → U-phase → V-phase → W-phase...
The phase is the first phase, the W phase is the last phase, and W
For the phase, the V phase is the first phase, the U phase is the last phase, and for the U phase, the W phase is the first phase, V
The phases are in reverse order.

Therefore, a voltage dividing circuit of resistors Rau and Rbu, a voltage dividing circuit of resistors Rav and Rbv, and resistors Raw and Rb
The voltage of each voltage input to the positive terminals of the comparator CPu, the comparator CPv, and the comparator CPw, that is, each of the positive terminals of the comparator CPu, the comparator CPv, and the comparator CPw is shown in FIG. The U-phase divided voltage Ua, the V-phase divided voltage Va, and the W-phase divided voltage Wa have waveforms such as U-phase, V-phase, and W-phase.

The bus voltage Dcc is divided by a voltage dividing circuit composed of resistors Rd and Rc, and the negative terminal of the virtual neutral point voltage E0 input to the negative terminals of the resistance comparators CPu, CPv and CPw, ie, the-terminal. The waveform of the voltage is as shown in FIG. 8 [divided waveform of power supply voltage (virtual neutral point voltage)]. Note that the resistances Rd and Rc are
The resistors Ra to R in the U-phase, V-phase, and W-phase voltage dividing circuits
d, [Rb / (Ra + Rb)] = [2Rd /
(Rc + Rd)] so that the virtual neutral point voltage E0 becomes the U-phase divided voltage Ua · V-phase divided voltage V
The a / W phase divided voltage Wa is positioned at the center of the amplitude.

The comparator CPu is a U-phase position detection comparator, the comparator CPv is a V-phase position detection comparator, and the comparator CPw is a W-phase position detection comparator.
Position detection signal Su · Sv · S obtained by detecting with CPw
w is given to a control processing section mainly composed of a microcomputer, that is, a microcomputer 5, and the microcomputer 5 controls the drive circuit 4 by a predetermined control, thereby driving each of the transistors TrU to TrZ of the inverter circuit 2. I have.

When the rotor 3R rotates, the stator winding 3U
Since an induced voltage appears in the stator winding of the phase in which the pulse width modulation voltage of 3V / 3W is not energized, as shown in the figure, "rising induced voltage" and "falling edge" follow each spike voltage. "Induced voltage" appears.

Then, each of the comparators CPu, CPv,
By comparing these voltages, CPw detects the intersection P with the above-described virtual neutral point voltage E0, that is, the zero-crossing point P, in the “rising electromotive voltage” and “falling electromotive voltage” parts. The detection signals are output as position detection signals Su, Sv, Sw.

For example, taking the comparison detection state of the comparator CPu as an example, it is as shown in [U-phase position detection comparator positive / negative terminal input voltage (overwriting)], and the zero cross point P is detected. Then, the “U-phase rising position detection point” and the “U-phase rising position detection point” are output as position detection signals, as in “U-phase position detection comparator output voltage” in FIG. Note that the comparison detection states of the comparators CPv and CPw of the other phases are shown in FIG.
Phase position detection comparator positive and negative input voltage (overwrite)]
Is shifted by 120 ° in phase.

In this detection, the microcomputer 5 first detects the rising edge from Low to High after the output of the U-phase position detection comparator CPu has elapsed after the elapse of the time when the spike voltage in the previous energization pattern has ended. The obtained signal is captured as a position detection signal Su1,
After a lapse of time during which the rotor 3R rotates by a certain angle, the energization is switched to the energization pattern from the next transistor TrU to the transistor TrY.

Then, after elapse of the time when the spike voltage in the previous energization pattern from the transistor TrU to the transistor TrY has elapsed, the microcomputer 5 first changes the W-phase comparator output CPw from High to Lo.
The signal obtained by detecting the falling edge to w is taken in as a position detection signal (not shown), and after a lapse of time during which the rotor 3R rotates by a certain angle, the current is applied according to the energization pattern from Tru to TrZ. Switch to energization.

Similarly, when power is supplied from transistor TrU to transistor TrZ, V-phase comparator CPv
In response to a position detection signal (not shown) that detects the rising edge of the output of
Switch to energization to rZ.

From the transistor TrV to the transistor Tr
At the time of energization to Z, the current is switched from the transistor TrV to the transistor TrX by the position detection signal Su2 which detects the falling edge of the output of the U-phase comparator CPv.

From the transistor TrV to the transistor Tr
At the time of energization to X, switching to energization from transistor TrW to transistor TrX is performed by a position detection signal (not shown) that detects the rising edge of the output of W-phase comparator CPW. When the transistor TrW is energized to the transistor TrX, an operation is performed to switch the energization from the transistor TrW to the transistor TrY according to a position detection signal (not shown) that detects the falling edge of the output of the V-phase comparator CPv.

In this manner, the microcomputer 5 controls the inverter circuit 2 so that the rotor 3R can continue rotating while obtaining the position information of the rotor 3R based on the output waveforms of the comparators CPu, CPv, and CPw. It is driving.

The driving state as described above is such that the rotor 3R
Inverter circuit 2 using position detection signals Su, Sv, Sw
This is a state of operation (referred to as steady-state operation in the present invention) in which the inverter circuit 2 can rotate while following the increase or decrease in the drive frequency of the inverter circuit 2 while rotating synchronously with the drive.

On the other hand, when the driving of the inverter circuit 2 is started to start the rotation of the rotor 3R, the stationary inertia of the rotor 3R, the shaft friction, the rotor 3R
In this case, the position detection of the rotor 3R is unstable due to the load driven by the motor, so that it is not easy to perform the operation synchronized with the position detection signals Su, Sv, Sw.

As a configuration for solving such inconvenience, immediately after the drive of the inverter circuit 2 is started, the energization of the stator windings 3U, 3V, 3W by the position detection signals Su, Sv, Sw of the rotor 3R is performed. Without switching, for example, a clock circuit provided in the microcomputer 5 forcibly switches the energization to the stator windings 3U, 3V, and 3W, and performs forced synchronous operation of the inverter circuit 2. For example, Japanese Patent No. 9682164 discloses a configuration in which, after an operation of gradually increasing the output voltage by a predetermined amount with time, the operation is shifted to a synchronous operation based on a steady position detection (hereinafter, referred to as a first related art). .

In addition, the position of the rotor 3R is detected immediately after the start of the inverter circuit 2 without performing the above-described forced synchronous operation. For example, “TrW → TrY” in FIG.
Taking the section of “TrUu → TrY” as an example, as shown in FIG. 9 [normal operation state], a transistor that is previously energized, for example, a transistor TrW • Tr
The point at which the operation of switching from X to the next energized transistor, for example, the transistor TrW / TrY (referred to as commutation in the present invention), that is, the commutation point Wt
Then, the position detection signal Su1 is detected.

In detecting the position detection signal Su1,
The next commutation is performed based on the time width (referred to as position detection mask time in this invention) Mt for performing position detection after restricting the position detection not to be performed for a predetermined section time, and the position detection. The time point Ut, that is, a delay time for regulating the time point of switching to the energization of the transistors TrU and TrY to a time point delayed by a predetermined time from the position detection position (the commutation delay time in the present invention) ) Lt is set to a predetermined time length to control the driving of the inverter circuit 2.

In addition to this control, a configuration is known in which the frequency of driving the inverter circuit 2 is gradually increased, and the operation is shifted to synchronous operation by stationary position detection (hereinafter referred to as a second conventional technique).

FIG. 9 shows the normal operation state of FIG.
Although only the portion corresponding to the “U-phase falling position detection point” in FIG. 8 is shown, the portion corresponding to the “U-phase falling position detection point” in FIG. Similarly, it appears as an amplitude change opposite to the amplitude change in FIG. Furthermore, for the V and W phases,
Similarly, two position detection portions appear. And, as described above, the rotor 3R has two pairs of N and S poles,
In the case where two counter electrodes are magnetized, (3 phases × 2 places) × 2 counter electrodes, that is, 12 position detection portions appear.

In the configuration of such a DC brushless motor device, as shown in FIG. 10, due to the synchronous operation with the rotor 3R, the detection position of the position detection signals Su, Sv, Sw is changed to the intersection Pa or the intersection Pb. In order to shift the induced voltage forward or backward, the virtual neutral point voltage E0
Voltage dividing circuit or divided voltage Ua, Va, W for each phase
By changing the voltage dividing ratio of the voltage dividing circuit obtaining a,
A configuration for detecting the virtual neutral point voltage E0 by shifting it up and down like E01 and E02 in FIG. 10 (hereinafter, referred to as a third conventional technique) is well known, and in such a configuration, the virtual neutral point voltage E0 may correspond to the intersection Pa or the intersection Pb. Needless to say, the position detection mask time Mt and the commutation delay time Lt are set.

[0026]

In the first prior art, the forced synchronous operation is performed without performing the position detection. Therefore, the drive is tuned or stepped out due to the fluctuation of the load driven by the rotor 3R. Since the output voltage of the inverter circuit 2 must be gradually increased to such a degree that the inverter circuit 2 does not stop abnormally, the time required to shift to synchronous operation by steady-state position detection cannot be accelerated, and is considerably long. There is a disadvantage that it takes time.

In the second prior art, there is an advantage that the operation can be shifted to the synchronous operation by the stationary position detection in a shorter time than in the first prior art, but when there is a change in the load driven by the rotor 3R, there is an advantage. However, since the position detection is disturbed by the fluctuation, there is an inconvenience that the operation cannot be shifted to the synchronous operation based on the stationary position detection. Therefore, there is a problem that it is desired to provide a device that eliminates such inconveniences.

[0028]

SUMMARY OF THE INVENTION The present invention provides a rotor having a plurality of magnetized poles as described above, and a plurality of phase stator windings arranged to apply a rotating magnetic field to the rotor when energized. In the DC brushless motor provided with the above, a predetermined stator winding is energized with a pulse width modulation voltage generated by an inverter circuit to form a rotating magnetic field, and the energization is performed by rotation of the rotor. The point at which the energization is performed is controlled based on a position detection signal obtained by comparing and detecting an induced voltage generated in the stator winding of a non-phase and a predetermined voltage for each of the plurality of phases. In the DC brushless motor device,

In starting the inverter circuit 2 described above,
Mask time control for controlling the increase or decrease of the position detection mask time that regulates the detection of the position detection signal following the preceding commutation time point in accordance with the number of the position detection signals obtained after starting the start. A first configuration for providing means,

In addition to the first configuration, in the above-described start, an increase or decrease in the commutation delay time that regulates the commutation time following the preceding position detection signal can be obtained after the start is started. A second configuration including a commutation time control unit that performs control in accordance with the number of times of the position detection signal,

In addition to the above-described first configuration, the increase rate of the drive frequency of the inverter circuit immediately after the start of the start is determined by the increase rate of the drive frequency during the steady operation of the inverter circuit. A third configuration in which a drive frequency increase / decrease control means for controlling at a larger increase rate is provided;

In the first configuration, the control for increasing or decreasing the position detection mask time is performed only during the period from the start of the start to the time when the rotation of the rotor reaches a predetermined rotation speed. A fourth configuration to be performed;

In the second configuration, the control for increasing or decreasing the commutation delay time is performed only during the period from the start of the start to the time when the rotation of the rotor reaches a predetermined rotation speed. A fifth configuration adapted to be performed,

In the third configuration, the control based on the large increase rate is performed only from the time when the starting is started to the time when the rotation of the rotor reaches a predetermined rotation speed. A sixth configuration,

In the DC brushless motor device similar to the DC brushless motor device according to the first configuration, from the time when the inverter circuit 2 is started to the time when the rotation of the rotor reaches a predetermined rotation speed. Only during the period, the increase or decrease of the position detection mask time that regulates the detection of the position detection signal following the preceding commutation point is controlled in accordance with the number of the position detection signals obtained after the start is started. Mask time control means,

The commutation delay time that regulates the commutation time following the preceding position detection signal only during the period from the start of the start to the time when the rotation of the rotor reaches a predetermined number of revolutions. Commutation time control means for controlling the increase / decrease in accordance with the number of times of the position detection signal obtained after starting the start,

Only during the period from the start of the start to the time when the rotation of the rotor reaches a predetermined speed, the drive frequency of the inverter circuit immediately after the start of the start is increased by The seventh object of the present invention is to solve the above-mentioned problem by providing a driving frequency increase / decrease control means for controlling the driving frequency at an increasing rate larger than the increasing rate of the driving frequency during the steady operation of the inverter circuit.

[0038]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS As an embodiment of the present invention, an embodiment in which the present invention is applied to the configuration of the prior art shown in FIGS. 6 to 9 will be described with reference to FIGS. 1 to 5
6, the same reference numerals as those in FIGS.
This is a part having the same function as the part with the same reference numeral described in. 1 to 5 are the same as those in FIG.
5 have the same functions as the portions denoted by the same reference numerals described in any of FIGS.

[0039]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS [First Embodiment] A first embodiment will be described below with reference to FIGS. The configuration of the first embodiment generally constitutes the first configuration and the fourth configuration described above, and different points from the configuration of the prior art shown in FIGS. In order to perform the control processing described with reference to FIGS. 2 and 3, a program of a control processing flow for performing the control processing is stored in advance in the processing memory 5A of the microcomputer 5 in FIG. This is a place where data such as a reference value, for example, data of each value in FIG. 3 is stored in the data memory 5B of the microcomputer 5 in FIG. 1 in advance.

The position detection portion when the inverter circuit 2 is in a steady operation state, that is, when the rotor 3R is performing follow-up rotation in synchronization with the rotating magnetic field generated by driving the inverter circuit 2 based on the position detection signals Su to Sw, For example, similarly to FIG. 9, “TrW → TrY”, “TrUu → T” in FIG.
In the example of the section of “rY”, the state appears as [steady state of operation] in FIG. 2, but the state where the rotation of the rotor 3R has not been able to follow the rotation of the rotor 3R immediately after starting the inverter circuit 2 is started. The position detection part shown in FIG. 2 appears as shown in FIG.

The [steady state of operation] in FIG. 2 corresponds to the position detection portion of the "U-phase rising position detection point" in [U-phase position detection comparator positive / negative terminal input voltage] in FIG. The intersection P after a predetermined position detection mask time Mt has elapsed from the preceding commutation time Wt,
That is, the zero cross point is detected and the position detection signal Su1 is detected.
And the time when the commutation delay time Lt has elapsed from the time of the position detection signal Su1 is defined as the next commutation time Ut.

In the [starting operation state] of FIG. 2, immediately after the start of the inverter circuit 2, the rotating direction of the rotor 3R is not fixed, and the rotating speed of the rotor 3R is extremely low. The induced voltage appearing on line 3U is small. For this reason, an induced voltage waveform like the uncertainty C shown in the figure may occur, and it is difficult to accurately detect the position, which causes a reduction in the starting performance.

Therefore, in the configuration of the first embodiment, FIG.
The position detection mask time Mt
Is increased or decreased in accordance with the number of times of detection Sn of the position detection signal, for example, the number of times of detection Sn obtained by summing the number of times of detection of all the position detection signals Su, Sv, and Sw.
The structure is such that stable start can be performed and the operation can be reliably shifted to synchronous operation based on steady position detection.

More specifically, as shown in FIG. 3, the position detection mask time Mt is represented by, for example, an electrical time width, that is, a phase angle width, and a plurality of steps, for example, in advance.
The first stage Mt1, the second stage Mt2, and the third stage Mt3 are set, and each of these stages is set to a plurality of stages, for example, the first stage Sn1 and the second stage Sn2.
It is set to correspond to.

Here, the number Sn of the position detection signal is, for example, the number of times per unit time at which the position detection signal is integrated up to that point, ie, the rotational speed. , And both. That is, in the present invention, the “number of times of the position detection signal” refers to both the case of using the integration number and the case of using the rotation speed. In the following description, a case will be described in which the configuration is made using the integrated rotation.

The specific value of each data is set as follows in the case of (3 phases × 2 places) × 2 counter electrodes, for example. Mt1 = 45 ° Mt2 = 37.5 ° Mt3 = 30 ° Sn1 = 12 times (for one rotation of the rotor 3R) Sn2 = 120 times (for 10 rotations of the rotor 3R).

Although the [operating conditions] of FIG. 3 are shown in a graph for easy understanding, in practice, a table corresponding to the data values of FIG. 3 is stored in the data memory 5B. In addition, the control operation is performed while being selected by a control processing flow program stored in the processing memory 5A in advance. Note that the control processing flow is as simple as discriminating the data on the horizontal axis from the detection signal and outputting the data on the vertical axis as a control signal, and a description thereof is omitted here.

According to this control process, even when the load of the rotor 3R fluctuates and the rotational speed of the rotor 3R fluctuates, the position detection mask time Mt can be increased or decreased in accordance with the fluctuation. Despite such fluctuations, synchronous operation is possible. For example, the second stage Sn2 of the rotational speed Sn
When it becomes, it is possible to stably and reliably shift to the synchronous operation by the steady position detection.

In the configuration of the first embodiment, the first
, The position detection mask time Mt is controlled in accordance with the number Sn of the position detection signals of the rotor 3R.
The control is performed only from the time when the start of the inverter circuit 2 is started to the time when the rotor 3R reaches the predetermined number of revolutions, that is, only until the number of times of detecting the position detection signal reaches the predetermined number of times. It is something that will be.

In the above setting, each stage of the control of the position detection mask time Mt, for example, the first stage Mt1 and the second stage
Step Mt2 / Third step Mt3 is defined as Mt1>Mt2> Mt3
Although the configuration is such that the number of times of the position detection signal Sn is gradually decreased so as to satisfy the condition described above, if there is a large pulsation in the load of the rotor 3R after the start of the start, the load of such a load is reduced. The setting may be made so as to correspond to the fluctuation.

That is, for example, when the load fluctuates as in [Load state (No. 1)] in FIG. 3, Mt1 <Mt
3 <Mt2, and, for example,
When the load changes as in [Load state (No. 2)] in FIG. 3, the condition is set so that Mt1 <Mt2 <Mt3.

[Second Embodiment] A second embodiment will be described below with reference to FIGS. The configuration of the second embodiment generally constitutes the above-described second configuration and the fifth configuration. Differences from the configuration of the first embodiment are as follows.
In addition to the configuration of the first embodiment, a program for a control processing flow for performing the control processing as described in FIGS. 2 and 4 is stored in the processing memory 5A in advance, and a reference value required for the control processing is stored. Such data, for example, data of each value in FIG. 4 is stored in the data memory 5B in advance.

Then, as shown in FIG. 4, the commutation delay time Lt
Is increased or decreased in accordance with the increase or decrease of the number of times of detection Sn of the position detection signal, for example, the number of times of detection Sn which is the sum of the number of times of detection of all position detection signals Su, Sv, and Sw. In addition, the configuration is such that the operation can be reliably shifted to the synchronous operation based on the stationary position detection.

Specifically, as shown in FIG. 4, the commutation delay time Lt is represented by, for example, an electrical time width, that is, a phase angle width, and a plurality of stages, for example, a first stage Lt1 2nd stage Lt2, 3rd stage Lt3,
These steps are defined as a first step Sn1 and a second step Sn1 similar to the plurality of steps of the number of times of detection Sn of the position detection signal in the first embodiment.
This is set so as to correspond to step Sn2.

Lt1 = 15 ° Lt2 = 11.25 ° Lt3 = 7.5 °

FIG. 4 is a graph for easy understanding, but in practice, a table corresponding to the data values of FIG. 4 is stored in the data memory 5B and stored in the processing memory 5A. The control operation is performed while being selected by a control processing flow program stored in advance. Since the control processing flow is as simple as that of the first embodiment described above, the data on the horizontal axis is determined from the detection signal and the data on the vertical axis is output as a control signal, the description is omitted here. I do.

According to this control processing, even when the load of the rotor 3R fluctuates and the rotational speed of the rotor 3R fluctuates, the position detection mask time Mt according to the configuration of the above-described first embodiment increases or decreases. Since the response and the response by the increase / decrease change of the commutation delay time Lt based on the control data of FIG. 4 are performed, irrespective of such a variation, it is faster than the configuration of the first embodiment. Sn2 can be reached quickly, and synchronous operation by steady position detection
The transition can be performed stably and reliably.

In the structure of the second embodiment, in addition to the structure of the first embodiment, firstly, the commutation delay time Lt is made to correspond to the number of times of detecting the position detection signal of the rotor 3R. Second, the control is performed only during the period from the start of the start of the inverter circuit 2 to the time when the rotor 3R reaches a predetermined rotation speed, that is, when the number of times of detection of the position detection signal is a predetermined value. It is something that is going to be done only until the number of times.

In the above setting, each stage of the control of the commutation delay Lt, for example, the first stage Lt1 and the second stage Lt2
The third stage Lt3 is configured to gradually decrease as the number Sn of the position detection signals increases so as to satisfy the condition of Lt1>Lt2> Lt3, but the rotor 3 after the start is started.
If there is a large pulsation or the like in the load of R, the setting may be made to cope with such a change in the load.

That is, for example, when the load fluctuates as in [Load state (No. 1)] in FIG. 3, Lt1 <Lt
3 <Lt2, and for example,
When the load changes as in [Load state (No. 2)] of FIG. 3, the condition is set so that Lt1 <Lt2 <Lt3.

Third Embodiment A third embodiment will be described below with reference to FIGS. The configuration of the third embodiment is as follows.
In general, the above-described third and sixth configurations are configured. Differences from the configuration of the above-described first embodiment are the same as those of the first embodiment. 5 is stored in the processing memory 5A in advance, and data such as reference values required for the control processing, for example, data of each value in FIG. Are stored in advance in the memory 5B.

Then, as shown in FIG.
The start rate of the drive frequency Ft of the inverter circuit 2 immediately after the start of the start of the inverter circuit 2 is controlled to an increase rate larger than the increase rate ρ2 of the inverter circuit 2 at the time of the steady operation, thereby performing a stable start. , So that the operation can be reliably shifted to the synchronous operation based on the stationary position detection.

Specifically, in FIG. 5, the drive frequency Ft of the inverter circuit 2 is set so as to be controlled in a frequency change range from a lower limit frequency Ft1 to an upper limit frequency Ft3 during a steady operation. As can be seen, for example, immediately after the start of the inverter circuit 2, the drive frequency Ft is increased from the frequency 0 to an appropriate frequency between the lower limit frequency Ft1 and the upper limit frequency Ft3 as indicated by the control curves L1, L2, and L3. After that, the control is shifted to the control based on the frequency change range during the steady operation.

Then, the driving frequency F at the time of steady operation is
The increase rate ρ2 of t is controlled by setting the frequency increase amount per unit time T1 to fa, whereas the increase rate ρ1 of the drive frequency Ft immediately after the start of the inverter circuit 2 is calculated by the unit time T1. The frequency increase per hit is fb, and control is performed by setting fb> fa.

The specific values are set, for example, as follows. Ft1 = 10 to 30 Hz Ft3 = 150 Hz ρ2 = fa / T1 = 1 Hz / sec to 2 Hz / sec ρ1 = fb / T1 = ρ2 × 10

FIG. 5 is shown as a graph for easy understanding. Actually, a table corresponding to the data values shown in FIG. 5 is stored in the data memory 5B, and the table is stored in the processing memory 5A. The control operation is performed while being selected by a control processing flow program stored in advance. Since the control processing flow is as simple as that of the first embodiment described above, the data on the horizontal axis is determined from the detection signal and the data on the vertical axis is output as a control signal, the description is omitted here. I do.

According to this control processing, even when the load of the rotor 3R fluctuates and the number of rotations of the rotor 3R fluctuates, the position detection mask time Mt according to the configuration of the above-described first embodiment increases or decreases. Since the response and the response by the increase rate of the drive frequency Ft of the inverter circuit 2 based on the control data of FIG. 5 are performed, regardless of such a variation, the response is faster than the configuration of the first embodiment. The driving frequency Ft1 during the operation can be quickly reached, and the operation can be shifted to the synchronous operation based on the stationary position detection stably and reliably.

In the configuration of the third embodiment, in addition to the configuration of the first embodiment, first, the drive frequency Ft of the inverter circuit 2 immediately after the start of the inverter circuit 2 is started is increased. The rate ρ1 is controlled by an increase rate larger than the increase rate ρ2 during the steady operation of the inverter circuit 2. Secondly, the control is performed by the rotor 3R starting from the time when the start of the inverter circuit 2 is started. This operation is performed only until the rotation speed is reached, that is, only until the number of times of detection of the position detection signal reaches a predetermined number.

[Fourth Embodiment] The fourth embodiment will be described below with reference to FIGS. The configuration of the fourth embodiment is configured by combining all of the configurations of the above-described first to third embodiments. Therefore, it generally constitutes the seventh configuration described above.

According to the configuration of the fourth embodiment,
Since the configuration is such that all the control processes described in the first to third embodiments are performed, even when the load of the rotor 3R fluctuates and the rotation speed of the rotor 3R fluctuates, the above-described operation is performed. According to the configuration of the first embodiment, the response by the increase and decrease of the position detection mask time Mt, the configuration of the second embodiment by the increase and decrease of the commutation delay time Lt, and the configuration of the third embodiment. The response by the increase rate of the drive frequency Ft of the inverter circuit 2 is performed at the same time.

Therefore, irrespective of such load fluctuations, the drive frequency Ft can reach, for example, the drive frequency Ft1 at the time of steady operation faster than in the case of the configuration of the first to third embodiments. It is possible to stably and reliably shift to synchronous operation based on steady-state position detection.

[Modification] (1) The configuration of the first to fourth embodiments is applied to the configuration of the third conventional technique. (2) When the voltage of the power supply unit 1 is low, the voltages of the terminals R, S, and T are not divided, and the respective comparators CPu, CP are not divided.
The configuration is applied to the configuration given to v · CPw.

[0073]

According to the present invention, as described above, the control processing operation from the start of the start of the inverter circuit to the start of the steady operation is performed by changing the position detection mask time and changing the commutation delay time. Since the response is performed by any one of the response based on the change and the response based on the increase rate of the drive frequency of the inverter circuit 2 or the response operation based on a combination of a plurality of these, the load on the rotor is reduced. Even when the rotational speed of the rotor fluctuates due to fluctuations, it is possible to stably, reliably, and quickly shift to the steady operation state regardless of such fluctuations. Further, since such a function can be provided only by adding a control processing function in the microcomputer, there is an effect that the apparatus configuration can be provided simply and inexpensively.

[Brief description of the drawings]

1 to 5 show an embodiment of the present invention, and FIGS.
10 show a conventional technique, and the contents of each figure are as follows.

FIG. 1 is an overall block diagram.

FIG. 2 is an operation waveform diagram of a main part.

FIG. 3 is an operating condition diagram of a main part.

FIG. 4 is an operating condition diagram of a main part.

FIG. 5 is an operating condition diagram of a main part.

FIG. 6 is an overall block diagram.

FIG. 7 is an operation waveform diagram of a main part.

FIG. 8 is an operation waveform diagram of a main part.

FIG. 9 is an operation waveform diagram of a main part.

FIG. 10 is an operation waveform diagram of a main part.

[Explanation of symbols]

 Reference Signs List 1 power supply unit 2 inverter circuit 3 DC brushless motor 3R rotor 3U to 3W stator winding 4 drive circuit 5 microcomputer C unstable time CPu to CPw comparator E0 virtual neutral point voltage Eus to Ews Comparison voltage (negative terminal input voltage) ) Ft drive frequency Ft1 Lower limit frequency Ft3 Upper limit frequency fa Frequency increase amount fb Frequency increase amount Lt Commutation delay time L1 Control curve L2 Control curve L3 Control curve Mt ・ Mt1 to Mt3 Position detection mask time P ・ Pa ・ Pb Intersection point / zero cross point RU phase terminal Rau-Rfw resistance SV phase terminal Sn, Sn1, Sn2 Number of times of position detection Su-Sw position detection signal Su1-Sw2 position detection signal TW-phase terminal T1 Time width TrU-TrZ Transistor Tt Elapsed time U U-phase Ua To Wa phase divided voltage (positive terminal input voltage) U Commutation point in time V V-phase Vcc bus voltage W W phase Wt commutation time

 ──────────────────────────────────────────────────の Continued on the front page (72) Inventor Hideaki Kato 2-5-5 Keihanhondori, Moriguchi-shi, Osaka Sanyo Electric Co., Ltd. (72) Yuichi Izawa 2-5-1 Keihanhondori, Moriguchi-shi, Osaka No. 5 Sanyo Electric Co., Ltd. F term (reference) 3L092 AA01 FA05 5H560 BB04 BB07 BB12 DA13 DA19 DC13 EB01 GG04 SS01 TT07 UA06 XA12

Claims (7)

[Claims] 1. A predetermined brushless motor in a DC brushless motor including a rotor having a plurality of magnetized poles and a plurality of stator windings arranged to apply a rotating magnetic field to the rotor when energized. The winding is energized with a pulse width modulation voltage generated by an inverter circuit to form a rotating magnetic field, and the induced voltage generated in the stator winding of the phase not energized by the rotation of the rotor, and a predetermined voltage. A DC brushless motor device that controls the point of time at which the energization is performed based on a position detection signal obtained by comparing and detecting the voltage of each of the plurality of phases. The increase or decrease of the position detection mask time that regulates the detection of the position detection signal following the commutation point corresponding to the number of times of the position detection signal obtained after the start is started. DC brushless motor apparatus characterized by having a mask time control means for controlling. 2. The method according to claim 1, further comprising: controlling the commutation delay time, which regulates a commutation time following the preceding position detection signal, in accordance with the number of the position detection signals obtained after starting the start. 2. The DC brushless motor device according to claim 1, further comprising a commutation time control unit that performs the commutation. 3. A drive frequency increase / decrease control means for controlling a rate of increase of the drive frequency of the inverter circuit immediately after the start of the start by a rate of increase greater than the rate of increase during the steady operation of the inverter circuit. 2. The DC brushless motor device according to claim 1, wherein: 4. The method according to claim 1, wherein the control for increasing or decreasing the position detection mask time is performed only from the time when the starting is started to the time when the rotation of the rotor reaches a predetermined rotation speed. A DC brushless motor device according to claim 1. 5. A control for increasing or decreasing the commutation delay time,
3. The DC brushless motor device according to claim 2, wherein the driving is performed only from the time when the starting is started to the time when the rotation of the rotor reaches a predetermined rotation speed. 6. The DC brushless apparatus according to claim 3, wherein the control based on the large increase rate is performed only from the time when the starting is started to the time when the rotation of the rotor reaches a predetermined rotation speed. Motor device. 7. A predetermined fixed state in a DC brushless motor provided with a rotor having a plurality of magnetized poles and a plurality of stator windings arranged to apply a rotating magnetic field to the rotor when energized. To the child winding, while applying a pulse width modulation voltage generated in the inverter circuit to form a rotating magnetic field, the induced voltage generated in the stator winding of the phase that is not energized by the rotation of the rotor, A DC brushless motor device configured to control a point in time at which the energization is performed based on a position detection signal obtained by comparing and detecting a predetermined voltage with each of the plurality of phases, wherein starting of the inverter circuit is started. Only during the period from the time when the rotation of the rotor reaches the predetermined number of rotations to the time when the rotation of the rotor reaches the predetermined number of rotations, the position detection mask time for restricting the detection of the position detection signal following the preceding commutation time is increased or decreased. A mask time control means for controlling the number of times of the position detection signal obtained after the start of the engine is started, and from a time when the start is started to a time when the rotation of the rotor reaches a predetermined speed. Only, a commutation time control means for controlling the increase or decrease of the commutation delay time regulating the commutation time following the preceding position detection signal in accordance with the number of the position detection signals obtained after the start is started. Only during the period from the start of the start to the time when the rotation of the rotor reaches a predetermined rotation speed, the drive frequency of the inverter circuit immediately after the start of the start is increased by a steady rate of the inverter circuit. A drive frequency increase / decrease control means for performing control by an increase rate greater than the drive frequency increase rate during operation.
C brushless motor device.