JP2001178013A - Charging circuit and charging control method thereof - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a charging circuit and a charging control method thereof, capable of attaining safe charging using a simple structure, using a commercial AC power supply, and downsizing and cost reduction. SOLUTION: This charging circuit comprises a rectifying circuit 20, which conducts half-wave rectification for AC voltage supplied by a commercial power supply 10 and produces pulsating current having a voltage waveform of fixed cycle, a current limiting circuit 30, a switching circuit 40, a switching control circuit 50 which arbitrarily adjusts the supply condition (charging current supply period and current value) of charging current to a capacitor storage battery 70 and controls the conducting condition of the switching circuit 40, and a counterflow inhibiting circuit 60 to which the capacitor storage battery 70 is connected.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a charging circuit and a charging control method thereof, and more particularly to a charging circuit having a capacitor type storage battery such as an electric double layer capacitor and a charging control method thereof.

[0002]

2. Description of the Related Art Conventionally, in charging secondary batteries such as lead storage batteries and alkaline storage batteries, methods such as constant current charging, constant voltage charging, and constant voltage pulse charging have been used.
When a secondary battery is charged by these charging methods, the change in terminal voltage due to charging is very small, so that when detecting the end state (end time) of charging, it is possible to detect a small voltage fluctuation or change the battery temperature. It was necessary to adopt a method such as detecting Therefore, in order to accurately detect the state of charge and perform the charging operation efficiently, the configuration and control of the device become complicated, which causes a problem that the device becomes large and the manufacturing cost increases.

On the other hand, in recent years, application of a charging circuit (apparatus) including a capacitor type storage battery such as an electric double layer capacitor as a driving power source for an electric vehicle or the like has been studied. Generally, the voltage V between both ends of a capacitor including an electric double layer capacitor is represented by the following equation, where Q is a charge amount and C is a capacitor capacity. V = Q / C (11) The charge amount Q is expressed by the following equation, where IA is the current flowing through the capacitor (charging current), and t is the charging time. Q = IA · t (12)

Accordingly, the amount of charge Q stored in the electric double layer capacitor increases in proportion to the elapse of the charging time t, and the charging voltage corresponding to the amount of stored charge Q also increases in the charging time t.
In addition, it has the advantage of being capable of rapidly charging and having a longer cycle life due to repeated charging / discharging as compared to secondary batteries such as the lead storage battery and the alkaline storage battery described above. In such an electric double layer capacitor, the use of a charging method in which a constant current is applied to improve charging efficiency is disclosed in, for example, Japanese Patent Application Laid-Open No. 7-8 / 1995.
No. 7668, for example.

[0005]

However, in the prior art described above, when the electric double layer capacitor is charged with a constant current, the AC voltage from the commercial power supply (AC power supply) is stepped down by a transformer or the like and rectified. Since a constant current is generated and used as a charging power source, there is a problem that a power supply circuit portion of the charging device becomes large, and further, the manufacturing cost of the device increases. In view of the above, the present invention has been made in consideration of the above-described problems, and it is possible to charge a capacitor-type storage battery that can be safely charged with a simple configuration while using a commercial AC power supply, and that can be reduced in size and cost. It is an object to provide a circuit and a charge control method thereof.

[0006]

According to a first aspect of the present invention, there is provided a charging circuit comprising: a power supply for rectifying an AC voltage component of a commercial power supply to generate a pulsating current having a predetermined voltage cycle; Charging current supply means for supplying a corresponding charging current, charging control means for controlling the operation state of the charging current supply means to control the supply state of the charging current, and the charging current supply means A capacitor-type storage battery that stores electrical energy corresponding to the charging current. According to a second aspect of the present invention, in the charging circuit according to the first aspect, the charging control unit performs the charging according to the voltage component of the pulsating flow only when the voltage component is within a predetermined voltage range. The operation of the charging current supply means is controlled so as to supply a current to the capacitor type storage battery.

According to a third aspect of the present invention, in the charging circuit of the first aspect, the charging control means adjusts and controls the supply state of the charging current by arbitrarily setting the voltage amplitude of the pulsating current. It is characterized by doing. The charging circuit according to claim 4 is the charging circuit according to claim 1, wherein the charging control unit compares a voltage component of the pulsating current with a predetermined voltage range based on a charging voltage of the capacitor-type storage battery. When the voltage component of the pulsating current is within the voltage range, the operation of the charging current supply means is controlled to supply the charging current to the capacitor type storage battery.
And a comparison determining means. According to a fifth aspect of the present invention, in the charging circuit according to the first aspect, the charging control means sets an arbitrary signal width and a signal period of an operation control signal for controlling an operation of the charging current supply means. The present invention is characterized in that the supply state of the charging current is adjusted and controlled.

According to a sixth aspect of the present invention, in the charging circuit of the first aspect, the charging control means includes a control signal generating means for generating an operation control signal having an arbitrary signal width and a signal period. It is characterized by: According to a seventh aspect of the present invention, in the charging circuit according to the first aspect, the charging control unit adjusts and controls a supply state of the charging current by arbitrarily setting a delay time of a voltage cycle of the pulsating current. It is characterized by doing. The charging circuit according to claim 8 is the charging circuit according to claim 1, wherein the charging control unit charges a voltage component of a delayed pulsating current obtained by delaying a voltage cycle of the pulsating current by a predetermined time, and charges the capacitor-type storage battery. When the voltage component of the delayed pulsating flow has a predetermined relationship with the charging voltage, the operation of the charging current supply unit is controlled so as to supply the charging current to the capacitor type storage battery. And a second comparison / determination unit for performing the comparison.

According to a ninth aspect of the present invention, in the charging circuit according to the first aspect, the charging control means includes a voltage component of a partial pressure pulsating flow obtained by dividing the pulsating flow at a predetermined partial pressure ratio, and the pulse component. The present invention is characterized in that the supply state of the charging current is adjusted and controlled by arbitrarily setting a comparison condition with a voltage component of a delayed pulsating current obtained by delaying the current for a predetermined time. According to a tenth aspect of the present invention, in the charging circuit according to the first aspect, the charge control means determines a voltage component of a partial pressure pulsation obtained by dividing the pulsation at a predetermined division ratio and the pulsation. Comparing the voltage component of the time-delayed pulsating flow, and when the comparison result satisfies a predetermined condition, controlling the operation of the charging current supply means so as to supply the charging current to the capacitor type storage battery. 3 is provided. The charging circuit according to claim 11, wherein the charging control means extracts a charging voltage of the capacitor-type storage battery and, when the charging voltage reaches a predetermined voltage or more, sets the capacitor. A charging stop means for controlling the operation of the charging current supply means so as to stop the supply of the charging current to the rechargeable battery.

According to a twelfth aspect of the present invention, in the charging circuit according to the first aspect, the charging control means extracts a charging voltage of the capacitor type storage battery, and according to a potential difference of the charging voltage at predetermined time intervals. And a charging current stabilizing means for controlling an operation of the charging current supplying means so as to make the charging current supplied to the capacitor type storage battery substantially constant. 14. The charging control method for a charging circuit according to claim 13, wherein a pulsating current having a predetermined voltage cycle is generated by rectifying an AC voltage component of a commercial power supply, and charging is performed according to a voltage component of the pulsating current during a predetermined period. Supplying a current, arbitrarily setting the predetermined time period, adjusting and controlling the supply state of the charging current, and supplying electric energy corresponding to the charging current supplied in the predetermined time period to the capacitor type storage battery. And a step of storing.

First, the overall configuration of the charging circuit according to the present invention will be described with reference to the drawings. FIG. 1 is a block diagram showing the overall configuration of the charging circuit according to the present invention. As shown in FIG. 1, the charging circuit according to the present invention is roughly divided into a rectifier circuit 20, a current limiting circuit 30, a switch circuit 40,
, A switch control circuit 50 and a backflow prevention circuit 60. The rectifier circuit 20 is connected to the commercial power supply 10, and the backflow prevention circuit 60 is connected to a capacitor type storage battery 70. Here, the rectifier circuit 20 constitutes power supply means according to the present invention, the current limiting circuit 30, the switch circuit 40 and the backflow prevention circuit 60 constitute charge current supply means according to the present invention, and the switch control circuit 50 And a charge control means according to the present invention.

The rectifier circuit 20 converts the AC voltage supplied from the commercial power supply 10 into a positive voltage component period, only a negative voltage component period, or a half-wave rectifier that extracts both positive and negative voltage component periods. It has a full-wave rectification (or double-wave rectification) function and generates a pulsating flow having a positive voltage waveform at a constant cycle. This pulsating current is supplied to the capacitor-type storage battery 70 via a switch circuit 40 described later, and a switch circuit 4 for defining the supply timing.
It is also used for 0 conduction control. Details will be described later. The current limiting circuit 30 limits and sets the maximum current value of the charging current flowing when the switch circuit 40 described later is in a conductive state according to the pulsating voltage. The switch circuit 40 controls the supply and cutoff of the current-limited charging current to the capacitor-type storage battery 70 based on a control signal from a switch control circuit 50 described later.

[0013] The switch control circuit 50 is based on the pulsating voltage (input voltage) generated by the rectifier circuit 20 and a predetermined voltage range, or based on the pulsating voltage and any pulse timing, or Based on the voltage and the pulsating voltage delayed for a predetermined time, or the pulsating voltage divided by a predetermined dividing ratio and the pulsating voltage delayed for a predetermined time, an operation control signal that defines the supply period and the current value of the charging current is generated. Output to control the conduction state of the switch circuit 40. In the conduction control of the switch control circuit 50, when the voltage of the pulsating current on the switch circuit 40 side is lower than the charging voltage of the capacitor-type storage battery 70, the backflow prevention circuit 60 causes the electric energy stored in the capacitor-type storage battery 70 to flow backward. And prevent it from falling. In the charging circuit having such a configuration, a pulsating voltage component having a predetermined voltage cycle generated by rectifying an AC voltage component of the commercial power supply 10 and a predetermined voltage range, or an arbitrary pulse timing, or ,
By arbitrarily setting the charging current supply period and the current value based on the relationship with the pulsating voltage delayed for a predetermined time,
The supply state of the charging current is controlled.

Hereinafter, a charging circuit according to the present invention will be described in detail with reference to embodiments. <First Embodiment> Next, a first embodiment of the charging circuit according to the present invention will be described.
An embodiment will be described with reference to the drawings. FIG.
FIG. 1 is a block diagram showing a first embodiment of a charging circuit according to the present invention. As shown in FIG. 2, the charging circuit according to the present embodiment includes a rectifier circuit 20A, a current limiting circuit 30A,
An input voltage detection circuit 50B, a switch circuit 40A, a voltage determination circuit (first comparison determination means) 50A, a backflow prevention circuit 60A, and a charging voltage detection circuit 50C are provided. An AC voltage (for example, AC 100 V) is supplied from the commercial power supply 10 to the terminal Tin, and an electric double layer capacitor 70A is connected to the output terminal Tout.

Here, the rectifier circuit 20A generates a pulsating current having a predetermined voltage cycle by half-wave rectifying or full-wave rectifying the AC voltage component of the commercial power supply 10 as described above, 50A is a voltage component of the pulsating current detected by the input voltage detection circuit 50B (input voltage Vin).
And a predetermined voltage range set based on the charging voltage Vc of the electric double layer capacitor 70A detected by the charging voltage detection circuit 50C.
Depending on whether or not the voltage is within the voltage range, the switch circuit 4
The continuity state of 0A is controlled by switching.

Therefore, according to the charging circuit having such a configuration, the voltage change of the input voltage Vin falls within the predetermined voltage range defined by the voltage determination circuit 50A (the predetermined voltage range based on the charging voltage Vc). Only during a certain period, the switch circuit 40A is controlled to conduct, and the charging current generated by the rectifier circuit 20A is reduced by the current limiting circuit 30A.
A, is supplied to the electric double layer capacitor 70A via the switch circuit 40A and the backflow prevention circuit 60A. In addition,
In the charging circuit according to the present embodiment, the input voltage Vin and the charging voltage Vc are divided and extracted at a predetermined division ratio by the input voltage detection circuit 50B and the charging voltage detection circuit 50C, and the magnitude of the extracted voltages is determined. By comparing and determining the relationship, the supply of the charging current to the electric double layer capacitor 70A is controlled. In particular, the configuration is such that the supply control of the charging current is optimized by making it possible to arbitrarily change and set the division ratio of the input voltage Vin.

Hereinafter, a specific circuit configuration example of the charging circuit according to the present embodiment will be described. FIG. 3 is a circuit configuration diagram illustrating a specific example of the charging circuit according to the first embodiment. As shown in FIG. 3, in this specific example, a 100 V AC power supply which is supplied as a commercial power supply in Japan is connected between a pair of input terminals (power supply terminals) Tina and Tinb of the charging circuit 100A. A pair of output terminals (charging terminals)
The electric double layer capacitor 70A is connected between Touta and Toutb. A half-wave rectifier diode D11, a current limiting resistor R11, a switching field-effect transistor (hereinafter, referred to as a switch) Tr11, and a reverse current blocking diode D12 are connected in series between one input terminal Tina and the output terminal Touta. It is connected to the.

A contact N11 between the half-wave rectifier diode D11 and the current limiting resistor R11 and a switch Tr1
A switch control transistor (hereinafter, referred to as a control switch) Tr12 including a resistor R12 and a phototransistor is provided between the first gate and the first gate.
A resistor R13 is connected between the contact N11 and the ground potential to which the other input terminal Tinb and output terminal Toutb are connected.
A series connection of a capacitor C11 and a series connection of an input voltage detection resistor R14 and an input voltage adjustment resistor R15 are provided in parallel. Here, the input voltage adjustment resistor R1
Reference numeral 5 denotes, for example, a variable resistor, which is capable of arbitrarily adjusting the amplitude of a pulsating voltage component (input voltage Vin), as described later. The input voltage detection resistor R14 and the input voltage adjustment resistor R15 constitute the above-described input voltage detection circuit. A contact N12 between the switch Tr11 and the backflow prevention diode D12 is connected to the gate of the switch Tr11, and is connected between the contact N12 and the ground potential to which the other input terminal Tinb and output terminal Toutb are connected. Is provided with a series connection of charging voltage detection resistors R16 and R17. Here, the charging voltage detection resistors R16 and R17 constitute the above-described charging voltage detection circuit.

A contact N13 between the input voltage detecting resistor R14 and the input voltage adjusting resistor R15 is connected to the negative input side of the comparator CM11 and the positive input side of the comparator CM12. And R
17 is connected to the negative input side of the comparator CM12 and is connected to the Zener diode D1.
3 is connected to the positive input side of the comparator CM11. The outputs from the comparators CM11 and CM12 are input to a two-input AND gate, and the logical output is output to the light emitting diode D14. Here, the control switch Tr12 and the light emitting diode D14 have a photocoupler structure arranged to face each other (hereinafter, these are collectively referred to as a photocoupler PC). Comparators CM11, CM12, 2-input AND
The gate and the photocoupler PC are individually integrated circuits (I
C). Comparator CM1
1, CM12, 2-input AND gate, photocoupler P
C and the Zener diode D13 constitute the above-described voltage determination circuit.

Next, the operation of the charging circuit according to this embodiment will be described with reference to the drawings. FIG. 4 is a voltage / current waveform diagram showing a basic operation in the charging circuit according to this example, and FIG. 5 is a voltage / current waveform diagram showing another operation in the charging circuit according to this example. In the circuit configuration described above, as shown in FIG. 4A, when a sine AC voltage of 100 V AC is applied as a commercial power supply voltage, the rectifying action of the half-wave rectifier diode D11 causes the rectifying action of FIG. As shown, only the positive voltage component is extracted, and an input voltage Vin having a positive voltage waveform is generated at a cycle equivalent to the commercial power supply voltage.

Here, the charging voltage of the electric double layer capacitor 70A (the voltage between the output terminals Touta and Toutb) Vc
Is divided by a predetermined voltage dividing ratio by the charging voltage detection resistors R16 and R17, and the reference voltage Vre follows the charging voltage Vc.
f (= Vc × R17 / (R16 + R17)) is input to the negative input side of the comparator CM12.
A voltage Vd (= Vref) obtained by adding (adding) the Zener voltage Vz of the Zener diode D13 to the reference voltage Vref.
+ Vz) is input to the positive input side of the comparator CM11. The voltage Vd is held by the capacitor C11. On the other hand, the input voltage Vin is the input voltage detection resistance R
14 and an input voltage adjusting resistor R15, the voltage is divided at an arbitrary voltage dividing ratio, and the pulsating voltage Va (= V) follows the input voltage Vin.
In × R15 / (R14 + R15)) is commonly input to the negative input side of the comparator CM11 and the positive input side of the comparator CM12. Note that the input voltage adjustment resistor R15 is a variable resistor, is configured to be able to change the resistance value, and is configured to be able to arbitrarily set the division ratio of the input voltage Vin.

Thus, the input voltage Vin and the charging voltage V
c, the voltage change that follows each of the comparators CM
11. The operation of the photocoupler PC is controlled on the basis of the comparison judgment results (magnitude relationship) that are input to the CM 12. Specifically, when the following input condition is satisfied in the comparator CM11, the logical output becomes high level, and a pulse-like operation control signal is output. Va <Vref + Vz (1) In the comparator CM12, when the following input condition is satisfied, the logical output becomes high level, and a pulse-like operation control signal is output. Va> Vref (2) Then, the comparator CM is input by a two-input AND gate.
11. When the logical sum of the outputs of the CM 12 is calculated, the condition for turning on the photocoupler PC (that is, turning on the switch Tr11) is expressed as follows. Vd>Va> Vref (3)

That is, when the pulsating voltage Va changes within a voltage range satisfying the condition of the above equation (3), that is, as shown in FIG. 4B, the input voltage divided by an arbitrary voltage dividing ratio is obtained. The voltage Vin (pulsating voltage Va) is in a voltage range (Vc to Vc + Vz) obtained by adding the Zener voltage Vz of the Zener diode D13 to the charging voltage Vc (reference voltage Vref) divided by a predetermined voltage dividing ratio. In this case, a current flows through the light emitting diode D14 of the photocoupler PC to emit light, and the control switch Tr12 is turned on. As a result, the input voltage Vin becomes equal to the resistance R12 and the control switch Tr12.
Is supplied to the gate of the switch Tr11, and the switch Tr11 is turned on. Switch Tr11 is ON
Upon operation, as shown in FIG. 4C, a charging current corresponding to the input voltage Vin is supplied to the current limiting resistor R11 and the switch Tr.
The charging operation is performed by supplying the electric power to the electric double layer capacitor 70A via the backflow prevention diode 11 and the backflow prevention diode D12 (time t11, t13). Here, the charging current supplied to the electric double layer capacitor 70A is the current limiting resistor R11
Since the current is limited by the conduction resistance of the switch Tr11 and the like, the terminal potential (charging voltage Vc) of the large-capacity electric double layer capacitor 70A is suppressed to a minute change as compared with a change in the input voltage Vin.

When the input voltage Vin rises or falls with the elapse of time (t) beyond the voltage range (Vc to Vc + Vz) defined by the Zener diode D13, at least one of the comparators CM11 and CM1.
2 becomes low level, no current flows through the light emitting diode D14 of the photocoupler PC, and the control switch Tr12 is turned off. Thereby, the switch T
When r11 is turned off (time t12, t14), supply of the charging current to the electric double layer capacitor 70A is cut off. That is, the charging current is, as shown in FIG.
Only a very short time (t11 to t12, t13 to t14) in the rising period and the falling period of the voltage waveform is supplied to the electric double layer capacitor 70A.
The charging current to the electric double layer capacitor 70A is determined by the voltage applied to the electric double layer capacitor 70A and the charging voltage Vc.
And the charging voltage Vc increases with the progress of charging, the charging current decreases with the progress of charging. When the charging voltage Vc becomes about the input voltage Vin, the charging current substantially increases. It becomes zero.

Further, in the above-described series of charging operations, as shown in FIG. 5, by appropriately changing and setting the resistance value of the input voltage adjusting resistor R15, the voltage dividing ratio with the input voltage detecting resistor R14 connected in series can be increased. The voltage amplitude (maximum voltage value) of the input voltage Vin is arbitrarily set and controlled to be changed (for example, FIG. 5B shows a change in the voltage amplitude when the resistance value of R16 is reduced). Thus, the time during which the input voltage Vin is within the voltage range (Vc to Vc + Vz), that is, the charging current supply period (t11 to t1)
2 ′, t13 ′ to t14) and the current value of the charging current can be adjusted. Therefore, according to the charging circuit in the present specific example, in the charging operation of the electric double layer capacitor, the input voltage Vin capable of supplying the charging current becomes the charging voltage V
It is limited to the case where the voltage is within a predetermined voltage range (Vc to Vc + Vz) based on c, so that an excessive charging current based on an excessive input voltage Vin is suppressed from being supplied to the electric double layer capacitor, Deterioration and power loss of the electric double layer capacitor can be reduced, and an appropriate charging operation can be performed.

In particular, the supply period of the charging current can be arbitrarily adjusted by appropriately changing and setting the voltage dividing ratio when the input voltage Vin is detected, so that the charging condition for the electric double layer capacitor is optimized. be able to. Further, according to the charging circuit in this specific example, the half-wave rectifier diode D1 is converted from the AC voltage supplied from the commercial power supply without stepping down the AC voltage from the commercial power supply using a transformer or the like.
1, a pulsating current is generated, and the current value of the charging current and the supply period are set based on the pulsating current (input voltage) and the charging voltage of the electric double layer capacitor, thereby simplifying the circuit configuration of the charging circuit. In addition, heat generation from the circuit element can be suppressed, and a significant reduction in size, weight, and cost can be achieved.

In the present embodiment, the case where both the upper limit voltage and the lower limit voltage are set using the pair of comparators CM11 and CM12 as the voltage range for controlling the supply of the charging current has been described. Only one of them may be set. That is, when the supply of the charging current is controlled by setting only the lower limit voltage, the charging current is supplied when the input voltage Vin is equal to or higher than a certain voltage. Can be effectively applied when a small power supply having a relatively small power is used. In addition, when the supply of the charging current is controlled by setting only the upper limit voltage, the charging current is supplied when the input voltage Vin is equal to or lower than a certain voltage, which is effective when the charging operation is performed with a negative power supply. Can be applied to

<Second Embodiment> Next, a charging circuit according to a second embodiment of the present invention will be described with reference to the drawings. FIG. 6 is a block diagram showing a second embodiment of the charging circuit according to the present invention. Here, the same components as those in the above-described embodiment are denoted by the same reference numerals, and description thereof will be omitted. As shown in FIG. 6, the charging circuit according to the present embodiment includes a rectifier circuit 20A, a current limiting circuit 30A, a switch circuit 40A, a pulse generation circuit (control signal generation means) 50D, and a stabilized power supply circuit 50E. , A backflow prevention circuit 60A, and an input terminal Tin of the charging circuit.
Is supplied with an AC voltage from the commercial power supply 10, and an output terminal Tout is connected to an electric double layer capacitor 70A.

Here, the rectifier circuit 20A performs a half-wave rectification or a full-wave rectification of the AC voltage component of the commercial power supply 10 in the same manner as in the above-described embodiment, so that the pulsating current (input voltage Vin) has a predetermined voltage cycle. ) To generate the stabilized power supply circuit 50E.
Supplies drive power to each component (including the pulse generation circuit 50D) in the charging circuit based on the pulsating flow.
The pulse generation circuit 50D generates and outputs a pulse signal (operation control signal) having an arbitrary phase and an arbitrary period, and controls the conduction state of the switch circuit 40A. Here, the pulse signal may have either a synchronous or asynchronous relationship with the AC voltage cycle of the commercial power supply 10, but is generated so as to have at least a cycle shorter than the AC voltage cycle. . Therefore, according to the charging circuit having such a configuration, it is independent of the AC voltage cycle of the commercial power supply 10,
In addition, based on the timing of a pulse signal having an arbitrary period shorter than the AC voltage period, the switch circuit 40A
Is turned on.

The operation of the charging circuit according to the present embodiment will be described below with reference to the drawings. FIG. 7 is a voltage / current waveform diagram showing an operation in the charging circuit according to the second embodiment. In the circuit configuration described above, as shown in FIG.
The sine AC voltage of V is obtained by a rectifier circuit such as a diode.
As shown in FIG. 7B, for example, half-wave rectification for extracting only the positive voltage component period of the sine AC voltage is performed, and a pulsating current having a positive voltage waveform with a cycle equivalent to that of the commercial power supply 10 ( An input voltage Vin) is generated.

On the other hand, as shown in FIG. 7 (c), a pulse signal having a predetermined phase and period synchronized or independent (asynchronous) with the commercial power supply 10 is generated by the pulse generation circuit 50D and When output as an operation control signal to the circuit 40A, the switch circuit 40A repeats the ON operation only depending on the phase and cycle of the pulse signal. As a result, as shown in FIG. 7D, the charging current corresponding to the input voltage Vin is synchronized with the timing of the pulse signal and the current limiting circuit 30A and the switch circuit 40A.
And a charging operation is performed through the backflow prevention circuit 60A to the electric double layer capacitor 70A (t21 to t21).
22, t23 to t24). Here, during a period (t22 to t23) where there is no voltage waveform of the input voltage Vin, the charging current is not supplied to the electric double layer capacitor 70A. Note that the charging current to the electric double layer capacitor 70A flows due to the potential difference between the voltage applied to the electric double layer capacitor 70A and the charging voltage Vc, and the charging voltage Vc increases with the progress of charging. As the charging proceeds, the charging current decreases. When the charging voltage Vc becomes approximately equal to the input voltage Vin, the charging current becomes substantially zero.

Therefore, according to the charging circuit of the present embodiment, the pulse signal having an arbitrary phase and period is generated and output by the pulse generating circuit 50D, and the electric double layer capacitor 70A is generated at each timing of the pulse signal. Since the charging current supplied to the charging circuit can be controlled, the period of the pulse signal is set to be sufficiently small compared to the AC voltage period, so that the heat generation of the charging circuit is suppressed intermittently based on the pulse signal. The charging current for a period substantially corresponding to the entire voltage waveform of the input voltage Vin can be supplied to the electric double layer capacitor 70A, and the time required for charging can be greatly reduced. Further, since the pulse signal can be set to an arbitrary phase and cycle independently of the commercial power supply, it is not necessary to consider the AC voltage cycle of the commercial power supply, and the design flexibility can be improved. The control for averaging the charging current value can be easily performed by appropriately controlling the phase and cycle of the pulse signal. For example, control such as appropriately changing the charging current value according to the heat generation state of the charging circuit and the like can be performed. It can be performed.

Further, when the pulse signal is set to an arbitrary phase and cycle synchronized with the commercial power supply, the pulse signal can be generated based on the cycle of the commercial power supply. There is no need to provide an oscillation circuit, and the circuit configuration can be simplified. In the present embodiment, as in the case described above, the AC voltage from the commercial power supply is not stepped down using a transformer or the like, but is rectified by a diode or the like to generate a pulsating flow, and is generated by a pulse generation circuit. Based on the pulse signal alone,
Since the current value and supply period of the charging current are set, the circuit configuration of the charging circuit can be simplified, and heat generation from the circuit elements is suppressed, thereby achieving a significant reduction in size, weight, and cost. Can be.

<Third Embodiment> Next, a third embodiment of the charging circuit according to the present invention will be described with reference to the drawings. FIG. 8 is a block diagram showing a third embodiment of the charging circuit according to the present invention. Here, the same components as those in the above-described embodiment are denoted by the same reference numerals, and description thereof will be omitted. As shown in FIG. 8, the charging circuit according to the present embodiment includes a rectifier circuit 20A, a current limiting circuit 30A, a delay circuit 50G, a switch circuit 40A, a comparison circuit (second comparison determination unit) 50F, A backflow prevention circuit 60A;
A charging voltage detection circuit 50C, an input terminal Tin of the charging circuit is supplied with an AC voltage from the commercial power supply 10, and an output terminal Tout is connected to the electric double layer capacitor 7C.
0A is connected.

Here, the rectifier circuit 20A generates a pulsating current having a predetermined voltage cycle by half-wave rectifying or full-wave rectifying the AC voltage component of the commercial power supply 10 as described above, Is a delay voltage (voltage component of the delayed pulsating current) Vdly obtained by delaying the pulsating current (input voltage Vin) by an arbitrary time Tdly by the delay circuit 50G, and the electric double layer capacitor 70A detected by the charging voltage detecting circuit 50C. By comparing with the charging voltage Vc, based on the magnitude relation,
The conduction state of the switch circuit 40A is switched and controlled. Therefore, according to the charging circuit having such a configuration, the delay voltage Vdly delayed by an arbitrary time Tdly is applied to the comparison circuit 50.
Only during a period within a voltage range equal to or lower than the reference voltage (charging voltage Vc) defined by F, the switch circuit 40A is turned on, and the charging current corresponding to the input voltage Vin generated by the rectifier circuit 20A is applied to the electric double layer capacitor. 70
A. That is, the maximum value of the input voltage Vin during the charging operation is uniquely determined by the charging voltage Vc, and the supply state (current value, supply timing) of the charging current is arbitrarily set by the delay time Tdly.

Hereinafter, a specific circuit configuration example of the charging circuit according to the present embodiment will be described. FIG. 9 is a circuit configuration diagram illustrating a specific example of the charging circuit according to the third embodiment. As shown in FIG. 9, in this specific example, a 100 V AC power supply supplied as commercial power is connected between a pair of input terminals Tina and Tinb of the charging circuit 100B, and a pair of output terminals Touta, The electric double layer capacitor 70A is connected between Toutb. Also, one input terminal Tina
And a half-wave rectifier diode D2
1, a current limiting resistor R21, a switch Tr21, and a backflow prevention diode D22 are connected in series. A half-wave rectifier diode D21 and a current limiting resistor R21
Between the contact N21 between the input terminal Tinb and the ground potential to which the other input terminal Tinb and the output terminal Toutb are connected.
2 and a series connection of a delay time adjusting resistor R23 and a capacitor C21 are provided in parallel. Here, the delay time adjusting resistor R23 and the capacitor C21 constitute the above-described delay circuit.

Further, charging voltage detection resistors R24 and R25 are provided between the contact N22 on the output terminal Tota side of the backflow prevention diode D22 and the ground potential to which the other input terminal Tinb and output terminal Toutb are connected. ing. Here, the charging voltage detection resistors R24 and R25 constitute the above-described charging voltage detection circuit. The contact N23 between the delay time adjusting resistor R23 and the capacitor C21 is
The contact N24 connected to the negative input side of the comparator CM21 and between the charging voltage detection resistors R24 and R25 is
It is connected to the positive input side of the comparator CM21. The output of the comparator CM21 is input directly to the gate of the switch Tr21 or via a photocoupler or the like (not shown). Here, the comparator CM21
Constitutes the comparison circuit described above.

Next, the operation of the charging circuit according to this example will be described with reference to the drawings. FIG. 10 is a voltage / current waveform diagram showing the operation of the charging circuit according to this example. In the circuit configuration described above, as shown in FIG. 10A, the sine AC voltage of 100 V AC supplied from the commercial power supply 10 is rectified by the half-wave rectifier diode D21 as shown in FIG. For example, only the positive voltage component period of the sine AC voltage is extracted, and a pulsating current (input voltage Vin) having a positive voltage waveform is generated at a cycle equivalent to that of the commercial power supply 10. Here, the charging voltage (voltage between the output terminals Touta and Toutb) Vc of the electric double layer capacitor 70A is extracted by the charging voltage detection resistors R24 and R25, and is input as a reference voltage to the positive input side of the comparator CM21. You. On the other hand, the input voltage Vin is delayed by the delay time adjusting resistor R23 and the capacitor C21, and is delayed by a predetermined time (Tdly).
Is input to the negative input side of the comparator CM21. The delay time adjusting resistor R23 is a variable resistor, is configured to be able to change the resistance value, and is configured to be able to arbitrarily set the delay time Tdly of the input voltage Vin.

As a result, the voltage changes of the delay voltage Vdly and the charging voltage Vc are input to the comparator CM21,
The conduction state of the switch Tr21 is controlled based on the comparison result (the magnitude relation). Specifically, when the condition of Vc> Vdly is satisfied in the comparator CM21, the logical output goes high, a pulse-like operation control signal is output, and the switch Tr21 is turned ON. That is, during a period in which the delay voltage Vdly having an arbitrary delay time Tdly with respect to the input voltage Vin changes within a voltage range equal to or lower than the charging voltage Vc, the switch Tr2
1 is turned on, and as shown in FIGS. 10B and 10C, the charging current corresponding to the input voltage Vin is increased by the current limiting resistor R.
21, switch Tr21 and backflow prevention diode D22
Is supplied to the electric double layer capacitor 70A through
The charging operation is performed (time t31 to t32).

When the delay voltage Vdly rises beyond the charging voltage Vc as time (t) elapses, the output of the comparator CM21 goes low, and the switch Tr21 turns off (time t32). The supply of the charging current to the electric double layer capacitor 70A is cut off. In this way, as shown in FIG. 10C, the charging current has a very short time (t3) in the rising period of the delay voltage waveform.
1 to t32) are supplied to the electric double layer capacitor 70A. Here, even in the falling period of the delay voltage waveform, the delay voltage Vdly satisfies the condition of Vc> Vdly and turns on the switch Tr21. However, since the input voltage Vin in this case is zero, the electric double layer Capacitor 7
No supply of charging current to 0A is performed. Note that the charging current to the electric double layer capacitor 70A flows due to the potential difference between the voltage applied to the electric double layer capacitor 70A and the charging voltage Vc, and the charging voltage Vc increases with the progress of charging. As the charging proceeds, the charging current decreases, and when the charging voltage Vc becomes about the input voltage Vin, the charging current becomes substantially zero.

Further, in the above-described series of charging operations, the resistance value of the delay time adjusting resistor R22 is appropriately changed and set, so that the resistance value of the capacitor C21 connected in series is reduced.
The time constant of the C circuit is arbitrarily set, and the delay time Tdly with respect to the input voltage Vin is changed and controlled. As a result, the time during which the delay voltage Vdly is equal to or lower than the charging voltage Vc, that is,
The supply period of the charging current and the current value of the charging current can be adjusted. Therefore, according to the charging circuit of this specific example, in the charging operation of the electric double layer capacitor, the pulse-like operation control signal for controlling the supply of the charging current is generated and output with a simple configuration without using an oscillation circuit or the like. By appropriately changing and setting the delay time of the delay voltage Vdly, the charging current supply period (pulse width of the operation control signal) can be arbitrarily adjusted, and the charging conditions for the electric double layer capacitor can be adjusted. Can be optimized. In this embodiment, as in the case described above, the AC voltage from the commercial power supply is not stepped down using a transformer or the like, but is rectified by a diode or the like to generate a pulsating flow, and the pulsating current is generated by a delay circuit. Since the current value and supply period of the charging current are set based on the delay voltage of the pulsating current, the circuit configuration of the charging circuit can be simplified, and heat generation from the circuit elements can be suppressed, thereby significantly reducing the size. Weight reduction and cost reduction can be achieved.

<Fourth Embodiment> Next, a fourth embodiment of the charging circuit according to the present invention will be described with reference to the drawings. FIG. 11 is a block diagram showing a fourth embodiment of the charging circuit according to the present invention. Here, the same components as those in the above-described embodiment are denoted by the same reference numerals, and description thereof will be omitted. As shown in FIG. 11, the charging circuit according to the present embodiment includes a rectifier circuit 20A and a current limiting circuit 30A.
, Delay circuit 50G, voltage dividing circuit 50H, switch circuit 40A, and comparing circuit (third comparison determining means) 50F.
, Backflow prevention circuit 60A, charging voltage detection circuit 50C
And the input terminal Tin of the charging circuit includes:
An AC voltage is supplied from the commercial power supply 10 and the output terminal Tout
Is connected to an electric double layer capacitor 70A.

Here, the rectifier circuit 20A generates a pulsating current having a predetermined voltage cycle by half-wave rectifying or full-wave rectifying the AC voltage component of the commercial power supply 10 as described above, Is obtained by dividing the pulsating current (input voltage Vin) by an arbitrary time Tdly by a delay circuit 50G and dividing the pulsating current (input voltage Vin) by an arbitrary dividing ratio by a voltage dividing circuit 50H described later. Divided voltage V
The continuity of the switch circuit 40A is controlled based on the magnitude relationship with the div. Therefore, according to the charging circuit having such a configuration, the comparison circuit 50
By F, the switch circuit 40A is turned on only during a period in which the voltage change of the delay voltage Vdly delayed by an arbitrary time Tdly has a predetermined relationship with the reference voltage (divided voltage Vdiv) defined by the voltage dividing circuit 50H. As a state, a charging current according to the input voltage Vin generated by the rectifier circuit 20A is supplied to the electric double layer capacitor 70A.

Hereinafter, a specific circuit configuration example of the charging circuit according to the present embodiment will be described. FIG. 12 is a circuit configuration diagram illustrating a specific example of the charging circuit according to the fourth embodiment. FIG.
As shown in FIG. 5, in this specific example, a 100 V AC power supply supplied as commercial power is connected between a pair of input terminals Tina and Tinb of the charging circuit 100C, and a pair of output terminals Touta and Toutb of the charging circuit 100C are connected. Is connected to the electric double layer capacitor 70A. Also, one input terminal T
A half-wave rectifier diode D31, a current limiting resistor R31, a switch Tr31
And a backflow prevention diode D32 are connected in series.

Further, a resistor R32 and a delay R32 are provided between a contact N31 between the half-wave rectifier diode D31 and the current limiting resistor R31 and a ground potential to which the other input terminal Tinb and the output terminal Toutb are connected. The time setting resistor R33 and the capacitor C31 are connected in series, and the voltage dividing resistors R36, R37,
R38 are connected in series and individually.
Here, the delay time setting resistor R33 and the capacitor C31
Constitutes the delay circuit described above, and the voltage dividing resistors R36 and R3
7, R38 constitutes the above-mentioned voltage dividing circuit. Further, a contact N32 on the output terminal Touta side of the reverse current blocking diode D32, the other input terminal Tinb and the output terminal Toutb
Is connected to the ground potential to which the charging voltage detection resistor R is connected.
34 and R35 are provided. Here, the charging voltage detection resistors R34 and R35 constitute the above-described charging voltage detection circuit.

The contact N33 between the delay time setting resistor R33 and the capacitor C31 is connected to the comparator CM3.
1 (the negative input side in FIG. 11). On the other hand, a contact N34 between the charging voltage detection resistors R34 and R35 is connected to a contact between the voltage dividing resistors R37 and R38, and a contact N35 between the voltage dividing resistors R36 and R37.
Is connected to the other input (the positive input side in FIG. 11) of the comparator CM31. The output of the comparator CM31 is input directly to the gate of the switch Tr31 or via a photocoupler (not shown).
Here, the comparator CM31 constitutes the comparison circuit described above.

Next, the operation of the charging circuit according to this example will be described with reference to the drawings. FIG. 13 is a voltage / current waveform diagram showing an operation in the charging circuit according to this example. In the circuit configuration described above, as shown in FIG. 13A, the sine AC voltage of 100 V AC supplied from the commercial power supply 10 is rectified by the half-wave rectifier diode D31 as shown in FIG. For example, only the positive voltage component period of the sine AC voltage is extracted, and a pulsating current (input voltage Vin) having a positive voltage waveform is generated at a cycle equivalent to that of the commercial power supply 10. Here, the input voltage Vin is delayed by the delay time adjusting resistor R33 and the capacitor C31, and is delayed by a predetermined time (Tdly).
ly is input to one input terminal of the comparator CM31.

On the other hand, the charging voltage (voltage between the output terminals Touta and Toutb) Vc of the electric double layer capacitor 70A is
Extracted by the charging voltage detection resistors R34 and R35,
The divided voltage supplied to the contact between the voltage dividing resistors R37 and R38 and further divided at a predetermined voltage dividing ratio by the voltage dividing resistors R36 to R38 (the voltage at the contact N35 between the voltage dividing resistors R36 and R37) ) Vdiv is input to the other input terminal of the comparator CM21. Here, the division voltage Vdiv follows the input voltage Vin and indicates a voltage change according to the charging voltage Vc. As a result, the voltage changes of the delay voltage Vdly and the divided voltage Vdiv are input to the comparator CM31, and based on the comparison determination result (the magnitude relationship),
The conduction state of the switch Tr31 is controlled by the following two methods.

The first control method is as follows.
, When the condition of Vdiv> Vdly is satisfied, the logical output becomes high level, a pulse-like operation control signal is output, and the switch Tr31 is turned on, and as shown in FIG. Is supplied to the electric double layer capacitor 70A via the current limiting resistor R31, the switch Tr31, and the backflow prevention diode D32, and the charging operation is performed (time t41 to t42).
In the second control method, when the state is changed from the state satisfying the condition of Vdiv> Vdly to the state satisfying the condition of Vdiv <Vdly, the logical output becomes a high level and a pulse-like operation control signal is output. Switch Tr31 is ON
Then, as shown in FIG. 13D, a charging current corresponding to the input voltage Vin is supplied to the electric double layer capacitor 70A for a fixed time Ton from the switching, and the charging operation is performed (time t42). To t43). In this case, an operation control signal generation circuit (not shown) for outputting a pulse-like operation control signal for turning on the switch Tr31 for a predetermined time Ton in response to the logical output is provided by the comparison circuit 50.
It is provided between F and the switch circuit 40A.

As described above, the charging current is as shown in FIG.
As shown in (d), only during a certain time (time t41 to t42 or t42 to t43) satisfying the above conditions,
It is supplied to the electric double layer capacitor 70A. Here, since the charging voltage Vc extracted by the charging voltage detection resistors R34 and R35 is supplied to the contact point between the voltage dividing resistors R37 and R38, the division voltage Vdiv is raised by the charging voltage Vc. That is, the supply period of the charging current and the current value of the charging current can be changed in accordance with the progress of the state of charge of the electric double layer capacitor 70A. Therefore, according to the charging circuit of this specific example, in the charging operation of the electric double layer capacitor, the pulse-like operation control signal for controlling the supply of the charging current is generated and output with a simple configuration without using an oscillation circuit or the like. In addition, the supply state of the charging current is adjusted according to the change in the charging voltage Vc accompanying the progress of the charging state, so that the charging conditions for the electric double layer capacitor can be optimized.

Also in this embodiment, as in the case described above, the AC voltage from the commercial power supply is rectified by a diode or the like without being stepped down by using a transformer or the like, to generate a pulsating current, and generated by a delay circuit. Since the current value and supply period of the charging current are set based on the delayed voltage of the pulsating current and the divided voltage of the charging voltage generated by the voltage dividing circuit, the circuit configuration of the charging circuit is simplified. In addition, heat generation from the circuit element can be suppressed, and a significant reduction in size, weight, and cost can be achieved. In addition,
In this specific example, the configuration has been described in which the charging voltage Vc is extracted and supplied to the contact point between the voltage dividing resistors R37 and R38, and the division voltage Vdiv is raised by the charging voltage Vc.
Instead of supplying the charging voltage Vc, a voltage change of the input voltage Vin with respect to a predetermined voltage (for example, a ground potential) may be divided. In this case, a constant charging current is always supplied to the electric double layer capacitor 70A regardless of the charging voltage Vc.

<Fifth Embodiment> Next, a fifth embodiment of the charging circuit according to the present invention will be described with reference to the drawings. FIG. 14 is a block diagram illustrating a fifth embodiment of the charging circuit according to the present invention, and FIG. 15 is a schematic configuration diagram illustrating an example of a charging stabilizing circuit applied to the charging circuit according to the present invention. . Here, the same components as those in the above-described embodiment are denoted by the same reference numerals, and description thereof will be omitted.
FIG. 14A shows an example in which the charge stabilizing circuit 80A constituting the charge stopping means or the charging current stabilizing means is applied to the structure shown in the first embodiment (see FIG. 2). The electric double layer capacitor 70A is provided by the stabilizing circuit 80A.
Of the electric double layer capacitor 7 is detected.
0A state of charge is determined, and based on the determination result,
The conduction state of the switch circuit 40A is controlled to optimize the supply state of the charging current. FIG. 15B shows an example in which the charge stabilizing circuit 80A is applied to the configuration shown in the second embodiment (see FIG. 6). The charge stabilizing circuit 80A uses the charging voltage of the electric double layer capacitor 70A. Vc is detected,
The charge state of the electric double layer capacitor 70A is determined, and based on the determination result, the pulse signal in the pulse generation circuit 50A is adjusted and controlled to optimize the supply state of the charging current. Although not shown, the present invention can be similarly applied to the configurations of the third embodiment (see FIG. 8) and the fourth embodiment (see FIG. 11). That is, the third and fourth
In the case of the configuration of the embodiment, the delay time in the delay circuit is adjusted and controlled based on the charge stabilizing circuit 80A to optimize the supply state of the charging current.

Hereinafter, each component will be described in sequence. In the charging circuit having the above configuration, the charging stabilization circuit 8
When 0A is applied as the charge stopping means, the charging voltage Vc of the electric double layer capacitor 70A is detected at any time, and the charging voltage Vc and a predetermined charge that defines the saturation (or termination) of the charging state of the electric double layer capacitor are determined. By comparing with the stop voltage, the progress of charging is determined. Then, when the charging voltage Vc reaches the charging stop voltage, an operation control signal for turning off the switch circuit 40A is output, the supply of the charging current is cut off, and the control for stopping the charging operation is performed.
Thereby, overcharging of the electric double layer capacitor is prevented, deterioration and power loss of the electric double layer capacitor can be reduced, and a safe and appropriate charging operation can be performed.

In the above-described charging circuit, when the charging stabilizing circuit 80A is applied as charging current stabilizing means, the charging voltage Vc of the electric double layer capacitor 70A is detected as needed, and the time derivative of the charging voltage Vc is calculated. On the basis of the differential value, an operation control signal for adjusting the conduction state (the conduction period of the switch circuit) of the switch circuit 40A is output to perform control for making the charging current supplied to the electric double layer capacitor 70A substantially constant. Do. That is, in each of the above-described embodiments, the operation control signal for controlling the supply of the charging current has a pulse waveform, and based on this operation control signal, the conduction state of the switch is controlled, Is supplied to the electric double layer capacitor. Therefore, when a large current instantaneously flows as a charging current, a power supply voltage may drop due to power supply impedance, and the charging current may be temporarily difficult to flow.

Specifically, for example, the average charging current is 1 A
In this case, when a current of 10 A flows down as an instantaneous current,
Even if the power supply impedance is 0.2Ω, it is about 2V
Will occur. With respect to such a voltage drop, in each of the above-described embodiments, since a resistance element is used as a current limiting circuit, the charging current significantly decreases, and its operation must be compensated. Therefore, the present embodiment is characterized in that such fluctuation of the charging current (drop of the power supply voltage) is compensated to stabilize the charging operation. Here, the charge stabilizing circuit 80A applied to the present embodiment will be described in more detail. The charge stabilizing circuit 80A, as shown in FIG. Voltage holding circuits 81 and 82 for sequentially holding the instantaneous voltage at a predetermined time of the charging voltage Vc of the multilayer capacitor, and a predetermined control signal in accordance with the voltage difference between the respective instantaneous voltages held in the voltage holding circuits 81 and 82. An amplification circuit 83 that outputs
It has.

Charge stabilizing circuit 8 having such a configuration
According to 0A, as shown in FIG. 15B, based on a predetermined operation clock CK, an instantaneous voltage V1 applied to the electric double layer capacitor 70A at time t1 and a time after a predetermined time Dt has elapsed Instantaneous voltage V2 at t2
Is taken in and held by the voltage hold circuits 81 and 82,
The amplifying circuit 83 outputs a predetermined control signal based on the voltage difference ΔVc between the instantaneous voltages V1 and V2 with respect to the time change (t1-t2), for example, a pulse-like operation control signal for controlling the conduction state of the switch circuit. The signal width (pulse width) is adjusted (wide / narrow) so that control is performed so that the charging current supplied by the switch circuit 40A becomes constant.
That is, the differential value of the instantaneous voltage applied to the electric double layer capacitor 70A (dVc / dt; corresponding to the charging current)
The adjustment of the voltage range in the first embodiment, the adjustment of the pulse period in the second embodiment, and the adjustment of the delay time in the third and fourth embodiments are performed on the basis of By doing so, fluctuations in the charging current (average current value) can be suppressed and control can be made substantially constant.

Thus, in the charging operation of the electric double layer capacitor, the average charging current can be controlled to be substantially constant irrespective of the change in the power supply impedance caused by the instantaneous large current flowing. It is possible to suppress the deterioration of the electric double layer capacitor due to the flow of the charging current and the prolongation of the charging time due to the shortage of the charging current, etc., and to set appropriate charging conditions (setting of the current value) to ensure safe and optimal A charging operation can be performed. The control process in the charging stabilization circuit is performed at the start of the charging operation by combining the charging voltage and the time differential value thereof, or
The control of changing the charging current may be performed at the end of the charging operation. In this case, the charging state of the electric double layer capacitor can be optimized in accordance with the more realistic charging operation of the charging circuit. .

[0058]

According to the first aspect of the present invention, a power supply means for rectifying an AC voltage component of a commercial power supply to generate a pulsating current having a predetermined voltage cycle, and a charging current corresponding to a voltage component of the pulsating current. And a charging control means for controlling the operation state of the charging current supply means to control the supply state of the charging current to the capacitor type storage battery. It does not require the configuration of a transformer for stepping down the voltage or an oscillation circuit such as an inverter.The circuit configuration of the charging circuit is simplified and the size and weight are reduced. Operation can be optimized.

According to the second or fourth aspect of the present invention, the charging control means only supplies the charging current according to the voltage component of the pulsating current when the voltage component is within a predetermined voltage range. The charging current supply means is controlled so as to supply power to the capacitor-type storage battery, so that an excessive charging current can be suppressed from being supplied to the capacitor-type storage battery, and deterioration and power loss of the capacitor-type storage battery can be reduced. A charging operation can be performed. According to the invention described in claim 3,
Since the charging control means is configured to arbitrarily set the voltage amplitude of the pulsating flow to adjust and control the supply state of the charging current, it is possible to arbitrarily adjust the charging current supply period and the current value. It is possible to optimize the condition for charging the capacitor type storage battery. According to the fifth aspect of the present invention, the charging control means sets the signal width and the signal cycle of the operation control signal (pulse signal) for controlling the operation of the charging current supply means, thereby arbitrarily setting the charging current supply state. , The cycle of the operation control signal is set sufficiently smaller than the AC voltage cycle of the commercial power supply to increase the charging current supplied to the capacitor-type storage battery and to perform charging. Time can be reduced.

According to the present invention, the charging control means includes the control signal generating means for generating an operation control signal having an arbitrary signal width and a signal period. Since it can be set to any phase and cycle independent of the AC power supply, it is not necessary to consider the AC voltage cycle of the commercial power supply. It can be changed as appropriate. According to the seventh aspect of the invention, the charging control means is configured to adjust and control the supply state of the charging current by arbitrarily setting the delay time of the voltage cycle of the pulsating current. It is possible to arbitrarily adjust the supply period of the charging current and the current value with a simple configuration without using any other means, and to optimize the charging conditions for the capacitor-type storage battery. According to the invention as set forth in claim 8, the charging control means, when the voltage component of the delayed pulsating current obtained by delaying the voltage cycle of the pulsating current for a predetermined time has a predetermined relationship with the charging voltage of the capacitor-type storage battery, Since the second comparison / determination means for controlling the operation of the charging current supply means so as to supply the charging current to the capacitor type storage battery is provided, it is possible to arbitrarily adjust the charging current supply period and the current value with a simple configuration. Thus, the condition for charging the capacitor-type storage battery can be optimized.

According to the ninth or tenth aspect of the present invention, the charging control means includes a voltage component of the partial pressure pulsating flow obtained by dividing the pulsating flow at a predetermined partial pressure ratio, and a delay pulse obtained by delaying the pulsating flow by a predetermined time. The charge current supply state is adjusted and controlled by arbitrarily setting the comparison condition with the voltage component of the current.Therefore, the charge current supply period can be reduced with a simple configuration without using an oscillation circuit or the like. And the current value can be arbitrarily adjusted, and the charging condition for the capacitor-type storage battery can be optimized. According to the eleventh aspect, the charging control means includes:
A charge stopping means for extracting the charging voltage of the capacitor type storage battery and controlling the operation of the charging current supply means so as to stop supplying the charging current to the capacitor type storage battery when the charging voltage reaches a predetermined voltage or more. Accordingly, overcharging of the capacitor-type storage battery can be prevented, deterioration and power loss of the capacitor-type storage battery can be reduced, and a safe and appropriate charging operation can be performed.

According to the twelfth aspect of the present invention, the charging control means extracts the charging voltage of the capacitor-type storage battery and supplies it to the capacitor-type storage battery in accordance with the potential difference (time differential value) of the charging voltage every predetermined time. Charging current stabilizing means for controlling the operation of the charging current supplying means so as to make the charging current substantially constant, regardless of the change in the power supply impedance accompanying the supply of the pulsed charging current. Can be controlled to be substantially constant, and it is possible to suppress deterioration of the capacitor type storage battery due to excessive flow of the charging current and prolong the charging time due to insufficient charging current, and to set an appropriate charging condition. , Safe and optimal charging operation can be performed. According to the invention of claim 13, the AC voltage component of the commercial power supply is rectified to generate a pulsating current having a predetermined voltage cycle, and based on an arbitrarily set predetermined period,
A procedure for adjusting and controlling the supply state of the charging current by supplying a charging current corresponding to the voltage component of the pulsating current to the capacitor-type storage battery is included. , The supply period and the current value can be appropriately set, and a safe and favorable charging operation can be realized.

[Brief description of the drawings]

FIG. 1 is a block diagram showing the overall configuration of a charging circuit according to the present invention.

FIG. 2 is a block diagram showing a first embodiment of a charging circuit according to the present invention.

FIG. 3 is a circuit configuration diagram showing a specific example of a charging circuit according to the first embodiment.

FIG. 4 is a voltage / current waveform diagram showing a basic operation in the charging circuit according to the first embodiment.

FIG. 5 is a voltage / current waveform diagram showing another operation in the charging circuit according to the first embodiment.

FIG. 6 is a block diagram showing a second embodiment of the charging circuit according to the present invention.

FIG. 7 is a voltage / current waveform diagram showing an operation in the charging circuit according to the second embodiment.

FIG. 8 is a block diagram showing a third embodiment of the charging circuit according to the present invention.

FIG. 9 is a circuit configuration diagram illustrating a specific example of a charging circuit according to a third embodiment.

FIG. 10 is a voltage / current waveform diagram showing an operation in the charging circuit according to the third embodiment.

FIG. 11 is a block diagram showing a fourth embodiment of the charging circuit according to the present invention.

FIG. 12 is a circuit configuration diagram showing a specific example of a charging circuit according to a fourth embodiment.

FIG. 13 is a voltage / current waveform diagram showing an operation in the charging circuit according to the fourth embodiment.

FIG. 14 is a block diagram showing a fifth embodiment of the charging circuit according to the present invention.

FIG. 15 is a schematic configuration diagram showing an example of a charging stabilization circuit applied to the charging circuit according to the present invention.

[Description of Signs] 10 Commercial power supply 20, 20A to 20D Rectifier circuit 30, 30A Current limiting circuit 40, 40A Switch circuit 50 Switch control circuit 50A Voltage judgment circuit 50B Input voltage detection circuit 50C Charging voltage detection circuit 50D Pulse generation circuit 50E Stable Power supply circuit 50F comparison circuit 50G delay circuit 50H voltage divider circuit 60, 60A backflow prevention circuit 70 capacitor type storage battery 70A electric double layer capacitor 80A charge stabilization circuit 100A-100C charging circuit

Claims (13)

[Claims] 1. A power supply means for rectifying an AC voltage component of a commercial power supply to generate a pulsating current having a predetermined voltage cycle; a charging current supplying means for supplying a charging current according to a voltage component of the pulsating current; Charge control means for controlling an operation state of the charging current supply means to control a supply state of the charging current; and a capacitor type storage battery for storing electric energy corresponding to the charging current supplied from the charging current supply means. And a charging circuit comprising: 2. The method according to claim 1, wherein the charge control unit is configured to supply the charging current corresponding to the voltage component to the capacitor type storage battery only when the voltage component of the pulsating current is within a predetermined voltage range. The charging circuit according to claim 1, wherein the operation of the current supply means is controlled. 3. The charging circuit according to claim 1, wherein the charging control means adjusts and controls the supply state of the charging current by arbitrarily setting the voltage amplitude of the pulsating flow. 4. The charge control unit compares a voltage component of the pulsating current with a predetermined voltage range based on a charging voltage of the capacitor-type storage battery, and the voltage component of the pulsating current is within the voltage range. 2. The charging circuit according to claim 1, further comprising a first comparison / determination unit that controls an operation of the charging current supply unit so as to supply the charging current to the capacitor-type storage battery. 5. The charging control unit according to claim 1, wherein the charging control unit controls the charging current supply state by arbitrarily setting a signal width and a signal period of an operation control signal for controlling an operation of the charging current supply unit. The charging circuit according to claim 1, wherein: 6. The charging circuit according to claim 1, wherein said charging control means includes a control signal generating means for generating an operation control signal having an arbitrary signal width and a signal period. 7. The charge control unit according to claim 1, wherein the charge control unit adjusts and controls a supply state of the charging current by arbitrarily setting a delay time of a voltage cycle of the pulsating current.
The charging circuit as described. 8. The charging control means compares a voltage component of a delayed pulsating current obtained by delaying a voltage cycle of the pulsating current for a predetermined time with a charging voltage of the capacitor type storage battery, and determines a voltage component of the delayed pulsating current. Has a second comparison / determination means for controlling an operation of the charging current supply means so as to supply the charging current to the capacitor type storage battery when the charging voltage has a predetermined relationship. The charging circuit according to claim 1, wherein 9. The charge control means compares a voltage component of a partial pressure pulsation obtained by dividing the pulsation at a predetermined division ratio with a voltage component of a delayed pulsation obtained by delaying the pulsation for a predetermined time. 2. The charging circuit according to claim 1, wherein the supply state of the charging current is adjusted and controlled by arbitrarily setting conditions. 10. The charge control means compares a voltage component of a partial pressure pulsation obtained by dividing the pulsation at a predetermined division ratio with a voltage component of a delayed pulsation obtained by delaying the pulsation for a predetermined time. And a third comparison / determination means for controlling the operation of the charging current supply means so as to supply the charging current to the capacitor type storage battery when the comparison result satisfies a predetermined condition. The charging circuit according to claim 1. 11. The charging control means extracts a charging voltage of the capacitor-type storage battery, and stops supplying the charging current to the capacitor-type storage battery when the charging voltage reaches a predetermined voltage or more. 2. The charging circuit according to claim 1, further comprising a charging stop means for controlling an operation of said charging current supply means. 12. The charging control means extracts a charging voltage of the capacitor-type storage battery and makes the charging current supplied to the capacitor-type storage battery substantially constant according to a potential difference of the charging voltage at predetermined time intervals. 2. The charging circuit according to claim 1, further comprising a charging current stabilizing means for controlling an operation of said charging current supplying means. 13. A procedure for rectifying an AC voltage component of a commercial power supply to generate a pulsating current having a predetermined voltage cycle, supplying a charging current according to a voltage component of the pulsating current for a predetermined period, Arbitrarily setting a predetermined period to adjust and control the supply state of the charging current; and storing electric energy corresponding to the charging current supplied in the predetermined period in a capacitor type storage battery. A charging control method for a charging circuit, comprising: