JP2001160708A - Adaptive array antenna - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide an adaptive array antenna used in a radio communication system by simple circuit constitution. SOLUTION: Relating to this adaptive array antenna, the phase shift amount of one of plural phase shift means is setting-changed to a value for which the phase shift amount set at present is increased by a prescribed angle and then setting-changed to the value for which the phase shift amount set at present is decreased by the prescribed angle. The strength change of synthesized reception signals at the time is detected by a signal strength detection means, a partial differential coefficient to the phase shift amount of an evaluation function is obtained by using only the detected strength change of the reception signals and phase control based on the partial differential coefficient to the phase shift amount of the evaluation function is performed by the simple circuit constitution without using signals for respective antenna elements. The prescribed angle can be 90 degrees to put it concretely. Also, a differential coefficient to real number weight based on a steepest lowering method can be obtained by adopting real number weight control.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an adaptive array antenna, and more particularly to a radio communication system and a radio base station used in the radio communication system, and an adaptive array antenna used in the radio base station.

[0002]

2. Description of the Related Art Currently, wireless local loops (WL)
Development of a technology for inexpensively configuring a direct communication path to a subscriber by using a radio called L) has begun. Of which
A type of system in which a plurality of terminal stations can be accommodated for one base station is called point-to-multipoint (PTMP). FIG. 37 is an explanatory view of this PTMP-type WLL.

In general, in PTMP, it is necessary to communicate with a plurality of terminal stations having different directions as viewed from the base station. Therefore, a base station antenna having a relatively large half-value angle of 60 to 120 degrees is used. On the other hand, a terminal station generally uses an antenna having a small half-value angle of about 10 degrees and a large gain. Therefore, in the case of PTMP, interference from a base station other than a desired terminal station at the time of base station reception becomes a serious problem. FIG. 38 shows an arrival state of an interference wave when a sector antenna having a half value angle of 120 degrees is used. In particular, since the control channel used to make a call to the base station is a random access method that cannot be scheduled by the base station, there is a high possibility that many interference waves will occur, and the control channel can accept calls. There is a possibility that communication is disabled.

Therefore, when a general sector antenna is used, a transmission signal from a terminal having a sharp directional antenna may reach a very distant base station.
A distance interval for performing frequency repetition is required. Specifically, about four to seven cells are defined as one unit, a frequency channel is divided in this unit, and the frequency is spatially reused by performing frequency repetition for each unit. FIG. 39 shows an arrival state of an interference wave in the case of four-cell frequency repetition. However, in this case, there is a limitation that the number of frequency channels allocated to the system is limited due to the restriction on the repeated use of the frequency, so that the capacity of the subscriber that can be accommodated in the system as a whole is reduced.

[0005] In order to avoid interference at the same time without performing frequency repetition or reducing the number of repetitions, together with an interference canceller that removes a signal from another interfering station from the original received signal by signal processing, other interference cancellers are used. The use of an adaptive array antenna that directs the null direction of the antenna to the station is being considered.

However, like a control channel of a PTMP system, an interference signal is generated at an unpredictable random timing, and the duration of the interference signal is as short as several microseconds to several tens of microseconds. Therefore, an extremely fast signal is needed to perform control using digital signal processing or the like to sequentially detect the interference wave from this terminal and the direction of arrival at its own base station and direct null to the direction of the terminal. There is a problem that a processing speed is required.

Further, as shown in FIG. 40, in the case of a DBF (Digital Beam Forming) type adaptive antenna which has been mainly studied in recent years, if the transmission rate becomes faster, such as 1 Mbaud or more, which is studied in the PTMP system, real-time There is a problem that very fast digital signal processing is required to perform reception.

On the other hand, in the case of the PTMP system, similarly to the mobile communication, in order to suppress the occurrence of unnecessary interference waves, it is conceivable to control the transmission power from the mobile station and make the reception power at the base station as constant as possible. Can be However, even in this case, the actual received power may not be constant due to the effects of fading, shadowing, and the like.Therefore, in order to make the signal level at the final stage of the receiver almost constant, an adaptive array is required. AG to base station including antenna
C function is required. For example, as shown in FIG.
It is conceivable to provide an AGC function by inserting a variable gain amplifier 3801 into the output after the synthesis of the adaptive array antenna. However, for example, in the case where a signal from a terminal other than the desired terminal is stopped in a cell and the null point is scanned by continuously changing the phase shift amount by a phase shifter, the dynamic range of the signal level after the synthesis is considerably large. On the other hand, the signal strength from each antenna before combining is expected to be at a substantially constant level. In this case, just because the level of the received signal after the combination has been lowered, the level of FIG.
As shown in (5), if the gain of the AGC variable gain amplifier 3801 inserted into the combined signal line is increased,
There is a problem that saturation occurs in a part of the signal flow before the synthesis.

Conversely, if the combining is performed such that the beam is directed in that direction after the terminal direction can be almost identified, or after converging to an almost optimal weighting coefficient, the signal strength after the combination is stable. And fluctuations are reduced. On the other hand, the intensity of the signal from each antenna before combining may increase in level due to combining of signals from a plurality of terminal stations. In this case, since the AGC function hardly operates, there is a problem that saturation occurs in a part of the signal flow before the synthesis.

When an adaptive array antenna is used for transmission, transmission power control is performed only by a variable gain amplifier 3901 before distribution to each element as shown in FIG. 42, or as shown in FIG. When the transmission power is controlled only by the plurality of variable gain amplifiers 4001 inserted in the signal paths for the respective elements after distribution, the effective radiation power (ERP-EffectiveRadiation Power-) in consideration of the directivity gain of the adaptive array antenna is obtained. There has been a problem that the value may exceed a predetermined value or the high-frequency circuit element for each individual element may be saturated.

[0011]

As described above, the conventional technique requires a very high signal processing speed when an adaptive array antenna is used to reduce interference from a terminal station in PTMP. was there.

[0012] In recent years, D which has been mainly studied
In the case of a BF (Digital Beam Forming) type adaptive array antenna, when the transmission rate is increased, there is a problem that very fast digital signal processing is required for real-time reception.

[0013] Further, by inserting a variable gain amplifier into the output after the synthesis of the adaptive array antenna, the AGC
When the function is provided, if the gain of the AGC amplifier is increased just because the level of the received signal after the combination is lowered, there is a problem that saturation occurs in a part of the signal flow before the combination. there were.

When an adaptive array antenna is used for base station transmission, transmission power is controlled only by a variable gain amplifier before distribution to each element, or inserted into a signal path for each element after distribution. If transmission power control is performed only with multiple variable gain amplifiers, the effective radiated power in consideration of the directional gain of the adaptive array antenna will exceed the specified value, or the high-frequency circuit for each individual element will saturate. There was a problem that it might be.

In order to solve the above problems, the present invention provides an evaluation function using a plurality of individual element signal strengths detected by individual element signal strength detecting means and a combined signal strength detected by the combined signal strength detecting means. The real weight control based on the steepest descent method can be performed by finding the differential coefficient for the real weight of, and it is realized with a simpler circuit configuration than when using the demodulated signal of each antenna element as in the prior art. It is an object of the present invention to provide an adaptive array antenna capable of performing such operations.

Further, according to the present invention, in an adaptive array antenna including a plurality of antenna elements, a high-frequency circuit connected to each antenna element, and a high-frequency synthesis circuit for synthesizing the outputs of the plurality of high-frequency circuits, the output signal level after the synthesis is obtained. It is an object of the present invention to provide an adaptive array antenna capable of controlling the width of the antenna to a fixed width and controlling the high-frequency circuit for each individual element so as not to be saturated.

Further, according to the present invention, there are provided a plurality of antenna elements, a high-frequency circuit connected to each antenna element, and a high-frequency distribution circuit for distributing an output to the plurality of high-frequency circuits. Or a weight control circuit that weights the phase, controls the effective radiated power in consideration of the directional gain from the antenna not to exceed a predetermined value, and saturates the high-frequency circuit for each individual element. It is another object of the present invention to provide an adaptive array antenna which can be controlled so as not to perform the control.

[0018]

In order to achieve the above object, an adaptive array antenna according to a first basic configuration of the present invention comprises a plurality of antenna elements and a reception signal received by each of the antenna elements. A plurality of phase shifting means for controlling the phase according to the phase shift amount, and a combining means for combining the received signals phase-controlled by these phase shifting means,
A signal strength detection means for detecting the strength of the received signal synthesized by the synthesis means; and a phase shift amount calculated based on the strength of the received signal detected by the signal strength detection means. Phase shift amount control means for setting the phase shift amount in each of the phase shift means, wherein the phase shift amount control means is based on various signal intensities output from the synthesis means and a plurality of phase shift amounts. Phase shift amount calculating means for calculating and outputting a phase shift amount in the plurality of phase shift means in a plurality of cycles; initial value storage means for storing initial values of the plurality of phase shift means; and storage in the storage means A first phase shift amount storing means for storing a first phase shift amount calculated by the phase shift amount calculating means as a value to be set for each of the plurality of phase shift means based on each of the initial values set And the first transfer Second phase shift amount storage means for storing a second phase shift amount in the plurality of phase shift means calculated by the calculation means so as to increase the amounts by 90 degrees, respectively, and the first phase shift amount Phase shift amount storage means for storing a third phase shift amount in the plurality of phase shift means calculated by the calculation means so that each of the phase shift amounts is reduced by 90 degrees; and the first to third shift amounts. One of the phase amount storage means
A plurality of phase shift amount setting means for respectively setting the phase shift amounts of the plurality of phase shift means calculated by the phase shift amount calculation means based on the stored phase shift amounts; The first signal strength detected by the signal strength detection means with the second phase shift amount set in the first
Signal strength storage means, and the third phase shift means
And a second signal strength storage means for storing a second signal strength detected by the signal strength detection means in a state where the phase shift amount is set.
When the difference between the signal strength of the second signal strength and the signal strength of the second signal strength is input, the first phase shift amount is calculated by increasing the first phase shift amount by a value proportional to the difference. It is characterized in that it is provided with an update stop means for inputting a phase amount, repeating the calculation of a plurality of cycles until the difference disappears, and stopping the operation of the phase shift amount control means based on a predetermined condition.

Further, in the adaptive array antenna according to the first basic configuration, the initial value storage means stores the initial values Φ1 (0) to Φn (0) of the phase shift amounts, respectively, and controls the phase shift amount control. When the means operates for the first time, Φ1 (0) to Φn (0) are input to Φ1 (k) to Φn (k) of the first phase shift amount storage means, respectively, and the first phase shift amount storage means Is the phase shift amount Φ (k) set in each of the phase shift means.
.About..PHI.n (k) (n is the number of antenna elements, k is the number of updates of the phase shift amount), and the second phase shift amount storage means stores the .PHI.1 (k) to .PHI.n (k) at a predetermined angle. Φ1 ′ (k) to Φn ′ (k) are calculated and stored, and the third phase shift amount storage means stores the Φ1 ′
(K) to Φn (k) are respectively reduced by a predetermined angle, and the phase shift amounts Φ1 ″ (k) to Φn ″ (k) calculated are stored, and the phase shift amount setting means stores the first phase shift. The phase shift amount stored in any one of the amount storage means, the second phase shift amount storage means, or the third phase shift amount storage means is set in each of the plurality of phase shift means, and the first .., Φi−1 are stored in the phase shift means, respectively, as Φ1 (k), Φ2 (k),.
(K), Φi '(k), Φi + 1 (k), ..., Φn
(K) When (1 ≦ i ≦ n) is set, the signal strength Pi ′ as the first signal strength detected by the signal strength detection means is stored, and the second signal strength storage means , Φ1 (k), Φ2 (k),...
Φi−1 (k), Φi ″ (k), Φi + 1 (k),.
The signal strength P as the second signal strength detected by the signal strength detection means in a state where Φn (k) is set
i ", and the phase shift amount calculating means stores the signal strength P
Φi (k) by a value proportional to the difference between i ′ and Pi ″
The update stopping means stops the operation after repeating the operation of the phase shift amount control means a predetermined number of times.

Further, the adaptive array antenna according to the second basic configuration of the present invention has a plurality of antenna elements and a phase shifter for performing phase control of a received signal received by these antenna elements in accordance with each set phase shift amount. Phase means, synthesizing means for synthesizing the received signals whose phases have been controlled by the phase shifting means, reference signal generating means for generating a reference signal, and the received signal synthesized by the synthesizing means and generated by the reference signal generating means Error detecting means for outputting a difference from the detected reference signal, error signal strength detecting means for detecting the signal strength of the error signal detected by the error detecting means, and an error signal detected by the error signal strength detecting means. Phase shift amount calculating means for calculating a phase shift amount based on the signal strength of the phase shifter and setting the calculated phase shift amounts to each of the plurality of phase shift means. In the phase shift amount control means,
A phase shift amount calculating means for calculating and outputting a plurality of cycles of a phase shift amount in the plurality of phase shift means based on various signal strengths and a plurality of phase shift amounts output from the error signal strength detecting means; Initial value storage means for storing respective initial values of the phase shift means, and each of the plurality of phase shift means by the phase shift amount calculating means based on the respective initial values stored in the initial value storage means. And a first phase shift amount storing means for storing a first phase shift amount calculated to be set to the first phase shift amount, and a first phase shift amount calculated by the calculating means to increase the first phase shift amount by a predetermined angle. A second phase shift amount storage unit for storing a second phase shift amount in the plurality of phase shift units; and a second phase shift amount calculated by the calculation unit so as to reduce the first phase shift amount by a predetermined angle. A plurality of phase shifting means A third phase shift amount storing means for storing the amount of phase shift, and the phase shift amount calculation based on the phase shift amount stored in one of the first to third phase shift amount storing means. A plurality of phase shift amount setting means for respectively setting the phase shift amounts of the plurality of phase shift means calculated by the means; and the error in a state where the second phase shift amount is set in the plurality of phase shift means. First error signal strength storage means for storing a first error signal strength detected by the signal strength detection means; and the error signal in a state where the third phase shift amount is set in the plurality of phase shift means. A second error signal strength storage means for storing a second error signal strength detected by the strength detection means, wherein the phase shift amount calculating means comprises the first error signal strength and the second error signal strength When the difference is input, the first phase shift amount is increased by a value proportional to the difference. The calculated new phase shift amount is input to the first phase shift amount, and a plurality of cycles of calculation are repeated until the difference disappears, and the operation of the phase shift amount control means is performed based on predetermined conditions. It is characterized by having an update stopping means for stopping the operation.

Further, in the adaptive array antenna according to the second basic configuration, the first phase shift amount storage means stores the phase shift amounts Φ1 (k) to Φn respectively set in the phase shift means.
(K) (n is the number of antenna elements, k is the number of updates of the phase shift amount)
And the second phase shift amount storage means stores the Φ1
(K) to Φn (k) are respectively increased by predetermined angles, and the phase shift amounts Φ1 ′ (k) to Φn ′ (k) calculated are stored, respectively, and the third phase shift amount storage means stores the Φ1 (K) ~ Φn
(K) are respectively reduced by a predetermined angle, and the phase shift amounts Φ1 ″ (k) to Φn ″ (k) calculated are stored, respectively, and the phase shift amount setting means is provided with the first phase shift amount storage means or Setting the phase shift amount stored in any one of the second phase shift amount storage means or the third phase shift amount storage means in each of the phase shift means;
The first error signal strength storage means stores Φ1 (k), Φ2 (k),..., Φi-1 (k), Φi ′ in the phase shift means, respectively.
(K), Φi + 1 (k),..., Φn (k) (1 ≦ i ≦
storing the second error signal strength Qi 'detected by the error signal strength detection means with n) set;
The second signal strength storage means stores the Φ1
(K), Φ2 (k), ..., Φi-1 (k), Φi "
(K), Φi + 1 (k),..., Φn (k) are set, and the second error signal strength Qi ″ detected by the error signal strength detection means is stored. Are the first and second error signal strengths Qi 'and Qi.
calculating a new phase shift amount Φi (k + 1) which is increased to Φi (k) by a value proportional to the difference of i ″ and inputting it to Φi (k) of the first phase shift amount storage means; The initial value storage means stores the initial values of the phase shift amounts Φ1 (0) to Φn (0), respectively, and when the phase shift amount control means operates for the first time, the initial values of the phase shift amounts Φ1 (0) to Φ1 (0). .PHI.n (0) is input to .PHI.1 (k) to .PHI.n (k) of the first phase shift amount storage means.

In the adaptive array antenna configured as described above, using only the signal strength detected by the signal strength detection means to perform the phase shift amount control based on the partial differential coefficient with respect to the phase shift amount of the evaluation function. Therefore, an antenna system can be configured with a simpler circuit configuration as compared with a case where a signal for each antenna element is used as in a conventional adaptive array antenna.

Further, the adaptive array antenna according to the third basic configuration of the present invention comprises a plurality of antenna elements and a circuit at a subsequent stage which receives signals received by these antenna elements in accordance with control signals input from the outside. A plurality of signal blocking means for passing or blocking the signal, a plurality of phase shifting means for controlling the phase of the received signal passing through the signal blocking means in accordance with each set phase shift amount, and a phase controlled by the phase shifting means. Combining means for combining the received signals, signal strength detecting means for detecting the strength of the received signal combined by the combining means, and a phase shift amount based on the strength of the received signal detected by the signal strength detecting means. Phase shift amount control means for calculating and setting the calculated phase shift amount to each of the phase shift means, wherein the phase shift amount control means comprises:
Any one of the plurality of signal cutoff means, and a signal selection means for selectively switching the plurality of signal cutoff means so that any two of the signal cutoff signals are set on the passing side and the rest are set on the cutoff side. In the state where two are set on the passing side and the rest are set on the blocking side, the phase shift amount at which the strength (P) becomes minimum based on the strength (P) of the received signal detected by the signal strength detection means. The phase shift amount calculated by the phase shift amount calculating means is connected to one of the plurality of phase shift means connected to the signal blocking means set on the passing side by the signal selecting means. And phase shift amount setting means for setting a phase amount.

An adaptive array antenna according to a fourth basic configuration of the present invention comprises a plurality of antenna elements and a circuit at a subsequent stage which receives signals received by these antenna elements in accordance with a control signal input from the outside. A plurality of signal blocking means for passing or blocking the signal, a plurality of phase shifting means for controlling the phase of the received signal passing through the signal blocking means in accordance with each set phase shift amount, and a phase controlled by the phase shifting means. Combining means for combining the received signals, signal strength detecting means for detecting the strength of the received signal combined by the combining means, and a phase shift amount based on the strength of the received signal detected by the signal strength detecting means. Phase shift amount control means for calculating and setting the calculated phase shift amount to each of the phase shift means, wherein the phase shift amount control means comprises:
A first signal strength storage means for storing a first strength (P1) of the received signal detected by the signal strength detection means in a state where the desired wave and the interference wave are present; A second signal strength storing means for storing a second strength (P2) of the received signal detected by the signal strength detecting means; and setting any two of the signal cutoff signals to the passing side, and cutting off the rest. The first intensity (P1) and the second intensity (P2) are set in a state in which any two of the signal selection means and the signal blocking means are set to the passing side and the rest are set to the blocking side. ), The difference (P1-P2)
A phase shift amount calculating means for calculating a phase shift amount for minimizing the phase shift amount, and a phase shift amount connected to a signal blocking means set on the passing side by the signal selecting means among the plurality of phase shift means. Phase shift amount setting means for setting the phase shift amount calculated by the calculation means.

Further, the adaptive array antenna according to the fifth basic configuration of the present invention has a distribution means for distributing a transmission signal, and the transmission signal distributed by the distribution means is phase-shifted in accordance with each set phase shift amount. A plurality of phase-shift means for controlling, a plurality of signal cut-off means for passing or blocking a transmission signal whose phase is controlled by these phase-shift means to a subsequent circuit in accordance with a control signal input from the outside, respectively; An antenna element for transmitting a transmission signal passing through the means,
Phase shift amount control means for calculating the phase shift amount based on the input information and setting the calculated phase shift amount to the phase shift means, respectively, by a notification from a communication partner station, etc. A signal strength detecting means for detecting the signal strength of the received signal received at the partner station is provided, and the phase shift amount controlling means sets any two of the signal blocking means to the passing side, and sets the rest to the blocking side. Signal selection means to be set to
In a state where any two of the plurality of signal cutoff means are set on the pass side and the rest are set on the cutoff side, the strength (P) of the received signal detected by the signal strength detection means is determined based on the strength (P) of the received signal. P) a phase shift amount calculating means for calculating a phase shift amount which minimizes P), and a phase shift means connected to a signal cutoff means set on the passing side by the signal selecting means among the plurality of phase shift means. Phase shift amount setting means for setting the phase shift amount calculated by the phase amount calculation means.

Further, the adaptive array antenna according to the sixth basic configuration of the present invention has a distribution means for distributing a transmission signal, and the transmission signal distributed by the distribution means is phase-shifted in accordance with each set phase shift amount. A plurality of phase-shift means for controlling, a plurality of signal cut-off means for passing or blocking a transmission signal whose phase is controlled by these phase-shift means to a subsequent circuit in accordance with a control signal input from the outside, respectively; An antenna element for transmitting a transmission signal passing through the means,
Phase shift amount control means for calculating the phase shift amount based on the input information and setting the calculated phase shift amount to the phase shift means, respectively, by a notification from a communication partner station, etc. A signal strength detecting means for detecting the signal strength of the received signal received at the partner station is provided, and the phase shift amount controlling means is detected by the signal strength detecting means while a transmission signal is transmitted by the antenna element. First signal strength storage means for storing a first strength (P1) of the received signal, and a first signal strength storage means for storing a first signal strength of the received signal detected by the signal strength detection means in a state where the transmission signal is not transmitted by the antenna element. A second signal strength storage means for storing the strength (P2) of any one of the plurality of signal cutoff means;
One is set to the passing side, the signal selecting means for setting the rest to the blocking side, and the other of the plurality of signal blocking means is set to the passing side and the rest is set to the blocking side, and the second A phase shift amount calculating unit that calculates a phase shift amount that minimizes the difference (P1−P2) based on the first intensity (P1) and the second intensity (P2); A phase shift amount setting means for setting a phase shift amount calculated by the phase shift amount calculation means to one connected to the signal cutoff means set on the passing side by the signal selection means, I have.

In the above-described adaptive array antennas according to the third to sixth basic configurations, only the signal strength detected by the signal strength detecting means is used to take into account the phase shift deviation in the own station or the communication partner station. The amount of phase shift required to receive a signal in the same transmission can be obtained by simple processing.Therefore, it is necessary to set the amount of phase shift to compensate for the deviation of the phase shift for the conventional adaptive array antenna. There is also an advantage that an adaptive array antenna system can be realized with a simple circuit configuration and the processing time is shortened.

An adaptive array antenna according to a seventh basic configuration of the present invention comprises a plurality of antenna elements and a plurality of real numbers for weighting a reception signal received by the plurality of antenna elements by a set real number weight. Weighting means, a plurality of individual element signal strength detection means each detecting the strength of the received signal weighted by these plurality of real number weighting means as individual element signal strength,
Combining means for combining the received signals weighted by the plurality of real number weighting means; signal strength detecting means for detecting the strength of the received signal combined by the combining means as a combined signal strength; and A real number weight is calculated based on the change amount of the combined signal strength when the sign of the real number weight set to at least one is changed and the plurality of individual element signal strengths, and the calculated real number weight is converted to the plurality of real numbers. Real number weight control means for repeating processing set in the weighting means for a plurality of cycles.

The adaptive antenna according to the seventh basic configuration
In the Ray antenna, the real number weight control means includes:
A real number weight set in the plurality of real number weighting means
Initial values W_1 (0) to W_n (0) (where n is the antenna element
A plurality of initial value storage means for storing
When the gate control means operates for the first time, these W_1
(0) to W_n (0) are respectively assigned to a plurality of real number weighting means.
Real weights W_1 (k) to W_n (k) to be set in
(K is the number of real weight updates)
Real number weight storage means and a plurality of real number weight
Based on W_1 (k) to W_n (k) stored in the storage means
As a real weight of the plurality of real weighting means.
What is W_i (k) or -W_i (k) (1 ≦ i ≦ n)
A plurality of real number weight setting means for setting one of them
W_1 (k) to W_1 (k)
With the W_n (k) set, the combined signal strength detection is performed.
The combined signal strength Py (k) detected by the means is input.
Similarly, each of the plurality of real number weighting means
1 (k) to W_n (k) are set and the plurality of
Individual elements detected by the individual element signal strength detection means
The child signal strengths Px_1 (k) to Pxn (k) are input respectively.
W_1 is assigned to each of the plurality of real number weighting means.
(K), W_2 (k), ..., W_i-1 (k), W_i
(K), W_i + 1 (k),..., W_n (k) (1 ≦ i
≦ n) is set to the synthesized signal strength detection means.
Signal intensity Py_i (k) (1 ≦
i ≦ n), a new real weight
W_i (k + 1) = W_i (k) + a ^*[Px_i
(K) + {Py (k) -Py_i (k)} / 4] / W_
Calculate i (k) (a is a constant) and (1 ≦ i ≦ n)
And W_1 (k) to
W_n (k) and real weight calculating means
May be provided.

Further, in the adaptive array antenna according to the seventh basic configuration, the real number weight control means may include an update stop means for stopping its operation based on a predetermined condition. In the above configuration, the update stop means may stop the operation after repeating the operation of the real number weight control means a predetermined number of times. Further, in the above configuration, the update stop means may stop the operation of the real number weight control means when the spice of the real number weight set in the real number weighting means becomes a predetermined value or less. .

Further, in the adaptive array antenna according to the seventh basic configuration, each of the plurality of antenna elements may be a directional antenna. Further, in the adaptive array antenna according to the seventh basic configuration, each of the plurality of antenna elements may be an array antenna.

An adaptive array antenna according to an eighth basic configuration of the present invention is used in a radio communication system for service in an area by arranging a plurality of radio base stations for accommodating a terminal station. For each direction of the base station group other than the own base station or a part of the directions, null is applied to the remaining directions excluding those having a small difference from the direction of the terminal with which the own base station communicates. It is characterized in that the antenna beam is controlled by adding a constraining condition for pointing.

An adaptive array antenna according to a ninth basic configuration of the present invention includes a plurality of antenna elements and a high-frequency circuit connected to the antenna elements. As a local signal phase shift circuit that changes the phase of a signal for each high-frequency circuit for the antenna element, or a part thereof, using a quadrature modulator that inputs a local frequency signal and a control signal, the high-frequency circuit includes: It is characterized by having a coupler for branching a part of a signal from an antenna element and a quadrature demodulator for an individual element to which a signal from the coupler is inputted.

In the adaptive array antenna according to the ninth basic configuration of the present invention, a demodulated signal from the individual element quadrature demodulator is input, and the phase and amplitude of each input signal are compared to detect a difference between them. Phase and amplitude comparison circuit, and a difference detected based on a comparison result of the phase and amplitude comparison circuit, and a part of a signal from each antenna force element and a routing length of an antenna feed line and other wiring lengths. Phase deviation compensation control means for controlling an output signal of a phase control signal output circuit so as to compensate for a phase deviation caused by at least a difference in a passing phase characteristic of a component provided at a subsequent stage from the coupler, and at least the phase deviation compensation control A phase shift control signal output circuit for outputting a control signal to the quadrature modulator of the local signal phase shift circuit based on the output of the means.

An adaptive array antenna according to a tenth basic configuration of the present invention includes a plurality of antenna elements, a high-frequency circuit connected to each antenna element, and a high-frequency synthesis circuit for synthesizing outputs of the plurality of high-frequency circuits. And at least one first RSSI circuit for monitoring at least one signal level of RF or IF signals from a plurality of individual elements, and a signal of an RF or IF signal after combining signals from the individual elements. A second RSSI circuit for monitoring the level, at least (N-1) first variable gain circuit elements capable of varying the relative levels of all RF or IF signals of each of the N individual elements, and A second variable gain circuit element capable of varying the signal level of the Rf or IF signal after synthesizing the signals of
RSS from first and second RSSI circuits
Based on the I signal, the first variable gain circuit element and the second variable gain circuit element are controlled so that the combined output signal level is controlled to a fixed width and the high frequency circuit element for each individual element is not saturated. And a gain control circuit for controlling the gain circuit element.

In the adaptive array antenna according to the tenth basic configuration, a predetermined number of past output values of the RSSI circuit is stored, and a gain control circuit is provided only when a deviation from this value exceeds a certain value. May output a gain change command to the first variable gain circuit element or the second variable gain circuit element. The above R
SSI stands for Receive Signal Strength
Indication), which is a numerical value of the strength of the received radio signal.

An adaptive array antenna according to an eleventh basic configuration of the present invention includes a plurality of antenna elements, a high-frequency circuit connected to the antenna elements, and a high-frequency distribution circuit for distributing an output to the plurality of high-frequency circuits. A weight control circuit for weighting the amplitude or phase of each antenna element in the high-frequency circuit, wherein a signal level of a radio frequency signal (RF) or an intermediate frequency signal (IF) before distribution to individual elements is adjusted. A second variable gain circuit element to be variable, and all radio frequency signals (RF) or intermediate frequency signals (I
F) at least (N-1) first variable gain circuit elements that make the relative level variable, and effective radiation taking into account the directivity gain from the adaptive array antenna estimated from the output of the weight control circuit A gain control circuit for controlling the power so as not to exceed a predetermined value and controlling the first variable gain circuit element and the second variable gain circuit element so that the high-frequency circuit element for each individual element is not saturated; , Is provided.

[0038] DETAILED DESCRIPTION OF THE PREFERRED
EMBODIMENTS Hereinafter, a preferred embodiment of an adaptive array antenna according to the present invention will be described in detail with reference to the accompanying drawings. Before starting the description of a specific embodiment, the basic concept of the present invention will be described with reference to FIG. FIG. 1 illustrates the basic principle of an adaptive array antenna as a general concept of the first embodiment and the second embodiment.

In FIG. 1, the adaptive array antenna includes first to n-th antenna elements 111 to 11
n and first to n-th phase shifters 121 to 12n for controlling the phases of the received signals received by the antenna elements 111 to 11n in accordance with the set phase shift amounts.
Synthesizing means 130 for synthesizing the received signals phase-controlled by the phase shifting means 121 to 12n; signal intensity detecting means 150 for detecting the intensity of the received signal synthesized by the synthesizing means 130; A phase shift amount control means for calculating a phase shift amount based on the intensity of the received signal detected by the detection means, and setting the calculated phase shift amount in each of the phase shift means. The output of the combining means 130 is normally demodulated by a demodulator 140.

The phase shift amount control means 160 determines a plurality of phase shift amounts in the plurality of phase shift means 121 to 12n based on various signal intensities output from the signal strength detection means 150 and a plurality of phase shift amounts. A phase shift amount calculating means 161 for calculating and outputting a cycle;
And an initial value storage means 162 for storing the initial values of the phase shift amount calculating means 161 based on the respective initial values stored in the initial value storage means 162. And a first phase shift amount storing means 163 for storing a first phase shift amount calculated as one to be set for each of the second to 12n, and increasing the first phase shift amount by a predetermined angle X. Second phase shift amount storage means 164 for storing a second phase shift amount in the plurality of phase shift means calculated by the calculation means 161
And a third phase shift amount storage for storing a third phase shift amount in the plurality of phase shift means calculated by the calculation means so as to reduce the first phase shift amount by a predetermined angle X. Means 165.

The phase amount control means 160 further includes the first to third phase shift amount storage means 163 to 165.
A first to n-th phase shift amount setting for setting the phase shift amounts of the plurality of phase shift units calculated by the phase shift amount calculation unit 161 based on the phase shift amounts stored in any one of the above. Means 1661 to 166n and said plurality of phase shifting means 1
The first signal strength storage means 167 for storing the first signal strength detected by the signal strength detection means 150 in a state where the second phase shift amount is set in 661 to 166n.
A second signal strength storage means 168 for storing a second signal strength detected by the signal strength detection means in a state where the third phase shift amount is set in the plurality of phase shift means;
It has.

When the difference between the first signal strength and the second signal strength is input, the phase shift amount calculating means 161 increases the first phase shift amount by a value proportional to the difference. The new phase shift amount is calculated and input to the first phase shift amount, and the calculation for a plurality of cycles is repeated until the difference disappears. Further, the adaptive array antenna includes an update stop unit 170 that stops the operation of the phase shift amount control unit 160 based on a predetermined condition.

The signal strength detecting means 150 may be configured to detect the signal strength of the received signal as it is. However, a reference signal generating means 151 as shown by a broken line in FIG. The signal strength of the error signal output from the subtractor 152 for detecting the error may be detected. In this case, the details will be described in the second embodiment, but the first and second signal strength storage means 167 and 168 function as error signal strength detection means, respectively.

This basic principle is a summary of the highest concept of the present invention, and is a superordinate concept of the following first to tenth embodiments. The adaptive array antenna according to the first and second embodiments can be considered. Details will be described below.

(First Embodiment) FIG. 2 is a configuration diagram of an adaptive array antenna according to a first embodiment of the present invention. 2, 11 to 1n are antenna elements, 21 to
Reference numerals 2n denote amplifiers for amplifying the received signals received by the antenna elements 11 to 1n, and 41 to 4n denote phases of the amplified received signals in accordance with phase shift amounts respectively set by phase shift amount control means 3 described later. A variable phase shifter for controlling, 5 is a synthesizer for synthesizing the phase-controlled received signals, 6 is a demodulator for demodulating the synthesized received signal, and 71 is an intensity of the received signal synthesized by the synthesizer 5. Is calculated based on the detected received signal strength, and the calculated phase shift amounts are set in the variable phase shifters 41 to 4n, respectively. The phase shift amount control means 8 is an update stop means for stopping the operation after repeating the operation of the phase shift amount control means 3 a predetermined number of times.

341 to 34n store the phase shift amounts Φ1 (k) to Φn (k) (n is the number of antenna elements and k is the number of updates of the phase shift amounts) set in the variable phase shifters 41 to 4n, respectively. The first phase shift amount storage means 351 to 35n store the phase shift amounts Φ1 ′ (k) to Φn ′ (k) obtained by increasing the stored phase amounts Φ1 (k) to Φn (k) by 90 degrees. Calculated and stored second phase shift amount storage means 361-36n are the phase shift amount Φ stored by the first phase shift amount storage means 341-34n.
A phase shift amount Φ1 ″ (k) to Φn ″ (k) in which 1 (k) to Φn (k) are respectively reduced by 90 degrees is calculated and stored.
371-37n are the first phase shift amount storage means 341-34n, the second phase shift amount storage means 351-35n, or the third phase shift amount storage means 361-3
6n for setting the phase shift amounts stored in any one of the variable phase shifters 41 to 4n, respectively. The phase shift amount setting means 311 sets the variable phase shifters 41 to 4n to Φ1 (k) and Φ2 (k), respectively. ),…, Φ
i−1 (k), Φi ′ (k), Φi + 1 (k),.
In the state where n (k) (1 ≦ i ≦ n) is set, first signal strength storage means for storing the received signal strength Pi ′ detected by the signal strength detection means 71, and 321 is a variable phase shifter Φ1 (k), Φ2 (k),..., Φi−
1 (k), Φi "(k), Φi + 1 (k), ..., Φn
In the state where (k) is set, the second signal strength storage means 331 for storing the strength Pi "of the received signal detected by the signal strength detection means 71 is proportional to the difference between Pi 'and Pi". A new phase shift amount Φi (k + 1) obtained by increasing Φi (k) stored in the ith phase shift amount storage means by the value is calculated, and a phase shift amount to be input to the ith phase shift amount storage means is calculated. Calculation means, 381 to 38n are initial values Φ1 (0) to Φn of the phase shift amount
(0) are stored, and when the phase shift amount control means 3 operates for the first time, those Φ1 (0) to Φn (0) are stored in the first phase shift amount storage means 341 to 34n, respectively. Φn
(K) is an initial value storage means.

The operation of the adaptive array antenna configured as described above will be described. FIG. 3 is a flowchart showing the operation of the adaptive array antenna. First,
Phase shift amount Φ1 stored by initial value storage means 381
(0) is input to the first phase shift amount storage unit 341. Based on this, Φ1 (0) is stored by the phase shift amount storage means 341.
Is stored in Φ1 (k) as follows (step S
1).

Φ ₁ (k) = Φ ₁ (0) Subsequently, the phase shift amount Φ ₁ (k) stored by the first phase shift amount storage unit 341 is input to the second phase shift amount storage unit 351. You. Based on this, the second phase shift amount storage unit 341
Φ1 ′ (k) is obtained as follows (step S2).

Φ ₁ ′ (k) = Φ ₁ (k) +90 Subsequently, the phase shift amount Φ ₁ (k) stored by the first phase shift amount storage unit 341 is stored in the third phase shift amount storage unit 361. Is entered. Based on this, the third phase shift amount storage means 361
Φ1 ″ (k) is obtained as follows (step S3).

Φ ₁ ″ (k) = Φ ₁ (k) −90 S2 to S3 may be processed in the order of S3 → S2.
Subsequently, the phase shift amount Φ1 (k) stored by the first phase shift amount storage unit 341 is input to the phase shift amount setting unit 371. This phase shift amount is set in the variable phase shifter 41 by the phase shift amount setting means 371 (step S4). Subsequently, the phase shift amount Φ2 stored by the initial value storage units 382 to 38n
Similarly, (0) to Φn (0) are set in the variable phase shifters 42 to 4n by the phase shift amount setting means 372 to 37n.

Initial values of the phase shift amounts Φ1 (0) to Φn (0)
May be set to, for example, a phase shift amount for in-phase synthesis of a desired wave. Next, in step S5, it is determined whether or not i is equal to or more than n. If i is not equal to or more than n, steps S1 to S4 are performed.
Is repeated, and if i is equal to or more than n, step S6
Is set to k = 1.

At time t, the received signals received by the antenna elements 11 to 1n and amplified by the amplifiers 21 to 2n are denoted by S1 (t) to Sn (t). These signals are phase-controlled by the variable phase shifters 41 to 4n, and are synthesized by the synthesizer 5. Assuming that the phase shift amounts set in the variable phase shifters 41 to 4n are Φ1 (k) to Φn (k), the combined received signal y (t) is

(Equation 1) It is expressed as The combined received signal y (t) is input to the signal strength detecting means 71. Based on this, the strength P of the received signal detected by the signal strength detection means 71 is

(Equation 2) It is expressed as Here, E [•]: expected value operation, *: complex conjugate. The expected value calculation is actually replaced by the time average calculation. This can be obtained by setting the time constant of the signal strength detecting means 71 to a sufficiently large value.

This embodiment is characterized in that the signal strength detecting means 7
1, the partial differential coefficient of the signal strength of the received signal detected by the signal strength detection means 71 with respect to the phase shift amount set in each of the variable phase shifters 41 to 4n. It can be obtained by using The phase shift amount control is performed based on this partial differential coefficient.
The phase shift amounts set in the variable phase shifters 41 to 4n are calculated by the phase shift amount control means 3 one by one. Here, a method of updating the phase shift amount of the variable phase shifter 41 will be described.

The phase shift amount Φ′1 (t) stored by the second phase shift amount storage unit 351 is input to the phase shift amount setting unit 371. This phase shift amount is set in the variable phase shifter 41 by the phase shift amount setting means 371 (step S8). In this state, the received signal strength P1 'detected by the signal strength detection means 71 is input to the first signal strength storage means 311 (step S9). Subsequently, the phase shift amount Φ ″ 1 (t) stored by the third phase shift amount storage unit 361 is input to the phase shift amount setting unit 371. The phase shift amount is variable by the phase shift amount setting unit 371. Set to phase shifter 41 (step S
10). In this setting state, the received signal strength P1 "detected by the signal strength detection means 71 is input to the second signal strength storage means 321 (step S11).
S11 may be processed in the order of S10 → S11 → S8 → S9.

Subsequently, the received signal strength P 1 ′ stored in the first signal strength storage means 311, the received signal strength P 1 stored in the second signal strength storage means 321, and the first
Phase shift amount Φ1 stored by the phase shift amount storage means 341
(K) is input to the phase shift amount calculating means 331. Based on these inputs, a new phase shift amount Φ1 (k + 1) is calculated by the phase shift amount calculating means 331 as follows (step S).
12).

Φ ₁ (k + 1) = Φ ₁ (k) + α (P ₁ ′ −P ₁ ″) where α is a real number.

Subsequently, the new phase shift amount Φ1 (k + 1) calculated by the phase shift amount calculating means 331 is input to the first phase shift amount storing means 341. Based on this, the first phase shift amount storage means 341 converts Φ1 (k + 1) into Φ1
(K) (step S13).

Φ ₁ (k) = Φ ₁ (k + 1) Subsequently, the phase shift amount Φ ₁ (k) stored by the first phase shift amount storage unit 341 is input to the second phase shift amount storage unit 351. You. Based on this, the second phase shift amount storage unit 351
Φ1 ′ (k) is obtained as follows (step S14).

Φ ₁ ′ (k) = Φ ₁ (k) +90 Subsequently, the phase shift amount Φ ₁ (k) stored by the first phase shift amount storage unit 341 is stored in the third phase shift amount storage unit 361. Is entered. Based on this, the third phase shift amount storage means 361
Φ1 ″ (k) is obtained as follows (step S15).

Φ ₁ ″ (k) = Φ ₁ (k) −90 S 14 to S 15 may be processed in the order of S 15 → S 14. Subsequently, the shift stored by the first phase shift amount storage means 341. The phase amount Φ1 (k) is input to the phase shift amount setting means 371. The phase shift amount is set in the variable phase shifter 41 by the phase shift amount setting means 371 (step S16).

Subsequently, the same procedure is used to update the phase shift amounts of the variable phase shifters 42 to 4n. After the above operation of updating the phase shift amounts of the variable phase shifters 41 to 4n by the phase shift amount control means 3 is repeated K times, the operation is stopped by the update stop means 8 (steps S17 to S18). In the present invention, during the operation of updating the phase shift amount, the phase shift amount largely fluctuates, so that the intensity of the received signal input to the demodulator 6 also fluctuates greatly, making demodulation processing difficult. Therefore, it is necessary to stop after repeating the operation of updating the phase shift amount a predetermined number of times.

Therefore, it is determined in step S17 whether or not i is equal to or greater than n. If i is equal to or greater than n, it is determined in step S18 whether or not k is equal to or less than K. If it is less than or equal to one, the numerical value is incremented by one and the processing of steps S7 to S17 is repeated. If k is not less than K, the processing is stopped.

In this case, the operation is stopped by counting the number of repetitions of the phase shift amount update.
It is also conceivable to stop the operation when i′−Pi ″ becomes equal to or less than a predetermined value.

(Equation 3) It is expressed as Where i is an integer satisfying 0 ≦ i ≦ n, Im
｛｝: Imaginary part. On the other hand, the partial differential δP /
δΦi is

(Equation 4) It is expressed as From the above, δP / δΦi = (Pi′−P
i ″) / 2 holds. Therefore, the processing in step S12 is

(Equation 5) This means that the equivalent processing is performed.

When the real number α is a negative value, the phase shift amounts of the variable phase shifters 41 to 4n are updated so as to reduce the output signal strength of the adaptive array antenna, and finally δP / δ
Since the phase shift amount at which Φi = 0 is set, when only an interference wave exists, it can be suppressed. When such a phase shift amount control is applied to, for example, an adaptive array antenna for reception of a base station, the phase shift amount of the variable phase shifter is controlled before a communication channel is given to a terminal station that has requested communication. Then, the amount of phase shift for suppressing co-channel interference is calculated, and thereafter, the communication channel is provided to the terminal station, and the amount of phase shift for suppressing the co-channel interference is set in the variable phase shifters 41 to 4n. A method of receiving a signal transmitted by the terminal station may be considered.

When the desired wave and the interference wave exist simultaneously,
By fixing the amount of phase shift of one or more variable phase shifters to an initial value, suppression of a desired wave can be avoided.

On the other hand, when the real number α is a positive value, the phase shift amounts of the variable phase shifters 41 to 4n are set so as to increase the output signal strength of the adaptive array antenna. Can be synthesized in-phase. When such phase shift amount control is applied to, for example, an adaptive array antenna for reception of a base station, when there is no co-channel interference, a signal is transmitted to one terminal station, and the phase shift amount of the variable phase shifter is set. To calculate the amount of phase shift for in-phase synthesis, and then, when the terminal station performs communication,
It is conceivable that the amount of phase shift for the in-phase synthesis is set in the variable phase shifters 41 to 4n to receive a signal transmitted by the terminal station.

In this embodiment, the case where the phase shift amount is increased or decreased by 90 degrees has been described. However, the same effect can be obtained when the phase shift amount is increased or decreased by X degrees.

Pi′-P when the phase shift amount is increased or decreased by X degrees
i ”

(Equation 6) It is expressed as

From this, δP / δΦi = (Pi′−P
i ") / (2 sin (X)). Therefore, the processing in step S9 is as follows.

(Equation 7) This means that the equivalent processing is performed.

In particular, when X is 90 degrees, the difference between Pi ′ and Pi ″ becomes maximum, so that δP / δΦi can be obtained with high accuracy.
Can be requested.

As described above, according to the first embodiment of the present invention, the phase shift amount of the intensity of the reception signal synthesized by the synthesizer 5 using only the signal intensity detected by the signal intensity detection means 71 Since the phase shift amount control based on the partial differential coefficient with respect to can be performed, it can be realized with a simple circuit configuration as compared with the case where a signal is used for each antenna element as in the related art.

(Second Embodiment) Next, a second embodiment of the present invention will be described. FIG. 4 is a configuration diagram of the adaptive array antenna according to the second embodiment of the present invention. The difference from the first embodiment is that reference signal generation means, error detection means, error signal strength detection means, first error signal strength storage means, second error signal strength storage means, and phase shift amount calculation means are used. On the point.

In FIG. 4, reference numeral 91 denotes a reference signal generating means for generating a reference signal, and 92 denotes an error detection for outputting a difference between the received signal synthesized by the synthesizer 5 and the reference signal generated by the reference signal generating means 91. Means 72, an error signal strength detecting means for detecting the strength of the output error signal;
Numeral 12 designates Φ1 (k) and Φ2 as variable phase shifters 41 to 4n, respectively.
(K), ..., Φi-1 (k), Φi '(k), Φi + 1
(K),..., Φn (k) (1 <= i <= n) is set, and the first error signal strength that stores the strength Qi ′ of the received signal detected by the error strength detection means 72 The storage means 322 supplies the variable phase shifters 41 to 4n with Φ1 (k),
Φ2 (k),..., Φi-1 (k), Φi ″ (k), Φi
+1 (k),..., Φn (k) are set, and the strength P of the received signal detected by the signal strength detection means 72 is set.
The second signal strength storage means 332 for storing i ″ increases Φi (k) stored in the first phase shift amount storage means i by a value proportional to the difference between Qi ′ and Qi ″. Is a phase shift amount calculating means for calculating the new phase shift amount Φi (k + 1) and inputting the calculated new phase shift amount to the first phase shift amount storing means i. Other configurations are the same as those in FIG.

The operation of the adaptive array antenna configured as described above will be described in more detail. FIG.
9 is a flowchart showing the operation of the adaptive array antenna.

First, steps S1 to S7 are performed in the same procedure as in the first embodiment. At time t, the antenna element 1
The received signals received by the amplifiers 1 to 1n and amplified by the amplifiers 21 to 2n are referred to as S1 (t) to Sn (t). These signals are controlled in phase by the variable phase shifters 41 to 4n,
The signals are synthesized by the synthesizer 5. On the other hand, reference signal generating means 9
Let the reference signal generated by 1 be D (t). The difference between the received signal synthesized by the synthesizer 5 and the reference signal generated by the reference signal generation means 91 is output by the error detection means 92. The error detecting means 92 includes, for example, a 180-degree phase shift circuit 921 that shifts the phase of the reference signal by 180 degrees and a synthesis circuit 922 that synthesizes the 180-degree phase-shifted reference signal and the received signal, as shown in FIG. , Is constituted. The phase shift amount set in the variable phase shifters 41 to 4n is Φ1
Assuming that (k) to Φn (k) (n is the number of antenna elements and k is the number of updates of the phase shift amount), the error signal E (t) output from the error detecting means 92 is

(Equation 8) It is expressed as The output error signal E (t) is input to the error signal strength detection means 72. Based on this, the strength Q of the error signal detected by the error signal strength detection means 72 is

(Equation 9) It is expressed as

The feature of the second embodiment is that the partial differential coefficient of the signal strength of the error signal detected by the error signal strength detecting means 72 with respect to the phase shift amount set in each of the variable phase shifters 41 to 4n is calculated. This can be obtained by using only the signal strength of the error signal detected by the error signal strength detection means 72. The phase shift amount control is performed based on this partial differential coefficient. The amount of phase shift set in the variable phase shifters 41 to 4n is 1
It is calculated by the phase shift amount control means 3 on an individual basis. here,
A method of updating the phase shift amount of the variable phase shifter 41 will be described.

Step S8 is performed in the same procedure as in the first embodiment. In this setting state, the error signal strength detection means 7
2 is input to the first error signal strength storage means 312 (step S10).
1). Subsequently, the phase shift amount Φ ″ 1 (t) stored in the third phase shift amount storage unit 361 is input to the phase shift amount setting main unit 371. The phase shift amount is set by the phase shift amount setting unit 371. (Step S102) In this setting, the error signal strength Q1 "detected by the error signal strength detection means 72 is stored in the second error signal strength storage means 32.
2 (step S103).

Subsequently, the first error signal strength storage means 31
2, the error signal strength Q1 ″ stored in the second error signal strength storage means 322, and the phase shift amount Φ1 stored in the first phase shift amount storage means 341.
(K) is input to the phase shift amount calculating means 332. Based on these inputs, a new phase shift amount Φ1 (k + 1) is calculated by the phase shift amount calculating means 332 as follows (step S104).

[0079]

(Equation 10) Here, α is a real number.

Subsequently, steps S13 to S16 are performed in the same procedure as in the first embodiment. Subsequently, the variable phase shifter 42
The same procedure is used for updating the phase shift amounts of .about.4n. Subsequently, step S18 is performed in the same procedure as in the first embodiment.

Qi'-Qi "is

[Equation 11] It is expressed as

On the other hand, the partial differential δQ / δΦi of Q by Φi
Is

(Equation 12) It is expressed as

From the above, δQ / δΦi = (Qi′−Q
i ″) / 2 holds, so step S104
The processing of

(Equation 13) This means that the equivalent processing is performed.

When the real number α is a negative value, the phase shift amounts of the variable phase shifters 41 to 4n are updated so as to reduce the error between the output of the adaptive array antenna and the reference signal, and finally δQ / δΦi Since the phase shift amount that satisfies = 0 is set, when the desired wave and the interference wave exist, the interference wave can be suppressed. When such a phase shift amount control is applied to, for example, an adaptive array antenna for reception of a base station,
The terminal station transmits a known signal before starting communication, and the base station uses the same signal as the known signal as a reference signal to control the amount of phase shift of the variable phase shifter to reduce co-channel interference. After calculating the amount of phase shift to be suppressed, the terminal station starts communication, and the base station sets the amount of phase shift to suppress the co-channel interference in the variable phase shifters 41 to 4n, and A method of receiving a signal to be transmitted can be considered.

In the present embodiment, the case where the phase shift amount is increased or decreased by 90 degrees has been described. However, the same effect can be obtained when the phase shift amount is increased or decreased by X degrees.

Qi'-Q when the phase shift amount is increased or decreased by X degrees
i ”

[Equation 14] It is expressed as

Thus, δQ / δΦi = (Qi′−Q
i ") / (2 sin (X)). Therefore, the processing in step S9 is as follows.

(Equation 15) This means that the equivalent processing is performed.

In particular, when X is 90 degrees, the difference between Qi 'and Qi "becomes maximum, so that δQ / δΦi
Can be requested.

As described above, according to the second embodiment of the present invention, in an adaptive array antenna that minimizes the strength of the difference between a received signal and a reference signal synthesized by a synthesizer as an evaluation function, Since the partial differential coefficient of the evaluation function required for performing the phase amount control can be obtained by using only the signal strength detected by the error signal strength detecting means 72, the signal for each antenna element as in the related art is obtained. Can be realized with a simple circuit configuration as compared with the case of using.

(Third Embodiment) FIG. 7 is a configuration diagram of an adaptive array antenna according to a third embodiment of the present invention. 7, 11 to 1n are antenna elements, 71
1 to 71n are signal blocking means for passing or blocking a received signal received by the antenna element to a subsequent circuit in accordance with a control signal input by a signal selecting means 75 described later, and 21 to 2n are those signal blocking means. Amplifiers 41 to 4n for amplifying the received signals that have passed therethrough are variable phase shifters for controlling the phases of the amplified received signals in accordance with the phase shift amounts respectively set by phase shift amount control means 3 described later. A synthesizer for synthesizing the phase-controlled received signals; 6 a demodulator for demodulating the synthesized received signal; 7 a signal intensity detecting means for detecting the intensity of the received signal synthesized by the synthesizer 5; Is a phase shift amount control means for calculating a phase shift amount based on the detected intensity of the received signal and setting the calculated phase shift amounts to the variable phase shifters 41 to 4n.

The signal blocking means 711 to 71n are, for example,
It is conceivable to use the power switches of the amplifiers 21 to 2n. 75 is a signal selecting means for setting any two of the signal blocking means 1101 to 110n on the passing side, and setting the remaining to the blocking side, and 331 is a signal selecting means for setting any two of the signal blocking means 711 to 71n to the passing side. A phase shift amount calculating means for calculating a phase shift amount that minimizes the P based on the strength P of the received signal detected by the signal strength detection means 7 in a state where the others are set to the cutoff side; 37n is a variable phase shifter i connected to the signal blocking means i (1 ≦ i ≦ n) set on the passing side by the signal selecting means 75 among the variable phase shifters 41 to 4n. Means for setting the amount of phase shift.

The operation of the above-configured adaptive array antenna according to the third embodiment will be described. FIG.
9 is a flowchart showing the operation of the adaptive array antenna.

When a new terminal station starts operation, or when an existing terminal station resumes operation for the first time after changing its position, the terminal station transmits a first control signal to the base station. When the communication channel is free, the base station performs subsequent transmission and reception using the second control signal.
One or more communication channels are specified, and the terminal station performs transmission with a constant transmission power on the communication channel specified by the base station (steps S1001 to S100).
4).

Subsequently, the first signal blocking means 711 is set to the passing side and the second to nth signal blocking means 712 to 71n are set to the blocking side by the signal selecting means 75 (step S10).
05).

The feature of the third embodiment is that the reception signal phase-controlled by the second to n-th variable phase shifters 42 to 4n based on the signal strength of the reception signal detected by the signal strength detection means 7 Has an opposite phase relationship with the phase of the received signal phase-controlled by the first variable phase shifter 41, that is, the variable phase shifters 2 to n (1042 to 104).
The point is that the phase shift amount is controlled so that the phases of the received signals subjected to the phase control according to n) become the same. Variable phase shifters 2 to n
The phase shift amounts set in (1042 to 104n) are calculated by the phase shift amount control unit 1003 one by one. Here, a method of setting the phase shift amount of the variable phase shifter 2 (1042) will be described.

The second signal blocking means 712 is set on the passing side by the signal selecting means 75, and the fact that the second signal blocking means 712 is set on the passing side is notified to the phase shift amount calculating means 331 (step S).
1006). In this state, the strength P of the received signal detected by the signal strength detecting means 7 is input to the phase shift amount calculating means 331 (step S1007). Based on this, the phase shift amount Φ for minimizing the intensity P is calculated by the phase shift amount calculating means 331.
2 is calculated (step S1008).

A method for minimizing the signal strength P is, for example, as follows.
The method described with reference to FIG. 3 and the method of sequentially setting the phase shift amount and determining the phase shift amount that minimizes the signal intensity P are conceivable. FIG. 9 shows a change in the intensity P when the phase shift amount is sequentially set, in dB. As shown in FIG. 9, since the minimum point of the reception intensity has a sharp characteristic, the phase shift amount can be determined with high accuracy.

Subsequently, based on the notification from the signal selection unit 75, the phase shift amount Φ2 calculated by the phase shift amount calculation unit 331 is input to the phase shift amount setting unit 372. This phase shift amount Φ2 is converted into the second variable phase shifter 4 by the phase shift amount setting means 372.
It is set to 2 (step S1009). Subsequently, the second signal cutoff means 712 is set to the cutoff side by the signal selection means 75 (step S1010). Subsequently, the same procedure is used for setting the phase shift amounts of the third to n-th variable phase shifters 43 to 4n.

By the above processing, the phase of the received signal whose phase is controlled by each of the second to n-th variable phase shifters 42 to 4n is changed to the phase of the received signal whose phase is controlled by the first variable phase shifter 41. The phase and the phase are opposite. Subsequently, the first signal cutoff means 711 is turned off by the signal selection means 75,
The second to n-th signal blocking means 712 to 71n are set to the passing side (step S1011).

By the above processing, the variable phase shifters 2 to n (1
042 to 104n), the phases of the received signals subjected to the phase control become the same, and the signals transmitted by the terminals can be combined in phase by the combiner 5. For example, if the calculated phase shift amount is stored, it can be used for resuming a call after once terminating the call. The effects of the third embodiment of the present invention described above are summarized as follows.

Based on the signal strength of the received signal detected by the signal strength detecting means 7, the phase shift amount for in-phase combining and receiving the signal transmitted by the terminal station can be obtained by simple processing. Therefore, there is an advantage that it can be realized with a simple circuit configuration and the processing time is short. This is particularly effective when a real-time process is required in a high-speed transmission wireless communication system.

Even if there is a deviation of a device connected to each antenna element, an arrangement error of an antenna element, or a deviation of a phase due to multipath propagation or the like, a shift for in-phase synthesis and reception taking this into account. It is possible to obtain the phase amount, and it is not necessary to set the phase shift amount so as to compensate for the phase deviation unlike the conventional beam steering method, and the compensation by the deviation measurement can be omitted or simplified. it can.

The optimal phase shift amount once stored is, in particular, WL
When the base station and the terminal station are spatially fixed as in the L (Wireless Local Loop) system, the radio wave propagation environment is almost fixed in time, so that the radio wave can be reused and used for communication. Control can be simplified.

(Fourth Embodiment) Next, an adaptive array antenna according to a fourth embodiment of the present invention will be described. Since the configuration of the adaptive array antenna according to the fourth embodiment of the present invention is similar to the configuration of the third embodiment,
The hardware configuration will be described according to the configuration of FIG.

The difference from the third embodiment is that a new phase shift amount is set in the first variable phase shifter 41 after step S1011 in FIG. 8 showing the processing operation of the third embodiment.
The point is that the received signal received by the first antenna element 11 is also used when the optimum phase shift amount to be set is determined and the signals transmitted by the terminal stations are combined in phase.

The operation of the fourth embodiment will be described in more detail. FIG. 10 is a flowchart showing the operation of the adaptive array antenna.

Steps S1001 to S10 shown in FIG.
11 is performed in the same procedure as in the third embodiment. Subsequently, the phase shift amount Φ1 currently set in the first variable phase shifter 41 is set to 1
First phase shift setting means 3 sets the phase shift increased by 80 degrees
The first variable phase shifter 41 is set by 71 (step S1101). Subsequently, the first signal blocking unit 711 is set to the passing side by the signal selecting unit 75 (step S1).
102).

By the above processing, the phases of the received signals whose phases are controlled by the second to n-th variable phase shifters 42 to 4n become the same, and the signals transmitted from the terminal stations are combined in phase by the combiner 5. Can be.

As described above, according to the fourth embodiment of the present invention, when the signals transmitted by the terminal stations are combined in phase, the first
By using the received signal received by the antenna element 11 described above, the directivity gain for the terminal station can be increased.

(Fifth Embodiment) Next, a fifth embodiment of the present invention will be described. FIG. 11 is a configuration diagram of the adaptive array antenna according to the fifth embodiment of the present invention.

The fifth embodiment differs from the third embodiment in the configuration using a variable gain circuit and gain control means. In FIG. 11, reference numerals 1101 to 110n denote variable phase shifters 41 to 4 according to a control signal input from the outside.
n to amplify the received signals whose phases are controlled by n and input the amplified received signals to the combiner 5 in the first to n-th stages.
The variable gain circuit 110 is configured such that, based on the strength of the reception signal detected by the signal strength detection means 7, the strengths of the reception signals amplified by the first to n-th variable gain circuits 1101 to 110n become equal. Variable gain circuit 110
This is gain control means for setting gains of 1 to 110n. Other configurations are the same as those in FIG. 7 showing the configuration of the third embodiment.

The operation of the adaptive array antenna configured as described above will be described in more detail. FIG.
2 is a flowchart showing the operation of the adaptive array antenna.

First, steps S1001 to S1001 shown in FIG.
The operation of S1004 is performed in the same procedure as in the third embodiment. Next, the first to n-th signal blocking means 711 to 71n are set to the blocking side by the signal selecting means 75 (step S1201).

The fifth embodiment is characterized in that, based on the signal strength of the received signal detected by the signal strength detecting means 7,
The point is that the gains of the variable gain circuits 1101 to 110n are controlled so that the received signals amplified by the first to nth variable gain circuits 1101 to 110n have the same intensity. First to n-th variable gain circuits 1101 to 110
The gain set to n is set by the gain control means 110 one by one. Here, the first variable gain circuit 1101
A method for setting the gain of the first embodiment will be described.

The first signal cutoff means 711 is set to the pass side by the signal selection means 75, and this is set to the gain control means 110.
(Step S1202). In this state, the strength Q of the received signal detected by the signal strength detection means 1007 is input to the gain control means 110 (step S12).
03). Based on this, the first variable gain circuit 110 controls the gain of the first variable gain circuit 110 so that the intensity of the received signal amplified by the first variable gain circuit 1101 becomes a specified value.
A gain of 1 is set (step S1204). continue,
The first signal cutoff means 711 is set to the cutoff side by the signal selection means 75 (step S1205). Then, the second
The gain setting of the n-th variable gain circuits 1102 to 110n is performed in the same procedure.

Subsequently, step S1005 shown in FIG.
Steps S1011 to S1011 are performed in the same procedure as in the third embodiment.

In the third embodiment, the description has been made on the assumption that the signal strength of the received signal received by each antenna element is the same. However, the reflection of the signal transmitted by the terminal station,
It is also conceivable that the signal strength of the received signal received by each antenna element differs due to the influence of the deviation of the amplifier connected to each antenna element. In this case, as shown in FIG. 13, the signal strength of the received signal shown in FIG. 9 has no sharp characteristic at the minimum point, and highly accurate phase matching between the antenna elements cannot be performed.

On the other hand, in the fifth embodiment, even if the signal strengths of the received signals received by the respective antenna elements are different, the first to n-th signals are required before the operation for determining the optimum phase shift amount. The gain control of the variable gain circuits 1101 to 110n is performed so that the intensities of the received signals respectively amplified by the variable gain circuits 1101 to 110n become equal. Therefore, the minimum point of the signal strength of the received signal is again as shown in FIG. It has sharp characteristics, and highly accurate phase matching can be performed between antenna elements.

Note that signal strength measuring means is provided after each of the variable gain circuits 1101 to 110n.
A method is also conceivable in which the intensities of the received signals respectively amplified by 1 to 110n are measured.

(Sixth Embodiment) Next, a sixth embodiment of the present invention will be described. FIG. 14 is a configuration diagram of the adaptive array antenna according to the sixth embodiment of the present invention.

The sixth embodiment differs from the third embodiment in the configuration using the first signal strength storage means, the second signal strength storage means, and the phase shift amount calculation means. In FIG. 14, a phase shift amount control means 3 stores a first signal strength storage means 141 for storing a first strength P1 of a received signal detected by a signal strength detection means 7 in a state where a desired wave and an interference wave are present.
A second signal strength storage means 142 for storing a second strength P2 of the received signal detected by the signal strength detection means 7 in a state where only the interference wave exists;
71n are set on the passing side and the rest are set on the blocking side, and the first intensity P1 and the second intensity P2 are set.
And a phase shift amount calculating unit 331 that calculates a phase shift amount that minimizes the difference “P1−P2” based on. The other configuration is the same as that of FIG.

The operation of the adaptive array antenna configured as described above will be described in more detail. FIG.
5 is a flowchart showing the operation of the adaptive array antenna. A method for setting the phase shift amount of the second variable phase shifter 42 will be described with reference to FIG. First, steps S1001 to S1006 shown in FIG. 8 are performed in the same procedure as in the third embodiment. Next, the first strength P1 of the received signal detected by the signal strength detection means 7 is input to the first signal strength storage means 141 (step S130).
1). Subsequently, the base station instructs a desired terminal station to suspend transmission for a certain period, and the terminal station suspends transmission for a certain period according to the instruction (step S1302).
1303). In this state, the received signal strength P2 detected by the signal strength detection means 7 is input to the second signal strength storage means 142 (step S1304). Based on this, the first intensity and the second intensity are calculated by the phase shift amount calculating means 331.
Is calculated (Step S1305). Subsequently, steps S1009 to S1011 shown in FIG. 8 are performed in the same procedure as in the third embodiment.

In the third embodiment, when calculating the amount of phase shift, it is assumed that the signal strength detection means 7 detects only the reception strength of a signal transmitted from a desired terminal station. Therefore, if other terminal stations are transmitting at the same time,
The signal strength of the received signal detected by the signal strength detecting means 7 is obtained by adding the received strength of a signal transmitted by another terminal station to the received strength of a signal transmitted by a desired terminal station.
In this case, highly accurate phase matching between the antenna elements cannot be performed.

On the other hand, in the sixth embodiment, even if there is a signal transmitted by another terminal station, the reception intensity of the signal transmitted by another terminal station is detected when calculating the amount of phase shift. However, since the influence is removed, highly accurate phase matching can be performed between the antenna elements.

(Seventh Embodiment) FIG. 16 is a configuration diagram of an adaptive array antenna according to a seventh embodiment of the present invention used for transmission. In FIG. 16, the antenna system is set by a transmitter 161, a distributor 162 for distributing the transmission signal transmitted by the transmitter 161, and the distributed transmission signal set by the phase shift amount control means 3 described later. Variable phase shifter 41 for controlling the phase according to the amount of phase shift
To 4n, amplifiers 21 to 2n for amplifying these phase-controlled transmission signals, and passing these amplified transmission signals to subsequent circuits in accordance with control signals respectively input by signal selection means 75 to be described later. Signal interrupting means 7 for interrupting
11 to 71n, antenna elements 11 to 1n for transmitting the transmission signals passing through these signal blocking means, and signal strength detection for detecting the signal strength of the received signal received by the terminal station based on a notification from the communicating terminal station. Means 7;
Phase shift amount control means 3 for calculating a phase shift amount based on the strength of the detected received signal and setting the calculated phase shift amounts to the first to n-th variable phase shifters 41 to 4n. Have been.

The signal strength detected by the signal strength detecting means 7 can be determined, for example, by receiving notification of signal strength information from the terminal station by the receiver 163 and inputting the signal strength information to the signal strength detecting means 7. Obtainable. The phase shift amount control means 3 in the seventh embodiment includes a signal selection means 75 for setting any two of the signal cutoff means 711 to 71n on the passing side and setting the rest on the cutoff side;
In a state where any two of 11 to 71n are set on the passing side and the rest are set on the blocking side, the strength P is minimized based on the strength P of the received signal detected by the signal strength detecting means 7. A phase shift amount calculating means 331 for calculating a phase shift amount;
The calculated phase shift amount is set in the variable phase shifter i connected to the signal cutoff means i (1 ≦ i ≦ n) set on the passing side by the signal selection means 75 among the variable phase shifters 41 to 4n. Phase shift amount setting means 371 to 37n.

The operation of the above-configured adaptive array antenna according to the seventh embodiment will be described. FIG.
7 is a flowchart showing the operation of the adaptive array antenna. When a new terminal station starts operation or resumes operation for the first time after an existing terminal station changes its position, the terminal station transmits a first control signal to the base station, and the communication channel becomes If it is free, the base station uses the second control signal to designate one or more communication channels for subsequent transmission and reception (step S30).
01 to S3003). Subsequently, the signal selecting unit 75 moves the first signal blocking unit 711 to the passing side, and
Are set to the blocking side (step S3004).

The feature of the seventh embodiment is that, based on the signal strength of the received signal detected by the signal strength detecting means 7,
The relationship between the phase of the received signal whose phase has been controlled by the second to n-th variable phase shifters 712 to 71n and the phase of the transmission signal whose phase has been controlled by the first variable phase shifter 41 in the terminal station. That is, the phase shift amount control is performed so that the phases of the transmission signals whose phases are controlled by the second to n-th variable phase shifters 42 to 4n become the same in the terminal station. The phase shift amounts set in the second to n-th variable phase shifters 42 to 4n are calculated by the phase shift amount control means 3 one by one. Here, a method of setting the phase shift amount of the first variable phase shifter 42 will be described.

The second signal blocking means 712 is set to the passing side by the signal selecting means 75, and this is set to the phase shift amount calculating means 33.
1 is notified (step S3005). Subsequently, the base station performs transmission with a fixed transmission power on the designated communication channel (step S3006). In this state, the strength P of the received signal detected by the signal strength detection means 7 is input to the phase shift amount calculation means 331 (step S300).
7 to S3008). Based on this, the phase shift amount calculating means 3
The phase shift amount Φ2 that minimizes P is calculated by 31 (step S3009).

Subsequently, based on the notification from the signal selection unit 75, the phase shift amount Φ2 calculated by the phase shift amount calculation unit 331 is input to the second phase shift amount setting unit 372. This phase shift amount Φ2 is set in the second variable phase shifter 42 by the phase shift amount setting means 372 (step S3010). continue,
The second signal blocking means 712 is provided by the signal selecting means 3032.
Is set to the cutoff side (step S3010). continue,
The same procedure is used for setting the phase shift amounts of the third to n-th variable phase shifters 43 to 4n.

By the above processing, the phase of the transmission signal whose phase is controlled by each of the second to n-th variable phase shifters 42 to 4n is controlled by the first variable phase shifter 41 in the terminal station. And the phase of the transmitted signal becomes opposite. Subsequently, the first signal cutoff means 711 is cut off by the signal selection means 75, and the second to nth signal cutoff means 7
12 to 71n are set to the passage side (step S301)
1).

By the above processing, the phases of the received signals, the phases of which are controlled by the second to n-th variable phase shifters 42 to 4n, become the same at the terminal station, and the signal transmitted by the base station is received at the terminal station in-phase. can do. For example, if the calculated phase shift amount is stored, it can be used for resuming a call after once terminating the call.

(Eighth Embodiment) Next, an adaptive array antenna according to an eighth embodiment of the present invention will be described. The configuration diagram of the adaptive array antenna according to the eighth embodiment of the present invention is similar to the configuration of FIG. 16 of the seventh embodiment.

The eighth embodiment is different from the seventh embodiment in that after step S3012 of the seventh embodiment, a new phase shift amount is set in the first variable phase shifter 41, and the optimum phase shift amount to be set is set. The configuration is such that the amount of phase shift is determined and the transmission signal transmitted by the first antenna element 11 is also used when the base station transmits.

The operation of the eighth embodiment will be described in more detail. FIG. 18 is a flowchart showing the operation of the adaptive array antenna.

Steps S3001 to S3012 are performed in the same procedure as in the seventh embodiment. Subsequently, the phase shift amount obtained by increasing the phase shift amount Φ1 currently set in the first variable phase shifter 41 by 180 degrees is converted into the first variable phase shifter 41 by the first phase shift amount setting means 371. (Step S310)
1). Subsequently, the first signal blocking means 711 is set to the passing side by the signal selecting means 75 (step S310).
2).

By the above processing, the phases of the transmission signals phase-controlled by the second to n-th variable phase shifters 42 to 4n become the same in the terminal station, and the directivity gain for the base station can be increased. .

As described above, according to the eighth embodiment of the present invention, when the base station transmits, the first antenna element 11
By using the transmission signal transmitted in step (1), the directivity gain for the terminal station can be increased.

(Ninth Embodiment) Next, an adaptive array antenna according to a ninth embodiment of the present invention will be described. FIG. 19 is a configuration diagram of the adaptive array antenna according to the ninth embodiment of the present invention.

The ninth embodiment differs from the seventh embodiment in the configuration using a variable gain circuit and gain control means.
In FIG. 19, an adaptive array antenna amplifies transmission signals distributed by distributor 162 in accordance with a control signal input from the outside, and amplifies these amplified transmission signals into variable phase shifters 41 to 4n. , And variable gain circuits 81 to 8n based on the received signal strength detected by the signal strength detecting means 7.
and gain control means 85 for setting the gains of the variable gain circuits 81 to 8n such that the strengths of the transmission signals respectively amplified by n become equal in the terminal station. The other configuration is the same as that of FIG. 16 showing the seventh embodiment, and the same or corresponding components are denoted by the same reference numerals, and redundant description will be omitted.

The operation of the adaptive array antenna configured as described above will be described in more detail. FIG.
0 is a flowchart showing the operation of the adaptive array antenna according to the ninth embodiment. Step S300
Steps 1 to S3003 are performed in the same procedure as in the seventh embodiment. Next, the first to n-th signal blocking means 711 to 71n are set to the blocking side by the signal selecting means 75 (step S3201).

The ninth embodiment is characterized in that, based on the signal strength of the received signal detected by the signal strength detecting means 7, the strengths of the transmission signals amplified by the variable gain circuits 81 to 8n are equal in the terminal station. The gain control of the variable gain circuits 81 to 8n is performed so that The gain set in the first to n-th variable gain circuits 81 to 8n is 1
It is set by the gain control means 85 one by one. here,
A method for setting the gain of the first variable gain circuit 81 will be described.

The first signal cutoff means 711 is set to the pass side by the signal selection means 75, and this is notified to the gain control means 85 (step S3202). Then, the base station
Transmission is performed with a fixed transmission power on the specified communication channel (step S3203). In this state, the strength G of the received signal detected by the signal strength detection means 7 is input to the gain control means 3009 (steps S3204 to S3204).
S3205). Based on this, the gain of the first variable gain circuit 81 is set by the gain control means 85 so that the intensity of the transmission signal amplified by the first variable gain circuit 81 becomes a specified value (step S3206). Subsequently, the first signal cutoff unit 711 is set to the cutoff side by the signal selection unit 75 (step S3207). Subsequently, the gain setting of the second to n-th variable gain circuits 82 to 8n is performed in the same procedure. Finally, steps S3004-S
Step 1012 is performed in the same procedure as in the seventh embodiment.

In the seventh embodiment, it is assumed that the signal strength of the transmission signal transmitted by each antenna element is the same in the terminal station. However, it is also assumed that the signal strength of the transmission signal transmitted by each antenna element differs in the terminal station due to the reflection of the signal transmitted by the base station and the deviation of the amplifier connected to each antenna element. .
In this case, for the same reason as described in the fifth embodiment, highly accurate phase matching between the antenna elements cannot be performed.

On the other hand, in the ninth embodiment, even if the signal strength of the transmission signal transmitted by each antenna element is different, the first through n-th transmissions are performed before the operation for determining the optimal phase shift amount. Since the gain control of the variable gain circuits 81 to 8n is performed so that the intensity of the transmission signals amplified by the variable gain circuits 81 to 8n becomes equal in the terminal station, highly accurate phase matching can be performed between the antenna elements. .

(Tenth Embodiment) Next, a tenth embodiment of the present invention will be described.
The adaptive array antenna according to the embodiment will be described. FIG. 21 is a configuration diagram of the adaptive array antenna according to the tenth embodiment of the present invention.

The tenth embodiment differs from the seventh embodiment in that the sixth embodiment shown in FIG. 14 on the receiving side has the same configuration as the fifth embodiment shown in FIG. A first signal strength storage means 141 and a second signal strength storage means 142 are provided, and a phase shift amount for calculating a phase shift amount based on the first and second phase shift amount storage means 141 and 142 is provided. It has a configuration using the calculating means 331. In FIG. 21, an adaptive array antenna includes a first signal strength storage unit 141 for storing a received signal strength P1 detected by the signal strength detection unit 7 while the base station is transmitting, and a signal transmitted by the base station. A second signal strength storage means 142 for storing the strength P2 of the reception signal detected by the signal strength detection means 7 in a state where the signal is not stored, and a first to n-th signal strength storage means 142.
In the state where any two of the signal blocking means 711 to 71n are set to the passing side and the other is set to the blocking side, P1 and P2
And a phase shift amount calculating means 331 that calculates a phase shift amount that minimizes the difference “P1−P2” based on
The other configuration is the same as that of FIG.

The operation of the adaptive array antenna configured as described above will be described in more detail. FIG.
2 is a flowchart showing the operation of the adaptive array antenna. Referring to FIG. 22, second variable phase shifter 4
The method of setting the phase shift amount of No. 2 will be described. First, the processing in steps S3001 to S3007 shown in FIG. 17 is performed in the same procedure as in the seventh embodiment. Subsequently, the strength P1 of the received signal detected by the signal strength detection means 7 is input to the first signal strength storage means 141 (step S).
3301). Next, for the desired terminal station,
A notification that transmission is to be interrupted for a certain period is given, and transmission is interrupted for a certain period (step S3302). In this state, the intensity P2 of the received signal detected by the signal
(Step S3).
303 to S3304). Based on this, the phase shift amount calculating means 331 calculates the phase shift amount Φ2 that minimizes the difference “P1−P2” between the intensities P1 and P2 (step S330).
5). Subsequently, steps S3010 to S3 shown in FIG.
The processing of 012 is performed in the same procedure as in the seventh embodiment.

In the adaptive array antenna according to the seventh embodiment, when calculating the amount of phase shift, it is assumed that only the transmission signal transmitted from the base station is received by the terminal station. Therefore, if another interfering station is transmitting at the same time, the signal strength of the received signal detected by the signal strength detecting means 3007 will be equal to the received strength of the signal transmitted by the interfering station. Is added. In this case, highly accurate phase matching between the antenna elements cannot be performed.

On the other hand, in the adaptive array antenna according to the tenth embodiment, even if there is a signal transmitted by the interfering station, when calculating the amount of phase shift, the terminal station of the signal transmitted by the interfering station is used. In this case, the reception intensity is detected and the influence thereof is removed, so that highly accurate phase matching can be performed between the antenna elements.

(Eleventh Embodiment) Next, an eleventh embodiment of the present invention will be described with reference to FIG. FIG. 23 is a diagram illustrating the adaptive array antenna according to the eleventh embodiment.

Considering a time zone in which the radio base station 2301 and the terminal station 2302 communicate with each other, when viewed from the radio base station 2301, the constraint that a null is directed to another radio base station 2303 in the same direction as the terminal station 2302 is set. With no conditions added, other wireless base stations relatively close to base station 2301 and within an angle range where the directivity of an adaptive array antenna installed in base station 2301 is variable 2304, 23
05, 2306, 2307, 2308, 2309, 23
10 is characterized by applying an algorithm for controlling a beam by adding a constraint for pointing a null.

In particular, in the case of a subscriber radio access system, an interference signal from a terminal communicating with another base station occurs in bursts at unpredictable random timings, and in many cases, the number of transmission symbols is reduced. It is very short, from several tens of symbols to several hundreds of microseconds, and from several microseconds to several tens of microseconds. As in the conventional control method, an interference wave from a terminal in another cell and its arrival direction are sequentially detected by its own base station, and digital signal processing or the like for turning null to the direction of the terminal is used. To perform the control, a very fast signal processing speed is required. On the contrary,
In the case of the adaptive array antenna according to the eleventh embodiment, since the position information of another base station is obtained in advance and the terminal uses the directional antenna, the outline of the direction in which the interference wave arrives is acquired in advance. Take advantage of what you can do,
The direction of a terminal station communicating with its own base station is detected at the time of the first call or the position information of another base station is quoted from a pre-registered database to quickly determine the null binding direction. Can be determined. This provides an advantage that control processing during communication can be reduced. During communication with the terminal, there is no particular need to change beam control for slots allocated to the terminal, and therefore, compared to a method of sequentially detecting interference waves, calculation processing for control during communication is more difficult. It also has the advantage that the volume is very small.

In general, TDD (Time Division Dupl)
ex), in the case of a cellular radio communication system, TDMA (Time Division Multiple Access) between base stations.
If synchronization is not achieved, transmission waves from other base stations at the same frequency will cause interference, so the direction of arrival of the interference wave from the base station is detected according to the level of the interference wave and detected. There is a method of adaptive suppression. In contrast to such a system, the adaptive array antenna according to the eleventh embodiment has a dual mode FDD.
(Frequency Division Duplex), and has a unique effect that simple control is possible. It should be noted that in the case of a wireless communication system using FDD as a duplexing method, the frequency transmitted from the base station is a cause of interference in base station reception even if time division multiplexing between base stations is not synchronized. Must not be
The conventional algorithm for preventing interference does not add a constraint condition toward another base station. Even in a system using FDD, when a directional antenna is used on the terminal side, a signal from each interfering terminal is used by using a constraint condition in the direction of another base station as in the control method of the eleventh embodiment. , It is not necessary to detect, and very high-speed control is possible.

As can be understood from FIG. 23, base stations 2304 and 2305, 2306 and 2307 and 2309
And 2310 are located in directions closer to each other when viewed from the base station 2301. In such a case, among the plurality of other base stations, the level of the interference wave is estimated to be the largest, including the gain of the adaptive array antenna, the distance, the propagation conditions such as the visibility to the corresponding base station, and the like. Only possible base station directions are added to the constraint condition, or the above conditions of a plurality of base stations are weighted and averaged as a constraint condition. The constraint condition can be reduced by using a method such as a constraint condition.

It is to be noted that a terminal that performs communication with a distant base station has a low probability of causing interference. In general, the number of nulls that can be formed by an array antenna having the number of antenna elements N_el is limited to N_el. Therefore, the direction in which the constraint condition is provided is set to N_el or less, and it is estimated that the level of the interference wave increases, including the gain, the distance of the adaptive antenna, the propagation condition such as the line of sight to the corresponding base station, and the like as necessary. It is appropriate to set the constraint condition preferentially from the available base stations. Therefore, the first
In one embodiment, 2311, 231 of the other base stations
No constraint condition is set for 2,2313,2314.

In the eleventh embodiment, null is not directed to another base station 2303 located in a direction closer to the terminal 2302 in communication as viewed from the base station 2301. On the other hand, since control information is generally not exchanged between base stations, the relationship between the position of a terminal communicating with base station 2301 and the position of a terminal communicating with base station 2303 is random. For example, as shown in FIG. 24, while the terminal 1402 is communicating, the base station 240
3 while the terminal 2416 is communicating with the value terminal 5216
Since the antenna directivity is not suitable for the base station 2401, the interference wave does not matter. FIG. 25
While the terminal 2502 is communicating and the base station 2503 and the terminal 2516 are communicating by chance,
Since the antenna directivity of terminal 2516 is directed to base station 2501, the transmission signal of terminal 2516 is an interference wave.
However, when a sector antenna is used as shown in FIGS. 38 and 39, another base station (for example, 350
4,3505,3506,3507,3508,350
9, 3510), the terminal station transmitting with the directional antenna receives interference from all terminals in the range 3515 of the position where interference with the base station 3501 occurs. In the case of, there is an advantage that interference from a terminal communicating with another base station other than the base station 2503 is not received.

As for the method of knowing the direction of another radio base station, it is possible to register the positional relationship with another existing radio base station or the direction of another radio base station in advance when setting the radio base station. Conceivable. Also, when a new radio base station is installed, a value from a control station that controls a plurality of radio base stations is notified to each radio base station as position information of the new radio base station as control information. As necessary, it is conceivable to calculate the positional relationship with the own radio base station from the position information and add it to the existing registration. Also,
When installing a new radio base station, use a radio station that can transmit a control burst for registration of a new base station at the reception frequency of the base station, such as a remodeled terminal radio station, and use a new radio base station for the existing base station. Transmit a control burst for base station registration,
When the existing known station recognizes the control burst as a new base station registration, it detects the direction and propagation conditions of the new base station from the transmission signal and its signal strength, and newly registers the new base station, It is conceivable to calculate and register a priority order and its direction when setting a null constraint condition. As a method for determining whether or not the difference between the direction of a certain base station and the direction of a terminal performing communication (here, δθ) is small, for example, the following various methods can be considered. For example, if the directional beam width of the terminal is θ_t,
As shown in FIG. 26, the range of the position of a terminal station that communicates with another base station 2603 causing interference with its own base station 2601 is within the radio zone of the other base station 2603 and the base station 2601 and the base station. Base station 2 in a straight line passing through station 2603
The range 2615 is included in the angle θ_t from 603 to the line opposite to the base station 2601. This range 261
5 from the base station 2601 is equal to the base station 2
Distance d_BB between base station 601 and base station 2603 and base station 26
Using the radius r_z of the wireless zone 03, θ_i = 2 × arctan ｛((r_z) × tan ((θ_t)
/ (2)) / ((r_z) + (d_BB)))}. Therefore, by using δθ <θ_iθ × 0.5 as a criterion for determining whether or not the difference δθ between the direction of a certain base station and the direction of a terminal performing communication is small,
It can be determined whether or not there is a direction of the terminal performing communication within the range of interference.

As a method for obtaining an approximation of the above θ_i, as shown in FIG. 26, when base stations are arranged almost regularly, the average radio zone radius r_g of the target system is calculated as follows. Using r_z = r_g, d_
By approximating by BB = 3 × r_g, θ_i ′ = 2 × arctan ｛tan ((θ_t) / 2)) /
4｝ can be used as an approximate value of θ_i. There is an advantage that interference waves can be removed without having to consider the distance between base stations and the like.

Since FIG. 26 clearly shows that θ_t> θ_i, a simpler method than the above method is as follows.
If the directional beam width θ_t of the terminal is used as the threshold value, the angle tends to be slightly widened, but there is no need to consider the distance between base stations or the size of the wireless zone of each base station. There is an advantage that waves can be removed.

As described above, when the number of elements of the adaptive array antenna is limited, the number of nulls that can be formed is limited. Generally, the number of elements N_e
The number of nulls that can be formed by the 1 array antenna is at most N
_El. In this case, using a criterion such as a short distance from the own base station, or a direction of the base station to which the terminal station is more connected, or a direction in which the angles are separated from each other, At most, it is conceivable to select up to N_el directions and use them as a constraint for turning null.

The directional beam width θ_ of the antenna element
When t is relatively narrow, the angle width at which the beam as a broadside array antenna can be swung is also about θ_
t. Therefore, it is desirable to exclude the direction from the angle to the base station located in the outward direction from the direction of the base station group of the eleventh embodiment.

Note that the eleventh embodiment is, for example, shown in FIG.
Considering the frame configuration as described above, the case where the base station adaptive array antenna is used for transmission and reception of data packets communicating in the uplink payload window has been described, but transmission and reception of control packets in the uplink control window are performed in the following manner. It is also conceivable to apply to
That is, when applied to the rising control window,
For example, when there are n directions in which null constraint conditions are to be provided according to other base station direction relations, a plurality of radiation patterns are prepared by removing some of them. At this time,
When a certain direction is picked up, at least one of the plurality of patterns is a combination in which null is not directed in that direction. Then, by appropriately switching the plurality of patterns for each slot in an up control window in which a control channel can be transmitted, it is possible to receive control signals from terminals in the own cell throughout while reducing interference. Will be possible. In particular, when a lot of traffic occurs in a specific adjacent cell, in order to avoid interference from the terminal of the adjacent cell, the number of slots for nulling to the base station of the adjacent cell is made slightly larger, and the interference in this time zone is increased. By lowering the level to increase the throughput and providing a slot in which no null is directed to the base station of this adjacent cell, there is an advantage that a control signal from a terminal existing in this direction can also be received.

(Twelfth Embodiment) Next, an adaptive array antenna according to a twelfth embodiment of the present invention will be described with reference to FIG. FIG. 28 shows the configuration of the twelfth embodiment. As shown in FIG. 28, the adaptive array antenna according to the twelfth embodiment includes a plurality of antenna elements and a high-frequency circuit connected to each antenna element, and adjusts a phase of a local signal applied to a frequency conversion circuit in the high-frequency circuit. As a part of the local signal phase shift circuit 2811 that changes for each high frequency circuit for each antenna element,
In an adaptive array antenna using a quadrature modulator 2812 that receives a local frequency signal and a control signal, a coupler 2801 that branches a part of a signal from each antenna element into the high-frequency circuit; It is characterized by having a quadrature demodulator 2802 for individual elements to which a signal from 5601 is input.

A phase control signal output circuit for outputting a control signal to the quadrature modulator 2812 of the local signal phase shift circuit 2811 and a demodulated signal from the individual element quadrature demodulator 2802 are input and input to the individual element. A plurality of individual element signal sensors for detecting the phase and amplitude of the signal, a comparison circuit for comparing the signals from the plurality of individual element signal sensors and detecting the difference, and based on the comparison result, the detected difference And a compensation control means for controlling an output signal of the phase control signal output circuit so as to compensate for a phase difference due to a difference in the routing length of the antenna feed line and other wiring lengths.
It is also characterized in that it is provided inside the amplitude weight calculation circuit 2813.

Further, the second IF from a plurality of individual elements
A first for monitoring the signal level of one of the signals
(Including a coupler 2820 for extracting a certain percentage of signal power of a signal, an RSSI output circuit 2821 including a logarithmic amplifier for amplifying the extracted signal and an ADC for converting the output of the signal to a digital value) and A second RSSI circuit for monitoring the signal level of the combined second IF signal (a coupler 2822 for extracting a certain percentage of signal power of the combined signal, a logarithmic amplifier for amplifying the extracted signal, and its output) To convert A into a digital value
DC output RSSI output circuit 2823), N first IF variable gain amplifiers 2816 for varying the relative levels of all IF signals of each individual element, and N second IF variable gains An amplifier 2815, a combined variable gain amplifier 2825 for varying the signal level of the second IF signal after combining the signals from the individual elements, and a first RS
Based on the RSSI signals from the SI circuit and the second RSSI circuit, the combined output signal level is controlled to a fixed width, and the first and second high-frequency circuit elements for individual elements are not saturated. IF variable gain amplifier 2816, second IF variable gain amplifier 2815, and combined variable gain amplifier 2
825 is controlled by an AGC control circuit 2824. Note that the RSSI is a received signal strength indication (Receive Signal Strength Indication).
, Which is a numerical representation of the strength of the received radio signal.

Also, in order to reduce a clock recovery circuit which is generally complicated and requires a high-speed circuit such as oversampling the baud rate, a receiver 2819 is required.
The output of the clock recovery circuit 2828 mounted on the
If necessary, the receiver 2819 and the combined output demodulation circuit 28
After compensating for the internal delay between the signal 29 and the individual element demodulation circuit 2803 for weight determination, and passing through a clock timing adjustment circuit 2827 for adjusting the timing for supplying the timing with the highest aperture ratio of the eye, the combined output It is also characterized by being supplied to the ADC 2826 of the demodulation circuit 2829 and the plurality of ADCs 2809 of the individual element demodulation circuit 2803 for weight determination.

As a result, the combined output demodulation circuit 2829
Therefore, it is not necessary to apply oversampling to the individual element demodulation circuit 2803 for weight determination, and the sampling rate of the ADC can be reduced, so that power consumption can be reduced.

In general, the output frequency of the clock recovery circuit is substantially equal to the baud rate. However, depending on the modulation method or the like, it may be preferable to apply a relatively small multiple oversampling to the ADC 2826 or the plurality of ADCs 2809. In this case, the clock recovery circuit 2828
Output a frequency which is a multiple of the baud rate. Note that, instead of being provided in the clock recovery circuit and the receiver 2819, it may be provided in the combined output demodulation circuit 2829, or provided in the individual element demodulation circuit 2803 for weight determination.

With these configurations, the DBF (Digital Be
am Forming) type adaptive antenna, PTM
When the transmission rate becomes faster, such as 1 Mbaud or more, which is being studied in the P system, there is a problem that very fast digital signal processing is required for real-time reception. In the adaptive array antenna of the form, the actual signal weighting and combining are performed by a local signal phase circuit 2811, an amplitude weight weighting circuit 2817, and a high frequency adder 2818.
, Real-time reception can be performed by a normal receiver 2819 even when a very high transmission rate is used.

In addition, high frequency circuits constituting the array antenna, for example, element deviation of phase distortion of an amplifier or a mixer,
There is no need to provide a special additional circuit (for example, a high-frequency phase shifter) for compensating for a phase difference or the like due to a difference in the wiring length of the antenna feed line or other wiring lengths, and it is only necessary to correct the digital input value. Cost reduction can be achieved. Also, with respect to a local phase shift circuit using a quadrature modulator, deviations of individual element circuits may occur.
In this embodiment, it is possible to perform calibration including this local phase shift circuit.

FIG. 30 shows a configuration example for compensating the phase difference and the amplitude difference in the adaptive array antenna according to the twelfth embodiment. The demodulated signal from the individual element demodulation circuit for weight determination 2803 is input, and the phase and amplitude for comparing the phase and amplitude of each input signal and detecting the difference between them are determined.
The amplitude comparison circuit 3202, the phase deviation detected based on the comparison result, the difference between the length of the antenna feed line and other wiring lengths, the passing phase characteristics of the amplitude weighting variable gain amplifier 3208 and the combiner 2818 Deviation compensation control means 320 for controlling the output signal of the phase control signal output circuit so as to compensate for the phase deviation due to the difference between
3 and a phase shift control signal for outputting a control signal to the quadrature modulator of the local signal phase shift circuit based on the output of the phase shift amount from the phase deviation compensation control means 3203 and the phase shift amount / amplitude weight calculation circuit 3205. Based on the comparison result between the output circuit 3204 and the phase shift / amplitude comparison circuit 3202, the detected amplitude deviation, the difference in the length of the antenna feed line and other wiring lengths, and the amplitude gain weighting variable gain amplifier 320
AGC / amplitude deviation compensating circuit 3201 so as to compensate for the amplitude deviation caused by the passing amplitude characteristic of combiner 28 and combiner 2818.
IF / AGC control and amplitude deviation compensation circuit 2
Amplitude deviation compensation control means 3 for controlling the output signal to output signal 814
206.

In general, components constituting an RF / IF circuit, a local phase shift circuit, and the like for each antenna element of an adaptive array antenna have variations in gain, loss, phase characteristics associated with signal passage, and the like. The deviation of the amplitude and phase of each antenna element system due to this variation causes an error in the radiation pattern characteristic due to the control of the phase shift amount and the amplitude weight.

The deviation of the amplitude and phase of each antenna element system is measured at the time of manufacture of the antenna or at certain intervals during operation, and if the deviation can be compensated, the error of the radiation pattern can be suppressed. You can do it.

For example, at the time of manufacture, a signal having the same phase and the same amplitude is input to each antenna input by a distributor or the like,
Alternatively, a radio wave is transmitted from a sufficiently distant position in the boresight direction in an anechoic chamber or the like, and the phase deviation and the amplitude deviation of the input from each antenna element system are compared with the phase / amplitude comparison circuit 3202.
To detect. The comparison result is obtained by the phase deviation compensation control means 3.
203 and the amplitude compensation control means 3206, which calculate a phase shift amount and an amplitude adjustment amount for compensating for the phase deviation and the amplitude deviation. Phase shift amount for phase deviation compensation and phase shift amount / amplitude weight calculation circuit 3205
The amount of phase shift for controlling the radiation pattern of the antenna output from is added by the phase control signal output circuit 3204, converted into a control signal to the quadrature modulator of the local signal phase shift circuit, and output. Further, the obtained amplitude adjustment amount for amplitude deviation compensation and the amplitude adjustment amount for performing AGC are added by AGC / amplitude deviation compensation control circuit 3201 to obtain a second IF / AGC control and amplitude deviation compensation circuit 2814. The signal is converted into a digital signal for variable gain and output. These control methods can suppress errors in the radiation pattern.

Also, during operation, a signal from a specific transmitting station whose position is known in advance is received at a timing where signals from other transmitting stations do not arrive as much as possible, and prediction is made from the direction of the specific transmitting station. By detecting the deviation from the phase difference of the input from each antenna element system and the amplitude deviation of the input by the phase / amplitude comparison circuit 3202, it is possible to perform compensation in the same manner as the above-described method.

Note that, depending on the format of the IF frequency converter 3207, the output level of the conversion signal of the IF frequency converter 3207 may be changed depending on the output level of the local signal phase shifter 2811. In this case, the phase deviation compensation control means 320 is used without using the amplitude compensation control means 3206.
The phase / amplitude deviation compensation control means provided at a location corresponding to 3 fetches the phase deviation and the amplitude deviation from the phase / amplitude comparison circuit 3202, calculates the phase shift amount and the amplitude adjustment amount, and corresponds to the phase shift control signal output circuit 3204 The phase shift / amplitude control signal output circuit provided at the position where the phase shift / amplitude weight calculation circuit 3205 outputs the phase shift for controlling the radiation pattern of the antenna and the deviation obtained as described above. It is also conceivable to compensate the amplitude deviation and the phase deviation by adding the phase shift amount for compensation and adjusting the I and Q inputs to each of the N quadrature modulators according to the amplitude adjustment amount. Can be In this example, the amplitude compensation control means 3206 may be used together, and the compensation amount of the amplitude deviation may be distributed and controlled by the phase / amplitude deviation compensation means and the amplitude compensation control means 3206.

FIG. 31 shows another configuration example for compensating the above-mentioned phase difference and amplitude difference. FIG. 31 differs from FIG. 30 in that the output of the amplitude compensation control means 3206 is
The signal is input to the amplitude control signal output circuit 3303 together with the amplitude weight from the amplitude weight calculation circuit 3205, added thereto, and converted into a digital signal for varying the gain of the amplitude weight weighting and amplitude deviation compensation circuit 3302 and output. In this configuration, phase and amplitude can be compensated by the same control as in the example described in the operation description of FIG.

An adaptive array antenna having the configuration shown in FIG. 28 differs from a normal wireless communication device in that it is necessary to monitor both the signal level after combination and the signal level before combination. For example, in a case where a signal from a terminal other than a desired terminal is stopped in a cell and a null point is searched by continuously changing a phase shift amount by a phase shifter, a dynamic range of a signal level after synthesis becomes considerably large. On the other hand, it is expected that the intensity of the signal from each antenna before combining will be at a substantially constant level. In this case, saturation occurs if the gain of the variable gain amplifier up to the synthesizer is increased just because the level of the received signal after the synthesis is lowered. Therefore, the level of the received signal before combining is also monitored, the gain is increased to the extent that saturation does not occur before reaching the combiner, and the remaining shortage is compensated for by the increase in the gain of the variable gain amplifier after combining.

On the other hand, after the terminal direction can be almost identified, or after the beam converges to the optimal weighting coefficient and then the beam is directed in that direction, the signal strength after the synthesis is stable. And fluctuations are reduced. On the other hand, the level of the signal strength from each antenna before combining may decrease due to interference of signals from a plurality of terminal stations.

However, since the transmission signal of the radio communication is generally scrambled so that the line spectrum does not stand, it can be assumed that the phase of the information signal follows a uniform distribution in a certain long time interval. In the case of the PTMP system of the subscriber wireless access system, the position of each terminal station does not basically move. Therefore, in the RSSI circuit, the symbol duration (transmission symbol rate T
averaging over a sufficiently long period of time, the phase difference between a plurality of transmission signals becomes a random uniform distribution,
It is considered that the fluctuation of the RSSI output due to the interference has no effect. This property is considered to be irrelevant regardless of the output of any of the plurality of antennas. Therefore, it is not always necessary to monitor all input powers from a plurality of elements. As shown in FIG. 28, if a coupler 2820 and an RSSI circuit 2821 for monitoring at least one of the inputs are used, each antenna Can be estimated.

Then, the two RSSI circuits are used in combination, and the gains of the three sets of variable gain amplifiers 2816, 2815, and 2825 are adjusted based on the results of these two monitors. That is, the AGC control circuit 2824 prepares a table for obtaining three gain adjustment voltage outputs for two inputs.

FIG. 29 shows a case in which the adaptive array antenna according to the twelfth embodiment is used.
An example of a voltage control method will be described. It should be noted that the gain increase or decrease in FIG. 28 is generally set to be substantially the same as the difference between the desired lower limit and the desired upper limit, but in order to simplify the control although the convergence is slow, A method of performing stepwise control at a predetermined constant value smaller than a desired value range is also conceivable. By performing the above control,
The effect is obtained that the output signal level after the synthesis can be controlled to a fixed width and the high-frequency circuit element for each individual element can be controlled so as not to be saturated.

The combined receiver 2819 has ± 2d
Usually, an input fluctuation margin of about B is provided. Therefore, it is conceivable to provide a hysteresis so that the gain adjustment function does not react excessively with a change much smaller than this, and the gain is not changed very frequently. Specifically, a predetermined number of past output values of the RSSI circuit is stored, and only when a deviation from this value exceeds a certain value, the AGC control circuit 2824 sends the first IF variable gain amplifier 2816 If the IF variable gain amplifier 2815 and the combined variable gain amplifier 2825 are limited so as to output a gain change command, a slight fluctuation in the signal level due to the noise component of the RSSI circuit or minute fading of the input RF signal is performed. Thus, there is an advantage that unnecessary control can be prevented from being performed because the AGC control circuit 2824 excessively reacts and originally falls within the allowable reception power range of the receiver 2819.

In the case where the amount of phase shift is continuously changed by the phase shifter and the property of the received signal after combining at that time is measured, the speed of change of the amount of phase shift is determined by the speed of RSSI. It is desirable to make it sufficiently slower than the constant. If the time constant of the RSSI is set to a certain value, the speed of measurement may be reduced. In this case, a mode for changing the time constant of the RSSI may be provided.

(Thirteenth Embodiment) Next, an adaptive array antenna according to a thirteenth embodiment of the present invention will be described in detail with reference to FIG.

The thirteenth embodiment comprises a plurality of antenna elements 11 to 1n, a high-frequency circuit 30 connected to each antenna element, and a high-frequency distribution circuit 162 for distributing an output to the plurality of high-frequency circuits. , An amplitude weight weighting circuit 31 for weighting the amplitude for each antenna element, and a local signal phase shift circuit 32 for weighting the phase.
A pre-distribution variable gain amplifier 33 that makes the signal level of the F signal variable, and N second IF variable gain amplifiers 34 that can change the relative level of the second IF signal of each of the N individual elements.
And controlling the effective radiated power in consideration of the directivity gain from the adaptive array antenna estimated from the output of the amplitude weighting circuit 31 so as not to exceed a predetermined value. It has a gain control circuit 35 for controlling the pre-distribution variable gain amplifier 33 and the N second IF variable gain amplifiers 34 so that the circuit elements are not saturated.

FIG. 33 shows a case in which the adaptive array antenna according to the thirteenth embodiment is used.
4 shows an example of a voltage control method. It is also conceivable to use the N second IF variable gain amplifiers 34 after distribution in FIG. 32 as a circuit for weighting the amplitude weight of each antenna element. In this case, the desired E in FIG.
The gain control voltages written in the gain setting value tables of the pre-distribution variable gain amplifier corresponding to the RP value and the N second IF variable gain amplifiers take into account the upper and lower limits of the variable range of the gain used as the amplitude weight. However, it is necessary that the control voltage has a gain that does not cause distortion due to shortage of NF or saturation. If this condition cannot be satisfied at the same time, the upper limit and the lower limit of the variable range of the gain as an allowable amplitude weight are prepared as a table for the desired ERP value in addition to the gain setting value table. When it is important to prevent distortion due to shortage or saturation, it is conceivable to refer to this table when determining the amplitude weight and change the amplitude weight so that it falls between the upper limit and the lower limit.

According to the above-described method, an effect is obtained that an effective radiation power value equal to or less than a predetermined value and low distortion of the high-frequency circuit for each individual element can be simultaneously realized. Also, when the control width of the transmission power needs to be very large, it is difficult to provide input / output isolation to increase the gain because only one variable gain amplifier requires a large control width. Or the configuration may be complicated because the variable gain amplifier has an attenuation function. There is also an advantage that such a problem can be avoided by dividing the variable gain element before and after distribution as in the present embodiment.

Further, in the thirteenth embodiment, the amplitude weighting circuit 31 and the N second IF variable gain amplifiers 34 are separately provided. However, the two are realized by a single circuit. Is also conceivable. In this case, there is an advantage that the circuit scale for obtaining the necessary transmission power control width can be further reduced, and the above-described problems such as the isolation and the attenuation function can be solved.

(Fourteenth Embodiment) Next, a fourteenth embodiment of the present invention will be described.
Regarding the adaptive array antenna according to the embodiment,
This will be described in detail with reference to FIGS. Since the present invention has been described in detail with reference to a number of embodiments, the reference numerals used in the drawings used in the fourteenth embodiment are the same as those used in the drawings of other embodiments. However, the reference numerals used in FIGS. 34 to 36 are limited to the fourteenth embodiment and used.

In FIG. 34, reference numerals 11 to 1n denote antenna elements, and 21 to 2n weight reception signals received by the antenna elements 11 to 1n with real weights respectively set by a real weight control system 7 described later. There are a plurality of real number weighting means, and reference numerals 31 to 3n denote a plurality of individual element signal strength detecting means for respectively detecting the weighted received signal intensities as individual element signal strengths. Reference numeral 4 denotes a combiner that combines the received signals weighted by the real number weighting means 21 to 2n, reference numeral 5 denotes a demodulator that demodulates the received signal combined by the combiner 4, and reference numeral 6 denotes a demodulator. This is signal strength detection means for detecting the strength of the received signal combined by the combiner 5 as a combined signal strength.

Reference numeral 7 denotes an individual element signal intensity detecting means 31
3n, the real weights to be newly set are calculated based on the individual element signal intensities respectively detected by .about.3n and the combined signal strengths detected by the combined signal strength detection means 6, and these calculated real weights are weighted by weighting means 21 to 21, respectively. 2n
Is a real number weight control unit that repeats the process of setting a plurality of cycles.

The real number weight control means 7 stores a plurality of real number weight initial values W_1 (0) to W_n (0) (n is the number of antenna elements) set in the plurality of real number weighting means 21 to 2n. Initial value storage means 711-71
n and real number weights W_1 (k) to W_n (0) to be set in each of the plurality of real number weighting means 21 to 2n when the real number weight control means 7 operates for the first time. k) a plurality of real number weight storage means 7 storing as k (k is the number of real number weight updates)
21 to 72n and a plurality of these real number weight storage means 7
W_1 (k) to W_n (k) stored in 21 to 72n
W_i (k) or -W_i (k) as the real weight of the plurality of real weighting means 21 to 2n based on
A plurality of real number weight setting means 731 to 73n for setting any one of (1 ≦ i ≦ n) and the plurality of real number weighting means 21 to 2n are respectively assigned to W_1 (k) to W_n.
In the state where (k) is set, the combined signal strength detecting means 6
The combined signal strength Py (k) detected by
Similarly, the individual element signal strengths Px_1 detected by the plurality of individual element signal strength detection means 31 to 3n with W_1 (k) to W_n (k) being set by the plurality of real number weighting means 21 to 2n, respectively. (K) to Pxn
(K) is input to each of the plurality of real number weighting means 21 to 2n, and W_1 (k), W_2 (k),.
.., W_i-1 (k), W_i (k), W_i + 1
(K),..., W_n (k) (1 ≦ i ≦ n) are set, and the combined signal strengths Py_i (k) (1 ≦ i ≦ n) detected by the combined signal strength detection means 6 respectively. ) Is input, a new real number weight W_i (k +
1) = W_i (k) + a ^* [Px_i (k) + ｛Py
(K) −Py_i (k)｝ / 4] / W_i (k) (a is a constant) and (1 ≦ i ≦ n), and W_1 (k) of the plurality of real number weight storage units 721 to 72n. ~
Real number weight calculation means 741 to be input to W_n (k)
74n.

In FIG. 34, the real number weight control means 7 includes an update stop means 75 for stopping the operation based on predetermined conditions.

The real number weighting means 21 to 2n are, for example, shown in FIG.
5 is configured. In FIG. 35, the real number weighting means 21 (2n) includes a real number weight W_i.
An absolute value detecting means 211 for calculating an absolute value of (k);
_I (k), and a variable gain amplifier 21 that amplifies the received signal X_i (t) based on the absolute value calculated by the absolute value detector 211.
3 and a 1-bit phase shifter 214 for controlling the sign of the amplified received signal based on the sign calculated by the sign detecting means 212.

As described above, the weighting of the real number weight can be realized by a simple circuit configuration because the multi-bit phase shifter required for weighting the amplitude and the phase weight is not used. However, the present invention can be applied to a circuit configuration for weighting the amplitude and the phase weight.

The operation of the adaptive array antenna configured as described above will be described with reference to FIG. FIG. 36 is a flowchart for explaining the operation of the adaptive array antenna.

First, the real number weight W_1 (0) stored by the initial value storage means 711 is input to the real number weight storage means 721. Based on this, W_1 (0) is converted into W_1
(0).

W ₁ (k) = W ₁ (0) Subsequently, the real number weight initial values W_2 (0) to W_n (0) stored by the initial value storage means 712 to 71n are similarly stored. Means 722 to 72n
(Steps S1 to S4).

Subsequently, the real number weight initial value W_1 (k) stored by the real number weight storage means 721 is input to the real number weight setting means 731. This real number weight W_1 (k) is set in the real number weighting means 21 by the real number weight setting means 731.

Subsequently, real number weight storage means 722 to 72
The initial value W_2 (k) of the real number weight stored by n
Similarly, W_n (k) is input to real number weight setting means 732 to 73n, and real number weighting means 22 to
2n is set (step S5).

Initial values W_1 (0) to W_ of real number weights
For example, n (0) may be set so as to maximize the directional gain in the desired wave direction.

At time t, the received signals received by antenna elements 11 to 1n are denoted by X_1 (t) to X_n (t). These signals are weighted by real number weighting means 21 to 2n. These weighted received signals are input to individual element signal strength detection means 31 to 3n. Assuming that the real number weights set in the real number weighting means 21 to 2n are W_1 (k) to W_n (k), the individual element signal strengths Px_1 (k) to Px_n respectively detected by the individual element signal strength detecting means 31 to 3n. (K)

(Equation 16) It is expressed as Here, i: 1 <= i <= n, E [•]: Expected value calculation.

Subsequently, the received signals weighted by the real number weighting means 21 to 2n are combined by the combiner 4. The combined received signal is sent to a combined signal strength detecting means 6.
Is input to Based on this, the combined signal strength Py (k) detected by the combined signal strength detection means 6 is:

[Equation 17] It is expressed as Here, ^* : plural conjugates.

The fourteenth embodiment is characterized in that the differential coefficient of the combined signal strength detected by the combined signal strength detecting means 6 with respect to the real weight set in each of the real number weighting means 21 to 2n is determined by the individual element signal strength. Detecting means 31 to 3
n and the combined signal strength detected by the combined signal strength detection means 6. Using this differential coefficient, real number weight control based on the steepest descent method is performed.

The procedure of the weight control will be described below.
First, the update stop unit 75 sets the number of real number weight updates to k = 1 (step S6).

Subsequently, the combined signal strength Py detected by the combined signal strength detection means 6 with W_ (k) to W_n (k) set in the real number weighting means 21 to 2n, respectively.
(K) is input to the real number weight calculation means 741 to 74n (step S7).

Subsequently, the individual element signal strength Px_1 (k) detected by the individual element signal strength detecting means 31 is set in a state where W_1 (k) to W_n (k) are set in the real number weighting means 21 to 2n, respectively. It is input to the calculating means 741.

Subsequently, the individual element signal intensities Px detected by the individual element signal intensity detectors 32 to 3n with W_1 (k) set in the real number weighters 21 to 2n, respectively.
Similarly, _2 (k) to Px_n (k) are input to the real number weight calculating means 741 to 74n (steps S8 to S11).

Subsequently, real number weight setting means 731-7
3n to the real number weighting means 21 to 2n respectively by -W_1
(K), W_2 (k),..., W_n (k) are set, and the combined signal strength Py_1 (k) detected by the combined signal strength detection means 6 is a real number weight calculation means 74.
1 is input.

Subsequently, real number weight setting means 731 to 7
3n to the real number weighting means 21 to 2n respectively by W_1
(K), -W_2 (k),..., W_n (k) are set, and the combined signal strength Py_2 (k) detected by the combined signal strength detection means 6 is a real number weight calculation means 7.
42.

Subsequently, the combined signal strengths Py_3 (k) to P
Similarly, y_n (k) is input to real number weight calculating means 743 to 74n (steps S12 to S1).
6).

Based on these inputs, new real number weights W_1 set in the real number weighting means 21 to 2n respectively.
(K + 1) to W_n (k + 1) are calculated by real number weight calculation means 741 to 74n.

First, the combined signal strength Py (k), the individual element signal strength Px_1 (k), and the combined signal strength Py_1
Based on (k), a new real number weight W_1 (k + 1) set in the real number weighting means 21 is calculated by the real number weight calculating means 741 as follows. W ₁ (k + 1) = W ₁ (k) + a ｛P _X1 (k) + (P
_{Y (k) -P Y1 (k} )) / 4} / W 1 (k) where, a: real. Subsequently, the composite signal strength Py
(K), individual element signal strengths Px_2 (k) to Px_n
(K), and the combined signal strengths Py_2 (k) to Py_n
Similarly, for (k), the real number weight calculation means 742
(Steps S17 to S2)
0).

Subsequently, the new real number weight W_1 (k + 1) calculated by the real number weight calculating means 741 is input to the real number weight storing means 721. Based on this, W_1 (k +
1) is stored as W_1 (k) as in the following equation.

W ₁ (k) = W ₁ (k + 1) Subsequently, new real number weights W_2 (k + 1) to W_n calculated by the real number weight calculation means 742 to 74n.
Similarly, for (k + 1), the real number weight storage means 7
22 to 72n (steps S21 to S2).
4).

Subsequently, the new real number weight W_1 (k) stored by the real number weight storage means 721 is input to the real number weight setting means 731. This real number weight W
_1 (k) is set in the real number weighting means 21 by the real number weight setting means 731.

Subsequently, real number weight storage means 722 to 72
new real number weight W_2 (k) stored by n
Similarly, W_n (k) is input to the real number weight setting means 732 to 73n, and the real number weighting means 22 to 2
n is set (step S25).

Next, it is determined by the update stopping means 75 whether or not the number k of real number weight updates is smaller than K.
If it is smaller, k is increased by 1 and steps S7 to S2
The process of step 5 is repeated, and if k is equal to or larger than K, the process ends (steps S26 to S27).

By providing the update stop means 75, it is possible to prevent the real number weight control means 7 from continuing to operate.

Here, the process is terminated by counting the number of repetitions of the real number weight update. In this case, the operation of the real number weight control means 7 can be completed within a predetermined time. Also, W_i (k + 1) -W_i
(K) It is also conceivable to end the processing when (1 <= i <= n) becomes equal to or less than a predetermined value. In this case, the operation of the real number weight control means 7 can be terminated in a state where the so-called adaptive algorithm has converged.

(Px_i (k) + (Py (k) -Py_
i (k)) / 4) / W_i (k)

(Equation 18) It is expressed as Here, i is an integer satisfying 1 <= i <= n, and Reｎ ·｝ is a real part.

On the other hand, the differential coefficient δPy (k) / δW_ regarding the real number weight W_i (k) of the combined signal strength Py (k)
i (k) is

[Equation 19] It is expressed as

From the above, δPy (k) / δW_i (k)
= 2 (Px_i (k) + (Py (k) -Py_i)
(K)) / 4) W_i (k) holds. Therefore,
The processing in step S18 is

(Equation 20) This means that the equivalent processing is performed.

If the real number a is a negative value, the real number weights of the real number weighting means 21 to 2n are updated so as to reduce the combined signal strength of the adaptive array antenna, and finally, δPy (k) / δW_i ( k) = 0 (1 <= i
Since a real number weight that satisfies <= n) is set, if an interference wave exists, it can be suppressed. However, it is necessary to limit the amount of change of one or more real number weights from the initial value in order to avoid that all real number weights become zero.

Such real weight control is performed, for example, by
When applied to the adaptive array antenna for reception of the base station, the real weight of the real weighting means is controlled and the real weight for suppressing co-channel interference is calculated before giving the communication channel to the terminal station requesting communication. Then, a method is conceivable in which the communication channel is provided to the terminal station, a real number weight for suppressing the co-channel interference is set in the real number weighting means 21 to 2n, and a signal transmitted by the terminal station is received.

When the arrival direction of the desired wave is known in advance, a directional antenna or an array antenna in the desired wave direction may be used. In the case of a directional antenna, the signal received by each element can be limited by the direction of arrival. In the case of an array antenna, for example,
Appropriate directivity can be provided like an orthogonal beam.

As described above, according to the fourteenth embodiment of the present invention, the plurality of individual element signal intensities detected by the individual element signal intensity detecting means 31 to 3n and the combined signal intensity detected by the combined signal intensity detecting means 6 are used. Since the real weight control based on the steepest descent method can be performed by obtaining the differential coefficient of the evaluation function with respect to the real weight using the signal strength, the demodulated signal of each antenna element is used as in the related art. Can be realized with a simple circuit configuration.

[0230]

As described in detail above, according to the present invention,
By using the plurality of individual element signal strengths detected by the individual element signal strength detection means and the combined signal strength detected by the combined signal strength detection means, the differential coefficient with respect to the real number weight of the evaluation function is obtained. Since real weight control based on the real number can be performed, it can be realized with a simple circuit configuration as compared with the case of using a demodulated signal of each antenna element as in the related art.

Further, since only the signal intensity detected by the signal intensity detecting means can be used to perform the phase shift amount control based on the partial differential coefficient with respect to the phase shift amount of the evaluation function, as in the prior art, Compared to the case of using a signal for each antenna element, it can be realized with a simple circuit configuration.

Further, by using only the signal strength detected by the signal strength detecting means, the amount of phase shift for receiving signals in phase in the own station or the other station of the communication taking into account the phase shift deviation can be simplified. This eliminates the need to set the phase shift amount to compensate for the phase deviation unlike the prior art, and can be realized with a simple circuit configuration, and the processing time can be shortened. is there.

Further, in an adaptive array antenna used in a radio communication system for service in an area by arranging a plurality of radio base stations for accommodating terminal stations, each direction of a group of base stations other than the base station other than its own base station. Alternatively, by controlling the antenna beam by adding a constraint that turns null to the remaining directions excluding the direction in which the base station communicates with the direction of the terminal with which the base station communicates is small, in some of the directions. Thus, the null constraint direction can be quickly determined, and the number of control processes during communication can be reduced.

In the present invention, a plurality of antenna elements and a high-frequency circuit connected to each antenna element are provided, and the phase of a local signal applied to a frequency conversion circuit in the high-frequency circuit is adjusted for each high-frequency circuit for each antenna element. In the adaptive array antenna, which uses a quadrature modulator that receives a local frequency signal and a control signal as a local signal phase shift circuit or a part thereof to be changed,
In the high-frequency circuit, by providing a coupler for branching a part of the signal from each antenna element and a quadrature demodulator for an individual element to which a signal from the coupler is input, even when the transmission rate is high. , And easy real-time reception becomes possible.

Further, according to the present invention, in an adaptive array antenna including a plurality of antenna elements, a high-frequency circuit connected to each antenna element, and a high-frequency synthesis circuit for synthesizing the outputs of the plurality of high-frequency circuits, a plurality of antenna elements, At least one first RSSI circuit for monitoring at least one signal level of an RF or IF signal, and a second RSSI circuit for monitoring a signal level of an RF or IF signal after combining signals from individual elements And at least (N-1) first signals that can change the relative levels of all RF or IF signals of each of the N individual elements.
Variable gain circuit, a second variable gain circuit capable of varying the signal level of an RF or IF signal after combining signals from the individual elements, a first RSSI circuit and a second RSSI
The first variable gain circuit and the second variable gain circuit are controlled based on the RSSI signal from the circuit so that the combined output signal level is controlled to a constant width and the high-frequency circuit for each individual element is not saturated. By providing a gain control circuit for controlling the variable gain circuit, the combined output signal level is controlled to a fixed width, and the high-frequency circuit for each individual element is controlled so as not to be saturated. Becomes possible.

In the present invention, a plurality of antenna elements, a high-frequency circuit connected to each antenna element, and a high-frequency distribution circuit for distributing an output to the plurality of high-frequency circuits are provided. Or an adaptive array antenna provided with a weight control circuit for weighting the phase, all the R elements of each of the N individual elements
At least (N-1) first variable gain circuits capable of varying the relative level of the F or IF signal, and second variable gain circuit elements capable of varying the signal level of the RF or IF signal before distribution to individual elements And controlling the effective radiated power in consideration of the directivity gain from the adaptive array antenna estimated from the output of the weight control circuit so as not to exceed a predetermined value, and a high-frequency circuit element for each individual element. Is provided with a gain control circuit that controls the first variable gain circuit and the second variable gain circuit so that the effective radiated power from the adaptive array antenna in consideration of the directivity gain is reduced. It is possible to perform control so as not to exceed a predetermined value and to prevent the high-frequency circuit element for each individual element from being saturated.

[Brief description of the drawings]

FIG. 1 is a block diagram showing a configuration of an adaptive array antenna as a basic concept of the present invention.

FIG. 2 is a block diagram illustrating a configuration of an adaptive array antenna according to the first embodiment of the present invention.

FIG. 3 is a flowchart illustrating an operation of the adaptive array antenna according to the first embodiment of the present invention.

FIG. 4 is a block diagram illustrating a configuration of an adaptive array antenna according to a second embodiment of the present invention.

FIG. 5 is a block diagram illustrating a configuration of an error detection unit in an adaptive array antenna according to a second embodiment of the present invention.

FIG. 6 is a flowchart illustrating an operation of the adaptive array antenna according to the second embodiment of the present invention.

FIG. 7 is a block diagram illustrating a configuration of an adaptive array antenna according to a third embodiment of the present invention.

FIG. 8 is a flowchart illustrating an operation of the adaptive array antenna according to the third embodiment of the present invention.

FIG. 9 is a characteristic diagram illustrating a change in reception intensity with respect to a phase shift amount in the adaptive array antenna according to the third embodiment of the present invention.

FIG. 10 is a flowchart illustrating an operation of the adaptive array antenna according to the fourth embodiment of the present invention.

FIG. 11 is a block diagram illustrating a configuration of an adaptive array antenna according to a fifth embodiment of the present invention.

FIG. 12 is a flowchart illustrating an operation of the adaptive array antenna according to the fifth embodiment of the present invention.

FIG. 13 is a characteristic diagram illustrating a change in reception intensity with respect to a phase shift amount in the adaptive array antenna according to the fifth embodiment of the present invention.

FIG. 14 is a block diagram showing a configuration of an adaptive array antenna according to a sixth embodiment of the present invention.

FIG. 15 is a flowchart illustrating an operation of the adaptive array antenna according to the sixth embodiment of the present invention.

FIG. 16 is a block diagram illustrating a configuration of an adaptive array antenna according to a seventh embodiment of the present invention.

FIG. 17 is a flowchart illustrating an operation of the adaptive array antenna according to the seventh embodiment of the present invention.

FIG. 18 is a flowchart showing an operation of the adaptive array antenna according to the eighth embodiment of the present invention.

FIG. 19 is a block diagram illustrating a configuration of an adaptive array antenna according to a ninth embodiment of the present invention.

FIG. 20 is a flowchart showing an operation of the adaptive array antenna according to the ninth embodiment of the present invention.

FIG. 21 is a block diagram illustrating a configuration of an adaptive array antenna according to a tenth embodiment of the present invention.

FIG. 22 is a flowchart showing an operation of the adaptive array antenna according to the tenth embodiment of the present invention.

FIG. 23 is a block diagram illustrating a configuration of an adaptive array antenna according to an eleventh embodiment of the present invention.

FIG. 24 is a diagram illustrating a case where the antenna directivity of a terminal communicating with another base station is not directed to its own base station and there is no interference in the eleventh embodiment.

FIG. 25 is a diagram illustrating a case where the antenna directivity of a terminal communicating with another base station is directed to its own base station and interference occurs in the eleventh embodiment.

FIG. 26 is a diagram illustrating a relationship between an antenna beam width and a threshold value of a difference between directions in the eleventh embodiment.

FIG. 27 is a diagram illustrating an example of a frame configuration of a PTMP system.

FIG. 28 is a block diagram illustrating a configuration of an adaptive array antenna according to a twelfth embodiment of the present invention.

FIG. 29 is a diagram illustrating an example of a control method when using an adaptive array antenna according to a twelfth embodiment of the present invention.

FIG. 30 is a block diagram showing a configuration for compensating for a phase difference and an amplitude difference in the twelfth embodiment.

FIG. 31 is a diagram illustrating a configuration of the adaptive array antenna according to the twelfth embodiment, which is different from that of FIG. 30;

FIG. 32 is a block diagram illustrating a configuration of an adaptive array antenna according to a thirteenth embodiment of the present invention.

FIG. 33 is a diagram illustrating an example of a control method when using the adaptive array antenna according to the thirteenth embodiment of the present invention.

FIG. 34 is a block diagram illustrating a configuration of an adaptive array antenna according to a fourteenth embodiment of the present invention.

FIG. 35 is a configuration diagram showing real number weighting means in a fourteenth embodiment of the present invention.

FIG. 36 is a flowchart showing an operation of the adaptive array antenna according to the fourteenth embodiment of the present invention.

FIG. 37 is an explanatory diagram of a general PTMP-type WLL.

FIG. 38 is a diagram illustrating an arrival state of an interference wave when a sector antenna having a half value angle of 120 degrees is used.

FIG. 39 is a diagram showing an arrival state of an interference wave in the case of conventional four-cell frequency repetition.

FIG. 40 is a diagram showing a conventional DBF-type adaptive antenna.

FIG. 41 is a diagram showing a conventional adaptive antenna in which an AGC variable gain amplifier is inserted into a combined output.

FIG. 42 is a diagram showing a conventional transmission adaptive antenna in which a variable gain amplifier is inserted before distribution.

FIG. 43 is a diagram showing a conventional adaptive transmitting antenna in which a plurality of variable gain amplifiers are inserted after distribution.

[Explanation of symbols]

 11-1n antenna element 3 phase shift amount control means 311 first signal strength storage means 321 second signal strength storage means 331 phase shift amount calculation means 341-34n first phase shift amount storage means 351-35n second Phase shift amount storage means 361-36n Third phase shift amount storage means 371-37n Phase shift amount setting means 381-38n Initial value storage means 41-4n Variable phase shifter 5 Combiner 71 Signal strength detection means 8 Update stop means 91 Reference signal generation means 92 Error detection means 7 Real number weight control means 711-71n Initial value storage means 721-72n Real number weight storage means 731-73n Real number weight setting means 741-74n Real number weight calculation means 75 Update stop means

 ────────────────────────────────────────────────── ─── Continuing from the front page (72) Inventor Hiroki Shoki 1 Tokoba, Komukai Toshiba-cho, Saiwai-ku, Kawasaki-shi, Kanagawa F-term (Reference) 5J021 AA05 AA06 AA11 DB01 DB03 DB05 EA05 EA07 EA08 FA06 FA12 FA14 FA15 FA17 FA25 FA30 FA32 GA01 GA06 HA06 HA10 JA07 5K059 CC03 DD32 DD37

Claims (21)

[Claims] A plurality of antenna elements, a plurality of phase shift means for controlling a phase of a received signal received by these antenna elements according to a set phase shift amount, and a phase control by the phase shift means. Combining means for combining the received signals;
A signal strength detecting means for detecting the strength of the received signal combined by the combining means; and a phase shift amount calculated based on the strength of the received signal detected by the signal strength detecting means. An adaptive array antenna comprising: a phase shift amount control unit configured to set each of the phase shift units; wherein the phase shift amount control unit is configured to output various signal intensities and a plurality of phase shift amounts output from the signal intensity detection unit. A phase shift amount calculating unit that calculates and outputs a phase shift amount in the plurality of phase shift units in a plurality of cycles based on the plurality of phase shift units; an initial value storage unit that stores initial values of the plurality of phase shift units; A first phase shift amount calculated by the phase shift amount calculating means as to be set for each of the plurality of phase shift means based on the respective initial values stored in the storage means is stored. A first phase shift amount storage unit that stores the second phase shift amount in the plurality of phase shift units calculated by the calculation unit so as to increase the first phase shift amount by a predetermined angle. A second phase shift amount storage unit, and a third phase shift amount stored in the plurality of phase shift units calculated by the calculation unit so as to decrease the first phase shift amount by a predetermined angle. 3 phase shift amount storage means, and the plurality of phase shift amounts calculated by the phase shift amount calculation means based on the phase shift amounts stored in any one of the first to third phase shift amount storage means. A plurality of phase shift amount setting units each for setting a phase shift amount of the phase unit; and a first phase shift amount detected by the signal intensity detection unit in a state where the second phase shift amount is set in the plurality of phase shift units. First signal strength storage means for storing the signal strength of A second signal strength storage unit that stores a second signal strength detected by the signal strength detection unit in a state where the third phase shift amount is set, wherein the phase shift amount calculation unit includes: The first signal strength and the second
When a difference between the signal intensities is input, a new phase shift amount obtained by increasing the first phase shift amount by a value proportional to the difference is calculated and input to the first phase shift amount. An adaptive array antenna, comprising: updating a plurality of cycles until the difference disappears, and stopping the operation of the phase shift amount control means based on a predetermined condition. 2. The initial value storage means stores initial values .PHI.1 (0) to .PHI.n (0) of the phase shift amount, respectively, when the phase shift amount control means operates for the first time. Φn
(0) represents the values of Φ1 (k) to Φ1 (k) of the first phase shift amount storage
Φn (k), and the first phase shift amount storage means sets the phase shift amounts Φ1 (k) to Φn (k) respectively set in the phase shift means.
(N is the number of antenna elements, and k is the number of updates of the phase shift amount), and the second phase shift amount storage means stores the Φ1 (k) 〜
Each of the phase shift amounts Φ1 ′ (k) to Φn ′ (k) calculated by increasing Φn (k) by a predetermined angle is stored, and the third phase shift amount storage unit stores the phase shift amounts Φ1 (k) to Φn (k). Phase shift amount Φ1 ″ calculated by decreasing Φn (k) by a predetermined angle.
(K) to Φn ″ (k), wherein the phase shift amount setting means is any one of the first phase shift amount storage means, the second phase shift amount storage means, and the third phase shift amount storage means. Or setting the phase shift amount stored in one of the plurality of phase shift means in each of the plurality of phase shift means,
The first signal strength storage means stores a signal Φ1
(K), Φ2 (k), ..., Φi-1 (k), Φi '
(K), Φi + 1 (k),..., Φn (k) (1 ≦ i ≦
In the state where n) has been set, the signal strength Pi 'as the first signal strength detected by the signal strength detection means is stored, and the second signal strength storage means stores Φ1 in the phase shift means. (K), Φ2 (k), ..., Φi-1 (k),
Φn + 1 (k),..., Φn (k) are set, and the signal strength Pi ″ as the second signal strength detected by the signal strength detection means is stored. The phase amount calculating means calculates a new phase shift amount Φi (k + 1) obtained by increasing Φi (k) by a value proportional to the difference between the signal intensities Pi ′ and Pi ″, and calculates the calculated phase shift amount. Is input to Φi (k) of the first phase shift amount storage means,
2. The adaptive array antenna according to claim 1, wherein the update stop unit stops the operation after repeating the operation of the phase shift amount control unit a predetermined number of times. 3. A plurality of antenna elements, phase shift means for controlling a phase of a received signal received by these antenna elements in accordance with each set phase shift amount, and a received signal phase-controlled by the phase shift means. Synthesizing means, a reference signal generating means for generating a reference signal, and an error detecting means for outputting a difference between the received signal synthesized by the synthesizing means and the reference signal generated by the reference signal generating means, Error signal strength detection means for detecting the signal strength of the error signal detected by the error detection means; and a phase shift amount calculated and calculated based on the signal strength of the error signal detected by the error signal strength detection means. And a phase shift amount control means for setting the phase shift amount to each of the plurality of phase shift means, wherein the phase shift amount control means comprises: A phase shift amount calculating unit that calculates and outputs a plurality of cycles of the phase shift amount in the plurality of phase shift units based on various signal intensities output from the signal strength detection unit and a plurality of phase shift amounts; Initial value storage means for storing respective initial values of the phase means; and setting of each of the plurality of phase shift means by the phase shift amount calculating means based on the respective initial values stored in the initial value storage means. First phase shift amount storage means for storing a first phase shift amount calculated as an operation to be performed; and a plurality of the plurality of phase shifts calculated by the calculation means to increase the first phase shift amount by a predetermined angle. A second phase shift amount storage unit that stores a second phase shift amount in the phase shift unit; and the plurality of the plurality of phase shift amounts calculated by the calculation unit so as to decrease the first phase shift amount by a predetermined angle. Third in phase shifting means A third phase shift amount storage unit for storing a phase amount; and a phase shift amount calculation unit based on the phase shift amount stored in any one of the first to third phase shift amount storage units. A plurality of phase shift amount setting means for respectively setting the phase shift amounts of the plurality of phase shift means, and detecting the error signal intensity in a state where the second phase shift amount is set in the plurality of phase shift means. First error signal strength storage means for storing the first error signal strength detected by the means; and the error signal strength detection means in a state where the third phase shift amount is set in the plurality of phase shift means. And a second error signal strength storage means for storing a second error signal strength detected by the following equation: wherein the phase shift amount calculating means includes a difference between the first error signal strength and the second error signal strength. Increases the first phase shift amount by a value proportional to the difference when The calculated new phase shift amount is input to the first phase shift amount, and a plurality of cycles of calculation are repeated until the difference disappears, and the operation of the phase shift amount control means is performed based on predetermined conditions. An adaptive array antenna comprising an update stopping means for stopping the antenna. 4. The first phase shift amount storage means stores phase shift amounts Φ1 (k) to Φn (k) (n is the number of antenna elements, and k is the number of phase shift amount updates) set in the phase shift means. ),
The second phase shift amount storage means stores the Φ1 (k) to Φn
(K) are respectively increased by a predetermined angle, and the phase shift amounts Φ1 ′ (k) to Φn ′ (k) calculated respectively are stored. The third phase shift amount storage means stores the Φ1 (k) to Φn (K) is reduced by a predetermined angle, and the phase shift amount Φ1 ″ (k)-
.PHI.n "(k), and the phase shift amount setting means is provided in any one of the first phase shift amount storage means, the second phase shift amount storage means, and the third phase shift amount storage means. The stored phase shift amount is set for each of the phase shift means, and the first error signal strength storage means stores the phase shift means with Φ1 (k) and Φ1 (k), respectively.
2 (k),..., Φi−1 (k), Φi ′ (k), Φi +
1 (k),..., Φn (k) (1 ≦ i ≦ n) are set, and the first error signal strength Qi ′ detected by the error signal strength detection means is stored, and the second error signal strength Qi ′ is stored. The signal intensity storage means of Φ1 (k) and Φ2
(K),..., Φi−1 (k), Φi ″ (k), Φi + 1
.., Φn (k) are set, the second error signal strength Qi ″ detected by the error signal strength detection means is stored, and the phase shift amount calculation means stores A new phase shift amount Φ obtained by increasing Φi (k) by a value proportional to the difference between the second error signal strengths Qi ′ and Qi ″.
i (k + 1) is calculated and Φ of the first phase shift amount storage means is calculated.
i (k), the initial value storage means stores initial values of the phase shift amounts Φ1 (0) to Φn (0), respectively, and the phase shift amount when the phase shift amount control means operates for the first time. 4. The adaptive array antenna according to claim 3, wherein initial values Φ1 (0) to Φn (0) are input to Φ1 (k) to Φn (k) of the first phase shift amount storage means, respectively. . 5. A plurality of antenna elements, a plurality of signal blocking means for passing or blocking each of received signals received by these antenna elements to a subsequent circuit in accordance with a control signal input from the outside, and a plurality of signal blocking means. A plurality of phase shifting means for controlling the phase of the received signal passing through the means in accordance with the set phase shift amounts; a combining means for combining the received signals phase-controlled by the phase shifting means; Signal strength detecting means for detecting the signal strength; and a phase shifter for calculating a phase shift amount based on the strength of the received signal detected by the signal strength detector and setting the calculated phase shift amount to the phase shifter. An adaptive array antenna comprising: a phase amount control unit, wherein the phase shift amount control unit sets any two of the signal cutoff units to a pass side and sets the rest to a cutoff side. Signal selection means for selectively switching the plurality of signal cutoff means, and the signal strength detection means in a state in which any two of the plurality of signal cutoff means are set to the passing side and the rest are set to the cutoff side Phase shift amount calculating means for calculating a phase shift amount at which the strength (P) is minimum based on the strength (P) of the received signal detected by An adaptive array antenna, comprising: a phase shift amount setting unit configured to set a phase shift amount calculated by the phase shift amount calculation unit to a unit connected to a signal blocking unit set on a side of the adaptive array antenna. 6. A plurality of antenna elements, a plurality of signal blocking means for passing or blocking each of signals received by these antenna elements to a subsequent circuit in accordance with a control signal input from the outside, and a plurality of signal blocking means. A plurality of phase shifting means for controlling the phase of the received signal passing through the means in accordance with the set phase shift amounts; a combining means for combining the received signals phase-controlled by the phase shifting means; Signal strength detecting means for detecting the signal strength; and a phase shifter for calculating a phase shift amount based on the strength of the received signal detected by the signal strength detector and setting the calculated phase shift amount to the phase shifter. An adaptive array antenna comprising: First signal strength storage means for storing a first strength (P1) of a signal; and second strength (P2) of a received signal detected by the signal strength detection means in the presence of an interference wave. A second signal strength storage means, a signal selection means for setting any two of the signal cutoff means on the passing side, and setting the remaining signal on the cutoff side; and any two of the signal cutoff means on the passage side The first strength (P) is set in a state in which the first strength (P
1) and the second intensity (P2), the difference (P
1-P2), a phase shift amount calculating means for calculating a phase shift amount that minimizes; and one of the plurality of phase shift means connected to a signal blocking means set on the passing side by the signal selecting means, An adaptive array antenna, comprising: a phase shift amount setting unit that sets a phase shift amount calculated by the phase shift amount calculation unit. 7. A distributing means for distributing a transmission signal, a plurality of phase shifting means for controlling the phase of the transmission signal distributed by the distributing means in accordance with a set phase shift amount, respectively, A plurality of signal blocking means for passing or blocking each of the controlled transmission signals to a subsequent circuit according to a control signal input from the outside, an antenna element for transmitting a transmission signal passing through these signal blocking means, Phase shift amount control means for calculating the phase shift amount based on the information and setting the calculated phase shift amount to each of the phase shift means. A signal strength detecting means for detecting a signal strength of a received signal received at the partner station is provided, and the phase shift amount controlling means sets any two of the signal blocking means to a passing side. A signal selecting means for setting the rest on the cut-off side, and any two of the plurality of signal cut-off means being set on the pass side and the remaining being set on the cut-off side, detected by the signal strength detecting means. Phase shift amount calculating means for calculating a phase shift amount that minimizes the strength (P) of the received signal based on the strength (P) of the received signal; An adaptive array antenna, further comprising: a phase shift amount setting unit configured to set a phase shift amount calculated by the phase shift amount calculation unit to a unit connected to the signal blocking unit. 8. A distributing means for distributing a transmission signal, a plurality of phase shifting means for controlling the phase of the transmission signal distributed by the distributing means in accordance with each set phase shift amount, A plurality of signal blocking means for passing or blocking each of the controlled transmission signals to a subsequent circuit according to a control signal input from the outside, an antenna element for transmitting a transmission signal passing through these signal blocking means, Phase shift amount control means for calculating the phase shift amount based on the information and setting the calculated phase shift amount to each of the phase shift means. A signal strength detecting means for detecting a signal strength of a received signal received at the partner station is provided, and the phase shift amount controlling means transmits a transmission signal by the antenna element. A first signal strength storing means for storing a first strength (P1) of the received signal detected by the signal strength detecting means; and a signal strength in a state where a transmission signal is not transmitted by the antenna element. A second signal strength storage means for storing a second strength (P2) of the received signal detected by the detection means; and any two of the plurality of signal cutoff means are set to the pass side, and the rest are set to the cut side. And the first intensity (P1) and the second intensity (in a state in which any two of the plurality of signal blocking units are set to the passing side and the rest are set to the blocking side). P2), a phase shift amount calculating unit that calculates a phase shift amount that minimizes the difference (P1−P2), and a signal set on the passing side by the signal selecting unit among the plurality of phase shift units. The transfer to the one connected to the blocking means Adaptive array antenna characterized in that it comprises a phase shift amount setting means for setting a phase shift amount calculated by the amount computing means. 9. A plurality of antenna elements; a plurality of real number weighting means for weighting a reception signal received by the plurality of antenna elements with a set real number weight; and a reception weighted by the plurality of real number weighting means. A plurality of individual element signal strength detecting means for detecting signal strength as individual element signal strengths; a combining means for combining received signals weighted by the plurality of real number weighting means; a received signal combined by the combining means Signal strength detecting means for detecting the strength of the composite signal strength as a composite signal strength; and a change amount of the composite signal strength when the sign of a real weight set in at least one of the plurality of weighting means is changed, and The real weight is calculated based on the individual element signal strength, and the calculated real weight is Adaptive array antenna characterized in that it comprises a real number weight control means is repeated a plurality of cycles a process of setting each to a plurality of real number weighting means. 10. The real number weight control means includes a plurality of initial values storing initial values W_1 (0) to W_n (0) (n is the number of antenna elements) of real number weights set in the plurality of real number weighting means. When the memory means and the real number weight control means operate for the first time, these real number weights W_1 (k) to W_n (0) are to be set in each of the plurality of real number weighting means.
_N (k) (k is the number of updates of real number weights), and a plurality of real number weight storage means, and W_1 stored in the plurality of real number weight storage means
Based on (k) to W_n (k), W_i (k) or -W_
a plurality of real number weight setting means for setting any one of i (k) (1≤i≤n); and W_1 (k) to W_
In the state where n (k) is set, the combined signal strength Py (k) detected by the combined signal strength detection means is input,
Similarly, each of the plurality of real number weighting means W_1
In the state where (k) to W_n (k) are set, the individual element signal intensities Px_1 (k) to Pxn (k) respectively detected by the plurality of individual element signal intensity detecting means are input, respectively, and W_1 each for the real number weighting means
(K), W_2 (k), ..., W_i-1 (k), W_i
(K), W_i + 1 (k),..., W_n (k) (1 ≦ i
≦ n), the combined signal strength Py_i (k) (1 ≦ 1) detected by the combined signal strength detection means.
i ≦ n), a new real weight W_i (k + 1) = W_i (k) + a ^* [Px_i
(K) + {Py (k) -Py_i (k)} / 4] / W_
i (k) (a is a constant) and (1 ≦ i ≦ n) are calculated, and W_1 (k) to W_1 (k) of the plurality of real number weight storage means are calculated.
The adaptive array antenna according to claim 9, further comprising: a real number weight calculating unit that inputs the number to W_n (k). 11. The adaptive array antenna according to claim 9, wherein said real number weight control means includes update stop means for stopping its operation based on a predetermined condition. 12. The update stopping means repeats the operation of the real number weight control means a predetermined number of times.
The adaptive array antenna according to claim 11, wherein the operation is stopped. 13. The real number weight control means stops the operation of the real number weight control means when the spice of the real number weight set in the real number weighting means falls below a predetermined value. Item 12. An adaptive array antenna according to item 11. 14. The adaptive array antenna according to claim 9, wherein each of the plurality of antenna elements is a directional antenna. 15. The adaptive array antenna according to claim 9, wherein each of the plurality of antenna elements is an array antenna. 16. An adaptive array antenna used in a radio communication system for service in an area by arranging a plurality of radio base stations for accommodating a terminal station, wherein each direction of a group of base stations other than its own base station is different. Alternatively, control of the antenna beam by adding a constraint for pointing null to the remaining directions excluding those having a small difference from the direction of the terminal with which the own base station communicates, in some of the directions. An adaptive array antenna characterized by the following. 17. A high-frequency circuit connected to a plurality of antenna elements and said antenna element, and a local signal transfer for changing a phase of a local signal applied to a frequency conversion circuit in said high-frequency circuit for each high-frequency circuit for said antenna element. A quadrature modulator that receives a local frequency signal and a control signal as at least a part of a phase circuit, and an adaptive array antenna comprising: a part of a signal from the antenna element in the high-frequency circuit. An adaptive array antenna, comprising: a coupler; and a quadrature demodulator for an individual element to which a signal from the coupler is input. 18. A phase / amplitude comparison circuit for receiving a demodulated signal from a quadrature demodulator for an individual element, comparing the phase and amplitude of each input signal and detecting a difference therebetween, Based on the comparison result, at least the passing phase characteristic of the component provided at the subsequent stage from the coupler that branches the detected difference and the length of the antenna feed line and other wiring lengths and a part of the signal from each antenna element is provided. Phase deviation compensation control means for controlling an output signal of a phase control signal output circuit so as to compensate for a phase deviation caused by the difference; and quadrature modulation of a local signal phase shift circuit based on at least an output of the phase deviation compensation control means. 18. The adaptive array antenna according to claim 17, further comprising: a phase shift control signal output circuit that outputs a control signal to a device. 19. An adaptive array antenna comprising a plurality of antenna elements, a high-frequency circuit connected to each antenna element, and a high-frequency synthesis circuit for synthesizing the outputs of the plurality of high-frequency circuits. Alternatively, at least one first RSSI circuit that monitors at least one signal level of the IF signal, and a second RSSI circuit that monitors the signal level of the RF or IF signal after combining the signals from the individual elements. At least (N-1) first variable gain circuits capable of varying the relative levels of all the RF or IF signals of each of the N individual elements; and the RF or IF signals after combining the signals from the individual elements. Variable gain circuit capable of varying the signal level of the first and second RSSI circuits, and RSS from the first and second RSSI circuits.
The first variable gain circuit and the second variable gain are controlled based on the I signal so that the combined output signal level is controlled to a fixed width and the high-frequency circuit element for each individual element is not saturated. An adaptive array antenna, comprising: a gain control circuit that controls the circuit. 20. A storage means for storing a certain number of past output values of said RSSI circuit, and a deviation between an input value and a certain number of output values stored in said storage means exceeding a certain value. 20. The adaptive array antenna according to claim 19, further comprising: gain changing means for outputting a gain changing command from the gain control circuit to the first variable gain circuit or the second variable gain circuit only in a case where the gain is changed. 21. A plurality of antenna elements, a high-frequency circuit connected to the antenna elements, and a high-frequency distribution circuit for distributing an output to the plurality of high-frequency circuits, wherein the high-frequency circuit has an amplitude or phase weight for each antenna element. An adaptive array antenna having a weight control circuit for performing the assignment, wherein at least (N-1) th number of the radio frequency signals (RF) or intermediate frequency signals (IF) of all the N individual elements are made variable in relative level. A variable gain circuit, and a second variable gain circuit for varying a signal level of a radio frequency signal (RF) or an intermediate frequency signal (IF) before distribution to individual elements.
And a variable gain circuit for controlling the effective radiated power in consideration of the directivity gain from the adaptive array antenna estimated from the output of the weight control circuit so as not to exceed a predetermined value, and a high frequency for each individual element. An adaptive array antenna, comprising: a gain control circuit that controls the first variable gain circuit and the second variable gain circuit so that the circuit is not saturated.