GB2138500A - Dwell control for an i c engine spark ignition system - Google Patents
Dwell control for an i c engine spark ignition system Download PDFInfo
- Publication number
- GB2138500A GB2138500A GB08407455A GB8407455A GB2138500A GB 2138500 A GB2138500 A GB 2138500A GB 08407455 A GB08407455 A GB 08407455A GB 8407455 A GB8407455 A GB 8407455A GB 2138500 A GB2138500 A GB 2138500A
- Authority
- GB
- United Kingdom
- Prior art keywords
- transistor
- base
- control
- output
- collector
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Classifications
-
- F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
- F02—COMBUSTION ENGINES; HOT-GAS OR COMBUSTION-PRODUCT ENGINE PLANTS
- F02P—IGNITION, OTHER THAN COMPRESSION IGNITION, FOR INTERNAL-COMBUSTION ENGINES; TESTING OF IGNITION TIMING IN COMPRESSION-IGNITION ENGINES
- F02P7/00—Arrangements of distributors, circuit-makers or -breakers, e.g. of distributor and circuit-breaker combinations or pick-up devices
- F02P7/06—Arrangements of distributors, circuit-makers or -breakers, e.g. of distributor and circuit-breaker combinations or pick-up devices of circuit-makers or -breakers, or pick-up devices adapted to sense particular points of the timing cycle
- F02P7/067—Electromagnetic pick-up devices, e.g. providing induced current in a coil
- F02P7/0675—Electromagnetic pick-up devices, e.g. providing induced current in a coil with variable reluctance, e.g. depending on the shape of a tooth
-
- F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
- F02—COMBUSTION ENGINES; HOT-GAS OR COMBUSTION-PRODUCT ENGINE PLANTS
- F02P—IGNITION, OTHER THAN COMPRESSION IGNITION, FOR INTERNAL-COMBUSTION ENGINES; TESTING OF IGNITION TIMING IN COMPRESSION-IGNITION ENGINES
- F02P3/00—Other installations
- F02P3/02—Other installations having inductive energy storage, e.g. arrangements of induction coils
- F02P3/04—Layout of circuits
- F02P3/045—Layout of circuits for control of the dwell or anti dwell time
- F02P3/0453—Opening or closing the primary coil circuit with semiconductor devices
-
- F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
- F02—COMBUSTION ENGINES; HOT-GAS OR COMBUSTION-PRODUCT ENGINE PLANTS
- F02P—IGNITION, OTHER THAN COMPRESSION IGNITION, FOR INTERNAL-COMBUSTION ENGINES; TESTING OF IGNITION TIMING IN COMPRESSION-IGNITION ENGINES
- F02P3/00—Other installations
- F02P3/02—Other installations having inductive energy storage, e.g. arrangements of induction coils
- F02P3/04—Layout of circuits
- F02P3/05—Layout of circuits for control of the magnitude of the current in the ignition coil
- F02P3/051—Opening or closing the primary coil circuit with semiconductor devices
Description
1
SPECIFICATION
Dwell control for an 1. C. engine spark ignition system This invention relates to a dwel 1 control for an i.c. engine spark ignition system.
It has al ready been proposed to control spark ignition using a variable reluctance triggering transducer. The rapid zero crossing transition which occu rs in the output of voltage of such a transducer is excel lent fortriggering ignition. Various attempts have been made, in the past, to use the same transducer for determining when the coil current of a coil type ignition system is caused to commence. Such dwell control was obtained by superimposing a bias voltage on the transducer output waveform and comparing the thus biased waveform with a threshold. Problems were found, howeverwith controlling the dwell period in accordancewith engine speed so as to obtain a sufficient coil current on time at 85 high speed whilst obtaining economical operation at lowspeeds.
It is an object of the present invention to overcome these disadvantages of the prior dwell control arrangements.
According to the invention,there is provided an internal combustion engine spark ignition control comprising a variable reluctance transducer driven by the engine and providing an output having zero transitions coinciding with the desired instants of ignition, an integrating circuitto which the transducer output is connected, means for applying a variable preconditioning bias to the output of said integrating circuit, an ignition coil drive circuit connected to said integrating circuit and operating to commence coil currentflowwhen the integrating circuit goes into a saturated condition at an instant dependent on said variable bias means and to interrupt coil currentflow to produce a sparkwhen said integrating circuit comes out of said saturated condition on reversal of the polarity of the transducer output and means sensitive to the ratio of thetime in each cycle during which the coil current is adequateto produce a sparkto the ignition cycle duration, to control said variable bias meansto cause said ratio to take up a desired value. 110 Preferably, the ignition coil drive circuit includes coil current regulating meanswhich operates in each ignition cycleto limitthe coil currentto a prede temined level. In this case said ratio sensitive means may be connected so as to be controlled by said current regulating means.
An example of the invention is shown in the accompanying drawings in which:
Figure 1 is a fragmentary perspective view of a variable reluctance transducer intended for use in a control in accordance with the invention; Figure 2 is the circuit diagram of the control; Figure 3 is a set of graphs showing voltage waveforms at points A, Band E in Figure 2 and current waveforms at points C and D therein attwo different 125 enginespeeds; Figure 4 is a set of graphs showing waveforms at pointsA, B, C and E ata very lowenginespeed and on a different scale from Figure 3, and Figure 5 is afragmentary perspective view of 130 GB 2 138 500 A 1 anotherform of variable reluctance transducer.
Referring firstlyto Figure 1, the transducer shown is intended to be incorporated in a conventional ignition distributor incorporating convention speed and vacuum advance mechanisms in place of the contact set normally installed. The transducer includes a drum 10 of ferromagnetic material for mounting on the distributor shaft. This drum 10 hasfour equally spaced axially extending ribs 11 on its outer curved surface 1 Oa and also fourtriangular raised surface portions 12 on the surface 1 Oa between the ribs. The drum 10 coacts with a pick-up having an elongated pole piece 13 and an encapsulated winding 14 surrounding the pole piece. The pick-up is mounted on a bracket 15 which, in use, is mounted on the timing plate of the distributor, iethe part which is turned about the distributor axis bythe vacuum advance mechanism. A magnetic circuit is formed by the drum 10, the pole piece 13,the bracket 15, the timing plate and the shaft, a magnet, not shown, being included in this circuit as is usual in variable reluctance transducers.
With a transducer as described above, the output of the winding 14 depends on the rate of change of the flux in the magnetic circuit. Thus, as the triangular portion 12 is passing the pole piece, the flux is increasing linearly and a relatively low level constant voltage is output. As a rib reaches the pole piece the voltage rises suddenlyto a positive peak and then falls very quicklyto a negative peak, whereafter the waveform repeats. The voltage levels are substantially directly proportional to engine speed.
As shown in Figure 2, the circuit of the control includes a resistor R, and a diode D, connected in series across the winding 14, one end of the winding and the anode of the diode being grounded and the coil being arranged so that the diode D, conducts during the aforementioned negative peaks of the output waveform. A diode connected npn transistor Q, has its collector connected to the cathode of diode D, and its base and emitter connected to the base of a npn transistor Q2 which forms the input of an active integrating circuit.
A resistor R2connectsthe cathode of diode D, to the base of transistor Q2 which is also connected by a resistor R3 to a +5V rail 16. The collector of transistor Q2 is connected to the collector of a pnp transistor G3 which has its emitter connected by a resistor R4tO the rail 16. Transistor Q3 acts as a constant current collector load fortransistor Q2. The emitter of transis- torQ2isconnectedtoa ground rail 17 bya resistorR5 and is also connected bya resistor R6tO the sliderof a potentiometer R7 connected between the rail 16 and the ground rail 17. The collector of transistor Q2 is connected by a resistor R8to the base of a npn transistor Q4which provides the output of the integrating circuit. A resistor R9 connects the emitter of transistor Q3tO the rail 17 and a feedback path, comprising a capacitor Cl and a resistor R,() in series, connectsthe emitter of transistor Q4tO the base of transistor Q2. The collector of transistor Q4 is connected by two resistors R,,, R12 in seriestothe rail 16.
When the output voltage of the winding is positive, the integrating circuit acts as a normal active integrator. The transistor Q, is nonconductive so that the time constant of the integrator is detemined by 2 GB 2 138 500 A 2 resistor R2 and capacitor Cl. Thus the relatively low cc nstant voltage portion of the output waveform of thewinding 14 causes the voltage atthe emitter of transistorQ4to ramp downwardlyata constant rate so asto maintain a -virtual earth- atthe base of transistor Q2. The positive peakof theoutputwave form would causethe emittervoltage oftransistor Q4 tofall more rapidly brieflyif the transistor Q4 were not alreadyturned off, i.e. if the integrating circuitwere not already saturated. The circuitvalues are, however, 75 chosento ensurethatthe integrating circuitdoes saturate and the transistor Q4doesturn off in each cycle. When the output of the winding swings negatively, thetransistor Q4turns on very rapidly.
Transistor(I1 becomes conductive so that the input impedance of the integrating circuit becomes very low and its time constant becomes very short.
Acircuit is provided for limiting the voltage to which the base of transistor Q4 can rise when itturns on as mentioned above. This circuit comprises a pnp transistor Q5 having its base connected by a resistor R13tO one side of a capacitor C2the other side of which is grounded to rail 17. The emitter of the transistor Q5 is connected to the base of thetransistor Q4 and its collector is connected to the base of an npn transistor 90 Q6 which has its emitter connected to the base of the transistor Q2. The collector of thetransistor Q6 is connected bya resistor R14tO the emitter of transistor G5 and by a resistor R15to the emitter of an npn transistor C17. The collector of transistor Q7 is con nectedto the +5V rail 16 and its base is connected to the base of the transistor Q4. This circuit acts to clamp the base of the transistor Q4 at a maximum voltage one diode drop above the voltage on capacitor C2, and does this in a manner such that the clamping circuit turns on progressively and avoids unwanted parasitic oscillations.
The collectorof the transistor Q4 is connected to the base of a pnptransistor (18which has its emitter/base in series with the resistor R,, and its collector connected by two resistors R13, R14 in series to the rail 17. An npn transistor Q9 has its base connected to the junction of the resistors R13, R14 and its emitter connected to rail 17. A resistor R15 connects the collector of the transistor Q9 to the rail 16. A capacitor C3 and a resistor R16 in series connectthe collector of the transistor Q9 to the cathode of a diode D2 having its anode connected to the base of the transistor 08. A resistor R17 is connected in parallel with the capacitor C3, but has a high ohms value compared with resistor R16. Transistors 08 and Q_9 operate as a regenerative switch, both transistors turning on when transistor Q4 turns on and turning off when transistor Q4turns off.
The transient positive feedback provided by capacitor C3 and resistor R16 ensures that once the switch Q8, Q9 120 turns on, it remains on fora minimum period irrespective of what happens to transistor Q4, the values of the components being chosen to make this period about 0.3mS. This arrangement provides in known manner immunity from interference caused by 125 the ignition spark.
The emitter of thetransistor Q8 is connected to the base of a prip transistor Glowhich has its emitter connected to rail 16 and its collector connected to the collector of an npn transistor Q,, by a resistor R18. The130 collector of the transistor Ql() is also connected to the base of a pnp transistor 012 which has its emitter connected by a resistor R19to the rail 16, The collector of transistor Q12 is connected by a resistor R20tO the anode of a diode D3the cathode of which is connected to the collector of transistor Q11. The base of transistor Q11 isconnected bya resistorR21 tothe rail 16 and by a resistor R22tO the collector and base of an npn transistor Q13 which has its emitter connected to the rail 17.
Theemitterof transistor Q12 is also connectedtothe base of a pnp transistor Q14 which has its emitter connectedtothe rail 16and its collector connected to the collectorof an npn transistor Q15which has its emitter connected bya resistor R23tO the rail 17.The base of the transistor Q15 is connectedtothe base and collectorof an npn transistor Q16 the emitterof which is connectedtothe rail 17,the collectorand base of transistor C116 being connected bytwo resistorsR24, and R25in seriestothe emitterof an npn transistor Q17 having its base and collector connected to the rail 16. The transistor Q16 biases the transistor Q15to operate as a constant current sink and transistor Q17 provides bias for transistor Q3, which has its base connectedto thejunction of resistors R24, R25- The collector of the transistor Q14 is connectedtothe base of an npn transistor Q18which has its collector connectedtothe rail 16 and its emitter connected by two resistors R26, R27 in seriestothe rail 17 and by a capacitorC4and a resistor R28 in seriestothe collector of the transistor Q12. An npn Darlington output transistorQ19 has its base connectedto thejunction of resistors R26 and R27, its emitter connected by a currentsensing resistor R29tO ground and its collector connected via the primarywinding of ignition coil 18 to a 12Vsupply (a vehicle battery) to which the rail 16 is also connected bya voltage regulator circuit 19. The emitterof thetransistor Q19 is connectedto the emitter of transistorQ11. To protect the transistor Q19 against transient over voltages caused by itsinductive load, a zenerdiode D4and a resistor R30 are connected in series between the collectorand base of transistor Q19. Furthermore a diode D5 has its anode connected to the emitter of transistor Q19 and its cathode connected to the collector thereof to protectthe transistor Q19 against reverse voltages.
Transistor Q, operates to provide an ignition coil current regulation function. The voltage at its base is fixed by the resistors R21, R22 (transistor Q, 3 providing temperature compensation forthe base emitterjunction of transistor Q11). When the transistors Q8 and Q9 turnoff, transistor Q10 turns off and transistors Q12, Q14, Q18 and Q19 tu rn on so that currentflow in the primary winding startsto build up. At this stage the transistorQ11 is hard on because the voltage across R29 is low.As coil current grows, the emitter voltage of transistorQ11 startsto rise untilthe pointis reached where the current passed bytransistorQ11 startsto fall,thereby reducingthe current in transistor Q14 until,whenthe primarycurrent reaches a predetermined level an equilibrium condition is established. The stabili of the equilibrium is assured bythe resistor R28 and the capacitor C4which reducethe gain of the current control loop at high frequencies, thereby preventing excitation of the coil resonances. Diode D3 1,41 z 3 GB 2 138 500 A 3 is includedto preventany possibility of base currentin transistorQ19 being sustained briefly bycharging of capacitor C4 when transistor Q12 turns off.
Thevoltageon capacitorC2 is determined bythe fraction of the cycletime for which the coil current isat Its regulated level.Tothisend a pnp transistor Q20 has its base connected to the junction oftwo resistors R31, R32connectedin serieswith one another across the transistor Q18 and its emitter connected to the rail 16.
The collector oftransistor Q20 isconnected bya resistor R33tOthe rail 17and bya resistor R34tO the emitterof a pnp transistor Q21 which has its base connected to the junction ofthe resistors R24and R25. Thecollectorof the transistor Q21 isconnected in turn to the collector of an npn transistor G22 which has its base connected to the collectorof transistor Q16 and its emitter connected bya resistorl135to rail 17.The collectors oftransistors Q21, G22 are connected to the base of transistor Q5 and the transistors G21 and Q22 providea constant current sink and a switchable constant current source for respectively dis-charging and chargingthe capacitor C2. The values arechosen so that transistor Q22 sinks aboutonetenth ofthe currentwhich transistor G21 passeswhen conducting.
Adiode Dr)connectsthe emitterof transistorG21 to the collector of transistor Qq, sothat no currentis passed bytransistorQ21 except when transistor Q20 ison whilsttransistorQ9 is off.Thisoccurs onlywhen current limit operation istaking place, itbeing appreciated that transistor Q20 always turns on when transistor Q9 is on.
When the closed loop dwell control is in equilibrium, the current limit operation will betaking place for onetenth of the ignition cycle time. The amount of charge received bythe capacitor C2 in each cycle will then be equal to thetotal amount lostvia thetransistor Q22 and the voltage on capacitor C2will remain substantially constant. The capacitance of capacitor C2 is such, in relation to the charge and discharge currents, thatonly a small fractional change in the voltage on capacitorC2 can occur in any cycle at engine running speeds. Should the fractional on time of thetransistor Q20 fall below one-tenth, the capacitor C2voltage will fall slowly and hencethe voltage to which the integrator is resetwill fall. Thus the transistor Q4Will turn off earlier in the integrating period to restorethe fractional on time to one tenth. Similarly,the voltage on capacitor C2 rises and reducesthe fractional on time should the latter become higherthan onetenth.
Each time transistors Q8 and Q9turn on the output transistor Q19turns off and a sparkis generated in the usual way.
Figure 3 shows voltage and current waveforms at the marked points. in Figure 2 and illustrates equilibrium conditionsattwo different steady speeds.
Figure 4 showswhat occurs at a very low speed. It will, be notedthat the level of signal from the transduceras the triangular portion 12 is passing the 60. pick-up is insignificant at such a speed. The integrator 125 output being pulled down in each cyle by the capacitor C2 discharging, until transistor Q2 saturates at which point transistor Q4 still conducts sufficiently to prevent the coil conducting.
The purpose of the resistor R13 in serieswith the 130 capacitor C2 iStO preventthe capacitorfrom being charged up by interference spikes.
Although the tranducer shown in Figure 1 utilises thetriangular portions 12 to provide linearly increas- ing flux, the same effect could be obtained in many otherways. For example, the parts of the drum 10 between the ribs 11 could be shaped to cause the radial gap to decrease at an appropriate rate, it being borne in mind that the flux varies inversely with the gap. The ribs 11 provide an increase in fluxjust before the spark is required, sufficientto ensure that coil current is always switched on in every cycle, even at cranking speed.
In the above embodiment,the resistor R1O in series with the capacitor Cl hereby compensates for transducer eddy current lag athighspeedsand hasno significant effect on the integrator outputcluring the integration period. If desired a highervalue resistor R1O may be employed and the integrator waveform then includes a downward step atthe instantwhen the transducer output becomes positive and atvery high speedsthis step can be larage enough to commence the coil currentflow.
In the alternativeform of transducershown in Figure 5, the unit is again intended to be incorporated in a conventional speed and vacuum advance ignition distributor. Instead of the drum 10 of Figure 1 the unit of Figure 5 utilises a cup-shaped member 110 on the distributor shaft. The cylindrical surface of member 110 is cut awayto providefourtapering portions 112 corresponding to the portions 12 of Figure 1. Ribs 111 are provided on this surface atthe wider ends of the tapering portions 112. The surface of the member 110 is notched between these ribs and the narrower ends of the tapering portions 112.
The "stator" of the unit of Figure 5 includes a magnetic disc 11 Von which four equally spaced axially extending fingers 113 forming pole pieces are provided and these fingers lie outside the member 110. This disc 113% connectedto thevacuum advance mechanism. A winding 114 is incorporated in the unit within the member 11 0,the magnetic circuit of the transducer comprising the disc 113', the fingers 113, the cylindrical surface of the member 110, the end surface of member 110 and the shaft. Itwill be noted that all four polefingers 113 form parallel paths in the magnetic circuit and these will be adjacent the ribs 111 simulataneously as the shaft rotates.
The construction shown in Figure 5 is extremely compact and can provide abetter electrical output than a unitas shown in Figure 1 of thesame size.
Resistor R19 may, if desired, be replaced bya constant current source transistor (pnp) controlled by the voltage across Q17, ie similarto the arrangement
Claims (15)
1. An internal combustion engine spark ignition control comprising a variable reluctance transducer driven by the engine and providing an output having zero transitions coinciding with the desired instants of ignition, an integrating circuit to which the transducer output is connected, means for applying a variable preconditioning bias tothe output of said integrating circuit, an ignition coil drive circuit connected to said 4 GB 2 138 500 A 4 integrating circuitand operating to commence coil currentflowwhen and becausethe integrating circuit goes into a saturated condition atan instantdependenton saidvariable bias means andto interruptcoil currentflowto produce a sparkwhen said integrating circitcomes out of said saturated condition on reversal of the polarity of thetransducer outputand means sensitive to the time fraction in each cycle duringwhich the coil current is adequateto producea sparktothe ignition cycle cluration,to control said variable bias meansto cause said fraction to take up a desiredvalue.
2. Acontroi as claimed in claim 1 in which said ignition coil drive circuit comprises coil current regulating means operating in each ignition cycle to limitthe coil currentto a predetermined level.
3. A control as claimed in claim 2 in which said fraction sensitive means is connected to said coil current regulating means for control thereby.
4. A control as claimed in claim 3 in which said fraction sensitive means comprises a signal storage device, charge and discharge path means associated with said signal storage device and incorporating switch means connected to said coil current regulating meansfor control thereby, wherebywhen the ratio of thetime in each cycle during which said coil current regulating means is in operation to the ignition cycle duration is at a desired value, the average signal stored in said signal storage device remains substan- tiallyconstant.
5. A control as claimed in claim 1 in which said integrating circuit includes an input stage having an input terminal connected by a resistorto said transducer output, an output stage coupled to said input stage, and a capacitor connected between an output terminal of the output stage and the input terminal of the input stage; said variable bias means comprising an active clamp circuit connected to provide feedback around the input stage under the control of said ratio sensitive means.
6. A control as claimed in claim 1 in which said integrating circuit comprises an inputtransistor having its base connected by a first resistor to said winding, its emitter connected to a pointwhich is held at a su bstantia 1 ly fixed potential and its collector 110 connected to a supply via load means, an output transistor, a second resistor connecting the collector of said inputtransistor to the base of said output transistor, said output transistor having its collector and emitter connected across the supply via respective collector load means and emitter load means, and a capacitor connecting the emitter of the output transistorto the base of the input transistor, said variable bias means comprising an active clamping circuit connected to said ratio sensitive means and operating to clamp the base of said output transistor at a maximum value determined by said ratio sensitive means.
7. A control as claimed in claim 6 in which said active clamp circuit comprises a firsttransistor having its base connected to said ratio sensitive circuit and its emitter connected to the base of said outputtransistor and a second transistor having its base connected to the collectorof said first transistor, its emitter con- nected to the base of the input transistor and its collector connected to current source means.
8. A control as claimed in claim 7 in which said current source means comprises a third transistor having its base connected to the base of the output transistor, its emitter connected by resistor means to the collector of the second transistor and its collector connected to said supply, further resistor means connecting the collector of the second transistor to the base of said output transistor.
9. A control as claimed in claim 8 in which said ratio sensitive means includes a signal storage capacitor connecting the base of said frrsttransistorto ground, and charge and discharge path, meansforsaid capacitor connected to be controlled bysaid ignition coil drive circuit so as to store on said capacitor a voltage representing said ratio.
10. A control as claimed in claim 1 in which the transducer includes a rotor, a stator having at least one pole piece, said rotor and statorforming part of a magnetic circuit, the reluctance of which varies with the position of the rotor relative to the stator and a winding linked with said circuit, the rotor having a plurality of tapering portions arranged to pass said pole piece as the rotor turns and thereby provide continuously changing reluctance in said magnetic circuit over a significant angle of rotation of said rotor.
11. Acontrol as claimed in claim 10 in which said rotor is a drum having a generally cylindrical curved surface, said tapering portions being defined by triangularly shaped raised areas of said curved surface.
12. Acontrol as claimed in claim 11 in which the rotor also has ribs on said curved extending axially thereof and disposed at the wider ends of said 100 triangularly shaped areas.
13. A control as claimed in claim 10 in which the rotor is in the form of a cup-shaped member having a cylindrical curved surface and an end surface, said curved surface being cut awayto form said tapering 105 portions.
14. A control as claimed in claim 4 in which the said discharge path means operates continuously.
15. A control as claimed in claim 4 in which the discharge of the said storage device is effectively limited at a level too high to sustain or initiate coil currentwhen the transducer output is held at zero.
Printed in the United Kingdom for Her Majesty's Stationery Office. 8818935, 10184, 18996. Published at the Patent Office, 25 Southampton Buildings, London WC2A lAY, from which copies may be obtained.
1 -1k
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| GB8309134 | 1983-04-05 |
Publications (3)
| Publication Number | Publication Date |
|---|---|
| GB8407455D0 GB8407455D0 (en) | 1984-05-02 |
| GB2138500A true GB2138500A (en) | 1984-10-24 |
| GB2138500B GB2138500B (en) | 1987-04-01 |
Family
ID=10540637
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| GB08407455A Expired GB2138500B (en) | 1983-04-05 | 1984-03-22 | Dwell control for an i c engine spark ignition system |
Country Status (7)
| Country | Link |
|---|---|
| US (1) | US4617906A (en) |
| EP (1) | EP0124239A3 (en) |
| JP (1) | JPS59229054A (en) |
| GB (1) | GB2138500B (en) |
| IN (1) | IN160245B (en) |
| MY (1) | MY100265A (en) |
| ZA (1) | ZA842256B (en) |
Families Citing this family (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE3630272A1 (en) * | 1986-09-05 | 1988-03-17 | Bosch Gmbh Robert | DEVICE FOR CONTROLLING AN INTERNAL COMBUSTION ENGINE |
| FR2607278B1 (en) * | 1986-11-26 | 1989-06-23 | Bendix Electronics Sa | INTEGRATED CIRCUIT FOR CURRENT REGULATION IN AN INDUCTIVE LOAD AND ITS APPLICATION TO THE IGNITION COIL CONTROL OF AN INTERNAL COMBUSTION ENGINE |
| DE3922859A1 (en) * | 1989-07-12 | 1991-01-24 | Bosch Gmbh Robert | METHOD FOR CONTROLLING FUEL MEASUREMENT IN AN INTERNAL COMBUSTION ENGINE |
| CN111819358B (en) * | 2018-03-13 | 2022-06-10 | 罗姆股份有限公司 | Switch control circuit and igniter |
Family Cites Families (14)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE1539169C3 (en) * | 1966-07-20 | 1974-01-03 | Robert Bosch Gmbh, 7000 Stuttgart | Ignition device for internal combustion engines |
| US3465739A (en) * | 1967-10-16 | 1969-09-09 | Phelon Co Inc | Inductively triggered breakerless ignition system with automatic spark advance |
| US3591849A (en) * | 1969-06-20 | 1971-07-06 | Outboard Marine Corp | Variable timing means for capacitive discharge ignition system |
| US3882840A (en) * | 1972-04-06 | 1975-05-13 | Fairchild Camera Instr Co | Automotive ignition control |
| US3831571A (en) * | 1973-05-11 | 1974-08-27 | Motorola Inc | Variable dwell ignition system |
| US3937193A (en) * | 1973-11-19 | 1976-02-10 | Ford Motor Company | Electronic ignition system |
| US4043302A (en) * | 1975-08-25 | 1977-08-23 | Motorola, Inc. | Solid state ignition system and method for linearly regulating the dwell time thereof |
| DE2549586C3 (en) * | 1975-11-05 | 1979-03-29 | Robert Bosch Gmbh, 7000 Stuttgart | Ignition device for internal combustion engines |
| JPS5346528A (en) * | 1976-10-06 | 1978-04-26 | Nippon Denso Co Ltd | Non-contact ignition system with closing-angle controlling device |
| US4236094A (en) * | 1977-07-01 | 1980-11-25 | Societe Pour L'equipement De Vehicules | Ignition transducer for vehicle engines |
| DE2833434A1 (en) * | 1978-07-29 | 1980-06-04 | Bosch Gmbh Robert | IGNITION DEVICE FOR AN INTERNAL COMBUSTION ENGINE |
| DE2842386A1 (en) * | 1978-09-29 | 1980-04-17 | Bosch Gmbh Robert | IGNITION DEVICE FOR INTERNAL COMBUSTION ENGINES |
| US4324216A (en) * | 1980-01-09 | 1982-04-13 | Fairchild Camera & Instrument Corp. | Ignition control system with electronic advance |
| US4403591A (en) * | 1981-04-13 | 1983-09-13 | Motorola, Inc. | Ignition system having variable percentage current limiting |
-
1984
- 1984-03-22 EP EP84301935A patent/EP0124239A3/en not_active Ceased
- 1984-03-22 GB GB08407455A patent/GB2138500B/en not_active Expired
- 1984-03-22 US US06/592,439 patent/US4617906A/en not_active Expired - Fee Related
- 1984-03-27 ZA ZA842256A patent/ZA842256B/en unknown
- 1984-04-04 IN IN235/MAS/84A patent/IN160245B/en unknown
- 1984-04-05 JP JP59066815A patent/JPS59229054A/en active Pending
-
1987
- 1987-03-20 MY MYPI87000342A patent/MY100265A/en unknown
Also Published As
| Publication number | Publication date |
|---|---|
| GB8407455D0 (en) | 1984-05-02 |
| ZA842256B (en) | 1984-10-31 |
| MY100265A (en) | 1990-07-28 |
| GB2138500B (en) | 1987-04-01 |
| US4617906A (en) | 1986-10-21 |
| EP0124239A3 (en) | 1986-01-15 |
| EP0124239A2 (en) | 1984-11-07 |
| JPS59229054A (en) | 1984-12-22 |
| IN160245B (en) | 1987-07-04 |
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| PCNP | Patent ceased through non-payment of renewal fee |