GB2136645A

GB2136645A - Control circuit for gas discharge lamps

Info

Publication number: GB2136645A
Application number: GB08404621A
Authority: GB
Inventors: Dennis Capewell; Davud G Luchaco; Joel S Spira
Original assignee: Lutron Electronics Co Inc
Current assignee: Lutron Electronics Co Inc
Priority date: 1983-03-09
Filing date: 1984-02-22
Publication date: 1984-09-19
Also published as: FR2542555A1; DE3407067A1; HK5089A; KR910009482B1; KR840009024A; IT8419894A0; US4527099A; IT1173433B; ES530407A0; GB8605151D0; JPS59196598A; AU2463684A; FR2542555B1; SG63188G; GB2170025A; GB8404621D0; JPH05205886A; GB2136645B; ES8507309A1; HK5189A

Description

1 GB 2 136 645 A 1

SPECIFICATION

Control circuit for gas discharge lamps Background of the invention

This invention relates to a control circuit for gas discharge lamps, and more particularly relates to a control circuit which permits improved dimming of large numbers of various kinds of gas discharge lamps.

The present invention is an improvement over the circuits disclosed in U.S. Patent 4,350,935, dated September 21,1982, entitled "Gas Discharge Lamp ControV' in the name of Joel S. Spira et al and assigned to the assignee of the present invention. As disclosed in Patent 4,350,935, it is possible to regulate the output light of one or more fluorescent lamps by applying a voltage wave form to the lamp ballast which has a notch in each of the half waves, which notch is of variable width and of variable 85 location within the half wave form.

The circuit arrangement shown in Patent 4,350,935 provides good operation over a wide range but has several shortcomings. For example, the circuit em ploys a series switching means and shunt switching means for an inductive ballast. The series switching means is a high speed transistor which is operable to turn off at some desired point in the input voltage wave form to produce the desired notch in the input voltage. The shunt switching means turns on during this notch interval to provide a bypass path for the discharge of energy from the ballast. The shunt switching devices consist of anti-parallel connected controlled rectifiers. If, for any reason, a spurious control signal is applied to the controlled rectifiers out of their proper sequence, it becomes possible to produce a short circuit f rom the a.c. voltage power line through the series switching transistor and the parallel switching device. This could seriously dam age or destroy the series switch.

Another shortcoming of the circuit of Patent 4,350,935 is that the lamp life of energy saving lamps reduces when the lamps are operated in their lower dimming end region. One reason for this is that as the notch width increases, the RMS content of the voltage applied to the inductive ballast decreases. As a consequence, the effective output voltage of the filament transformers decreases so thatthe lamps will extinguish at relatively low dimming.

Afurther difficult experienced with the arrange ment of Patent 4,350,935 is "tracking" several banks of lamps so that they dim by the same amount.

Proper tracking requires placement of the notch close to the start of each of the half waves in the nearly fully illuminated condition so that the notch can move to the right during dimming without causing some or all of the lamps to drop out while remaining lamps become very bright.

Brief description of the present invention

In accordance with a first feature of the present invention, the control circuit of Patent 4,350,935 is modified such that the series switching means and shunt switching means can both be formed of anti-parallel connected controllably conductive de- vices such as transistors or controlled rectifiers. Commutating capacitors are discharged into the series switches by firing appropriate ones of the shunt switches in order to produce the notched wave form. The shunt switch also provides a discharge path for stored energy in the inductive ballast.

The novel circuit of the invention has a current limiting topology. Thus, a current limiting impedance, preferably a capacitor, is added in series with the shunt switching means so that the shunt switching means and impedance means are in a series circuit which is in parallel with the inductive ballast. If, for any reason, the devices of the series and shunt switch form a direct connection across the a.c.

source, current flow would be limited by the series impedance. The current limiting impedance can also be any combination of resistive, inductive, capacitive or active components either singly or in various combinations. The resistive, inductive and capacitive components or combinations thereof may be linear or non-linear. The active components may be twoterminal orthree-terminal devices ' semiconductor devices orarc discharge devices orthe like. Typically, a break-over semiconductor diode can be used as the active device.

As a further significant feature of the invention, the series impedance is a capacitor and the polarity of its voltage is allowed to reverse due to the transfer of stored ballast energy during a notch interval so that the net voltage applied to the inductive ballast will reverse during the notch period, thus significantly increasing the RMS content of the ballast voltage. By increasing the RMS content of the voltage applied to the ballast, the filament transformers are better operated so that, as the notch is widened, a greater degree of regulation of lamp light can be obtained than was previously possible. The rapid reversal of voltage across the ballast due to the capacitor also helps to maintain lamp ionization during the notch interval; minimizes lamp current crest factor; and also provides the well- known advantages of high frequency operation of gas discharge lamps.

It has also been found that, when employing the circuit of the present invention, the notch can be located closer to the 90' angle within each of the half waves of the input voltage wave shape to the ballast. By locating the notch in this position, the RMS content of the applied voltage is further increased, and it is still possible to obtain satisfactory tracking throughout the dimming range.

A novel automatic low end set circuit is provided which automatically adjusts for the different dimming curve of standard lamps and ballasts as compared to energy saving lamps and ballasts. The novel automatic low end set circuit will automatically calibrate the size of the notch so that a specified setting percentage from full illumination is maintained regardless of the type of lamp or ballast connected. The automatic low end set circuit em- ploys, as an input, either the RMS voltage input to the ballast or the total load current. This is used to generate a signal to one input of an error amplifier and is compared to a suitable reference value. The output error is then employed to adjust notch width and location.

2 GB 2 136 645 A 2 A novel notch signal generator is also provided and consists of a two phase shift network arrangement fed into a comparator circuit. The two phase shifted signals are compared to a given signal level and produce a signal output when the phase shifted signals are above and below, respectively, the preset level in order to mark the beginning and the end of the notch signal. The novel notch signal generating circuit provides very stable operation even on lines which are unstable due to large in-rush currents due to air conditioning compressors and other types of motors being started, as an example.

The novel circuit of the invention is applicable to any desired type of gas discharged lamp, including but not limited to all types of fluorescent lamps and high intensity discharge lamps.

Brief description of the drawings

Figure 1 is a circuit diagram of a first embodiment of the invention.

Figure 2 is a circuit diagram of a second and preferred embodiment of the invention.

Figure 3 shows the ballast input voltage as a function of time for a prior art control circuit.

Figure 4 shows the ballast input voltage as a function of time for the circuit of the present invention at a high illumination condition.

Figure 5 is similar to Figure 4 and shows the notch moved to an increased dimming position.

Figure 6 shows the load current for the circuit of Figure 2 in the dimming condition of Figure 5.

Figures 7athrough 7e are timing diagrams to show the timing of firing signals to the controlled rectifiers of Figure 2.

Figure 8 is a circuit diagram of a first embodiment 100 of an automatic low end set circuitfor maintaining a constant illumination level regardless of the kind of ballast and lamp which are employed in the load circuit.

Figure 9 is a circuit diagram of a second embodi ment of an automatic low end set circuit.

Figure 10 is a circuit diagram of a circuit for generating the notch signal shown in Figure 7b.

Figure 11 shows the phase-shifted voltages as a function of time which are employed in the circuit of 110 Figure 10 and the notch signal which is produced.

Detailed description of the drawings

Referring first to Figure 1, there is shown a control circuit which contains most of the components of the prior art control circuit of Patent 4,350,935 along with an exemplary inductive ballast and lamps operated by the ballast. A plurality of parallel connected ballasts and lamps can be provided. A conventional a.c. power line of any desired voltage and frequency, typically 277 volts and 60 Hz, is connected to the circuit input terminals 10 and 11.

A series switching means 12 is provided which consists of a single phase, full wave rectifier bridge containing diodes 13,14,15 and 16 and a high speed 125 switching transistor 17 connected across the d.c.

terminals of the bridge 12. An appropriate control circuit (not shown) is connected to the base 20 of transistor 17 as is described in Patent 4,350,935.

A "crowbar" circuit 21, which is a high speed protective switching means, is connected across the transistor 17 to protect the transistor during lamp switch-on when high surge currents might flow through the transistor 17.

There is also provided a shunt switching means consisting of antiparallel connected controlled rectifiers 30 and 31 which are connected in parallel with the inductive ballast 32. Ballast 32 may be a conventional ballast and is one of any desired number of parallel connected ballasts which are operated from the same control circuit. The ballast illustrated consists of a primary winding 40 having a secondary winding 41 and filament power windings 42 and 43 coupled thereto. A capacitor 44 is connected in series with winding 41 as shown. Ballast 32 is connected to two series- connected gas discharge lamps 45 and 46. Lamps 45 and 46 can, if desired, be energy saver type fluorescent lamps of commercially available types. Other lamps could be used.

Ballast filament winding 42 is connected to the upper filament of tube 45 while filament winding 43 is connected to the lower filament of tube 45 and the upper filament of tube 46. The lower filament of tube 46 is heated by the voltage from a winding tap 47 of the winding 40.

The structure described to this point, and excluding resistor 50 to be later described, is essentially identical to that of Patent 4,350,935. The transistor 17 is controlled such that. as shown in Figure 3, the transistor turns off at time t, and turns on at time t2 in each half wave to produce a notch in the voltage wave shape. In order to permit discharge of the ballast energy during the notch interval between times t, and t2, the appropriate controlled rectifier 30 or 31 is switched on to permit the flow of discharge current from the ballast. For example, during the half wave in which terminal 10 is positive relative to terminal 11, controlled rectifier 30 will turn on when the transistor 17 turns off. If, however, during any peiod outside of the notch interval the controlled rectifier 30 is turned on, then a direct short circuit would appear from terminal 10 through transistor 17, controlled rectifier 30 and back to terminal 11. This direct short circuit could cause serious damage or destruction of the high speed transistor 17.

In accordance with one aspect of the present invention, an intentional current limiting impedance is provided in series with the shunt switching means 30-31. In Figure 1 this current limiting means is shown in its simplest form as resistor 50.1 - f now there is a spurious control signal which causes "shoot througC of currentthrough thetransistor 17 and one of controlled rectifiers 30 or 31, the current would be limited by the impedance 50, thus tending to protectthe transistor 17 by limiting the maximum current through the transistor during the half wave.

A second and preferred embodiment of the invention is shown in Figure 2. In Figure 2, the current limiting impedance is a capacitor 73. The capacitor 73 is also employed to increase the RMS content of the voltage wave form applied to the ballast as will be described.

Referring to Figure 2, components similar to those of Figure 1 have been given the same identifying numerals. Thus, there is provided a series switch 12.

3 GB 2 136 645 A 3 In Figure 2, the series switching means 12 consists of anti-parallel connected controlled rectifiers 60 and 61. Other controllably conductive devices could be used. The gates of controlled rectifiers 60 and 61 are operated by pulses derived from a suitable control circuit 62.

A shunt switching means is provided in Figure 2 which includes rectifiers 30 and 31 or any othertype of controllably conductive device which is desired.

Controlled rectifiers 30 and 31 are connected in series with respective inductors 63 and 64 and with series diodes 65 and 66, respectively. Inductors 63 and 64 may be 90 microhenry air core inductors.

Note that diodes 65 and 66 are poled identically to the poling of controlled rectifiers 30 and 31, respec tively. A control circuit 71 is provided to control the firing of controlled rectifiers 30 and 31. Snubber circuits consisting of resistors 67 and 68 and respec tive series-connected capacitors 69 and 70 are connected in parallel with controlled rectifiers 30 and 85 31, respectively. Inductors 63 and 64 also provide inductance for the snubber circuits of controlled rectifiers 30 and 31 and also provide inductance in the commutation circuits which is necessary to turn off controlled rectifiers 60 and 61 with the initiation of their respective notches.

Capacitor 73-is an energy divertor and current limiting component connected in series with the shunt switch circuit and the series connected shunt switch circuit and capacitor 73 are connected in parallel with the various ballasts. Capacitor 73 can be replaced by any combination of resistive, inductive, capacitive or active components either singly or in various combinations. The resistive, inductive and capacitive components or combinations thereof may 100 be linear or non-linear. The active components may be two-terminal or three-terminal devices, semicon ductor devices or arc discharge devices or the like.

Typically, a break-over semiconductor diode can be used as the active device. Note that the current limiting divertor structure can be connected across the series switching means 12 and the shunt switch means may be eliminated.

The output of the control circuit of Figure 2 is connected suitably to ballasts which may be identic- 110 al to ballast 32 of Figure 1.

Two commutating capacitors 80 and 81 are con nected between terminal 10 and the node between diode 65 and controlled rectifier 30 and the node between diode 66 and controlled rectifier 31, respec- 115 tively. A conventional input filter capacitor 82 is connected across the input terminals 10 and 11.

It will be noted that the arrangement of the circuit of Figure 2 is current limiting since the impedance of capacitor 73 is in series with any path which can result due to a spurious control signal applied to controlled rectifiers 30, 31, 60 and 61. Similarly, inductors 63 and 64 are current.limiting in the circuit including capacitors 80, 81 and 73 in the event of an incorrect controlled rectifier firing. Thus, the circuit is 125 inherently very rugged.

The manner in which the circuit of Figure 2 operates is described in the following with reference to Figures 4, 5, 6 and 7a to 7e. The control signals which are to be applied from the control circuits 62 and 71 to controlled rectifiers 30 and 31, 60 and 61 are shown in Figures 7c, 7d and 7e relative to line voltage shown in Figure 7a and the width of the desired notch shown in Figure 7b.

The notch signals shown in Figure 7b are to be initiated at time t, and extinguished at time t2 so that the notch width will be the distance t2 minus tl. A notch-producing circuit is described hereinafter with reference to Figure 10. During positive half waves a firing pulse is applied to controlled rectifier 30 at the instant of the beginning of the notch period. After a short time delay, to, shown in Figure 7c, the conducting controlled rectifier 61 will be commutated off. Controlled rectifier 61 is then turned on again at the timeT2. During negative half waves and as shown in Figure 7e, the controlled rectifier 31 turns on at the beginning of the notch at time t, and the controlled rectifier 60 will commutate off after a short time delay, and will be turned back on again at the end of the notch.

Figure 4 shows the ballast input voltage for a notch condition in which the notch is initiated relatively early in the half wave and in which the notch width is relatively short to obtain a relatively small degree of dimming of the output light, for example, to 95% of full illumination. Note that, at full illumination, the notch may be eliminated.

It will be noted that the voltage swings through zero in each half wave during this notch interval This is because capacitor 73 goes to the opposite polarity as the load inductance stored energy is transferred through one of diodes 65 or 66 and controlled rectifier 30 and 31, respectively. At the same time, the commutating capacitor 80 or 81 is properly charged to be ready for a commutation operation during the next interval. As a result of the voltage swing through zero, the RMS voltage, which is applied to the ballast, will be significantly higher than in the prior art circuit in which the voltage during the notch interval is clamped to zero, as shown in Figure 3.

In order to obtain regulation or dimming, and as will be described in more detail later, the notch position is progressively widened and is progressively moved to the right, as shown in Figure 5. In the condition of Figure 5, lamp dimming may be at about 50% of full illumination. The load currentwave shape of the load currentflowing through the ballasts is shown in Figure 6 for the regulation condition of Figure 5.

The operation of the circuit of Figure 2 is now described in more detail.

Immediately priorto the time terminal 10 becomes positive, the capacitor 80 will be positively charged as shown. Capacitor 80 was charged in the prior half cycle through diode 65. The control circuit 62 causes the control rectifier 61 to conduct when the line voltage becomes positive and energy begins transferring from the load to the ballast until time t, in Figure 7b when a notch is to be placed in the input voltage wave shape. At this instant, controlled rectifier 30 is fired by the control circuit 71. Capacitor 80 then discharges through the closed circuit including controlled rectifier 30 and the forwardly conduct- ing controlled rectifier 61. The discharge current 4 GB 2 136 645 A 4 commutates down the forward current of controlled rectifier 61 and promptly turns off the controlled rectif i er 6 1.

The output voltage wave shape at the beginning of the notch will then swing through zero in a negative direction due to transfer of load inductance stored energy to capacitor 73. At the same time, the capacitor 81 is being charged to a condition in which it can commutate - off controlled rectifier 60 during the negative half cycle and when controlled rectifier 31 is fired.

For proper operation of the circuit of Figure 2, the novel capacitive divertor 73 will preferably have a low impedance compared to that of capacitors 80 and 81. Good results have been obtained when employing as 25 microfarad, 440 volt oil-filled capa citorfor divertor capacitor 73 and 1 microfarad, 800 volt oil-filled capacitors for capacitors 80 and 81.

An unexpected advantage of the circuit of Figure 2 and due to the increased RMS voltage content supplied to the ballast is that it can operate the lamp filaments of lamps 45 and 46 (Figure 1) of energy saving lamps as well as standard lamps at a much lower minimum setting. For example, in energy saving lamps, it has been difficult to reduce ouptut light significantly because the reduction in filament voltage causes decrease lamp life for energy saving lamps. In the present invention, however, energy saving lamps can be dimmed to a low end of 40% without lamps life loss, whereas such lamps could not be below 70% with prior art circuits.

It is believed that this improvement is obtained because the wave form of the voltage applied to the ballasts has a higher RMS content than prior circuits because the notch voltage swings through zero.

The circuit of Figure 2 also permits maintaining the notch position closer to the 90' position within each half wave without incurring tracking problems.

When the notch position is closer to 90', the notch width can be less so that the RMS voltage content is again greater.

The improvement is also due in part to better notch position and notch width control since it is possible, with the present invention, to move the notch shown in Figures 4 and 5 further to the right within the half wave without upsetting lamp track ing, as will be later described.

Thus, with the present invention, the notch posi tion can be at approximately 80' into the half wave for the unregulated condition and can then move to the right as the lamp power is regulated down. By contrast, in the prior art, as shown in Figure 3, the notch must be positioned at about 65'for starting conditions in order to provide adequate tracking. If the notch started at 800 in prior art circuits, some lamps would drop out during regulation while others would be very bright. Since this tracking problem is not as great with the present invention, the notch beginning point can be at about the 80' level so that RMS content is increased overthe entire range.

A preferred adjustment and tracking sequence for adjustment of notch width and notch position is as follows:

The notch begins at approximately 45'within the half wave for 95% of full light intensity. In order to 130 decrease the light intensity from 75% to full intensity, the beginning of the notch position is moved to the right and the notch is widened as it moves to the right until full regulation of light intensity, down to about 30% of its full value (for an energy saving lamp) is obtained. At this point, the notch begins at about 800 within the half cycle.

By using this sequence, it has been found that filament voltages can be optimized at the minimum setting and the smallest divertor capacitor possible is used. In general, a smaller capacitor will produce a larger RMS ballast input voltage for a given notch position and width. Therefore, the smallest possible divertor capacitor value is desirable to maximize filament voltages.

The circuit of Figure 2 operates to produce good automatic load regulation. Automatic load regulation refers to the condition wherein light level can be maintained constant regardless of the number of lamps which are connected to the control circuit and to keeping the filament voltages high enough regardless of the number of lamps connected.

The circuit of Figure 2 operates extremely well with respect to automatic load regulation because the RMS content of the wave forms of the ballast input voltage does not change significantly with the connection of more or less lamps to the same circuit. It is believed that this occurs because of two compensating factors between the amount of ener- gy which must be taken from the ballast inductance during the notch interval, and the time during which the energy can be depleted. In a case where a maximum number of lamps, for example, 90 lamps, are connected to the system, the greater energy must be diverted but, since the equivalent load resistance and equivalent ballast inductance is less, energy will be depleted at the fastest possible rate from the ballast. In the case of a minimum number of lamps connected, 10 for example, less energy is available but also the depletion rate is correspondingly reduced. Consequently, the RMS voltage in the input voltage wave shape to the ballast stays essentially the same, regardless of the number of lamps driven by the circuit of Figure 2.

One beneficial result of the good regulation characteristics of the circuit of Figure 2 is that the value of the divertor capacitor is not critical. Therefore, capacitor 73 of Figure 2 can be a relatively inexpensive capacitor.

Good results have been obtained with the circuit of Figure 2 when the timing circuits or control circuits 62 and 71 are such thatthe notch is held in the center of the lamp arc voltage throughoutthe dimming curve. This produces the highestfilament voltages and the lowest lamp peak arc voltage.

Referring next to Figure 8, there is shown an automatic low end set circultwhich can be employed with the circuit of Figure 2 in connection with the operation of the control circuits 62 and 71 and in particular for adjusting the position and duration of the notch signal of Figure 7b. Lamps and ballasts are commercially available which are designed to produce light more efficiently, previously referred to as energy saving lamps and ballasts.

The dimming curve of energy savings products p has been found to differ from those of standard lamps and ballasts, particularly fluorescent lamps.

The circuit of Figure 8 automatically calibrates the unit so that the specified low end or any other specified setting or dimming will be maintained regardless of the type of lamp and ballast which is employed. While the circuit is shown particularly in connection with a fluorescent lamp, it should be noted that the operation of the circuit of Figure 8 will apply to any light source.

In Figure 8, an RMS voltage detector circuit is formed of a potential transformer 100 which has its primary winding connected to the ballast input voltage and a secondary winding 101 connected to the single phase, full wave bridge connected rectifier 102. An output resistor 103 is connected across the d.c. output terminals of bridge 102 and a diode 104 and resistor 105 are connected in the positive output terminal of bridge 102. A capacitor 106, resistor 107 and capacitor 108 are also provided. The compo nents of Figure 8 described to this point serves the purpose of an RMS load voltage detector. Thus, the voltage at the node of resistor 107 and capacitor 108 will be proportional to the RMS voltage at the ballast imput voltage terminals 109 and 110 in Figure 8.

The output at the node of resistor 107 and capacitor 108 is then be connected through a scale factor correction circuit 111 or may be connected directly to an error amplifier 112.

Another input to error amplifier 112 is taken from 95 resistor 113 which is connected to a suitable control voltage source, as indicated, to define a voltage standard which can be easily adjusted.

The error signal output of amplifier 112 is then connected to the appropriate notch width control circuit which is operable to produce the notch signal of Figure 7b, modified in accordance with the output of the error amplifier 112. The notch width control circuit will be later described in connection with Figures 10 and 11.

The circuit of Figure 8 is an inexpensive circuit and is accurate, even though actual load current is not measured but only ballast input voltage is mea sured. Moreover, the circuit of Figure 8 inherently provides line voltage compensation so that no separate circuit is required for this function.

The scale factor correction circuit 111 can be employed if it is desired to correct the circuit operation for the number of lamps which are being excited, which is a function of the total load current.

The circuit will also make the slight correction needed by energy saving lamps as compared to standard lamps at light loads. The scale factor correction circuit 111 can be a simple variable gain amplifier in which gain varies in accordance with the 120 magnitude of the load current.

Figure 9 shows a second embodiment of an automatic low end set circuit inblock diagram form.

In the embodiment of Figure 9, the input signal controlling the system is derived from the total load current which is applied to the current transformer 120. The output of the current transformer 120 is then applied to an appropriate RMS current detector circuit 121. The output of circuit 121 is then applied to an appropriate storage circuit 122 which stores a GB 2 136 645 A 5 signal related to the 100% value of the total load current at the instant of measurement. The storage circuit 122 can, for example, be a digital counter. The output of detector 121 is also applied to operational amplifier 123.

A circuit 124 is also connected to the storage circuit 122 and consists of a gain set change enable circuit which is operable during a no-notch (full lamp intensity) condition in the voltage to the inductive ballasts of Figure 2.

The output of the storage or memory circuit 122 is then connected to a gain setting circuit 125 which adjusts the gain of operational amplifier 123 in accordance with the 100% value which is stored in circuit 122. Consequently, as the total load current changes, the input RMS current to operational amplifier 123 will also change to produce an output signal to the error amplifier 126 relative to the standard values set in the adjustable resistor 127.

The amplified output error signal is then applied to the notch width control circuit shown which will be later described and which is the same circuit as was shown in Figure 8.

During a start-up situation or reinitialization after load switching when there is no notch in the voltage to the ballast, the circuit of Figure 9 will store in memory the value of the full load current.This value will determine the gain of amplifier 123 such that the voltage v. reaches a value to indicate 100% illumination output. As dimming later occurs, the gain of amplifier 123 is locked in and the voltage v. will be proportional to the percentage of full load current. This output is applied to the error amplifier 126 and the closed loop system will hold the percentage of full load current at the desired setting by appropriately adjusting the notch width.

Figure 10 shows the circuit which can be employed to produce a notch signal shown in Figure 7b for the control of the series and shunt switches in Figure 2.

Referring to Figure 10, there is an input a.c. control voltage applied through the filter resistor 140 and capacitor 141 which are connected to the a.c. terminals of a single phase, full wave bridge con- nected rectifier 142. The output voltage of rectifier 142 is connected as shown to capacitors 143 and 144 and resistor 145. The diode 146 is connected across resistor 145 as shown. The node between resistor 145 and capacitor 144 is connected to the positive input of comparator 150 which can be a type LM339 comparator.

The negative input of comparator 150 and the positive input of identical comparator 151 are connected to a resistor 152 in a reference circuit which includes a reference voltage source and resistor 153, resistor 154 and capacitor 155. The outputs of error amplifiers such as the error amplifiers 112 and 126 in Figures 8 and 9, respectively, can be applied through the resistor 160 in Figure 10 to the positive terminal of comparator 151 and the negative terminal of comparator 150. The outputs of comparators 150 and 151 are then connected together and are connected to a resistor 161 which is connected to a 10 volt source.

The circuit of Figure 10 is a simple two phase 6 GB 2 136 645 A 6 shifted network feeding into a comparator. Thus, the voltages at points A and B in Figure 10 are shown in Figure 11 as phase-shifted voltages superimposed on a common time base. Voltages A and B fluctuate relative to the dotted line level of the error amplifier output which may vary or bounce due to an unstable system and due to factors such as large in-rush currents taken by air conditioning compressors or other motors on the same line as the lighting power supply. The novel circuit of Figure 10, however, produces a notch signal which starts when the slope of voltage A intersects the error amplifier output and terminates when the slope of the voltage B intersects the error amplifier output. Thus, a notch signal of the desired duration and position is produced simply by controlling the phase relationships and magnitudes of the voltages A and B and by controlling the level of the error amplifier output or other reference voltage output. If it is desired to increase the notch width, it is necessary only to raise the average level of the reference signal or error amplifier output. This increases in the size of the signal will be accompanied by a gradual shift to the right of the notch signal as is desired.

The system of the invention is compatible with various controller inputs derived from energy management systems, time clocks, photosensors, occupancy detectors and the like. These inputs would be connected to the node between resistor 152 and capacitor 155 in Figure 10, in liew of or in addition to potentiometer 153.

Although the present invention has been described in connection with preferred embodiments, many variations and modifications will become apparent to those skilled in the art. It is preferred, therefore that the present invention be limited not by the specific disclosure herein, but only by the appended claims.

Claims

1. A gas discharge lamp energizing circuit comprising inductive ballast means connectable to at least one gas discharge lamp; a source of a.c.

power; series switching means connected in series with said source of a.c. power and said inductive ballast means; shunt switching means and series connected energy divertor impedance means connected in parallel with said inductive ballast means and in series with said a.c. source and said series switching means; and switching control means connected to said series switching means and to said shunt switching means to synchronously and substantially simultaneously close said series switching means and open said shunt switching means to transfer power from said source of a.c. power to said inductive ballast means, and to simultaneously open said series switching means and close said shunt switching means to produce a short duration notch in each half cycle of the voltage wave form applied to said inductive ballast means; said series connected energy divertor impedance means limiting current flow from said a.c. source in the event that both said series switching means and said shunt switching means are simultaneously closed.

2. The circuit of claim 2 wherein impedance means is a capacitor.

3. The circuit of claim 1 wherein said series switching means and said shunt switching means both consist of first and second anti-parallel connected controllably conductive devices.

4. The circuit of claim 1 wherein said switching control means is operable to control the duration of said notch, and the position of said notch within7the voltage wave form in order to regulate the output of said at least one lamp.

5. The circuit of claim 2 wherein the polarity of the voltage wave form applied to said inductive ballast means reverses during said notch in said voltage wave form, whereby the RMS content of the voltage applied to said inductive ballast means is increased.

6. The circuit of claim 5 wherein said series switching means and said shunt switching means both consist of first and second anti-parallel connected controllably conductive devices.

7. The circuit of claim 6 wherein said switching control means is operable to control the duration of said notch, and the position of said notch within the voltage wave form in order to regulate the output of said at least one lamp.

8. The circuit of claim 5 wherein said inductive ballast means includes filament windings connected to said at least one lamp.

9. The circuit of claim 8 wherein said switching control means is operable to control the duration of said notch, and the position of said notch within the voltage wave form in orderto regulate the output of said at least one lamp.

10. The circuit of claim 9 wherein said series switching means and said shunt switbhing means both consist of first and second anti-parallel connected controllably conductive devices.

11. The circuit of claim 3 which includes respective diodes connected in series with said first and second controllably conductive devices of said shunt switching means, and first and second commutating capacitors connected between the respective nodes between each of said first and second controllably conductive devices and said first and second diodes respectively, and the a.c. input side of said series switching means; said first and second commutating capacitors being operable to commutate to zero the current in said first or second controllably conductive device of said series switching means in responseto the conduction of said first or second controllably conductive device of said shunt switch ing means.

12. The circuit of claim 11 wherein the polarity of the voltage wave form applied to said inductive ballast means reverses during said notch in said voltage wave form, whereby the RMS content of the voltage applied to said inductive ballast means is increased.

13. The circuit of claim 12 wherein said switching control means is operable to control the duration of said notch, and the position of said notch within the voltage wave form in order to regulate the output of said at least one lamp.

7 GB 2 136 645 A 7

14. The circuit of claim 13 wherein said inductive ballast means includes filament windings connected to said at least one lamp.

15. The circuit of claim 11 which further includes rate of rise of current limiting means in series with each of said first and second controllably conductive devices of said shunt switching means, and snubber circuit means for each of said first and second controllably conductive devices.

16. An excitation and dimming circuit for inductively ballasted gas discharge lamps comprising, in combination: a pair of power line input terminals; a pair of ballast terminals; a series switching circuit consisting of a pair of first and second controllably conductive devices connected in anti-parallel relation to one another and connected in series between a first of said pair of power line input terminals and a first of said pair of ballast terminals; a shunt switching circuit consisting of a pair of third and fourth controllably conductive devices and a pair of first and second diodes connected in series with respective and similarly poled ones of said third and fourth controllably conductive devices; said series connected third controllably conductive device and said first diode connected in anti-parallel relation with said series connected fourth controllably conductive device and said second diode; a divertor capacitor; said shunt switching circuit connected in series with said divertor capacitor; said series con- nected shunt circuit and divertor capacitor being connected between said pair of ballast terminals; and first and second commutating capacitors both having one terminal connected to said first of said pair of power line input terminals and a second terminal connected to a respective node between said third controllably conductive device and first diode, and said fourth controllably conductive device and said second diode respectively.

17. The circuit of claim 16 wherein said controll- ably conductive devices are both controlled rectifiers.

18. The circuit of claim 16 wherein said commutating capacitors are both substantially larger in capacitance than said divertor capacitor.

19. The circuit of claim 17 wherein said commutating capacitors are both substantially larger in capacitance than said divertor capacitor.

20. The circuit of claim 16,17,18 or 19 which further includes firing circuit means for firing said controllably conductive devices in a given sequence, whereby, at a given point in the forward conduction half wave of each of said first and second controllably conductive devices, said third and fourth devices respectively are fired to produce a commutat- ing current due to the discharge of said first and second commutating capacitors respectively through said first and second controllably conductive devices respectively to turn off said devices and to initiate a notch in the voltage wave form applied to said pair of ballast terminals, and whereby a signal is produced to fire said first or second controllably conductive device to terminate said notch and, whereby, during said notch, said divertor capacitor produces a reversal through zero of the voltage applied to said pair of ballast terminals.

21. The circuit of claim 16 which further includes first and second rate of change of current limiting inductors connected in series with said third controllably conductive device and said first diode, and said fourth controllably conductive device and said second diode, respectively.

22. The circuit of claim 16 or 21 which further includes a resistorcapacitor snubber circuit connected in parallel with each of said third and fourth controllably conductive devices.

23. Asynchronous pulse generating circuit for producing pulses of variable width and phase location; said circuit comprising, in combination: an a.c. voltage source; a rectifier means for producing a repetitive rectified wave form of the voltage of said a.c. voltage source; a phase shift network connected to the output of said rectifier means; a standard level signal generating means; first and second comparator circuits both having positive and negative inputs; said level signal generating means connected to said positive input of said first comparator circuit and to said negative input of said second comparator circuit; the output of said rectifier connected to the negative output of said first comparator circuit whereby the output of said first comparator circuit switches when the output of said rectifier exceeds said standard level signal generating means and a pulse is initiated; the output of said phase shift network connected to said positive input of said second comparator circuit, whereby the output of said second comparator circuit switches when the output of said phase shift network becomes less than the value of the signal generated by said standard level signal generating means to terminate said pulse; said pulse being varied in length and in phase location relative to the instantaneous phase of said a.c. voltage source by changing the value of the output of said standard level signal generating means.

24. The process of maintaining a constant reduction in available light output from a plurality of parallel connected gas discharge lamps, regardless of the impedance characteristics of said lamps; said process comprising the steps of establishing a 100% output illumination standard signal, measuring an instantaneous output parameter of said lamps, comparing a predetermined fraction of said standard signal and said instantaneous parameter to generate an error signal, and modify the output wave shape to said lamps to change their illumination level in such a manner as to reduce said error signal.

25. The process of claim 24 wherein said instan taneous parameter is the RMS voltage applied to said lamps.

26. The process of claim 24 wherein said instan taneous parameter is RMS load current.

27. The process of claim 24 wherein said lamps are either standard or energy saving fluorescent lamps.

28. The process of claim 24 wherein said modifi cation of wave shape consists of varying the width of a notch in each half wave of an a,c. wave shape.

29. A gas discharge lamp control circuit substan tially as hereinbefore described with reference to and as shown in the accompanying drawings.

8 GB 2 136 645 A 8

30. A process for maintaining a constant reduction in available light from a plurality of gas discharge lamps substantially as hereinbefore described.

Printed in the UK for HMSO, D8818935,7184,7102. Published by The Patent Office, 25 Southampton Buildings, London, WC2A lAY, from which copies may be obtained.

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