FI94918B - Discharge lamp ballast - Google Patents

Abstract

A ballast for a discharge lamp (L) contains, in the normal manner, an invertor (C) supplied from a DC voltage source (B), which invertor generates the alternating voltage for the discharge lamp (L). The discharge lamp (L) is located in parallel with the capacitor (C10) of a series-resonant circuit (L6/C10). A variable frequency AC voltage is supplied from a variable frequency generator (6, 7, 8, 9, 15, 16) to the invertor (C). The frequency of the variable frequency generator can be controlled by a control unit (10). Control signals are supplied to the control unit, which signals correspond to various parameters of the ballast. These parameters are the lamp voltage, the lamp current, the DC power, the DC voltage, a low-voltage DC voltage and the phase angle of the load circuit (E) for the invertor (C). The reaction of the control unit (10) to changes in the parameters mentioned is to change the frequency of the frequency generator or to switch off the frequency generator or the invertor (C). <IMAGE>

Description

94918

Preconditioning device for discharge lamp

The invention relates to a ballast for a discharge lamp arranged in parallel with respect to a capacitor of a series resonant circuit to an inverter load circuit connected to a DC source and controlled by a frequency generator whose frequency can be varied by

It is known from DE-PS 30 14 419 to measure the lamp current.

If it is too high, a bistable switching device is used that short-circuits the inverter transformer.

It is known from DE-PS 31 52 951 that when the ballast is switched on, the monostable flip-flop enters an unstable state in which it short-circuits the auxiliary winding in the inverter transformer so that it operates at a high frequency. At this high frequency, the lamp has a lower voltage at which ignition cannot occur. However, the heating coils of the lamp may heat up and radiate until the monostable flip-flop has returned to a stable state. After the flip-flop is reset, the short-circuit of the extra winding is canceled again, as a result of which the inverter operates at a lower frequency close to the resonant frequency of the series resonant circuit. The lamp is connected in parallel with respect to the capacitor of the series resonant circuit. At a lower frequency, an increased voltage is generated in the capacitor and lamp due to resonance, which is sufficient for ignition.

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It is known from DE-OS 32 08 607 to provide two frequency generators for controlling an inverter, one of which produces approximately the operating frequency and the other the idle frequency above it. Instead of two generators, an adjustable generator can also be provided.

First, a high idle frequency is switched on, at which no ignition can still occur. In this case, the lamp electrodes are preheated. Due to the high positive temperature coefficient of the electrode resistance, by selecting the response threshold of the threshold switch, it can be identified whether the electrodes have already been sufficiently preheated. If this is the case, the threshold switch will start to operate and the generator with the lower frequency will be switched on or - if an adjustable generator is provided - the frequency will be lowered in the direction of the operating frequency so that ignition can take place.

WO-A 82/01276 discloses a pre-switching device comprising an overcurrent detector for an inverter for thyristors, which overcurrent detector reacts when both thyristors are conductive. In this case, the thyristors are turned off.

In addition, it is known from DE-A 3,423,266 to connect a measuring coil to the lamp ballast, which generates a signal indicating the ignition state, which is fed to the monitoring circuit. The monitoring circuit determines from the signal whether the series resonant circuit containing the choke oscillates at the ignition frequency without significant attenuation caused by the lamp, which is the case with a non-ignited lamp, or whether the series resonant circuit is attenuated due to a burning lamp. The corresponding message of the monitoring circuit is received by the process controller of the oscillator controlling the inverter. The process controller controls the oscillator so that the oscillator oscillates in successive cycles of predetermined length, first at a high initial frequency, then at a reduced heating frequency, then at a further reduced series resonant circuit resonant frequency, and finally at a further reduced operating frequency.

When the ignition frequency signal of the monitoring circuit indicates that the lamp is not lit, the process controller returns the oscillator to its initial frequency and the operation is repeated.

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The object of the invention is to provide a pre-switching device whose reliability has been improved by monitoring and interpreting various parameters, whereby the requirement for improved reliability is met, in particular by implementing most components with integrated semiconductor chips.

The task is solved by the characteristic features of the claims, whereby the combination of requirements is considered to be a very advantageous solution of the task layout.

In the drawings:

Figure 1 is a block diagram of the preconditioning device and

Figure 2 shows the time course of the inverter control voltage compared to the total lamp current.

The block switching device shown in Fig. 1 consists of several modules, which are explained in the following order.

Module A is connected to the AC mains and acts as a High-frequency harmonic filter to reduce mains harmonics and for spark protection. It is formed in a conventional manner and includes chokes L1 and L2 and capacitors C1, C2, C3 and C4.

Module B is connected to module A. This consists only of a schematic rectifier bridge with a filter circuit. A DC voltage of approx. 250 V + is available at terminal 16 of module B.

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A module K is connected to the module B, which operates to produce a voltage Ueg corresponding to the direct current taken from the module B.

The module K consists of a resistor R1, in parallel with which a series circuit consisting of a choke L2 and a capacitor C5 is connected. A voltage can be taken from the junction between L2 and C5 [Jjq.

Module M operates to produce an actual value voltage Uq corresponding to the DC voltage produced by module B. Module M is connected to terminal 16 of module B and consists of a resistor voltage divider R2 / R3, where resistor R3 is connected in parallel with respect to capacitor C6. The voltage Uq taken from the voltage distribution point is proportional to the DC voltage obtained from the connection point 16 of the module B, but still less than this.

Module C is an inverter that produces an alternating voltage from the DC voltage produced by module B. For this purpose, the AC voltage is supplied to the module C from the module E to be explained later to the winding L3 of the phase transformer T1. The alternating phase transformer T1 has two windings L4 and L5 on the secondary side. The voltage generated in the winding L4 is supplied to the gate terminal of the field effect transistor FET1 via a resistor R4, in parallel with which a diode D1 is connected. Two zener diodes 21 and Z2 are connected in series between the gate terminal of the FET1 and the source interface. The voltage generated in the winding L5 of the phase transformer T1 is supplied to the gate terminal of the field effect transistor FET2 via a resistor R5 in parallel with which a diode D2 is connected. Two zener diodes Z3 and Z4 are connected in series between the gate interface and the source interface of the FET2. Resistors R4 and R5 are high-resistance and act to delay the connection of the FETs. The function of diodes D1 and D2 is to ensure fast disconnection of the FETs. In this way, it must be ensured that both FETs are never completely conductive at the same time, as this would cause a short circuit. The function of the zener diodes Z1, Z2, Z3 and Z4 is to protect the gate connections of the FETs t s 94918 from voltages. Otherwise, the inverter of module C has a conventional structure and its operation is known, so that a more detailed description can be omitted here.

Connected to the output of the inverter-forming module C is a load circuit including a discharge lamp L, shown as a module E. In addition to the discharge lamp L, this includes a series resonant circuit formed of a choke L6 and a capacitor C10. Capacitor C9 operates for separation. The oscillation circuit capacitor CIO is parallel to the gas discharge lamp L. The use of a series resonant circuit has several known advantages. Before lighting the gas discharge lamp L, alternating current flows through the heating coils of the lamp over the parallel capacitor CIO. Thus, the heating coils are heated and made to radiate. When the frequency of the voltage supplied from the module C to the module E is close to the resonant frequency of the series resonant circuit L6 / C10, a voltage increase occurs in the parallel capacitor CIO, which is used to turn on the lamp L. After ignition, the lamp L lowers the goodness of the series resonant circuit and the voltage of the lamp L decreases because the lamp L is then conductive. The choke L6 now acts as a lamp current limiter. In order to improve the service life of the lamp L, an attempt is made to preheat the heating coils of the lamp L long enough before ignition. To achieve this, a voltage is first applied to the module E at a frequency so much above the resonant frequency of the series resonant circuit L6 / C10 that the heating coils of the lamp L heat up, but the lamp L does not ignite yet because the voltage in the parallel capacitor C10 decreases. is too low due to its high frequency. The frequency is then reduced in the direction of the resonant frequency of the series resonant circuit L6 / C10 until said voltage rise in the parallel capacitor C10 occurs and ignition can occur. It will later be explained in more detail how said change in the frequency of the voltage applied to the module E is obtained.

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Module G operates to produce a voltage Un, which is a measure of the total current of the lamp L. Module G consists of a resistor R8 connected to the second electrode of the lamp, through which the total current of the lamp flows.

Module H operates to produce a low distribution voltage Unv of about 10 to 12 V, preferably for the components of module D, which is formed as a semiconductor chip and will be described in more detail later.

For this purpose, the module H is connected to the output of the module G, which, as mentioned, produces a voltage Un ,, which corresponds to the total current of the lamp. This voltage is thus derived from the total lamp current. It is applied to module H by diode D3, which rectifies the voltage Un ,, which is the AC voltage. Resistor R9 and both zener diodes Z5 and Z6 connected in series with it take care of voltage stabilization. The resistor RIO and the capacitor C11 connected to it in series as well as the capacitor C12 take care of equalizing the rectified voltage Ujjv. However, the voltage Ujjv could also be obtained by voltage distribution from the DC voltage (250 V) available at terminal 16 of module B. In this case, however, the amount corresponding to the voltage difference between 250 V and 10 to 12 V would have to be canceled, which would cause undesired heat loss and unnecessary energy consumption, respectively.

The core part of the ballast is a module D. The function of this is essentially to produce a variable frequency for the module C forming the inverter, specifically depending on several parameters of the ballast. With a variable frequency, it is possible to change the voltage at the terminals of the lamp L (module E). At an idle frequency that is substantially high. higher than the resonant frequency of the series resonant circuit L6 / C10, the module E forming the load circuit is inductive and the voltage at the terminals of the lamp L does not effectively exceed 250 V. This relatively low voltage is specified by relevant standards (e.g. German VDE 0712) to allow relatively safe lamp replacement. In contrast, at an ignition or operating frequency close to the resonant frequency of the series resonant circuit L6 / C10 7 94918, the AC voltage supplied to the terminals of the lamp L is about 500 V.

Module D includes a fixed frequency generator 6 provided with quartz, which produces a frequency of e.g. 8 MHz. This frequency is fed to a frequency control unit 10, which may include, for example, a correspondingly programmed microprocessor (CPU). The frequency control unit supplies the 8 MHz frequency transmitted from the fixed frequency generator 6 to block 7, which supplies the corresponding count pulses (clock) to the 8-bit counter 9 and at the same time causes the 8-bit counter 9 to count up or down. The latter depending on the level of the parameters input to the frequency control unit 10 of the ballast. The pointer of the 8-bit counter 9 is fed to a 7-bit comparator 16. The latter is further connected via a 7-bit bus line to one of the flip-flops FF connected in series to the counter logic 8. The 8 MHz frequency of the fixed frequency generator 6 is fed to the flip-flop chain for calculation, whereby each flip-flop FF of the chain divides the frequency by a factor of 2 downwards. When the level of the flip-flop chain is equal to that indicated by the 6-bit counter 9, then the logic part of the counter logic 8 connected to the 7-bit comparator 16 returns the flip-flop chain via the line R. At the same time, the logic part of the counter logic 8 respectively supplies a downlink divided frequency to the control circuit 15, the output of which is connected to the winding L3 of the phase transformer T1 of the inverter-forming module C.

The control unit 10 (CPU) with a programmed microprocessor processes the signals input to it, which correspond to the individual measured parameters, in parallel and / or in series. The microprocessor is programmed to execute a specific program to process these signals. This will be explained later in terms of mode of operation.

The first parameter is the lamp voltage UL produced in block F, which is the AC voltage. This is fed to the input of a comparator or controller 8 94918. The comparator or counter controller 12 is further connected to a nominal value sensor 11, which supplies it with three nominal residues U 1, U 2 and Ug. These three rated voltages are DC voltages. The comparator or counter controller 12 in each case compares the threshold value of the lamp AC voltage U1 with the nominal voltage in question.

After switching on the ballast, the lamp voltage ϋχ, usually increases. Only when the circuit is short-circuited does it remain below the rated short-circuit voltage Ug. The control unit 10 now checks for a certain period of time, for example during the mains AC voltage period, whether the lamp voltage U & remains below the nominal short-circuit voltage Ur. If so, the control unit 10 switches off the controller 15. Further, the control unit 10 switches the whole module D to the high-ohm mode. This means that the blocks and components of module D are ready for operation, but they only receive very little power. Since no AC voltage is supplied to module E and thus also to modules G and H due to the disconnection of the controller 15, the blocks and components of module D receive voltage from module B. However, as mentioned above, only high DC voltage is available at terminal 16 of module B, but as a semiconductor chip however, the power dissipation with respect to the distribution voltage due to the voltage difference of the components or blocks of the formed module D is small, because the power consumption of the module D is also small due to the high-density state.

When the module D is switched from the high-resistance mode to the operating mode again, the voltage distribution takes place by means of the low DC voltage Ujjv .. available at the output of the module H. The switching between the two voltage distribution possibilities takes place by means of the control unit 10 in block 17 for the voltage distribution of the module D.

Since immediately after the lamp L is turned on, the lamp voltage U1 drops sharply, namely below the rated short-circuit voltage Uk, it is necessary to turn off the check of the lamp voltage U1 with the comparator or controller 12 immediately after starting the lamp L.

The cut-out is programmed in the microprocessor program of the control unit 10.

The disconnection of the controller 15 and the setting of the module D to the high-ohmic state due to a short circuit detected can only be reversed by switching off and on again the mains AC voltage. When there is no short circuit in the circuit, the lamp voltage U1 exceeds the nominal short-circuit voltage Ur and rises until it reaches the nominal preheating voltage Uh · This is about 1.4 V. This corresponds to a voltage of approximately 200 V at the terminals of the lamp L. When the comparator or counter of the control unit 10 indicates that the lamp voltage U1 is equal to the nominal preheating voltage Uh / then the control unit 10 adjusts the frequency supplied to the module C so that the lamp voltage U1 remains equal to the nominal preheating voltage Uh · during this time the heating coils of the lamp L of the module E heat up and start to radiate. The idle frequency supplied to module C (inverter) in this case is approx. 123 kHz. The preheating time is included in the microprocessor (CPU) program of the control unit.

At the end of the preheating time, according to the program entered therein, the control unit causes the frequency supplied to the module C to be reduced in the direction of the operating frequency, which is approximately 62 kHz. Decreasing the frequency of the inverter (module C) causes the AC voltage to rise during lamp oscillations of the lamp L (module E) to approx. 500 V. By comparing the lamp voltage U1 with the third rated voltage delivered from the nominal sensor li, the nominal ignition voltage Ug in the controller, the control unit 10 now ensures, by interpreting the output signal of the controller 12, that the lamp voltage U1 is kept equal to the nominal ignition voltage Ug. The nominal ignition voltage Uz is approx. 3.5 V. The lamp L should now light up. When ignition occurs, the lamp voltage Ul drops sharply. This is detected by the control unit 10 via the comparator 1094918 or counter 12. The preheating device with the lamp L is thus in operation.

When the lamp voltage U1 does not fall below the nominal ignition voltage Uz within a certain period of time, this means that no ignition takes place. The reason for the non-ignition may be, for example, a gas failure of the lamp L or the radiative capacity of the heating coils of the lamp L may be exhausted.

If lamp L does not start for these or other reasons despite reaching the starting voltage, there is a risk that the connection will be damaged if a relatively high starting voltage is maintained for a long time. For this reason, the control unit (CPU) 10 is programmed so that the unsuccessful start attempt is stopped after a certain time. This is done by the control unit 10 increasing the frequency supplied to the inverter (module C) in the direction of the idle frequency, with the result that the voltage at the terminals of the lamp L decreases again. The control unit 10 is further programmed so that the first unsuccessful start attempt may be associated with a certain number of other similar start attempts. If, even after these other start-up attempts, the lamp L does not light up, then the frequency of the inverter is set to the highest possible value, i.e. idle frequency and remains there until either lamp L is replaced or the AC mains is disconnected and reconnected.

Another parameter that is monitored is the lamp current. The lamp current corresponds to the actual value voltage Uj ^, which is supplied by the module G. This is fed to the comparator 13 of the module D, which also receives a reference voltage ** Uilm · from the reference voltage sensor 1, which corresponds to the minimum lamp current. The comparator 13 compares the voltage Uil with the voltage Uilm 3a reports the result to the control unit 10. When the voltage Uj1 corresponding to the lamp current falls below the reference voltage, this may be due to a rupture of the heating coil of the lamp L or the fact that the lamp L is not properly held or removed. In this case, the control unit 10 controls the frequency supplied to the inverter (module C) again to the highest possible value, i.e. to the idle frequency. Thus, the connections (base) of the lamp L have a relatively low and thus harmless voltage, which is especially important when the lamp L is removed.

Another monitored parameter is the low DC voltage produced by module H for the supply of blocks and elements of module D. This voltage Ujjv is applied to a comparator 2, to which a reference voltage equal to the minimum DC voltage to be produced by the module H is further applied from the reference voltage sensor 1. The reference result of the comparator 2 is again fed to the control unit 10. When the low DC voltage Ujjv produced by the module H falls below the reference voltage the control unit 10 controls the frequency of the inverter again to the idle frequency and switches the module D to the high-ohmic state.

One monitored parameter is the DC voltage produced by module B.

The voltage corresponding to this DC voltage and distributed downwards is the voltage Uq, which can be taken from the module M. It is supplied to the comparator 3. The comparator 3 is also supplied with a reference voltage Uq * from the reference voltage sensor 1, which corresponds to the minimum DC voltage. The comparison result of the comparator 3 is in turn reported to the control unit 10. When the voltage Uq falls below the reference voltage Uqm #, this means, for example, that the DC voltage produced by the module B has fallen below 150 V. At this DC voltage, the inverter no longer generates energy to turn on the lamp. Attempts to start could then cause the lamp to be pre-damaged. The control unit now inspect at least half of the network cycle time is less than the module to H released tasajännnite Uq vähimmäistasajännitteen U ^ vm at least once. If this is the case, the controller 15 is disconnected. This means that no more boot attempts will be made.

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One parameter to be monitored is DC power. The actual DC power is calculated by multiplying the DC voltage Uq supplied by the module M and the DC voltage Ujg supplied by the module K. The latter DC voltage Ujg corresponds to the DC current obtained from the connection. The voltage Upc corresponding to the DC power produced by the multiplier 5 is supplied to the controller 4. A reference voltage Upg corresponding to the nominal power is additionally supplied to the controller 4. The output signal of the comparator controller 4 is fed to the control unit 10. This now adjusts the frequency of the inverter (module C) so that the received DC power remains constant. In this way, the light output of the lamp L is likewise constant. It should be mentioned in this connection that it can be arranged that the reference voltage Upg in the reference voltage sensor 1 is made externally adjustable in order to equalize the component tolerances and the power received from the lamp L can be adjusted to these tolerances by tuning a potentiometer (not shown).

When the frequency generator circuit has to be raised from the operating frequency to the idle frequency, the entire frequency range does not have to be swept continuously, but this can take place by the control unit 10 transmitting a reset pulse to the 8-bit counter 9 via line R.

Finally, the parameter to be monitored is the load impedance of the field effect transistors FET1 and FET2 of the inverter (module C). When the DC voltage of the inverter produced by the module B decreases, for example when the mains AC voltage drops sharply or - when the inverter distribution DC voltage is taken from the central battery, its voltage decreases, the load on the field effect transistors · * becomes capacitive. The capacitive load of the field effect transistors can occur especially with the above-mentioned decrease of the distribution DC voltage of the inverter when the control frequency supplied to the inverter approaches its lowest limit value. Under capacitive load »13 94918 there is a risk of breakage of the field effect transistors. To avoid ka-passive loading, the quality of the load impedance is therefore transmitted to the field effect transistors.

This is done by taking the voltage ϋχ from the output of the controller 15 and comparing it in the phase comparator 14 with the voltage Un i corresponding to the lamp current. The trailing edge of the voltage ϋχ, which is the rectangular voltage, then determines the reference time tv. When the load on the field effect transistors becomes inductive, the voltage Un ,, which consists of sinusoidal half-waves, shifts to the right in Fig. 2, because in the inductive case the voltage lags behind the current. In the capacitive case, this is the opposite. The output signal of the phase comparator 14 is fed to the control unit 10. As the load of the field effect transistors approaches the capacitive case, the control unit 10 causes the frequency supplied to the inverter to increase, with the result that the load becomes inductive again.

Several variations of the pre-switching device described above can be considered. Thus, for example, it is not necessary for all parameters to be measured and taken into account. The parameters can be measured continuously or intermittently. The control unit does not have to be formed by a microprocessor (CPU), but can be formed of several individual control block memories or the like. Measurement times, measurement intervals and other times, such as preheating time, can be determined by counter logic (flip-flop chain) or by a separate time countdown circuit. Of course, the above embodiments can also be used in a pre-switching device having more than? . one lamp. Thus, for example, two lamps may be connected in a conventional tandem connection.

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Claims (8)

14 94918 l. A ballast for a discharge lamp arranged in parallel with respect to the capacitor of a series resonant circuit to an inverter load circuit, which inverter is connected to a DC source and is controlled by is a voltage measuring unit connected to the control unit, which measures the voltage across the lamp and produces a measuring signal corresponding to this voltage, and a comparator, characterized in that a measuring signal (UL) corresponding to the lamp voltage is fed to a comparator (12) comparing this (UL) short circuit to the corresponding stored reference signal (UK) and informs the control unit (10) of the reference result, and that the control unit (10) switches off the frequency generator rin (6, 7, 8, 9, 15, 16) or an inverter (C) when the signal comparison shows that the lamp voltage does not exceed the short-circuit voltage within a specified period of time. : 2. A ballast for a discharge lamp arranged in parallel with respect to a capacitor of a series resonant circuit to an inverter load circuit connected to a DC source and controlled by a bias generator having a combined voltage measuring unit which measures the lamp voltage and produces a corresponding signal, and a controller, characterized in that a measuring signal (UL) corresponding to the lamp voltage is fed to a controller (12) which compares it (UL) with a stored reference signal corresponding to the preheating voltage (UL); UH) and informs the control result control unit (10) that the control unit (10) sets the frequency of the frequency generator (6, 7, 8, 9, 15, 16) close to idle then adjust the frequency of the lamp for a certain preheating time to be equal to the preheating voltage, and that at the end of the preheating time the control unit (10) adjusts the frequency of the frequency generator (6, 7, 8, 9, 15, 16) to decrease the operating frequency. in the direction of. 3. A biasing device for a discharge lamp arranged in parallel with respect to a capacitor of a series resonant circuit to an inverter load circuit, which inverter is connected to a DC voltage source and is controlled by a bias generator with unit which measures the lamp voltage and produces a corresponding signal, characterized in that the signal corresponding to the lamp voltage (UL) is compared with a reference signal (Uz) corresponding to the ignition voltage of the lamp and the reference result is fed to the control unit (10), the control unit (10) adjusts the frequency generator (6, 7, 8, 9, 15, 16) in a closed control circuit according to the comparative result of the comparator (12) so that the lamp voltage does not exceed the reference voltage for a specified ignition period, and that the control unit (10) increases the frequency of the frequency generator (6, 7, 8, 9, 15, 16) in the direction of the idle frequency at the end of the ignition period when the lamp voltage has not dropped sharply during the ignition period due to ignition . Pre-switching device according to Claim 3, characterized in that the control unit (10) calculates the frequency of the frequency generator (6, 7, 8, 9, 15, 16) again in the operating frequency direction, that the control unit (10) repeats 16 94918 ignition attempts a certain number of times. no ignition occurs, and that the control unit (10) permanently sets the frequency of the frequency generator (6, 7, 8, 9, 15, 16) to the idle frequency when no ignition has occurred after the specified firing attempts. 5. A pre-switching device for a discharge lamp arranged in parallel with respect to a capacitor of a series resonant circuit to an inverter peeling circuit connected to a DC voltage source and controlled by a frequency generator whose current frequency is variable B) the DC voltage produced is fed to a voltage measuring unit (M) which produces a signal corresponding to this DC voltage (UG) and supplies it to the multiplier (5) that the DC current from the DC voltage source (B) is fed to a current measuring unit (K) producing a signal corresponding to the input current (UIG), which is similarly fed to the multiplier (5), that the signal corresponding to the direct current power (UPG) produced by the multiplier (5) is fed to a controller (4) which compares the latter signal with a nominal to the signal corresponding to the switching voltage (UPS) that the reference. the result is fed to the control unit (10) and that the control unit (10) adjusts the frequency of the frequency generator (6, 7, 8, 9, 15, 16) so that the DC power taken from the DC voltage source (B) is kept constant. 6. A ballast for a discharge lamp arranged in parallel with respect to a capacitor of a series resonant circuit to a load circuit of an inverter operating in field effect transistors, which inverter is connected to a DC voltage source and is controlled by between the operating frequency, characterized in that the impedance phase angle of the load circuit (E) of the inverter (C) is determined, a signal corresponding to this phase angle is produced in the measuring unit (14) and fed to the control unit (10) and the control unit (10) adjusts the frequency generator (6), 7, 8, 9, 15, 16) so that the load formed by the load circuit (E) of the inverter (C) does not become capacitive. Pre-switching device according to Claim 6, characterized in that a signal (Uu) corresponding to the current of the lamp (L) is produced in the current measuring unit (G) and fed to a phase comparator (14), that a reference signal corresponding to the control voltage of the inverter (C) is further fed to the phase comparator. UT), and that the reference result of the phase comparator (14) is fed to the control unit (10). Pre-switching device, characterized in that a combination of at least two or more of the preceding claims is used. * 18 94918