EP3863379A1 - Led-konstantstrom-antriebssystem und verfahren dafür - Google Patents

Led-konstantstrom-antriebssystem und verfahren dafür Download PDF

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Publication number
EP3863379A1
EP3863379A1 EP20751466.2A EP20751466A EP3863379A1 EP 3863379 A1 EP3863379 A1 EP 3863379A1 EP 20751466 A EP20751466 A EP 20751466A EP 3863379 A1 EP3863379 A1 EP 3863379A1
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EP
European Patent Office
Prior art keywords
voltage
led
constant current
storage capacitor
led load
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
EP20751466.2A
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English (en)
French (fr)
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EP3863379A9 (de
EP3863379A4 (de
Inventor
Jun Liu
Quanqing Wu
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CRM ICBG Wuxi Co Ltd
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CRM ICBG Wuxi Co Ltd
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Application filed by CRM ICBG Wuxi Co Ltd filed Critical CRM ICBG Wuxi Co Ltd
Publication of EP3863379A4 publication Critical patent/EP3863379A4/de
Publication of EP3863379A1 publication Critical patent/EP3863379A1/de
Publication of EP3863379A9 publication Critical patent/EP3863379A9/de
Pending legal-status Critical Current

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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/355—Power factor correction [PFC]; Reactive power compensation
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/347—Dynamic headroom control [DHC]
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/10—Controlling the intensity of the light
    • H05B45/14—Controlling the intensity of the light using electrical feedback from LEDs or from LED modules

Definitions

  • the present disclosure relates to the field of system design, in particular, to an LED constant current drive system and a method thereof.
  • FIG. 1 shows a common single-segment linear LED drive structure 1.
  • An alternating current input voltage AC IN is converted to an input voltage V IN by a rectification module 11.
  • a positive electrode of the LEDs connected in series is connected to the output terminal of the rectification module 11.
  • a negative electrode of the LEDs connected in series is connected to a constant current control chip 12.
  • the sampling terminal of the constant current control chip 12 is grounded via a sampling resistor 13.
  • An adjustable module 14 is connected in parallel to the rectification module 11. Since the number of LEDs connected in series is fixed, when the input voltage V IN exceeds the LED forward voltage drop V LED , the excess voltage is borne by a constant current control transistor (provided in the constant current control chip 12, not shown in the figure) under the LED.
  • V IN -V LED is the voltage on the constant current control transistor.
  • An electrolytic capacitor C in the adjustable module 14 can store energy, thereby ensuring that the output LED has no strobing. However, the power factor PF of the system will be low.
  • a switch transistor may be connected in series under the input electrolytic capacitor C to control the charge voltage of the electrolytic capacitor C and turn off at a high voltage, such that the voltage on the electrolytic capacitor C decreases, thereby expanding the turn-on angle of the input current to obtain a higher power factor PF.
  • FIG. 2 is an LED drive with an external switch transistor, and a switch transistor N1 is connected in series with the lower plate of the electrolytic capacitor C.
  • FIG. 3 is an LED drive with a built-in switch transistor, and a switch transistor is located inside the constant current control chip 12, which is not shown in the figure.
  • the schemes shown in FIG. 2 and FIG. 3 only make a simple on-off switching operation for the input voltage V IN , that is, only on or off.
  • the system can only have high efficiency or high power factor. That is, the best combination cannot be achieved.
  • the present disclosure provides an LED constant current drive system and a method thereof, to balance the efficiency and power factor.
  • the present disclosure provides an LED constant current drive system, including at least:
  • the present disclosure provides an LED constant current drive method, including at least:
  • FIGs 4-5 It needs to be stated that the drawings provided in the following embodiments are just used for schematically describing the basic concept of the present disclosure, thus only illustrating components only related to the present disclosure and are not drawn according to the numbers, shapes and sizes of components during actual implementation, the configuration, number and scale of each component during the actual implementation thereof may be freely changed, and the component layout configuration thereof may be more complex.
  • this Embodiment provides an LED constant current drive system 2, which includes: an LED load, a constant current control module 21, a storage capacitor Co, a discharge voltage detection module 22, a bus voltage detection module 23 and a charge current control module 24.
  • the LED load is connected with the bus voltage Vin.
  • the bus voltage Vin is provided by the rectification module 25, and the rectification module 25 rectifies the alternating current power supply AC to obtain the bus voltage Vin.
  • the rectification module 25 includes a rectifier bridge structure BD1 and a fuse F1.
  • the rectifier bridge structure BD1 includes two sets of diodes connected in parallel. Each diode set includes two diodes connected in series.
  • the alternating current power supply AC is connected between the two diodes of each diode set after passing through the fuse F1.
  • the bus voltage Vin is a rectified voltage after sinusoidal voltage rectification.
  • the positive electrode of the LED load is connected with the output terminal of the rectification module 25.
  • the LED load includes a plurality of LEDs connected in series.
  • the LED load may also be a series-parallel structure of a plurality of LEDs, and is not limited to this embodiment.
  • the constant current control module 21 is connected with the negative electrode of the LED load, to perform constant current control on the LED load.
  • the constant current control module 21 includes: a first power switch transistor Q1, a first sampling unit 211, and a first operational amplification unit 212.
  • the drain of the first power switch transistor Q1 is connected with the negative electrode of the LED load, the source of the first power switch transistor Q1 is grounded via the first sampling unit 211, and the gate of the first power switch transistor Q1 is connected with the output terminal of the first operational amplification unit 212.
  • the first sampling unit 211 includes a first sampling resistor Rcs, one terminal of the first sampling resistor Rcs is connected with the source of the first power switch Q1, and the other terminal of the first sampling resistor Rcs is grounded.
  • the inverting input terminal of the first operational amplification unit 212 is connected with the source of the first power switch transistor Q1, the non-inverting input terminal of the first operational amplification unit 212 is connected with the reference voltage Vref, and the output terminal of the first operational amplification unit 212 is connected to the gate of the first power switch transistor Q1.
  • the first operational amplification unit 212 compares the sampling voltage of the source of the first power switch transistor Q1 with the reference voltage Vref, to control the current flowing through the LED load, thereby achieving the constant current control.
  • the reference voltage Vref is an internal fixed value or externally provided.
  • the output current of the LED load can be adjusted by changing the resistance value of the first sampling resistor Rcs.
  • the connection relationship between the input terminal and the output terminal of the first operational amplification unit 212 can be adjusted, and the same logic relationship can be achieved by adding an inverter, which is not limited to this embodiment.
  • the constant current control module 21 further includes a dimming unit 213, an input terminal of the dimming unit 213 receives a dimming control signal DIM, and an output terminal of the dimming unit 213 is connected with the non-inverting input terminal of the first operational amplification unit 212.
  • the reference voltage Vref is adjusted based on the dimming control signal DIM, thereby achieving dimming control.
  • the dimming control signal DIM includes, but is not limited to, an analog signal or a pulse width modulation signal (PWM), which will not be described in detail here.
  • the upper plate of the storage capacitor Co is connected to the positive electrode of the LED load.
  • the storage capacitor Co discharges to the LED load.
  • the upper plate of the storage capacitor Co is connected between the rectification module 25 and the LED load, and the lower plate is connected with the charge current control module 24.
  • the bus voltage Vin is greater than the voltage VCo on the storage capacitor Co
  • the bus voltage Vin charges the storage capacitor Co, and at the same time, the bus voltage Vin supplies power to the LED load.
  • the bus voltage Vin is less than the voltage VCo on the storage capacitor Co
  • the storage capacitor Co supplies power to the LED load.
  • the discharge voltage detection module 22 is connected with the negative electrode of the LED load, and the discharge voltage of the storage capacitor Co is determined based on the negative electrode voltage of the LED load to obtain a control signal.
  • the discharge voltage detection module 22 includes: a first detection unit 221 and a comparison unit 222.
  • the detection unit 221 is connected with the negative electrode of the LED load, and detects the negative electrode voltage of the LED load to obtain a second detection voltage.
  • the comparison unit 222 is connected with the output terminal of the detection unit 221, and the discharge voltage of the storage capacitor Co is determined based on the second detection voltage.
  • the detection unit 221 includes a first resistor R1 and a second resistor R2.
  • the first resistor R1 and the second resistor R2 are connected in series between the negative electrode of the LED load and ground, and the second detection voltage is obtained by dividing the voltage.
  • the comparison unit 222 includes a first comparator CMP1 and a second comparator CMP2.
  • the non-inverting input terminal of the first comparator CMP1 is connected with the second detection voltage, and the inverting input terminal is connected with the first preset voltage Ref1, to output a first control signal.
  • the first comparator CMP1 When the second detection voltage is greater than the first preset voltage Ref1, the first comparator CMP1 outputs a high level, and the first control signal is valid.
  • the first comparator CMP1 When the second detection voltage is less than the first preset voltage Ref1, the first comparator CMP1 outputs a low level, and the first control signal is invalid.
  • the inverting input terminal of the second comparator CMP2 is connected with the second detection voltage, and the non-inverting input terminal is connected with the second preset voltage Ref2, to output a second control signal.
  • the second detection voltage is greater than the second preset voltage Ref2
  • the second comparator CMP2 outputs a low level, and the second control signal is invalid.
  • the second comparator CMP2 outputs a high level, and the second control signal is valid.
  • the first preset voltage Ref1 is greater than the second preset voltage Ref2.
  • connection relationship between the input terminals and output terminals of the first comparator CMP1 and the second comparator CMP2 can be adjusted, and the same logic relationship can be achieved by adding an inverter, which is not limited to this embodiment.
  • the bus voltage detection module 23 is connected with the bus voltage Vin, and detects the bus voltage Vin to obtain a first detection voltage V LN .
  • the bus voltage detection module 23 includes a third resistor R3 and a fourth resistor R4.
  • the third resistor R3 and the fourth resistor R4 are connected in series between the output terminal of the rectification module 25 and ground, and the first detection voltage V LN is obtained by dividing the voltage.
  • the bus voltage detection module 23 may be integrated inside the chip, or may be provided outside the chip.
  • the charge current control module 24 is connected with the output terminals of the discharge voltage detection module 22 and the bus voltage detection module 23, and the lower plate of the storage capacitor Co.
  • the charge current of the storage capacitor Co is adjusted based on the control signal and the first detection voltage V LN .
  • the charge current control module 24 includes a second power switch transistor Q2, a second sampling unit 241, a compensation unit 242, a subtraction unit 243, and a second operational amplification unit 244.
  • the drain of the second power switch transistor Q2 is connected with the lower plate of the storage capacitor Co, the source of the second power switch transistor Q2 is grounded via the second sampling unit 241, and the gate of the second power switch transistor Q2 is connected with the output terminal of the second operational amplification unit 244, to adjust the charge current of the storage capacitor Co.
  • the second sampling unit 241 includes a second sampling resistor Rcs, one terminal of the second sampling resistor Rcs is connected with the source of the second power switch Q2, and the other terminal of the second sampling resistor Rcs is grounded.
  • the input terminal of the compensation unit 242 is connected with the discharge voltage detection module 22 and generates a corresponding compensation voltage Vcomp based on the output signal of the discharge voltage detection module 22.
  • the compensation unit 242 includes a compensation voltage generation circuit 242a, a compensation capacitor Ccomp, a first current source 11, and a second current source 12.
  • the compensation voltage generation circuit 242a is connected with the upper plate of the compensation capacitor Ccomp, and the lower plate of the compensation capacitor Ccomp is grounded.
  • One terminal of the first current source 11 is grounded, the other terminal of the first current source 11 is connected with the upper plate of the compensation capacitor Ccomp, and the control terminal of the first current source is connected with the first control signal.
  • the first current source 11 When the first control signal is valid, the first current source 11 is turned on and discharges to the compensation capacitor Ccomp.
  • One terminal of the second current source 12 is connected with the upper plate of the compensation capacitor Ccomp, the other terminal of the second current source 12 is connected with the working voltage VDD, and the control terminal of the second current source 12 is connected with the second control signal.
  • the second control signal When the second control signal is valid, the second current source 12 is turned on and charges the compensation capacitor Ccomp.
  • the value of the compensation voltage Vcomp is adjusted based on the charging and discharging of the first current source 11 and the second current source 12.
  • the compensation capacitor Ccomp may be provided outside the chip, or may be integrated into the chip using digital filtering technology to reduce peripheral components and simplify the system.
  • the subtraction unit 243 is connected with the compensation unit 242 and the output terminal of the bus voltage detection module 23, to obtain the difference between the compensation voltage Vcomp and the first detection voltage V LN .
  • the inverting input terminal of the second operational amplification unit 244 is connected with the source of the second power switch transistor Q2
  • the non-inverting input terminal of the second operational amplification unit 244 is connected with the output terminal of the subtraction unit 243
  • the output terminal of the second operational amplification unit 244 is connected with the gate of the second power switch transistor Q2.
  • the second operational amplification unit 244 compares the sampling voltage of the source of the second power switch transistor Q2 with the output voltage of the subtraction unit 243, to adjust the charge current of the storage capacitor Co.
  • connection relationship between the input terminal and the output terminal of the second operational amplification unit 244 can be adjusted, and the same logic relationship can be achieved by adding an inverter, which is not limited to this embodiment.
  • the compensation unit 242 further includes a third comparator CMP3 and a third current source 13.
  • the non-inverting input terminal of the third comparator CMP3 is connected with the gate of the first power switch transistor Q1, and the inverting input terminal of the third comparator CMP3 is connected with the third preset voltage Ref3, to output a third control signal.
  • the gate voltage of the first power switch transistor Q1 is greater than the third preset voltage Ref3, a high level is output, and the third control signal is valid.
  • One terminal of the third current source 13 is connected with the upper plate of the compensation capacitor Ccomp, the other terminal of the third current source 13 is connected with the working voltage VDD, and the control terminal of the third current source 13 is connected with the output terminal of the third comparator CMP3.
  • the third control signal is valid, the third current source is turned on.
  • connection relationship between the input terminal and output terminal of the third comparator CMP3 can be adjusted, and the same logic relationship can be achieved by adding an inverter, which is not limited to this embodiment.
  • the LED constant current drive system further includes a working voltage generation module 26.
  • the working voltage generation module 26 is connected with the bus voltage Vin.
  • the working voltage VDD is provided for the LED constant current drive system based on the bus voltage Vin.
  • the LED constant current drive system of the present disclosure eliminates LED strobing based on constant current control, supplies power to the LED through the storage capacitor Co during the valley period of the bus voltage, and reduces the charge current of the storage capacitor Co when the bus voltage is too high. Therefore, the power factor and system efficiency are balanced by the LED constant current drive system of the present disclosure.
  • this embodiment provides an LED constant current drive method.
  • the LED constant current drive method of the present disclosure is implemented based on the LED constant current drive system of Embodiment 1.
  • any hardware circuit or software code that can implement the LED constant current drive method of the present disclosure is applicable.
  • the LED constant current drive method includes:
  • the storage capacitor Co discharges to the LED load and performs constant current control on the LED load based on the constant current control module 21.
  • the voltage on the storage capacitor Co would not drop to a very low level, so the chip can be internally powered during the valley period of the bus voltage Vin.
  • the bus voltage Vin is less than the turn-on voltage of the LED load, the bus voltage Vin is insufficient to turn on the LED load.
  • the storage capacitor Co discharges to the LED load to light up the LED load, and the constant current control module 21 performs constant current control on the current flowing through the LED load.
  • the constant current control module 21 detects the source voltage of the first power switch transistor Q1 and compares the source voltage of the first power switch transistor Q1 with the reference voltage Vref, to control the gate of the first power switch Q1 based on the comparison result, thereby achieving the constant current control and assuring that the current flowing through the LED load is constant, so as to eliminate the strobing.
  • the reference voltage Vref is an internal preset value.
  • the output current of the LED can be adjusted by changing the resistance value of the first sampling resistor Rcs.
  • the reference voltage Vref is an adjustable value provided externally.
  • the constant current control module 21 further adjusts the value of the reference voltage Vref based on the dimming control signal DIM, thereby achieving dimming control.
  • the dimming control signal DIM includes, but is not limited to, an analog signal or a PWM signal.
  • the bus voltage Vin When the bus voltage Vin is greater than the turn-on voltage of the LED, the bus voltage Vin supplies power to the LED load, and performs constant current control on the LED load based on the constant current control module 21. At the same time, the bus voltage Vin charges the storage capacitor Co.
  • the bus voltage Vin gradually increases.
  • the bus voltage Vin supplies power to the LED load, and charges the storage capacitor Co.
  • the charge current of the storage capacitor Co is controlled by the second power switch transistor Q2, the second operational amplification unit 244 and the second sampling resistor Rs, thereby expanding the turn-on angle of the input current to improve the power factor.
  • the charge current of the storage capacitor is adjusted based on the negative electrode voltage of the LED load and the bus voltage Vin.
  • the bus voltage detection module 23 detects the bus voltage Vin, and reduces the charge current of the storage capacitor Co to zero when the bus voltage Vin is too high, thereby reducing the loss of the second power switch transistor Q2 and improving the overall efficiency of the system.
  • the discharge voltage of the storage capacitor Co cannot be too high.
  • the discharge voltage of the storage capacitor Co cannot be too low.
  • the first comparator CMP1 controls the turn-on of the first constant current source 11, discharges the compensation capacitor Ccomp and reduces the compensation voltage Vcomp, to reduce the charge current of the storage capacitor Co, so as to reduce the discharge voltage of the storage capacitor Co.
  • the second comparator CMP2 controls the turn-on of the second constant current source 12, charges the compensation capacitor Ccomp and increases the compensation voltage Vcomp, to increase the charge current of the storage capacitor Co, so as to increase the discharge voltage of the storage capacitor Co.
  • the compensation capacitor Ccomp is large, and the loop response is slow.
  • the LED current will drop.
  • the gate voltage of the first power switch transistor Q1 would rise to a high level (especially when the compensation voltage Vcomp is low immediately after turning-on).
  • the third comparator CMP3 detects that the gate voltage of the first power switch transistor Q1 exceeds the third preset voltage Ref3
  • the third constant current source 13 is controlled to be turned on (in this embodiment, the current flowing through the third current source is greater than the current flowing through the second current source, I1>I2), the compensation voltage Vcomp is rapidly increased, the charge current of the storage capacitor Co is enhanced, and the discharge voltage of the storage capacitor Co is quickly increased.
  • the storage capacitor Co discharges to the LED load and performs constant current control on the LED load based on the constant current control module 21.
  • the bus voltage Vin gradually decreases after reaching a peak value.
  • the storage capacitor Co discharges to the LED load until the bus voltage Vin is again greater than the turn-on voltage of the LED or the voltage of the storage capacitor Co is less than the turn-on voltage of the LED.
  • FIG. 5 shows the operational waveform diagram of the LED constant current drive method of the present disclosure:
  • VLED is the turn-on voltage of the LED load.
  • the storage capacitor Co discharges to the LED load.
  • the current ICo of the storage capacitor Co during discharge is a constant value.
  • the current flowing through the LED load is a constant value.
  • the negative electrode voltage VLED- of the LED load gradually decreases (the minimum value is VLED-_min).
  • the bus voltage Vin As shown in FIG. 5 , as the bus voltage Vin rises, at time t1, the bus voltage Vin is greater than the turn-on voltage VLED of the LED load.
  • the bus voltage Vin supplies power to the LED while charging the storage capacitor Co.
  • the current Iin provided by the bus voltage Vin includes the charge current of the storage capacitor Co and the constant current of the LED load.
  • the charge current is determined jointly by the compensation voltage Vcomp and the detection voltage of the bus voltage Vin.
  • the charge current of the storage capacitor Co generally decreases with the increase of the bus voltage Vin. In this embodiment, the charge current of the storage capacitor Co decreases first and then increases. As the voltage VCo of the storage capacitor Co is charged to the highest voltage VCo_max, the storage capacitor Co stops charging. During this process, the negative electrode voltage VLED- of the LED load gradually increases.
  • the bus voltage Vin starts to decrease after reaching a peak value.
  • the storage capacitor Co begins to discharge to the LED load until a power frequency cycle terminals at time t3.
  • the shadow area of the charge current A of the storage capacitor Co is equal to the shadow area of the discharge current B of the storage capacitor Co in the figure, C is the shadow area of the current provided by the bus voltage to the LED.
  • times t4-t7 and times t8-t11 are power frequency cycles of different bus voltages.
  • the charge current changes with the change of bus voltage.
  • the minimum charge current can be reduced to zero, and after the loop adjustment, the minimum value of the negative electrode voltage of the LED load is VLED-_min and remains unchanged, which keeps the output LED current constant while minimizing the loss of the second power switch transistor Q2.
  • the present disclosure reduces the charge current of the storage capacitor Co when the bus voltage Vin is high through detecting the bus voltage Vin, thereby reducing the charge power consumption of the second power switch transistor Q2 and improving the overall efficiency of the system.
  • Regulating the voltage division ratio of the third resistor R3 and the fourth resistor R4 can adjust the high-voltage drop current. The greater the peak value of the bus voltage Vin, the smaller the peak value of the charge current of the storage capacitor Co, thereby obtaining a compromise between system efficiency and power factor.
  • the present disclosure provides an LED constant current drive system and method, including: an LED load, a positive electrode of the LED load is connected with a bus voltage; a constant current control module, which is connected with a negative electrode of the LED load to perform constant current control on the LED load; a storage capacitor, an upper plate of the storage capacitor is connected with the positive electrode of the LED load; the storage capacitor discharges to the LED load when the bus voltage is less than a voltage on the storage capacitor; a discharge voltage detection module, which is connected with the negative electrode of the LED load, and obtains a control signal by judging the discharge voltage of the storage capacitor based on the negative electrode voltage of the LED load; a bus voltage detection module, which obtains a first detection voltage by detecting the bus voltage; a charge current control module, which is connected to the output terminal of the discharge voltage detection module and a lower plate of the storage capacitor; the charge current control module adjusts the charge current of the storage capacitor based on the control signal and the first detection voltage.
  • the storage capacitor discharges to the LED load and performs constant current control on the LED load based on the constant current control module.
  • the bus voltage is greater than the turn-on voltage of the LED, the bus voltage supplies power to the LED load, and performs constant current control on the LED load based on the constant current control module.
  • the bus voltage charges the storage capacitor.
  • the storage capacitor discharges to the LED load and performs constant current control on the LED load based on the constant current control module.
  • the LED constant current drive system and method of the present disclosure detects the negative electrode voltage of the LED to control the charge current of the storage capacitor, and minimizes the loss of the constant current power switch transistor while ensuring that the output LED has no strobing; the gate voltage of the constant current power switch transistor is detected, to speed up the loop response speed and ensure a quick start; the storage capacitor can supply power to the LED when the input voltage is during the valley period; at the same time, when the input voltage is high, the charge current of the storage capacitor is reduced. Therefore, the power factor and system efficiency are balanced. Moreover, the peripheral system of the LED constant current drive system of the present disclosure is the most simplified, and the system cost is low. Therefore, the present disclosure effectively overcomes various shortcomings and has high industrial utilization value.

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EP20751466.2A 2019-12-23 2020-06-04 Led-konstantstrom-antriebssystem und verfahren dafür Pending EP3863379A1 (de)

Applications Claiming Priority (2)

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CN201911339911.6A CN113099579B (zh) 2019-12-23 2019-12-23 Led恒流驱动系统及方法
PCT/CN2020/094377 WO2021128743A1 (zh) 2019-12-23 2020-06-04 Led恒流驱动系统及方法

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EP3863379A4 EP3863379A4 (de) 2021-08-11
EP3863379A1 true EP3863379A1 (de) 2021-08-11
EP3863379A9 EP3863379A9 (de) 2021-11-17

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CN108966430B (zh) * 2018-08-31 2020-06-30 广东工业大学 一种led照明灯具线性驱动电路
CN110505733A (zh) * 2019-08-14 2019-11-26 深圳市晟碟半导体有限公司 兼容可控硅调光器的led控制电路、装置和控制方法
CN110572897B (zh) * 2019-08-20 2024-03-19 深圳市晟碟半导体有限公司 高功率因数无频闪的led调光电路、装置及调光方法

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CN113099579B (zh) 2022-07-05

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