EP3807986A1 - Method for controlling the input voltage frequency of a dc-dc convertor - Google Patents

Method for controlling the input voltage frequency of a dc-dc convertor

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Publication number
EP3807986A1
EP3807986A1 EP19726693.5A EP19726693A EP3807986A1 EP 3807986 A1 EP3807986 A1 EP 3807986A1 EP 19726693 A EP19726693 A EP 19726693A EP 3807986 A1 EP3807986 A1 EP 3807986A1
Authority
EP
European Patent Office
Prior art keywords
voltage
eps
frequency
value
control
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
EP19726693.5A
Other languages
German (de)
French (fr)
Inventor
Miassa TALEB
Abdelmalek Maloum
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Ampere SAS
Original Assignee
Renault SAS
Nissan Motor Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Renault SAS, Nissan Motor Co Ltd filed Critical Renault SAS
Publication of EP3807986A1 publication Critical patent/EP3807986A1/en
Pending legal-status Critical Current

Links

Classifications

    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B60L53/20—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles characterised by converters located in the vehicle
    • B60L53/22—Constructional details or arrangements of charging converters specially adapted for charging electric vehicles
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/007—Regulation of charging or discharging current or voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0016—Control circuits providing compensation of output voltage deviations using feedforward of disturbance parameters
    • H02M1/0022—Control circuits providing compensation of output voltage deviations using feedforward of disturbance parameters the disturbance parameters being input voltage fluctuations
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/01—Resonant DC/DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33573—Full-bridge at primary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L2210/00—Converter types
    • B60L2210/10—DC to DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2207/00—Indexing scheme relating to details of circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J2207/20—Charging or discharging characterised by the power electronics converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4241—Arrangements for improving power factor of AC input using a resonant converter
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/70—Energy storage systems for electromobility, e.g. batteries
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/7072—Electromobility specific charging systems or methods for batteries, ultracapacitors, supercapacitors or double-layer capacitors
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/72—Electric energy management in electromobility
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/80—Technologies aiming to reduce greenhouse gasses emissions common to all road transportation technologies
    • Y02T10/92—Energy efficient charging or discharging systems for batteries, ultracapacitors, supercapacitors or double-layer capacitors specially adapted for vehicles
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02T90/10—Technologies relating to charging of electric vehicles
    • Y02T90/14—Plug-in electric vehicles

Definitions

  • the present invention relates to the field of electric accumulator chargers, in particular for electric or hybrid motor vehicles.
  • the invention relates to a method for frequency control of the input voltage of a DC-DC converter for an electric storage battery charger.
  • Chargers for electric accumulators, more commonly known as chargers, for electric motor vehicles require large recharging powers, for example up to 22kW in three-phase, or 7kW in single-phase.
  • These chargers generally include two stages of power conversion: a first stage of correction of the power factor, better known by its English name Power Factor Correction, generally abbreviated in PFC, ensuring the AC / DC conversion (AC / DC) of the network voltages to a DC bus (DC bus) and a second DC-DC conversion stage, called DCDC, ensuring control of the output current necessary for charging the battery as well as galvanic isolation of the charger thanks to a transformer.
  • PFC Power Factor Correction
  • DCDC DC-DC conversion stage
  • two DC output voltage bus at the terminals of the output capacitors, are coupled to a DCDC converter each.
  • the DCDC can in particular be of the LLC type, as shown in FIG. 2, comprising a transformer 22 ensuring galvanic isolation of the charger.
  • FIG. 3 represents a simplified diagram of the assembly of the DCDC converter of FIG. 2, comprising a capacitance Cr and two inductances Lr and Lm.
  • the input voltage corresponds to the DC direct bus and the output voltage is the battery voltage.
  • the gain then corresponds to the ratio of the two voltages.
  • the first DCDC mosfet 120 bridge type LLC operates with a duty cycle of 50% and is frequency controlled.
  • a frequency command makes it possible to adapt the gain of the DCDC and to adjust the voltage of the DC buses at the charger input to a determined setpoint.
  • the frequency can fluctuate for example between 60kHz and 200kHz.
  • the transfer function can also be obtained by the so-called “small signal” method which consists in deducing a transfer function from an excitation around a function point, and from the measurement of the DCDC response, such as described in the doctoral thesis of YANG, Bo. Topology investigation of front end DC / DC converter for distributed power System. 2003. Nevertheless, this transfer function is only valid at the operating point considered and becomes obsolete with each change of operating point. It is therefore necessary to recalculate it each time. Also such a solution is relatively complex to implement and costly in computation time.
  • the output voltage is imposed by the battery.
  • this output voltage varies over a wide range of values, for example between 250V and 430V.
  • regulation of the DC voltage at the input is desirable, because it makes it possible to impose a DC voltage across the capacitors, at the output of the PFC.
  • the method further comprising:
  • control frequency corresponds to said minimum control frequency
  • control frequency corresponds to said maximum control frequency
  • control frequency corresponds to an average frequency calculated as a function of the difference between the setpoint voltage value and the measured voltage, values of upper and lower error and maximum and minimum command frequency values.
  • the control frequency is calculated by applying the following equation: in which the error value corresponds to the difference VDCR-VDCM between the setpoint voltage value and the measured voltage.
  • control is at least partially regulated by an open loop regulator.
  • open loop regulator e.g., one can refine the calculation of control frequency.
  • the command is frequency-regulated by proportional-integral regulation only when the measured voltage is between said upper limit voltage and said lower limit voltage.
  • the control can be improved by selectively refining the control frequency calculation when the measured voltage is close to the setpoint voltage.
  • the invention also relates to a device for controlling the frequency of a direct current - direct current converter comprising means for implementing the method as described above.
  • the invention also relates to a battery charger for electric accumulators comprising:
  • FIG. 1 is a schematic view of an electric accumulator charger known from the prior art
  • FIG. 2 is a detail view of a DC-DC converter of a charger according to Figure 1;
  • FIG. 3 is a simplified diagram of an LLC circuit of a DC-DC converter according to Figure 2;
  • FIG. 4a is a schematic representation of the method according to an embodiment of the invention.
  • FIG. 4b is a detailed view of a step of calculating the method according to the embodiment of Figure 4a;
  • FIG. 5 is a diagrammatic representation of the applied frequency control of the method, with the time on the abscissa and the volts on the ordinate, as a function of the limit voltages, the reference voltage and the measured voltage, of the step of calculation of the method according to the embodiment of FIG. 4a;
  • FIG. 6 is a flow diagram of the method implemented according to the embodiment of Figure 4a.
  • a charger 1 for electric accumulators 13 connected to a three-phase electric network 10 includes a power factor correction stage 11, also called PFC stage 11, and converters direct current-direct current DCDC 12a and 12b each comprising an inverter 212.
  • the three-phase electrical network 10 is mounted to an input filter 14 transmitting filtered input currents to the PFC stage 11.
  • two DC voltage buses connected to the terminals of the output capacitors of step PFC 11, are each coupled to a DCDC converter 12a, 12b, connected in output in parallel to a storage battery 13.
  • Each DCDC 12a, 12b of which a single copy is shown in Figure 2, includes an input mosfet bridge 120, an LLC circuit 121, of which a simplified equivalent representation is shown in Figure 3, a transformer 22 and an output diode bridge 122.
  • the charger 1 further comprises control means 15 of the direct current / direct current converters 12 suitable for implementing a control method 60 according to the invention.
  • the control method 60 aims to frequency control the input voltages of the DC-DC converters 12.
  • the method for controlling a DC-DC converter comprises a plurality of preliminary steps 61, 62, 63. These preliminary steps 61 -63 are independent of each other.
  • the preliminary steps 61 -63 aim to define operating parameters of the process; they can be carried out prior to the implementation of the process, for example during a calibration phase, or dynamically at the start of the process.
  • a step 61 is implemented of defining a maximum control frequency value FRMAX and a minimum control frequency value FRMIN, for example here a maximum frequency FRMAX of 200 KHz, and a frequency minimum FRMIN of 60 KHz.
  • a step 62 of implementing a set voltage value VDCR is implemented towards which the input voltage must converge.
  • VDCR 450V.
  • an error zone 51 is defined 63, defined by two error values, a higher error value eps and a lower error value -eps, these two error values making it possible to define a limit voltage value upper VDRC + eps and a lower limit voltage value VDCR - eps.
  • the upper eps and lower -eps error values have an equal absolute value, so as to define an error zone around the symmetrical setpoint VDCR voltage value.
  • the invention is not limited to this equality of absolute value, and it is possible to provide error values greater eps and lower -eps having a different absolute value.
  • the method then implements a step 64 of obtaining a measured value of the input voltage VDCM.
  • a step 65 of calculating a control frequency value of the DC-DC converter is then implemented.
  • the measured input voltage VDCM is compared with the values of upper limit voltages VDCR + eps and lower limit VDCR - eps.
  • control frequency F corresponds to an average frequency FMOY calculated as a function of the difference between the measured voltage and the reference voltage, the values of the upper and lower limit errors and the values of maximum and minimum control frequency.
  • This average frequency FMOY is calculated according to the following equation:
  • the pair of error parameters -eps, eps makes it possible to define a zone of error close to the VDCR setpoint, in which the control means calculate a frequency FMOY which makes it possible to precisely converge to the VDCR setpoint value.
  • VDRC - VDRM error reaches one of the -eps, eps thresholds, a command frequency is calculated to precisely reach the setpoint and cancel the static error.
  • the minimum frequency FRMIN OR maximum FRMAX is applied as described by the following logic, to ensure efficient convergence.
  • an Integral Proportional Regulator 42 is activated when the measured voltage VDCM is strictly between said upper limit voltage VDCR + eps and said lower limit voltage VDCR - eps. This makes it possible to refine the frequency calculation F to be applied and improves the convergence of the voltage measured over a few volts.
  • the output of the first control stage 41 therefore arrives as an open-loop control command called feed-forward e t is added 43 to the results obtained by the PI regulator 42.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Transportation (AREA)
  • Mechanical Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention concerns a method (30) for controlling the input voltage frequency of a DC-DC converter (12) comprising a step (65) of calculating a control frequency value (F) of said DC-DC converter (12), wherein: - if the measured voltage (VDCM) is greater than said upper voltage limit (VDCR+eps), the control frequency (F) corresponds to said minimum control frequency (FRMIN); - if the measured voltage (VDCM) is less than said lower voltage limit (VDCR-eps), the control frequency corresponds to said maximum control frequency (FRMAX); and - if the measured voltage (VDCM) is between said upper voltage limit (VDCR+eps) and said lower voltage limit (VDCR-eps), the control frequency (F) corresponds to an average frequency (FMOY) calculated as a function of the difference between the setpoint voltage value (VDCR) and the measured voltage (VDCM), upper error values (eps) and lower error values (-eps) and maximum (FRMAX) and minimum (FRMIN) control frequency values.

Description

Procédé de commande en fréquence de la tension d’entrée d’un convertisseur courant continu-courant continu  Frequency control method of the input voltage of a DC-DC converter
La présente invention concerne le domaine des chargeurs d’accumulateurs électriques, en particulier pour les véhicules automobiles électriques ou hybrides. The present invention relates to the field of electric accumulator chargers, in particular for electric or hybrid motor vehicles.
Plus précisément l’invention concerne un procédé de commande en fréquence de la tension d’entrée d’un convertisseur courant continu-courant continu pour un chargeur d’accumulateurs électriques.  More specifically, the invention relates to a method for frequency control of the input voltage of a DC-DC converter for an electric storage battery charger.
Les chargeurs d’accumulateurs électriques, plus communément appelés chargeurs, de véhicule automobile électriques nécessitent d’importantes puissances de recharges, par exemple pouvant aller jusqu’à 22kW en triphasé, ou 7kW en monophasé.  Chargers for electric accumulators, more commonly known as chargers, for electric motor vehicles require large recharging powers, for example up to 22kW in three-phase, or 7kW in single-phase.
Ces chargeurs comprennent généralement deux étages de conversion de puissance : un premier étage de correction du facteur de puissance, plus connu sous son nom anglophone Power Factor Correction, généralement abrégé en PFC, assurant la conversion alternatif/continu (AC/DC) des tensions réseaux vers un bus continu (bus DC) et un deuxième étage de conversion continu- continu, dit DCDC, assurant le contrôle du courant de sortie nécessaire à la charge de la batterie ainsi qu’une isolation galvanique du chargeur grâce à un transformateur.  These chargers generally include two stages of power conversion: a first stage of correction of the power factor, better known by its English name Power Factor Correction, generally abbreviated in PFC, ensuring the AC / DC conversion (AC / DC) of the network voltages to a DC bus (DC bus) and a second DC-DC conversion stage, called DCDC, ensuring control of the output current necessary for charging the battery as well as galvanic isolation of the charger thanks to a transformer.
En référence à la figure 1 d’art antérieur, deux bus de tension continue DC de sortie, aux bornes des capacités de sortie, sont couplés à un convertisseur DCDC chacun.  With reference to FIG. 1 of the prior art, two DC output voltage bus, at the terminals of the output capacitors, are coupled to a DCDC converter each.
Le DCDC peut notamment être du type LLC, tel que représenté figure 2, comprenant un transformateur 22 assurant une isolation galvanique du chargeur.  The DCDC can in particular be of the LLC type, as shown in FIG. 2, comprising a transformer 22 ensuring galvanic isolation of the charger.
La figure 3 représente un schéma simplifié du montage du convertisseur DCDC de la figure 2, comprenant une capacité Cr et deux inductances Lr et Lm. La tension d’entrée correspond au bus continu DC et la tension de sortie est la tension de la batterie. Le gain correspond alors au rapport des deux tensions.  FIG. 3 represents a simplified diagram of the assembly of the DCDC converter of FIG. 2, comprising a capacitance Cr and two inductances Lr and Lm. The input voltage corresponds to the DC direct bus and the output voltage is the battery voltage. The gain then corresponds to the ratio of the two voltages.
Le premier pont de mosfet 120 du DCDC de type LLC fonctionne avec un rapport cyclique de 50% et est commandé en fréquence. En effet, une commande en fréquence permet d’adapter le gain du DCDC et de régler la tension des bus DC en entrée du chargeur à une consigne déterminée. Selon la tension de la batterie et la puissance demandée, la fréquence peut fluctuer par exemple entre 60kHz et 200kHz. The first DCDC mosfet 120 bridge type LLC operates with a duty cycle of 50% and is frequency controlled. In fact, a frequency command makes it possible to adapt the gain of the DCDC and to adjust the voltage of the DC buses at the charger input to a determined setpoint. Depending on the voltage of the battery and the power required, the frequency can fluctuate for example between 60kHz and 200kHz.
Les solutions proposées dans l’art antérieur pour la commande de ce type de convertisseurs DCDC présentent généralement des régulations de la tension de sortie tel que celle divulguée dans la publication DRGONA, Peter, FRIVALDSKŸ, Michal, et SIMONOVÂ, Anna. A New Approach of Control System Design for LLC Résonant Converter. In : MATLAB for Engineers-Applications in Control, Electrical Engineering, IT and Robotics. InTech, 2011, dans lequel la tension de sortie du DCDC est commandée en utilisant la fréquence de découpage. Une fonction de transfert entre rapport cyclique et tension de sortie est déduite à partir de méthodes d’identification en utilisant un modèle hardware PSPICE simulant des dynamiques des réponses de tension de sortie à un échelon de fréquence. Un régulateur est ensuite conçu en se basant sur la fonction de transfert déduite précédemment.  The solutions proposed in the prior art for the control of this type of DCDC converters generally present regulations of the output voltage such as that disclosed in the publication DRGONA, Peter, FRIVALDSKŸ, Michal, and SIMONOVÂ, Anna. A New Approach of Control System Design for LLC Resonant Converter. In: MATLAB for Engineers-Applications in Control, Electrical Engineering, IT and Robotics. InTech, 2011, in which the DCDC output voltage is controlled using the switching frequency. A transfer function between duty cycle and output voltage is deduced from identification methods using a PSPICE hardware model simulating the dynamics of output voltage responses at a frequency step. A regulator is then designed based on the transfer function deduced previously.
La fonction de transfert peut aussi être obtenue par la méthode dite « petit signal » qui consiste à déduire une fonction de transfert à partir d’une excitation autour d’un point de fonction, et de la mesure de la réponse du DCDC, tel que décrit dans la thèse de doctorat de YANG, Bo. Topology investigation of front end DC/DC converter for distributed power System. 2003. Néanmoins, cette fonction de transfert n’est valable qu’au point de fonctionnement considéré et devient obsolète à chaque changement de point de fonctionnement. Il est donc nécessaire de la recalculer à chaque fois. Aussi une telle solution est relativement complexe à mettre en œuvre et coûteuse en temps de calcul.  The transfer function can also be obtained by the so-called “small signal” method which consists in deducing a transfer function from an excitation around a function point, and from the measurement of the DCDC response, such as described in the doctoral thesis of YANG, Bo. Topology investigation of front end DC / DC converter for distributed power System. 2003. Nevertheless, this transfer function is only valid at the operating point considered and becomes obsolete with each change of operating point. It is therefore necessary to recalculate it each time. Also such a solution is relatively complex to implement and costly in computation time.
On connaît aussi des commandes en régulation de courant continu si la tension en sortie varie sur une plage réduite.  There are also known commands for direct current regulation if the output voltage varies over a reduced range.
Enfin on connaît aussi de la publication FANG, Zhijian, WANG, Junhua, DUAN, Shanxu, et al. Control of an LLC Résonant Converter Using Load Feedback Linearization. IEEE Transactions on Power Electronics, 2018, vol. 33, no 1, p. 887-898 dans laquelle une régulation est construite par commande linéarisante (aussi appelée en anglais feedback linearization) pour commander la tension de sortie d’un DCDC LLC. Cette publication décrit un modèle non linéaire à 7 états, réduit par la suite à 2 états et propose une commande par boucle PI. Toutefois une telle solution impose des adaptations matérielles et logicielles complexes et coûteuses. Finally, we also know from the publication FANG, Zhijian, WANG, Junhua, DUAN, Shanxu, et al. Control of an LLC Resonant Converter Using Load Feedback Linearization. IEEE Transactions on Power Electronics, 2018, vol. 33, no 1, p. 887-898 in which a regulation is constructed by linearizing control (also called in English feedback linearization) to control the output voltage of a DCDC LLC. This publication describes a non-linear 7-state model, subsequently reduced to 2 states and proposes a command by PI loop. However, such a solution requires complex and costly hardware and software adaptations.
Il arrive que la tension de sortie soit imposée par la batterie. En outre, il arrive, en particulier dans les applications de véhicules automobiles électriques que cette tension de sortie varie sur une large plage de valeurs, par exemple entre 250V et 430V.  Sometimes the output voltage is imposed by the battery. In addition, it sometimes happens, in particular in electric motor vehicle applications, that this output voltage varies over a wide range of values, for example between 250V and 430V.
Aussi, une régulation de la tension DC en entrée est souhaitable, car elle permet d’imposer une tension DC aux bornes des capacités, en sortie du PFC.  Also, regulation of the DC voltage at the input is desirable, because it makes it possible to impose a DC voltage across the capacitors, at the output of the PFC.
Toutefois, la régulation de la tension DC en entrée du convertisseur LLC DCDC est un sujet pour lequel l’art antérieur n’apporte aucune solution satisfaisante.  However, regulating the DC voltage at the input of the LLC DCDC converter is a subject for which the prior art provides no satisfactory solution.
Il existe dès lors le besoin d’une solution pour commander la tension continue DC en entrée du convertisseur LLC DCDC de manière rapide et fiable.  There is therefore a need for a solution to control the DC direct voltage at the input of the LLC DCDC converter quickly and reliably.
On propose un procédé de commande en fréquence de la tension d’entrée d’un convertisseur courant continu - courant continu comprenant des étapes préalables de :  We propose a method of frequency control of the input voltage of a direct current - direct current converter comprising preliminary steps of:
- définition d’une valeur de fréquence de commande maximale et d’une valeur de fréquence de commande minimale ;  - definition of a maximum command frequency value and a minimum command frequency value;
- définition d’une valeur de tension de consigne ;  - definition of a setpoint voltage value;
- définition d’une valeur d’erreur supérieure et d’une valeur de tension limite supérieure associée ; d’une valeur d’erreur inférieure et d’une valeur de tension limite inférieure associée, lesdites valeurs de tension limites supérieure et inférieure définissant une amplitude d’erreur autour de ladite valeur de tension de consigne ;  - definition of a higher error value and an associated upper limit voltage value; a lower error value and an associated lower limit voltage value, said upper and lower limit voltage values defining an error amplitude around said setpoint voltage value;
le procédé comprenant en outre :  the method further comprising:
- un étape d’obtention d’une valeur mesurée de la tension d’entrée ;  - a step of obtaining a measured value of the input voltage;
- une étape de calcul d’une valeur de fréquence de commande dudit convertisseur courant continu - courant continu, dans laquelle :  - a step of calculating a control frequency value of said direct current - direct current converter, in which:
- si la tension mesurée est supérieure à ladite tension limite supérieure, la fréquence de commande correspond à ladite fréquence de commande minimale ; - si la tension mesurée est inférieure à la dite tension limite inférieure, la fréquence de commande correspond à ladite fréquence de commande maximale; et - if the measured voltage is greater than said upper limit voltage, the control frequency corresponds to said minimum control frequency; - if the measured voltage is lower than said lower limit voltage, the control frequency corresponds to said maximum control frequency; and
- si la tension mesurée est comprise entre ladite tension limite supérieure et ladite tension limite inférieure, la fréquence de commande correspond à une fréquence moyenne calculée en fonction de l’écart entre la valeur de tension de consigne et la tension mesurée, des valeurs d’erreur supérieure et inférieure et des valeurs de fréquence de commande maximale et minimale.  - if the measured voltage is between said upper limit voltage and said lower limit voltage, the control frequency corresponds to an average frequency calculated as a function of the difference between the setpoint voltage value and the measured voltage, values of upper and lower error and maximum and minimum command frequency values.
Ainsi, on peut obtenir un procédé de commande de la tension d’entrée d’un convertisseur courant continu - courant continu rapide et robuste.  Thus, one can obtain a method of controlling the input voltage of a DC converter - DC direct fast and robust.
Avantageusement et de manière non limitative, lorsque la tension mesurée est comprise entre ladite tension limite supérieure et ladite tension limite inférieure, la fréquence de commande est calculée par l’application de l’équation suivante : dans laquelle la valeur erreur correspond à la différence VDCR-VDCM entre la valeur de tension de consigne et la tension mesurée. Ainsi, on peut assurer une convergence précise vers la valeur de consigne lorsque la tension mesurée est proche de la tension de consigne, et annuler l’erreur statique. Advantageously and without limitation, when the measured voltage is between said upper limit voltage and said lower limit voltage, the control frequency is calculated by applying the following equation: in which the error value corresponds to the difference VDCR-VDCM between the setpoint voltage value and the measured voltage. Thus, it is possible to ensure precise convergence towards the reference value when the measured voltage is close to the reference voltage, and to cancel the static error.
Avantageusement et de manière non limitative, la commande est au moins en partie régulée par un régulateur à boucle ouverte. Ainsi, on peut affiner le calcul de fréquence de commande.  Advantageously and in a nonlimiting manner, the control is at least partially regulated by an open loop regulator. Thus, one can refine the calculation of control frequency.
En particulier, la commande est régulée en fréquence par une régulation proportionnel-intégral seulement lorsque la tension mesurée est comprise entre ladite tension limite supérieure et ladite tension limite inférieure. Ainsi, on peut améliorer la commande en affinant de manière sélective le calcul de fréquence de commande lorsque la tension mesurée est proche de la tension de consigne.  In particular, the command is frequency-regulated by proportional-integral regulation only when the measured voltage is between said upper limit voltage and said lower limit voltage. Thus, the control can be improved by selectively refining the control frequency calculation when the measured voltage is close to the setpoint voltage.
L’invention concerne aussi un dispositif de commande en fréquence d’un convertisseur courant continu - courant continu comprenant des moyens pour mettre en œuvre le procédé tel que décrit précédemment. L’invention concerne aussi un chargeur de batterie d’accumulateurs électriques comprenant : The invention also relates to a device for controlling the frequency of a direct current - direct current converter comprising means for implementing the method as described above. The invention also relates to a battery charger for electric accumulators comprising:
- un étage de correction du facteur de puissance ;  - a power factor correction stage;
- un convertisseur courant continu-courant continu résonant de type LLC ; et  - a resonant DC-DC converter of the LLC type; and
- un dispositif de commande en fréquence dudit convertisseur courant continu-courant continu tel que décrit précédemment.  a device for controlling the frequency of said DC-DC converter as described above.
D’autres particularités et avantages de l’invention ressortiront à la lecture de la description faite ci-après d’un mode de réalisation particulier de l’invention, donné à titre indicatif mais non limitatif, en référence aux dessins annexés sur lesquels :  Other particularities and advantages of the invention will emerge on reading the description given below of a particular embodiment of the invention, given by way of indication but not limitation, with reference to the appended drawings in which:
- la figure 1 est une vue schématique d’un chargeur d’accumulateurs électrique connu de l’art antérieur ;  - Figure 1 is a schematic view of an electric accumulator charger known from the prior art;
- la figure 2 est une vue de détail d’un convertisseur courant continu-courant continu d’un chargeur selon la figure 1 ;  - Figure 2 is a detail view of a DC-DC converter of a charger according to Figure 1;
- la figure 3 est un schéma simplifié d’un circuit LLC d’un convertisseur courant continu-courant continu selon la figure 2 ;  - Figure 3 is a simplified diagram of an LLC circuit of a DC-DC converter according to Figure 2;
- la figure 4a est une représentation schématique du procédé selon un mode de réalisation de l’invention ;  - Figure 4a is a schematic representation of the method according to an embodiment of the invention;
- la figure 4b est une vue de détail d’une étape de calcul du procédé selon le mode de réalisation de la figure 4a ;  - Figure 4b is a detailed view of a step of calculating the method according to the embodiment of Figure 4a;
- la figure 5 est une représentation schématique de la commande en fréquence appliquée du procédé, avec en abscisse le temps et en ordonnée des Volts, en fonction des tensions limites, de la tension de consigne et de la tension mesurée, de l’étape de calcul du procédé selon le mode de réalisation de la figure 4a ; et  FIG. 5 is a diagrammatic representation of the applied frequency control of the method, with the time on the abscissa and the volts on the ordinate, as a function of the limit voltages, the reference voltage and the measured voltage, of the step of calculation of the method according to the embodiment of FIG. 4a; and
- la figure 6 est un organigramme du procédé mis en œuvre selon le mode de réalisation de la figure 4a.  - Figure 6 is a flow diagram of the method implemented according to the embodiment of Figure 4a.
Les figures 1 à 6 se rapportant à un même mode de réalisation, elles seront commentées simultanément.  Figures 1 to 6 relate to the same embodiment, they will be commented on simultaneously.
En référence à la figure 1 , un chargeur 1 d’accumulateurs électriques 13 connecté à un réseau électrique triphasé 10 comprend un étage de correction du facteur de puissance 11 , aussi appelé étage PFC 11 , et des convertisseurs courant continu-courant continu DCDC 12a et 12b comportant chacun un onduleur 212. With reference to FIG. 1, a charger 1 for electric accumulators 13 connected to a three-phase electric network 10 includes a power factor correction stage 11, also called PFC stage 11, and converters direct current-direct current DCDC 12a and 12b each comprising an inverter 212.
Le réseau électrique triphasé 10 est monté à un filtre d’entrée 14 transmettant des courants d’entrée filtrés à l’étage PFC 11.  The three-phase electrical network 10 is mounted to an input filter 14 transmitting filtered input currents to the PFC stage 11.
En sortie du PFC 11 deux bus de tension continue DC, connectés au bornes des capacités de sortie de l’étape PFC 11 , sont couplées chacun à un convertisseur DCDC 12a, 12b, reliés en sortie en parallèle à une batterie d’accumulateurs 13.  At the output of PFC 11 two DC voltage buses, connected to the terminals of the output capacitors of step PFC 11, are each coupled to a DCDC converter 12a, 12b, connected in output in parallel to a storage battery 13.
Chaque DCDC 12a, 12b, dont un seul exemplaire est représenté figure 2, comprend un pont de mosfet d’entrée 120, un circuit LLC 121 , dont une représentation équivalente simplifiée est représentée figure 3, un transformateur 22 et un pont de diodes de sortie 122.  Each DCDC 12a, 12b, of which a single copy is shown in Figure 2, includes an input mosfet bridge 120, an LLC circuit 121, of which a simplified equivalent representation is shown in Figure 3, a transformer 22 and an output diode bridge 122.
Le chargeur 1 comprend en outre des moyens de commande 15 des convertisseurs courant continu-courant continu 12 aptes à mettre en œuvre un procédé de commande 60 selon l’invention.  The charger 1 further comprises control means 15 of the direct current / direct current converters 12 suitable for implementing a control method 60 according to the invention.
Le procédé de commande 60 selon l’invention vise à commander en fréquence les tensions d’entrée des convertisseurs courant continu-courant continu 12.  The control method 60 according to the invention aims to frequency control the input voltages of the DC-DC converters 12.
En référence aux figures 4, 5 et 6, le procédé de commande d’un convertisseur courant continu-courant continu comprend une pluralité d’étapes préliminaires 61 , 62, 63. Ces étapes préliminaires 61 -63 sont indépendantes les unes des autres. Les étapes préliminaires 61 -63 visent à définir des paramètres de fonctionnement du procédé ; elles peuvent être réalisées préalablement à la mise en œuvre du procédé, par exemple lors d’une phase d’étalonnage, ou dynamiquement au début du procédé.  With reference to FIGS. 4, 5 and 6, the method for controlling a DC-DC converter comprises a plurality of preliminary steps 61, 62, 63. These preliminary steps 61 -63 are independent of each other. The preliminary steps 61 -63 aim to define operating parameters of the process; they can be carried out prior to the implementation of the process, for example during a calibration phase, or dynamically at the start of the process.
Ces étapes préliminaires 61-63 peuvent en outre être reproduites durant le fonctionnement du procédé 60, afin de modifier dynamiquement les paramètres de fonctionnement du procédé.  These preliminary steps 61-63 can also be reproduced during the operation of the process 60, in order to dynamically modify the operating parameters of the process.
Tout d’abord, on met en œuvre une étape de définition 61 d’une valeur de fréquence de commande maximale FRMAX et d’une valeur de fréquence de commande minimale FRMIN, par exemple ici une fréquence maximale FRMAX de 200 KHz, et une fréquence minimale FRMIN de 60 KHz. Ensuite on met en œuvre une étape de définition 62 d’une valeur de tension de consigne VDCR vers laquelle la tension d’entrée doit converger. Dans l’exemple de réalisation de la figure 5, VDCR = 450V. First of all, a step 61 is implemented of defining a maximum control frequency value FRMAX and a minimum control frequency value FRMIN, for example here a maximum frequency FRMAX of 200 KHz, and a frequency minimum FRMIN of 60 KHz. Next, a step 62 of implementing a set voltage value VDCR is implemented towards which the input voltage must converge. In the embodiment of Figure 5, VDCR = 450V.
Ensuite on définit 63 une zone d’erreur 51 , définie par deux valeurs d’erreur, une valeur d’erreur supérieure eps et une valeur d’erreur inférieure -eps, ces deux valeurs d’erreur permettant de définir une valeur de tension limite supérieure VDRC + eps et une valeur de tension limite inférieure VDCR - eps.  Then an error zone 51 is defined 63, defined by two error values, a higher error value eps and a lower error value -eps, these two error values making it possible to define a limit voltage value upper VDRC + eps and a lower limit voltage value VDCR - eps.
Dans cet exemple de réalisation on définit une tension d’erreur +eps=100V et -eps=-100V.  In this embodiment, an error voltage + eps = 100V and -eps = -100V are defined.
Ces valeurs de tensions limite supérieure VDRC + eps et inférieure VüCR-eps encadrant la tension de consigne VDCR, définissent ainsi une amplitude d’erreur autour de la tension de consigne VDCR. These upper limit VDRC + eps and lower limit VüC R -eps values framing the setpoint voltage VDCR, thus define an error amplitude around the setpoint voltage VDCR.
Dans ce mode de réalisation, les valeurs d’erreur supérieure eps et inférieure -eps présentent une valeur absolue égale, de sorte à définir une zone d’erreur autour de la valeur de tension de consigne VDCR symétrique. Toutefois l’invention n’est pas limitée à cette égalité de valeur absolue, et on peut prévoir des valeurs d’erreur supérieure eps et inférieure -eps ayant une valeur absolue différente.  In this embodiment, the upper eps and lower -eps error values have an equal absolute value, so as to define an error zone around the symmetrical setpoint VDCR voltage value. However, the invention is not limited to this equality of absolute value, and it is possible to provide error values greater eps and lower -eps having a different absolute value.
Ensuite le procédé met en œuvre une étape d’obtention 64 d’une valeur mesurée de la tension d’entrée VDCM.  The method then implements a step 64 of obtaining a measured value of the input voltage VDCM.
Une étape de calcul 65 d’une valeur de fréquence de commande du convertisseur courant continu-courant continu est alors mise en œuvre.  A step 65 of calculating a control frequency value of the DC-DC converter is then implemented.
Au cours de cette étape de calcul 65, on compare la tension d’entrée mesurée VDCM avec les valeurs de tensions limite supérieure VDCR + eps et inférieure VDCR - eps.  During this calculation step 65, the measured input voltage VDCM is compared with the values of upper limit voltages VDCR + eps and lower limit VDCR - eps.
Si la tension mesurée VDCM est supérieure ou égale à ladite tension limite supérieure VDCR + eps, alors on applique une fréquence de commande F égale à ladite fréquence de commande minimale FRMIN. If the measured voltage VDCM is greater than or equal to said upper limit voltage VDCR + eps, then a control frequency F equal to said minimum control frequency FR MIN is applied.
Si la tension mesurée VDCM est inférieure ou égale à la tension limite inférieure VDCR - eps, alors on applique une fréquence de commande F égale à la fréquence de commande maximale FRMAX. If the measured voltage VDCM is less than or equal to the lower limit voltage VDCR - eps, then a control frequency F equal to the maximum control frequency FR MAX is applied.
Enfin, si la tension mesurée VDCM est strictement comprise entre ladite tension limite supérieure VDCR + eps et ladite tension limite inférieure VDCR - eps, la fréquence de commande F correspond à une fréquence moyenne FMOY calculée en fonction de l’écart entre la tension mesurée et la tension de consigne, des valeurs des erreurs limites supérieure et inférieure et des valeurs de fréquence de commande maximale et minimale. Finally, if the measured voltage VDCM is strictly between said upper limit voltage VDCR + eps and said lower limit voltage VDCR - eps, the control frequency F corresponds to an average frequency FMOY calculated as a function of the difference between the measured voltage and the reference voltage, the values of the upper and lower limit errors and the values of maximum and minimum control frequency.
Cette fréquence moyenne FMOY est calculée selon l’équation suivante : This average frequency FMOY is calculated according to the following equation:
dans laquelle :  in which :
- la valeur erreur correspond à la différence entre la valeur de tension de consigne VDCR et la tension mesurée VDCM, soit erreur=VDCR-VDCM Autrement dit, le couple de paramètres d’erreur -eps, eps, permet de définir une zone d’erreur proche de la consigne VDCR, dans laquelle les moyens de commande calculent une fréquence FMOY qui permet de converger précisément à la valeur de consigne VDCR.  - the error value corresponds to the difference between the setpoint voltage value VDCR and the measured voltage VDCM, i.e. error = VDCR-VDCM In other words, the pair of error parameters -eps, eps, makes it possible to define a zone of error close to the VDCR setpoint, in which the control means calculate a frequency FMOY which makes it possible to precisely converge to the VDCR setpoint value.
En effet, lorsque l’erreur VDRC - VDRM atteint l’un des seuils -eps, eps une fréquence de commande est calculée pour atteindre précisément la consigne et annuler l’erreur statique.  Indeed, when the VDRC - VDRM error reaches one of the -eps, eps thresholds, a command frequency is calculated to precisely reach the setpoint and cancel the static error.
Au-delà ou en deçà de cette zone d’erreur, respectivement, la fréquence minimale FRMIN OU maximale FRMAX est appliquée comme décrit par logique suivante, pour assurer une convergence efficace.  Beyond or below this error zone, respectively, the minimum frequency FRMIN OR maximum FRMAX is applied as described by the following logic, to ensure efficient convergence.
En référence à la figure 4a, un régulateur Proportionnel Intégral 42, appelé plus communément régulateur PI, est activé lorsque la tension mesurée VDCM est strictement comprise entre ladite tension limite supérieure VDCR + eps et ladite tension limite inférieure VDCR - eps. Ceci permet d’affiner le calcul de fréquence F à appliquer et améliore la convergence de la tension mesurée sur quelques volts.  With reference to FIG. 4a, an Integral Proportional Regulator 42, more commonly called PI regulator, is activated when the measured voltage VDCM is strictly between said upper limit voltage VDCR + eps and said lower limit voltage VDCR - eps. This makes it possible to refine the frequency calculation F to be applied and improves the convergence of the voltage measured over a few volts.
La sortie du premier étage de commande 41 arrive par conséquent comme commande à régulation à boucle ouverte dite feed-forward e t est additionnée 43 aux résultats obtenus par le régulateur PI 42.  The output of the first control stage 41 therefore arrives as an open-loop control command called feed-forward e t is added 43 to the results obtained by the PI regulator 42.

Claims

REVENDICATIONS
1. Procédé de commande (60) en fréquence de la tension d’entrée d’un convertisseur courant continu-courant continu (12) de type LLC fonctionnant avec un rapport cyclique de 50% et commandé en fréquence, comprenant des étapes préalables de : 1. Frequency control method (60) of the input voltage of a DC type direct-current converter (12) of LLC type operating with a duty cycle of 50% and frequency controlled, comprising preliminary steps of:
- définition (61 ) d’une valeur de fréquence de commande maximale (FRMAX) et d’une valeur de fréquence de commande minimale (FRMIN); - Definition (61) of a maximum command frequency value (FR MAX ) and a minimum command frequency value (FR MIN );
- définition (62) d’une valeur de tension de consigne (VDCR);  - definition (62) of a setpoint voltage value (VDCR);
- définition (63) d’une valeur d’erreur supérieure (eps) et d’une valeur de tension limite supérieure (VDCR+eps) associée ; d’une valeur d’erreur inférieure (- eps) et d’une valeur de tension limite inférieure (VDCR-eps) associée, lesdites valeurs de tension limites supérieure (VüCR+eps) et inférieure (VDCR-eps) définissant une amplitude d’erreur (51 ) autour de ladite valeur de tension de consigne (VDCR); - Definition (63) of a higher error value (eps) and an associated upper limit voltage value (V DCR + eps); a lower error value (- eps) and an associated lower limit voltage value (V DCR -eps), said upper (VüC R + eps) and lower (V DCR -eps) limit voltage values defining an error amplitude (51) around said setpoint voltage value (VDCR);
le procédé comprenant en outre : the method further comprising:
- un étape d’obtention (64) d’une valeur mesurée de la tension d’entrée (VDCM) ;  - a step of obtaining (64) a measured value of the input voltage (VDCM);
- une étape de calcul (65) d’une valeur de fréquence de commande (F) dudit convertisseur courant continu-courant continu (12), dans laquelle :  - a step of calculating (65) a control frequency value (F) of said DC-DC converter (12), in which:
- si la tension mesurée (VDCM) est supérieure à ladite tension limite supérieure (VüCR+eps), la fréquence de commande (F) correspond à ladite fréquence de commande minimale (FRMIN); - if the measured voltage (VDCM) is greater than said upper limit voltage (VüC R + eps), the control frequency (F) corresponds to said minimum control frequency (FRMIN);
- si la tension mesurée (VDCM) est inférieure à la dite tension limite inférieure (VDCR-eps), la fréquence de commande correspond à ladite fréquence de commande maximale (FRMAX); et - if the measured voltage (VDCM) is less than said lower limit voltage (V DCR -eps), the control frequency corresponds to said maximum control frequency (FRMAX); and
- si la tension mesurée (VDCM) est comprise entre ladite tension limite supérieure (VüCR+eps) et ladite tension limite inférieure (VüCR-eps), la fréquence de commande (F) correspond à une fréquence moyenne (FMOY) calculée en fonction de l’écart entre la valeur de tension de consigne (VDCR) et la tension mesurée (VDCM), des valeurs d’erreur supérieure (eps) et inférieure (-eps) et des valeurs de fréquence de commande maximale (FRMAX) et minimale (FRMIN). - if the measured voltage (VDCM) is between said upper limit voltage (VüCR + eps) and said lower limit voltage (VüCR-eps), the control frequency (F) corresponds to an average frequency (FMOY) calculated as a function of the difference between the setpoint voltage value (VDCR) and the measured voltage (VDCM), upper (eps) and lower (-eps) error values and maximum (FRMAX) and minimum control frequency values ( FRMIN).
2. Procédé selon la revendication 1 caractérisé en ce que lorsque la tension mesurée est comprise entre ladite tension limite supérieure et ladite tension limite inférieure, la fréquence de commande est calculée par l’application de l’équation suivante : 2. Method according to claim 1 characterized in that when the measured voltage is between said upper limit voltage and said lower limit voltage, the control frequency is calculated by applying the following equation:
dans laquelle la valeur erreur correspond à la différence (VDCR-VDCM) entre la valeur de tension de consigne (VDCR) et la tension mesurée (VDCM).  in which the error value corresponds to the difference (VDCR-VDCM) between the setpoint voltage value (VDCR) and the measured voltage (VDCM).
3. Procédé selon la revendication 1 ou 2, caractérisé en ce que la commande est au moins en partie régulée par un régulateur à boucle ouverte. 3. Method according to claim 1 or 2, characterized in that the control is at least partially regulated by an open loop regulator.
4. Procédé selon la revendication 3, caractérisé en ce que la commande est régulée en fréquence par une régulation proportionnel-intégral seulement lorsque la tension mesurée est comprise entre ladite tension limite supérieure et ladite tension limite inférieure. 4. Method according to claim 3, characterized in that the command is regulated in frequency by proportional-integral regulation only when the measured voltage is between said upper limit voltage and said lower limit voltage.
5. Dispositif de commande en fréquence d’un convertisseur courant continu- courant continu comprenant des moyens pour mettre en œuvre le procédé selon l’une quelconque des revendications 1 à 4. 5. Device for controlling the frequency of a DC-DC converter comprising means for implementing the method according to any one of claims 1 to 4.
6. Chargeur (1 ) de batterie d’accumulateurs électriques (13) comprenant : 6. Charger (1) for an electric storage battery (13) comprising:
- un étage de correction du facteur de puissance (1 1 ) ;  - a power factor correction stage (1 1);
- un convertisseur courant continu-courant continu résonant de type LLC (12); - a resonant DC-DC converter of the LLC type (12);
- un dispositif de commande en fréquence dudit convertisseur courant continu- courant continu (12) selon la revendication 5. - a device for controlling the frequency of said DC-DC converter (12) according to claim 5.
EP19726693.5A 2018-06-15 2019-05-27 Method for controlling the input voltage frequency of a dc-dc convertor Pending EP3807986A1 (en)

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FR1855259A FR3082680B1 (en) 2018-06-15 2018-06-15 METHOD FOR FREQUENCY CONTROL OF THE INPUT VOLTAGE OF A DIRECT CURRENT-DIRECT CURRENT CONVERTER
PCT/EP2019/063690 WO2019238405A1 (en) 2018-06-15 2019-05-27 Method for controlling the input voltage frequency of a dc-dc convertor

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FR3082680B1 (en) 2020-05-29
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US20210257921A1 (en) 2021-08-19
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JP7258054B2 (en) 2023-04-14
FR3082680A1 (en) 2019-12-20

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