EP3179557B1 - Elementare mehrfachband-strahlungszelle - Google Patents

Elementare mehrfachband-strahlungszelle Download PDF

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Publication number
EP3179557B1
EP3179557B1 EP16201682.8A EP16201682A EP3179557B1 EP 3179557 B1 EP3179557 B1 EP 3179557B1 EP 16201682 A EP16201682 A EP 16201682A EP 3179557 B1 EP3179557 B1 EP 3179557B1
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EP
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Prior art keywords
frequency band
radiating
band
access
elements
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English (en)
French (fr)
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EP3179557A1 (de
Inventor
Olivier Maas
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Thales SA
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Thales SA
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/28—Combinations of substantially independent non-interacting antenna units or systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/48—Earthing means; Earth screens; Counterpoises
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/10—Resonant slot antennas
    • H01Q13/16—Folded slot antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/30—Combinations of separate antenna units operating in different wavebands and connected to a common feeder system
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/50—Feeding or matching arrangements for broad-band or multi-band operation
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna

Definitions

  • the present invention is in the field of radiating devices designed to operate in two distinct frequency bands. It applies in particular to dual-band radiating cells produced in printed technology, and used by radars with electronic scans for the surveillance of airspace. These radars operate in the S band, and in the band dedicated to IFF applications (English acronym for "Identification, Friend or Foe", or friend or enemy identification).
  • State-of-the-art electronic scanning radars consist of directional antennas made from radiating elements, or radiating cells, assembled within a network. The modification of the amplitude and the phase of each of the radiating elements of the network makes it possible to orient the direction of the radar beam.
  • the frequencies of interest for aerial surveillance applications are the S band, used for the primary radar, and in particular the sub-band 2.9GHz to 3.3GHz, as well as frequency bands of a few MHz or tens of MHz located around frequencies 1.03GHz and 1.09GHz, and used for IFF applications.
  • Current radar equipment whether it be ground speed radars or radars on board a carrier such as a vehicle, ship or aircraft, generally includes two independent systems: a rotary directive antenna dedicated to IFF applications and a array of radiant cells for the Band S radar. The rotary antenna is positioned above or next to the S band radar antenna. The two volumes are therefore added together, which can cause problems during transport or installation of antennas.
  • the invention seeks to solve the general problem of the multiplication of systems by proposing a radiating cell operating simultaneously and without interference, in two distinct frequency bands, in particular the S-band and the frequency band dedicated to IFF applications.
  • a radiating cell makes it possible to create a network radiating dual-band, thereby reducing the overall size of the radar system, as well as the installation complexity and associated usage constraints.
  • the invention proposes a radiating cell for which the accesses to the different frequency bands are independent, which makes it possible to integrate the invention into existing radar devices in a transparent manner.
  • the use, within the same radiating cell of elements specific to each of the operating bands, separated by a gap making it possible to minimize the problems of coupling between elements, is not a solution to the problem when the radiating cell is implemented in a radiating network.
  • the size of the cell is constrained by the pitch of the lattice of the network, which is generally equal to ⁇ / 2, with ⁇ the wavelength in the air corresponding to the maximum frequency.
  • the radiating elements required by the low frequency band become incompatible with the size of this networking step.
  • the step of networking a radiating mesh in S band at 3.3 GHz is around 5 cm.
  • a patch suitable for the band S when produced in the context of a substrate having a relative dielectric constant of 3.55, has dimensions of the order of 25mm x 25mm, compatible with the pitch of networking.
  • a patch for IFF applications due to the frequency ratio 3 between the two bands, will be 3 times larger (and with a surface area 9 times greater). It will then have a size of 75mm x 75mm.
  • a device comprising an S band patch and a patch for IFF applications will therefore not be compatible with the pitch of the radiating mesh.
  • the Australian patent AU 2015101429 A4 presents a dual-band device operating in the Wifi bands at 2.4GHz and 5GHz.
  • the frequency ratio is not an odd multiple, so it does not present any particular coupling problems. It also does not have independent access to each of the frequency bands: the radiating elements associated with each of the frequency bands cannot then be controlled independently.
  • a first known solution to the problem of making a bi-band cell of reduced dimensions consists in using a single broadband radiating element. Once networked, the result is a single broadband network, covering all the bands of interest. However, the production of such a radiating element proves to be complex when the band gap increases, and does not meet the need for independent access to each of the frequency bands.
  • a known solution consists in using, for the low frequency band, elements of the folded monopole or dipole type, or folded slots so as to be able to accommodate them in a reduced surface.
  • the simultaneous use of a patch for the high frequency band, and a slot for the low frequency band is of practical interest, because the slot can be housed in the metallization of the patch, or in that of its plane of mass.
  • Various solutions of this type have been explored, but they run up against the fact that, under these conditions, the radiating slots have a very narrow bandwidth, which limits their advantage.
  • the invention addresses the problem posed by associating a radiating element in the high frequency band of the patch type, with at least one radiating element in the low frequency band of the folded slot type.
  • This approach makes it possible to house the two radiating elements in a reduced size cell, compatible with a network of unit elements operating at the high frequency, that is to say less than a square with a side less than ⁇ H / 2.
  • the elements of the high frequency band (patch) and the low frequency band (slot) are each connected to a separate access, which allows them to be controlled independently in amplitude and in phase. Filters adapted to each of the frequency bands are implemented on each of the ports, so as to eliminate the undesirable contributions linked to the coupling resulting from the proximity between the radiating elements.
  • the invention therefore consists of a device radiating in two distinct frequency bands according to claim 1.
  • the slot-type element is housed in a ground plane of the device.
  • the one or more elements of the folded slot type are folded in a U shape and positioned at the periphery of the device.
  • the number of slot-type elements is equal to the number of sub-bands of the low frequency band, said slot-type elements being supplied by the same second port.
  • the number of slot-type elements is equal to the number of sub-bands of the low frequency band, said slot-type elements being supplied by different ports.
  • the device comprises a single slot-type element supplied by said second access to which it is connected by a resonator circuit, the coupling between said slot and said resonator circuit being adjusted to radiate in two distinct sub-bands of the low frequency band.
  • the resonator circuit is a parallel resonator circuit comprising an inductor and a capacitor.
  • the resonator is connected to the slit type element by a waveguide of length ⁇ / 4, where ⁇ is the wavelength associated with the center frequency of the low frequency band.
  • the filter positioned between the patch-type element and the first access comprises a plurality of sections of microstrip line of different widths.
  • This property allows it to radiate only for one of the frequency bands when these are multiples of one another.
  • the device further comprises a low-pass filter positioned between the said slot-type element or elements and said second port, and configured to filter the high frequency band.
  • the device further comprises a second patch type element suitable for the high frequency band, said second patch type element being disposed above said first patch type element.
  • the device according to the invention can be implemented in a multilayer printed circuit for which said patch type element, said slit type element (s), and said filter positioned between the patch type element and the first access are in different layers of the circuit board.
  • This layer distribution makes it possible to limit the surface of the printed circuit as much as possible. It is possible because the radiating elements do not come to hide, the slit type element or elements being positioned on the periphery of the printed circuit, and therefore of the patch type element.
  • the device according to the invention is adapted to operate when at least one frequency of the high frequency band is an odd integer multiple of a frequency of the frequency band low.
  • the device according to the invention is adapted to operate when the high frequency band comprises the band 2.9GHz - 3.3GHz.
  • the device according to the invention can easily be produced in printed technology.
  • the invention relates to a radiating network configured to radiate in two distinct frequency bands, and characterized in that it comprises radiating cells conforming to the radiating device in two distinct frequency bands according to the invention.
  • the descriptions of the embodiments set out below are dedicated to a particular mode of operation of the invention. This operating mode meets the needs of radar applications for airspace surveillance.
  • the radiating cell presented below seeks to operate in a dissociated manner in the band 2.9GHz - 3.3GHz (sub-band of the S band dedicated to radar applications), as well as in two sub-bands of a few MHz in the frequency band dedicated to IFF applications, a first centered around the 1030MHz frequency and a second centered around the 1090MHz frequency. These two sub-bands correspond to the outward and return paths of the IFF applications.
  • the invention is not limited to this operation or to this type of application, and can be extended mutatis mutandis to other frequency bands, or to other embodiments in which the number of sub-bands chosen within the low frequency band varies.
  • the ratio of the frequency bands is equal to about three. From this in fact, the coupling phenomena between the various radiating elements, introduced by their physical proximity, are reinforced. This is linked to the fact that, when the frequency ratio between the bands is an odd whole number, all the line-based resonant structures function naturally in the same way as the frequency f 0 and all of its odd multiples. As a result, the radiating elements dimensioned for the IFF applications also radiate for the S band.
  • the figure 1 represents a radiating cell according to a first embodiment of the invention.
  • This radiating cell 100 or antenna with printed radiating elements, is a printed circuit comprising multiple layers separated by a dielectric substrate, using distributed elements, that is to say microstrip lines (also designated by the English term “microstrip ").
  • microstrip lines also designated by the English term “microstrip ".
  • This technology is very widespread in microwave frequencies because, for high frequencies, the manipulation of waves from waveguides is simpler than the manipulation of currents and voltages.
  • One of the layers of the printed circuit forms a ground plane.
  • the radiating cell comprises a radiating element 101 of the patch type.
  • a patch is a metallized layer of square or rectangular shape supplied. The dimensions of the patch are chosen so that it radiates in the high frequency band (S band). It is positioned in one of the layers of the circuit.
  • the radiating cell also includes two folded radiating slots 102. These slots have the behavior of dipoles, while being less sensitive to coupling phenomena. They are tuned to operate around the sub-bands of interest in the low frequency band (in the example, 1030MHz and 1090MHz). This agreement is achieved by dimensioning each one with respect to a wavelength close to the desired wavelength, the slit then having a length of ⁇ / 2. In order to slightly decrease the size of the slits, tuning can be achieved by dimensioning them with respect to a wavelength slightly greater than the desired wavelength, then by adjusting their positions relative, the position of their exciter, and their position relative to the patch, so that the coupling phenomena push their operating frequency back onto the desired frequency.
  • slots whose length is adapted to an operating frequency slightly greater than 1100 MHz, which makes them compatible, once folded in three in shape of U, of a mesh dimensioned compared to the frequency of 3.3 GHz, then to push back by coupling their operating frequency on the frequencies of interest 1030 MHz and 1090 MHz by adjusting their positions.
  • the number of slots is adapted to the number of desired low frequency bands.
  • the use of two slots folded in three in the shape of a U and a patch antenna makes it possible to accommodate the three radiating elements in a very reduced environment. It is also possible to fold the slots in more than three to make them fit into the radiating cell according to the invention.
  • the slots are produced by partial de-metallization of the ground plane of the cell.
  • the excitation of the slots is carried out by a radiating strip 103 positioned between the two slots in one of the planes of the printed circuit, preferably the plane adjacent to the ground plane, and connected to the supply of the slots.
  • the relative positioning of the two slots 102 and the exciter 103 creates coupling phenomena, both between the elements of the low frequency band, but also with the patch 101. Their positioning must therefore be adjusted in order to repel the artifacts generated by this coupling outside the useful bands. Adjusting the gap between the slits allows the resonant frequency of each slit to be adjusted and their operation to be pushed back to the triple frequency outside the high frequency band.
  • the exciter 103 is supplied by the low frequency band access 105, to which it is connected by a coaxial line 104 and a low pass filter 106.
  • This low-pass filter comprises, for example, two capacitors 107, which in printed technology take the form of open line sections.
  • the role of the filter is to filter the components of the high frequency band due to the strong coupling between the slots and the patch.
  • the radiating element of the patch type 101 is supplied by the high frequency band access 109 to which it is connected by a coaxial line 108 and a filter 110.
  • the filter 110 has the role of filtering the components of the low frequency band due to the strong coupling between the slots and the patch.
  • a parallel waveguide acts as a series resonator circuit, and has a very small footprint. Its length is proportional to the wavelength in the dielectric of the frequency that it short-circuits.
  • a stub made from a microstrip line section of length ⁇ B / 4, with ⁇ B the wavelength of the low frequency band, will play the role of short circuit in its resonance band. In the example, this is the low frequency band.
  • resonant structures based on lines naturally function in the same way at the frequency f 0 and for all the odd multiples of this frequency. This is the case in the example, where the ratio of the frequency bands is 3.
  • such a stub will also play the role of short circuit for the high frequency band.
  • variable stub whose total length is divided into several sections of different impedances (known in English as "stepped impedance").
  • stepped impedance Such a stub is dispersive. It is dimensioned so as to present a short circuit on its fundamental frequency, and an open circuit on its triple frequency.
  • the filter 110 of the figure 1 has such a stub, consisting of several sections of microstrip line of different widths, and therefore having several distinct impedances. In the example, it has three different impedances, but the number of hops is a parameter specific to each implementation. Due to variable impedances, the system is not homogeneous, its electrical length no longer depends linearly on the frequency.
  • the different elements constituting the radiating cell according to the invention are arranged in different layers of the printed circuit.
  • the figure 2 shows the exploded view of a radiating cell according to the first embodiment of the invention, in which the arrangement of the elements is intended to limit the size of the radiating cell.
  • the printed circuit comprises four layers.
  • Each of the layers comprises a dielectric substrate on which an etched metal layer is deposited.
  • the upper layer 201 comprises the patch type element 101 tuned to operate in the high frequency band.
  • the immediately lower layer 202 comprises the ground plane of the radiating cell, in which two slot-type elements 102, tuned for the low frequency bands, are produced by de-metallization of the ground plane.
  • the slots are arranged so as not to be obstructed by the patch 101.
  • An advantageous positioning then consists in placing them on the periphery of the radiating cell, opposite the patch.
  • the lower layer 203 comprises the slot exciter 103.
  • the lowest layer 204 comprises the low-pass filter element 106 connected on the one hand to the access 105 and on the other hand to the exciter 103 by the bias of a coaxial line, described under reference 104 in the figure 1 , allowing it to pass through the different layers of the printed circuit, and the band pass filtering elements 110 connected on the one hand to the access 109 and on the other hand to the patch 101 by means of a coaxial line 108.
  • the resulting radiating cell has a format slightly larger than the format of the S band patch.
  • the size of the patch band S is 25mm x 25mm.
  • This cell radiates simultaneously in the upper frequency band and in the lower frequency band, but has separate access to each of these bands.
  • the different filtering elements ensure a strong decoupling between the two accesses.
  • an additional layer 205 comprising a second patch antenna 206 adapted to the high frequency band.
  • This additional layer is positioned on the highest layer 201, the second patch being superimposed on the first patch 101.
  • This addition makes it possible to increase the bandwidth in the high frequency band, by playing on the coupling effects between the two patches , without changing the size of the cell.
  • the Figures 3a and 3b represent an example of reflection coefficient of the inputs and of decoupling, respectively in the low frequency band and in the high frequency band, associated with each input of a radiating cell according to the first embodiment of the invention.
  • the results are obtained by simulations using an electromagnetic simulation software by the finite element method.
  • the reflection coefficient of the inputs is representative of the power of the signal reflected as a function of the frequency. When this coefficient tends to 1 (ie OdB), then all of the signal power at the frequency concerned is rejected. The lower this coefficient, the better the antenna.
  • Decoupling measures the leakage power in the first antenna when the second antenna is working and vice versa. It is therefore representative of the performance of coexistence of the two types of radiating elements within the same cell.
  • the curve 301 represents the reflection coefficient of the access dedicated to the low frequency band, for the low frequency band (the frequency sub-bands envisaged in this embodiment are bands of a few MHz or tens of MHz around the frequencies 1.03GHz and 1.09GHz). This coefficient is less than - 10dB around the frequencies 1.03GHz and 1.09GHz. Dedicated access to the low frequency band is therefore suitable for IFF applications.
  • the curve 302 represents the reflection coefficient of the access dedicated to the high frequency band, for the low frequency band.
  • this coefficient is constant, and is equal to 1 (i.e. OdB).
  • Dedicated access to the high frequency band therefore rejects all of the components of the low frequency band. It is not affected by coupling with the radiating elements in the low frequency band. This analysis is confirmed by measuring the decoupling 303 between the two inputs, which is greater than 24 dB across the band.
  • the curve 311 represents the reflection coefficient of the access dedicated to the low frequency band, for the high frequency band (the frequency band envisaged in this embodiment is the band 2.9GHz - 3.3GHz). This coefficient is constant, and is worth 1 (that is to say OdB). Dedicated access to the low frequency band therefore rejects all of the components of the high frequency band. It is then not affected by the coupling with the radiating elements in the high frequency band.
  • Curve 312 represents the reflection coefficient of the access dedicated to the high frequency band, for the high frequency band. In the 2.9GHz - 3.3GHz band, this coefficient is less than -12.5dB. The dedicated access to the high frequency band is therefore adapted to this frequency band. The decoupling 313 between the two antennas is greater than 25 dB in the band.
  • FIGS. 4a and 4b represent an example of radiation diagrams of the input associated with the low frequency band of a radiating cell according to the first embodiment of the invention.
  • the figure 4a represents the radiation diagram in the horizontal plane of access to the low frequency band, for a frequency of 1.03GHz in main polarization (401) and crossed (403), as well as for a frequency of 1.09GHz in main polarization ( 402) and crossed (404).
  • the cross-polarization response in this plane is almost zero (-30dB).
  • the main polarization of a radiating element is the axis on which the radiated electric field is maximum.
  • Cross polarization is the axis perpendicular to the axis of the main polarization. These two axes lie in the plane perpendicular to the direction of propagation.
  • the main polarization is situated in the vertical plane (represented by the y axis in the figures), while the crossed polarization is situated in the horizontal plane (represented by the x axis in the figures).
  • the figure 4b represents the radiation diagram in the vertical plane of access to the low frequency band, for a frequency of 1.03GHz (411) and 1.09GHz (412). In this plane, the level of cross polarization is almost zero.
  • the radiation patterns observed on the access to the low frequency band in the horizontal and vertical plane vary in cosine ⁇ for the main polarization, ⁇ being the direction of observation. This characteristic is necessary for the production of an antenna with electronic scanning.
  • FIGS. 5a and 5b represent an example of radiation diagrams of the input associated with the high frequency band of a radiating cell according to the first embodiment of the invention.
  • the figure 5a represents the radiation pattern in the horizontal plane of access to the high frequency band, for a frequency of 2.9GHz in main (501) and cross (502) polarization.
  • the response according to the cross polarization is weak compared to the response according to the main polarization (typically 15dB to 30dB difference).
  • the figure 5b represents the radiation diagram in the vertical plane of access to the high frequency band, for a frequency of 2.9 GHz in main polarization (511). The response in cross polarization in this plane is negligible.
  • the radiation patterns observed in the high frequency band are characteristic of the radiation pattern of a patch. Indeed, this diagram has a variation close to a cosine function ⁇ , necessary for the realization of an antenna with electronic scanning.
  • the figure 6 represents a radiating cell according to a second embodiment of the invention. This operating mode limits the number of sub-bands in the low frequency band to two.
  • the radiating cell 600 designed according to the second embodiment of the invention comprises a radiating element 101 of patch type tuned to the upper frequency band.
  • This radiating element is supplied by the high band output 109 to which it is connected by means of a coaxial line 108 allowing it to pass through the different layers of the printed circuit, and of a filter 110 produced in the form of a stub. having several sections of variable impedance, making it possible to filter the low frequency band while passing for the high frequency band.
  • a second patch type element, identical to the first can be superimposed on the first patch type element 101, in order to widen the passband in the high frequency band.
  • the main difference between this embodiment and the first consists in that it contains only a single slit-type element 601, folded in a U, and positioned to be free from the masking represented by the patch (s) 101
  • the operating band of this element is then widened to the whole of the low frequency band, in order to to understand the two sub-bands required by IFF applications, by the association of a 602 resonator.
  • the radiating slot which forms a parallel resonator, can be supplemented by a series resonator placed in the output plane, or by a parallel resonator placed a quarter wave further.
  • the resonator 602 is then placed at a distance L 1 from the connector 104 connecting it to the exciter 103 of the slot, L 1 being equal to ⁇ / 4, where ⁇ is the central wavelength of the low frequency band.
  • the slot 601 is not tuned to one of the sub-bands of the low frequency band, but to the central frequency, ie in the case of the example chosen, the frequency 1.06 GHz. It can also be tuned to a slightly higher frequency, so as to be compatible, once folded into three parts, of a mesh at the high frequency.
  • the resonator 602 is designed to resonate at the same frequency. The action on the coupling between these two elements, that is to say the mismatch created between these two elements, will cause them to resonate around the frequencies sought. The coupling between the two elements is adjusted by varying the position of the exciter 103 of the slot.
  • the slot 601, the resonator circuit 602 and the exciter 103 are therefore dimensioned and positioned so that the assembly resonates around the frequencies 1030MHz and 1090MHz, while allowing a strong mismatch in the intermediate frequency zone.
  • the radiating element thus obtained is dual-frequency. This approach offers the advantage of only introducing a single radiating slit into the cell, and of reducing the interference between the slit and the patch, and therefore the coupling phenomena between the low frequency band and the high frequency band. .
  • the positioning of the slot 601 and of the exciter 103 is therefore simplified compared to the first embodiment.
  • the resonator circuit 602 is of the parallel capacitance and inductance type.
  • Inductance 603 is of low value. It is produced in the form of a microstrip line of length L 2 connected to ground.
  • the capacitor 604 is produced in the form of a short-circuited microstrip line of length L 3 , L 3 being much greater than L 2 .
  • a low pass filter similar to the filter 106 of the first embodiment of the invention can be added to filter the components of the high bands linked to the coupling between the slot and the patch.
  • a filter is not essential in the second embodiment, the resonator circuit naturally performing the role of low pass filter.
  • the reduction in the number of radiating elements (slots) is compensated by an additional effort on the microwave circuit for adapting the slot.
  • the Figures 7a and 7b represent an example of reflection coefficient and decoupling associated with each input of a radiating cell according to the second embodiment of the invention.
  • the results are obtained by simulations using an electromagnetic simulation software by the finite element method.
  • the curve 701 represents the reflection coefficient of the access dedicated to the low frequency band for the low frequency band (the frequency bands envisaged in this embodiment are bands of a few MHz or tens of MHz around the frequencies 1.03GHz and 1.09GHz). This coefficient is close to or less than -10dB around the frequencies 1.03GHz and 1.09GHz. Dedicated access to the low frequency band is therefore suitable for IFF applications.
  • the curve 702 represents the reflection coefficient of the access dedicated to the high frequency band, for the low frequency band. In the 1GHz - 1.15GHz band, this coefficient is constant, and is equal to 1 (i.e. OdB). Dedicated access to the high frequency band therefore rejects all of the components of the low frequency band. It is not affected by coupling with the radiating elements in the low frequency band.
  • the decoupling 703 between the accesses of the slot and the patch is of the order of 30 dB.
  • the curve 711 represents the reflection coefficient of the access dedicated to the low frequency band, for the high frequency band (the frequency band envisaged in this embodiment is the band 2.9GHz - 3.3GHz). This coefficient is almost constant, and is equal to 1 (ie OdB) over almost the entire band. Dedicated access at the low frequency band therefore rejects all of the components of the high frequency band, it is not affected by the coupling with the radiating elements in the high frequency band.
  • Curve 712 represents the reflection coefficient of the access dedicated to the high frequency band. In the 2.9GHz - 3.3GHz band, this coefficient is much lower than -12.5dB. The dedicated access to the high frequency band is therefore adapted to this frequency band.
  • the decoupling 713 between the 2 antennas is greater than 12.5 dB in the band.
  • FIGS. 8a and 8b represent an example of radiation diagrams of the input associated with the low frequency band of a radiating cell according to the second embodiment of the invention.
  • the figure 8a represents the radiation diagram in the horizontal plane of access to the low frequency band, for a frequency of 1.03GHz in main polarization (801) and crossed (803), as well as for a frequency of 1.09GHz in main polarization ( 802) and crossed (804).
  • the response according to the main polarization in this plane is almost zero (-30dB).
  • the figure 8b represents the radiation diagram in the vertical plane of access to the low frequency band, for a frequency of 1.03GHz in main polarization (811), as well as for a frequency of 1.09GHz in main polarization (812). In this plane, the cross polarization is negligible.
  • the radiation patterns observed on the access to the low frequency band in the first and second plan vary in cosine ⁇ for the main polarization, ⁇ being the direction of observation. This characteristic is necessary for the production of an antenna with electronic scanning.
  • FIGS. 9a and 9b represent an example of radiation diagrams of the input associated with the high frequency band of a radiating cell according to the first embodiment of the invention
  • the figure 9a represents the radiation diagram in the horizontal plane of access to the high frequency band, for a frequency of 2.9 GHz in main (901) and cross (902) polarization.
  • the response according to the cross polarization is weak compared to the response according to the main polarization (typically 30dB difference).
  • the figure 9b represents the radiation diagram in a vertical plane of access to the high frequency band, for a frequency of 2.9 GHz in main polarization (911). There is no cross polarization response in this plane of the cell.
  • the radiation patterns observed in the high frequency band are characteristic of the radiation pattern of a patch. Indeed, this radiation diagram in the foreground has a variation in cosine ⁇ characteristic of a patch antenna, and necessary for the realization of an antenna with electronic scanning.
  • the figure 10 represents a radiating cell according to a third embodiment of the invention. It is a variant of the first embodiment, which comprises a radiating element of the slit type for each of the sub-bands envisaged in the low frequency band.
  • This embodiment differs from the first in that the two slot-type elements 1001 and 1011 are dissociated and placed on each side of the patch-type element, always on the periphery of the radiating cell so as not to be masked by the patch. This distance between the two slots makes it possible to reduce the coupling phenomena between them.
  • Each of the slots is tuned relative to the center frequency of one of the sub-bands of the low frequency band, or reduced to this frequency by coupling.
  • each of the slots is connected to a separate access.
  • the radiating cell then has three accesses: a first access to the high frequency band, and an access for each of the sub-bands of the low frequency band.
  • the first slot 1001 is supplied by the access 1003 to which it is connected by means of an exciter 1002, a coaxial line 1004, and a low pass filter 1005.
  • the second slot 1011 is supplied by the access 1013 to which it is connected by means of an exciter 1012, a coaxial line 1014, and a low pass filter 1015.
  • the invention also includes a radiating network produced from dual-band radiating cells as defined above.
  • Each of the cells can then be controlled in amplitude and / or in phase in each of the bands of interest, that is to say in the specific example, in the S band (and more particularly the 2.9GHz-3.3GHz subband) and in the band dedicated to IFF applications (1.03GHz and 1.09GHz).
  • a dual-band radar comprising a single electronic scanning antenna, the antenna being produced from the radiating network described above, and operating independently in the two frequency bands.

Landscapes

  • Waveguide Aerials (AREA)

Claims (17)

  1. In zwei unterschiedlichen Frequenzbändern strahlende Strahlungsvorrichtung, einem hohen Frequenzband und mindestens einem Teilband eines tiefen Frequenzbandes, wobei die Vorrichtung dadurch gekennzeichnet ist, dass sie Folgendes beinhaltet:
    • mindestens ein Element vom Typ Patch (101), welches für das hohe Frequenzband geeignet und mit einem ersten Zugang (109) verbunden ist,
    • mindestens ein Element vom Typ umgebogener Schlitz (102), welches für das tiefe Frequenzband geeignet und mit einem zweiten Zugang (105), welcher sich vom ersten Zugang unterscheidet, verbunden ist,
    • einen Filter (110), welcher zwischen dem Element vom Typ Patch und dem ersten Zugang positioniert ist, welcher konfiguriert ist, um das Tiefe Frequenzband zu filtern und das hohe Frequenzband passieren zu lassen,
    und dadurch, dass die sie bildenden Elemente in einer Fläche positioniert sind, welche kleiner oder gleich einem Quadrat mit Seitenlänge λ/2 ist, wobei λ die Wellenlänge ist, welche der maximalen Frequenz des hohen Frequenzbandes entspricht.
  2. Strahlungsvorrichtung nach dem vorhergehenden Anspruch, bei welcher das Element vom Typ Schlitz (102) in einer Massenebene der Vorrichtung angeordnet ist.
  3. Strahlungsvorrichtung nach einem der vorhergehenden Ansprüche, bei welcher das oder die Elemente vom Typ umgebogener Schlitz (102) zu einer U-Form umgebogen und am Umfang der Vorrichtung positioniert sind.
  4. Strahlungsvorrichtung nach einem der vorhergehenden Ansprüche, bei welcher die Anzahl der Elemente vom Typ Schlitz gleich der Anzahl der Teilbänder des tiefen Frequenzbandes ist, wobei die Elemente vom Typ Schlitz durch einen gleichen zweiten Zugang gespeist werden.
  5. Strahlungsvorrichtung nach einem der Ansprüche 1 bis 3, bei welcher die Anzahl der Elemente vom Typ Schlitz gleich der Anzahl der Teilbänder des tiefen Frequenzbandes ist, wobei die Elemente vom Typ Schlitz durch unterschiedliche Zugänge gespeist werden.
  6. Strahlungsvorrichtung nach einem der Ansprüche 1 bis 3, beinhaltend ein einziges Element vom Typ Schlitz (601), welches durch den zweiten Zugang (109) gespeist wird, mit welchem es durch einen Resonatorschaltkreis (602) verbunden ist, wobei die Kopplung zwischen dem Schlitz und dem Resonatorschaltkreis justiert ist, um in zwei unterschiedlichen Teilbändern des tiefen Frequenzbandes zu schwingen.
  7. Strahlungsvorrichtung nach Anspruch 6, bei welcher der Resonatorschaltkreis (602) ein paralleler Resonatorschaltkreis ist, welcher eine Induktivität (603) und einen Kondensator (604) beinhaltet, wobei der Resonator mit dem Element vom Typ Schlitz (601) durch einen Wellenleiter mit Länge λ/4 verbunden ist, wobei λ die der Mittelfrequenz des tiefen Frequenzbandes zugeordnete Wellenlänge ist.
  8. Strahlungsvorrichtung nach einem der vorhergehenden Ansprüche, bei welcher der Filter (110), welcher zwischen dem Element vom Type Patch (101) und dem ersten Zugang (109) positioniert ist, eine Vielzahl von Mikroband-Leitungsabschnitten mit unterschiedlichen Breiten beinhaltet.
  9. Strahlungsvorrichtung nach einem der vorhergehenden Ansprüche, zudem beinhaltend einen Tiefpassfilter (106), welcher zwischen dem oder den Element(en) vom Typ Schlitz (102) und dem zweiten Zugang (105) positioniert ist, und der konfiguriert ist, um das hohe Frequenzband zu filtern.
  10. Strahlungsvorrichtung nach einem der vorhergehenden Ansprüche, zudem beinhaltend ein zweites Element (206) vom Typ Patch, welches für das hohe Frequenzband geeignet ist, wobei das zweite Element vom Typ Patch oberhalb des ersten Elements vom Typ Patch angeordnet ist.
  11. Strahlungsvorrichtung nach einem der vorhergehenden Ansprüche, eingebaut in eine mehrschichtige Leiterplatte, bei welcher das Element vom Typ Patch (101), das oder die Element(e) vom Typ Schlitz (102) und der zwischen dem Element vom Typ Patch und dem ersten Zugang positionierte Filter (110) in unterschiedlichen Schichten (201, 202, 203, 204) der Leiterplatte liegen.
  12. Strahlungsvorrichtung nach dem vorhergehenden Anspruch, bei welcher mindestens eine Frequenz des hohen Frequenzbandes ein ganzzahliges ungerades Vielfaches einer Frequenz des tiefen Frequenzbandes ist.
  13. Strahlungsvorrichtung nach dem vorhergehenden Anspruch, bei welcher das hohe Frequenzband das Band von 2,9 GHz bis 3,3 GHz beinhaltet.
  14. Strahlungsvorrichtung nach einem der vorhergehenden Ansprüche, bei welcher ein Teilband des tiefen Frequenzbandes um eine Frequenz zentriert ist, gewählt aus der Frequenz 1030 MHz und der Frequenz 1090 MHz.
  15. Strahlungsvorrichtung nach einem der vorhergehenden Ansprüche, welche anhand von Drucktechnologie hergestellt wird.
  16. Strahlungsnetzwerk, welches konfiguriert ist, um in zwei unterschiedlichen Frequenzbändern zu strahlen, dadurch gekennzeichnet, dass es Strahlungsvorrichtungen nach einem der vorhergehenden Ansprüche beinhaltet.
  17. Radar mit elektronischer Abtastung, welcher konfiguriert ist, um gleichzeitig in den beiden unterschiedlichen Frequenzbändern zu arbeiten und dadurch gekennzeichnet ist, dass er ein Strahlungsnetzwerk nach Anspruch 16 beinhaltet.
EP16201682.8A 2015-12-09 2016-12-01 Elementare mehrfachband-strahlungszelle Active EP3179557B1 (de)

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CN108493590B (zh) * 2018-01-15 2020-02-11 深圳市信维通信股份有限公司 天线单元、mimo天线及手持设备
CN109378579A (zh) * 2018-10-15 2019-02-22 钟祥博谦信息科技有限公司 一种滤波型缝隙天线
CN110336130B (zh) * 2019-04-29 2021-08-31 中天宽带技术有限公司 一种偶极子滤波天线和电子设备
CN110401026B (zh) * 2019-06-10 2021-03-23 西安电子科技大学 一种具有近似椭圆滤波响应的磁电偶极子滤波天线

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US6919853B2 (en) * 2002-03-04 2005-07-19 M/A-Com, Inc. Multi-band antenna using an electrically short cavity reflector
US7848771B2 (en) * 2003-05-14 2010-12-07 Nxp B.V. Wireless terminals
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US10122076B2 (en) 2018-11-06
ES2815698T3 (es) 2021-03-30
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US20170170553A1 (en) 2017-06-15
FR3045219A1 (fr) 2017-06-16
EP3179557A1 (de) 2017-06-14

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