EP2452336B1 - Codage/décodage perfectionne de signaux audionumériques - Google Patents

Codage/décodage perfectionne de signaux audionumériques Download PDF

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EP2452336B1
EP2452336B1 EP10745327.6A EP10745327A EP2452336B1 EP 2452336 B1 EP2452336 B1 EP 2452336B1 EP 10745327 A EP10745327 A EP 10745327A EP 2452336 B1 EP2452336 B1 EP 2452336B1
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coding
band
improvement
decoding
core
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French (fr)
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EP2452336A1 (fr
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David Virette
Stéphane RAGOT
Balazs Kovesi
Pierre Berthet
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Orange SA
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Orange SA
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    • G—PHYSICS
    • G10—MUSICAL INSTRUMENTS; ACOUSTICS
    • G10L—SPEECH ANALYSIS TECHNIQUES OR SPEECH SYNTHESIS; SPEECH RECOGNITION; SPEECH OR VOICE PROCESSING TECHNIQUES; SPEECH OR AUDIO CODING OR DECODING
    • G10L19/00—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis
    • G10L19/002—Dynamic bit allocation
    • G—PHYSICS
    • G10—MUSICAL INSTRUMENTS; ACOUSTICS
    • G10L—SPEECH ANALYSIS TECHNIQUES OR SPEECH SYNTHESIS; SPEECH RECOGNITION; SPEECH OR VOICE PROCESSING TECHNIQUES; SPEECH OR AUDIO CODING OR DECODING
    • G10L19/00—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis
    • G10L19/02—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis using spectral analysis, e.g. transform vocoders or subband vocoders
    • G10L19/0212—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis using spectral analysis, e.g. transform vocoders or subband vocoders using orthogonal transformation
    • G—PHYSICS
    • G10—MUSICAL INSTRUMENTS; ACOUSTICS
    • G10L—SPEECH ANALYSIS TECHNIQUES OR SPEECH SYNTHESIS; SPEECH RECOGNITION; SPEECH OR VOICE PROCESSING TECHNIQUES; SPEECH OR AUDIO CODING OR DECODING
    • G10L19/00—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis
    • G10L19/02—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis using spectral analysis, e.g. transform vocoders or subband vocoders
    • G10L19/032—Quantisation or dequantisation of spectral components
    • G10L19/038—Vector quantisation, e.g. TwinVQ audio
    • G—PHYSICS
    • G10—MUSICAL INSTRUMENTS; ACOUSTICS
    • G10L—SPEECH ANALYSIS TECHNIQUES OR SPEECH SYNTHESIS; SPEECH RECOGNITION; SPEECH OR VOICE PROCESSING TECHNIQUES; SPEECH OR AUDIO CODING OR DECODING
    • G10L19/00—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis
    • G10L19/04—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis using predictive techniques
    • G10L19/16—Vocoder architecture
    • G10L19/18—Vocoders using multiple modes
    • G10L19/24—Variable rate codecs, e.g. for generating different qualities using a scalable representation such as hierarchical encoding or layered encoding

Definitions

  • the present invention relates to a sound data processing.
  • This processing is adapted in particular to the transmission and / or storage of digital signals such as audio-frequency signals (speech, music, or other).
  • the invention applies more particularly to hierarchical coding (or " scalable " coding) which generates a so-called “hierarchical” bitstream because it comprises a core rate and one or more improvement layer (s).
  • the G.722 standard at 48, 56 and 64 kbit / s is an example of scalable scalable codec
  • the ITU-T G.729.1 and MPEG-4 CELP codecs are examples of scalable codecs in both bitrate and bitrate. in bandwidth.
  • Hierarchical coding having the capacity to provide varied bit rates, is described below by distributing the information relating to an audio signal to be coded in hierarchical subsets, so that this information can be used in order of importance. in terms of audio rendering quality.
  • the criterion taken into account for determining the order is a criterion for optimizing (or rather reducing) the quality of the coded audio signal.
  • Hierarchical coding is particularly suited to transmission over heterogeneous networks or having variable available rates over time, or to transmission to terminals with varying capacities.
  • Hierarchical audio coding (or " scalable ) can be described as follows.
  • the bit stream includes a base layer and one or more enhancement layers.
  • the base layer is generated by a fixed rate codec, termed a " core codec ", guaranteeing the minimum quality of the coding.
  • This layer must be received by the decoder to maintain an acceptable level of quality. Improvement layers are used to improve quality. However, they may not all be received by the decoder.
  • the main advantage of hierarchical coding is that it allows an adaptation of the bit rate simply by " truncation of the bit stream ".
  • the number of layers i.e., the number of possible truncations of the bitstream
  • the number of layers defines the granularity of the coding.
  • scalable scalability and bandwidth encoding techniques with a CELP heart-coder, a telephone band, and one or more broadband enhancement layer (s).
  • An example of such systems is given in the ITU-T G.729.1 8-32 kbit / s fine grain standard.
  • the G.729.1 coding / decoding algorithm is summarized below.
  • the G.729.1 encoder is an extension of the ITU-T G.729 coder. It is a modified G.729 heart-coded core encoder producing a bandwidth ranging from narrowband (50-4000 Hz) to wideband (50-7000 Hz) at a rate of 8 to 32 kbit / s for conversational services. This codec is compatible with existing VoIP devices that use the G.729 codec.
  • the G.729.1 coder is schematized on the figure 1 .
  • the broadband input signal s wb sampled at 16 kHz, is first decomposed into two subbands by QMF (for "Quadrature Mirror Filter") filtering.
  • the low band (0-4000 Hz) is obtained by LP low-pass filtering (block 100) and decimation (block 101), and the band high (4000-8000 Hz) by high-pass filtering HP (block 102) and decimation (block 103).
  • the LP and HP filters are of length 64.
  • the low band is pretreated with a high-pass filter eliminating the components below 50 Hz (block 104), to obtain the signal s LB , before CELP coding in narrow band (block 105) at 8 and 12 kbit / s.
  • This high-pass filtering takes into account the fact that the wanted band is defined as covering the interval 50-7000 Hz.
  • the narrow-band CELP coding is a cascaded CELP coding comprising as a first stage a modified G.729 coding without a filter. preprocessing and as a second stage an additional fixed CELP dictionary.
  • the high band is first pretreated (block 106) to compensate for the folding due to the high-pass filter (block 102) combined with the decimation (block 103).
  • the high band is then filtered by a low pass filter (block 107) eliminating the components between 3000 and 4000 Hz from the high band (i.e. the components between 7000 and 8000 Hz in the original signal) to obtain the signal s HB .
  • a parametric band extension (block 108) is then performed.
  • the LB of error signal of the low band is calculated (block 109) from the output of the CELP coder (block 105) and a predictive transform coding (of TDAC type for "Time Domain Aliasing Cancellation" in the standard G .729.1) is carried out at block 110.
  • a predictive transform coding of TDAC type for "Time Domain Aliasing Cancellation" in the standard G .729.1
  • Additional parameters can be transmitted by the block 111 to a homologous decoder, this block 111 performing a so-called “FEC” treatment for "Frame Erasure Concealment", in order to reconstitute possible erased frames.
  • the different bitstreams generated by the coding blocks 105, 108, 110 and 111 are finally multiplexed and structured into a hierarchical bit stream in the multiplexing block 112.
  • the coding is performed by 20 ms sample blocks (or frames). 320 samples per frame.
  • the G.729.1 decoder is illustrated on the figure 2 .
  • the bits describing each frame of 20 ms are demultiplexed in block 200.
  • the bit stream of the 8 and 12 kbit / s layers is used by the CELP decoder (block 201) to generate the narrow-band synthesis (0-4000 Hz).
  • the portion of the bit stream associated with the 14 kbit / s layer is decoded by the tape extension module (block 202).
  • the portion of the bit stream associated with data rates greater than 14 kbit / s is decoded by the TDAC module (block 203).
  • Pre-echo and post-echo processing is performed by blocks 204 and 207 as well as enrichment (block 205) and aftertreatment of the low band (block 206).
  • the broadband output signal ⁇ wb sampled at 16 kHz, is obtained via the QMF synthesis filter bank (blocks 209, 210, 211, 212 and 213) incorporating the inverse folding (block 208).
  • the TDAC type transform coding in the G.729.1 encoder is illustrated on the figure 3 .
  • MDCT transforms (blocks 301 and 302) apply to 20 ms of sampled signal at 8 kHz (160 coefficients).
  • This spectrum is divided into eighteen sub-bands, a sub-band j being assigned a number of coefficients noted nb_ coef ( j ).
  • the subband splitting is specified in Table 1 below.
  • a subband j comprises the coefficients Y ( k ) with sb_bound ( j ) ⁇ k ⁇ sb_bound ( j + 1).
  • the coefficients 280-319 corresponding to the frequency band 7000 Hz - 8000 Hz are not coded; they are set to zero at the decoder because the bandwidth of the codec is 50-7000 Hz.
  • Table 1 ⁇ / b> TDAC Code Subband Bounds and Size J sb_bound ( j ) nb_coef ( j ) 0 0 16 1 16 16 2 32 16 3 48 16 4 64 16 5 80 16 6 96 16 7 112 16 8 128 16 9 144 16 10 160 16 11 176 16 12 192 16 13 208 16 14 224 16 15 240 16 16 256 16 17 272 8 18 280 -
  • the spectral envelope is coded at variable rate in block 305.
  • This quantized value rms _ index ( j ) is transmitted to the bit allocation block 306.
  • a bit (0 or 1) is transmitted to the decoder to indicate the encoding mode that has been chosen.
  • the number of bits allocated to each subband for its quantization is determined at block 306 from the quantized spectral envelope from block 305.
  • the bit allocation performed minimizes the squared error while respecting the constraint of a whole number of bits allocated per subband and a number of bits. maximum not to be exceeded.
  • the spectral content of the subbands is then encoded by spherical vector quantization (block 307).
  • the different bit streams generated by the blocks 305 and 307 are then multiplexed and structured into a hierarchical bit stream at the multiplexing block 308.
  • the TDAC type transform decoding step in the G.729.1 decoder is illustrated on the figure 4 .
  • the decoded spectral envelope (block 401) makes it possible to find the allocation of the bits (block 402).
  • each of the subbands is found by inverse spherical vector quantization (block 403).
  • the sub-bands not transmitted, due to a lack of "budget" of bits, are extrapolated (block 404) from the MDCT transform of the signal at the output of the band extension block (block 202 of FIG. figure 2 ).
  • IMDCT inverse MDCT transform
  • W LB inverse perceptual weighting
  • the subbands bit allocation (block 306 of FIG. figure 3 or block 402 of the figure 4 ).
  • nbits_ VQ 351 - nbits_rms
  • nbits_rms the number of bits used by the coding of the spectral envelope.
  • nbit ( j ) arg min r ⁇ R nb_coef j ⁇ nb_coef j ⁇ ip j - ⁇ Opt - r
  • the TDAC coding uses the perceptual weighting W LB ( z ) filter in the low band (block 300), as indicated above.
  • perceptual weighting filtering allows you to format the coding noise.
  • the principle of this filtering is to exploit the fact that it is possible to inject more noise in the frequency zones where the original signal has a high energy.
  • the most common perceptual weighting filters used in narrow-band CELP coding are of the form ⁇ (z / ⁇ 1) / ⁇ (z / ⁇ 2) where 0 ⁇ ⁇ 2 ⁇ ⁇ 1 ⁇ 1 and ⁇ (z) represents a prediction spectrum linear (LPC).
  • the synthesis analysis in CELP coding thus amounts to minimizing the quadratic error in a signal domain perceptually weighted by this type of filter.
  • the fac factor makes it possible to ensure at the junction of the low and high bands (4 kHz) a gain of the filter at 1 to 4 kHz. It is important to note that in the G.729.1 TDAC coding, the coding is based on an energetic criterion only.
  • the energy criterion of TDAC coding of G.729.1, used in the high band (4000-7000 Hz), is not optimal from a perceptual point of view, in particular to code musical signals.
  • the perceptual weighting filter is particularly suited to speech signals. It is widely used in speech coding standards based on the CELP coding format. However, for the musical signals, it appears that this perceptual weighting based on a shaping of the quantization noise according to the formants of the input signal is insufficient. Most audio coders rely on transform coding using frequency masking or simultaneous masking models; they are more generic (in the sense that they do not use a speech production model like the CELP) and are therefore more suitable for encoding musical signals.
  • the present invention improves the situation.
  • the coding according to the invention takes advantage of an enhancement coding layer to improve the coding quality from a perceptual point of view.
  • the enhancement layer will thus benefit from frequency masking which does not exist in the core coding stage, in order to best allocate the bits in the frequency bands of the enhancement coding.
  • This operation does not modify the core coding, which thus remains compatible with the existing standard coding, thus ensuring interoperability with equipment already on the market using existing standard coding.
  • the first perceptual importance that will be used for the enhancement layer does not take into account the core coding but only the signal to mask ratio to define a perceptual importance. This perceptual importance is determined on the input signal of the transform coder.
  • the encoding of the core is done simply by subtracting the average number of bits per sample already allocated.
  • the use of the perceptual importance based on the signal-to-mask ratio would make it possible to obtain an optimal allocation in the perceptual sense. However, this allocation would be useful if the input signal of the transform coding layer was coded directly.
  • a first transform coding layer based on an energy allocation has allocated a certain number of bits per subband.
  • the perceptual importance is furthermore determined as a function of bits allocated for a previous core coding enhancement coding having a binary allocation according to an energy criterion.
  • the sub-bands not transmitted, due to a lack of sufficient bit budget, are extrapolated (block 404) from the MDCT transform of the signal at the output of the band extension block (block 202 of FIG. figure 2 ). Even at the higher bit rate of G.729.1 (32 kbit / s) some frequency bands remain extrapolated.
  • a first encoding for improving the core coding to compensate for the lack of bit rate of the core coding for these non-transmitted subbands.
  • This first enhancement coding uses the original signal and operates according to energy criteria for bit allocation. According to one embodiment of the invention, this first improvement coding modifies the number of bits nbit ( j ) allocated to the subbands and the decoded subband Yq ( k ) (defined later on in FIG. figure 5 ).
  • the improvement coding according to the invention therefore also takes into account the bits allocated during this first improvement coding, in addition to the bits allocated in the core coding.
  • the method comprises a step of obtaining an information according to which the signal to be encoded is tonal or non-tonal and the steps of calculating the masking threshold and of determining a perceptual importance according to this masking threshold, are conducted only if the signal is non-tonal.
  • the coding is adapted to the signal whether it is tonal or not and allows optimal allocation of the bits.
  • the enhancement coding is coding for improving the coding of the MDCT type coefficients in an extended coder whose core coding is of G.729.1 standard encoder type.
  • the quality of the G.729.1 codec in the enlarged band (50-7000 Hz) is improved.
  • Such an improvement is important to extend the G.729.1 encoder band of the enlarged band (50-7000Hz) to the super-wide band (50-14000Hz).
  • the invention relates to a computer program comprising code instructions for implementing the steps of an encoding method according to the invention, when they are executed by a processor and to a computer program comprising instructions. code for implementing the steps of a decoding method according to the invention, when executed by a processor.
  • One of the objects of the invention is the improvement of the quality of G.729.1 in wideband (50-7000 Hz), in particular for musical signals. It will be recalled here that the G.729.1 coding has a useful band of 50 to 7000 Hz. Moreover, the quality of G.729.1 for some signals such as music signals is not transparent at its highest bit rate (32 kbit / s) - this limitation is due to the hierarchical structure CELP + TDBWE + TDAC and the bit rate limited to 32 kbit / s .
  • This invention is motivated by the ongoing ITU-T standardization of a scalable extension of G.729.1, in particular to extend the G.729.1 coded band to the super-wide band (50-14000 Hz).
  • the band extension eg 7000-14000 Hz
  • a limited band signal eg 50-7000 Hz
  • the band extension highlights the existing defects in this signal.
  • the G.729.1 quality improvement can be achieved with one or more additional rate enhancement layers (in addition to 32 kbit / s).
  • these additional flow enhancement layers can serve both the band extension (7000-14000 Hz) and the quality improvement in the enlarged band (50-7000 Hz).
  • part of the additional bit rate of the enhancement layers can be devoted to improving the broadband signal decoded by a G.729.1 decoder.
  • G.729.1 has a narrow-band CELP core coder, while the super-expanded band extension (50-14000Hz) of G.729.1 has for heart G.729.1.
  • core coding and heart rate we mean a G.729.1 type coding and the associated bit rate of 32 kbit / s.
  • it is more particularly a TDAC encoder and decoder as described above, in which an enhancement layer is integrated.
  • the figure 5 describes such an improved TDAC coder.
  • a scalable extension of G.729.1 is considered in several enhancement layers.
  • the core coding is a G.729.1 coding, which uses TDAC coding in the band [50-7000 Hz] from the bitrate of 14 kbit / s and up to 32 kbit / s. It is assumed that between 32 and 48 kbit / s two enhancement layers of 8 kbit / s are produced in order to extend the band from 7000 to 14000 Hz and to replace the non-transmitted subbands of the TDAC coding of G.729.1 . These enhancement layers of 8 kbit / s ranging from 32 to 48 kbit / s are not described here.
  • the present invention provides two additional 8 kbit / s enhancement layers of the TDAC coding in the 50 to 7000 Hz band that increase the bit rate from 48 kbit / s to 56 and 64 kbit / s.
  • the encoder applying the present invention has enhancement layers that add G.729.1 core bit rate (32 kbit). These enhancement layers serve both to improve the quality in the enlarged band (50-7000 Hz) and to extend the upper band from 7000 to 14000 Hz. In the following we ignore the extension of 7000 to 14000 Hz, because this feature does not influence the implementation of the present invention. For reasons of simplicity, the modules corresponding to the 7000 to 14000 Hz band extension are not illustrated on the figures 5 and 6 .
  • the TDAC encoder according to one embodiment of the invention here comprises an enhancement layer (blocks 509 to 513) which improves the core layer (blocks 504 to 507).
  • the block 507 here corresponds to the spherical vector quantization (SVQ) quantification of G.729.1, which may comprise a modification as mentioned above.
  • SVQ spherical vector quantization
  • This modification uses the original signal Y ( k ) and operates according to energy criteria for bit allocation. The number of bits nbit (j) allocated to the subbands and the decoded subband Yq ( k ) are then modified.
  • Block 506 performs a binary allocation based on energy criteria as described with reference to FIG. figure 3 .
  • the core layer is thus coded and sent to the multiplexing module 508.
  • the heart signal is also decoded locally in the encoder by the block 510 which performs spherical dequantization and scaling; this heart signal is subtracted from the original signal at 509, in the transformed domain, to obtain a residual signal err (k). This residual signal is then coded from a bit rate of 48 kbit / s in block 513.
  • An advantageous spreading function is that presented to the figure 7 .
  • This is a triangular function whose first slope is + 27dB / Bark and - 10dB / Bark for the second one.
  • ⁇ 1 ( j ) and ⁇ 2 ( j ) can be pre-calculated and stored.
  • the application of the masking threshold is in this embodiment, limited to the high band.
  • the masking threshold is normalized for example by its value on the last sub-band. band of the low band.
  • a first perceptual importance calculation step is then performed taking into account the signal-to-mask ratio given by: 1 2 ⁇ log 2 ⁇ ⁇ 2 j M j
  • FIG 8 An illustration of the standardization of the masking threshold is given in figure 8 , showing the connection of the high band on which the masking (4-7 kHz) is applied to the low band (0-4 kHz).
  • the standardization of the masking threshold can be rather carried out from the value of the band.
  • a first perceptual importance ip ( j ) is sent to the binary allocation block 512 for improvement coding.
  • This block 512 also receives bit allocation information nbit ( j ) from the core layer of the TDAC coding, G.729.1.
  • Block 512 thus defines a new perceptual importance that takes into account these two pieces of information.
  • the new perceptual importance is calculated by subtracting at the first perceptual importance, a ratio between the number of bits allocated for the core coding and the number of possible coefficients in the subband.
  • the block 512 performs a bit allocation on the residual signal to code the enhancement layer.
  • nbits _ VQ _ err corresponding to the additional number of bits in the enhancement layer (320 bits for the 2 8 kbit / s layers).
  • the residual signal err ( k ) is then coded by the module 513 by spherical vector quantization, using the number of allocated bits nbit- err ( j ) as previously calculated.
  • This coded residual signal is then multiplexed with the signal resulting from the core coding and the coded envelope by the multiplexing module 508.
  • This enhancement coding not only extends the allocated bit rate but improves from a perceptual point of view, the coding of the signal.
  • the TDAC coding enhancement layer as described can be applied after modifying the TDAC coding of G.729.1.
  • a first enhancement (not described here) of the TDAC coding of G.729.1 is performed.
  • This enhancement allocates bits to subbands between 4 and 7 kHz at which no bit rate was allocated by the G.729.1 TDAC core encoding even at its higher 32 kbit / s bit rate.
  • This first improvement of the TDAC coding of G.729.1 therefore uses the original signal between 4 and 7 kHz and does not implement the steps of calculating a masking threshold or determining the perceptual importance of the coding method of the 'invention.
  • Block 507 is considered to correspond to this modified TDAC coding integrating this improvement.
  • the determination of the perceptual importance takes into account not only the bits allocated for the core or base coding but also the bits allocated for the previous enhancement coding, in this case the 40 kbit / s rate enhancement coding.
  • the figure 6 illustrates the TDAC decoder with an enhancement decoding stage as well as the steps of a decoding method according to an embodiment of the invention.
  • the decoder comprises the modules (601, 602, 603, 606, 607, 608, 609 and 610) identical to those described for the TDAC decoding of the G.729.1 coder with reference to FIG. figure 4 (401, 402, 403, 406, 407, 408, 409 and 410).
  • the block 606 for processing in the MDCT domain (aimed at shaping the coding noise) is here optional because the invention improves the quality of the decoded MDCT spectrum from block 603.
  • the module 605 of the decoder corresponds to the encoder module 511 and operates in the same way from the quantized values of the spectral envelope.
  • the allocation module 604 determines a second perceptual importance in taking into account the allocation of bits received from the core coding, in the same way as in the coding module 512.
  • This bit allocation for the enhancement coding allows the module 611 to decode the signal received from the demultiplexing module 600 by spherical vector dequantization.
  • the decoded signal from the module 611 is an error signal err (k) which is then combined at 612 with the decoded heart signal at 603.
  • This signal is then processed as for the G.729.1 encoding described with reference to the figure 4 to give a difference signal d LB in low band and a signal S HB in high band.
  • the calculation of a frequency masking performed by the module 511 or 605 and as described above may or may not be carried out according to the signal to be encoded (in particular if it is tonal or not).
  • the application of the spreading function B (v) results in a masking threshold very close to a tone a little more spread out in frequencies.
  • the criterion of minimization of the masked coding noise ratio then gives a bit allocation that is not necessarily optimal.
  • the calculation of the masking threshold and the determination of the perceptual importance as a function of this masking threshold according to the invention is applied only if the signal to be encoded is not tonal.
  • the bit relating to the mode of the coding of the spectral envelope indicates a "differential Huffman" mode or a "natural direct binary” mode.
  • This mode bit can be interpreted as a tone detection, since, in general, a tonal signal leads to envelope coding by the "natural direct binary” mode, while most non-tonal signals, having a spectral dynamic more limited, lead to envelope coding by the "Differential Huffman" mode.
  • the super-expanded band extension of the G.729.1 encoder as shown consists of an extension of the frequencies coded by the module 915, the frequency band used from [50Hz-7KHz] to [50Hz-14kHz] and an improvement of the G.729.1 base layer by the TDAC coding module (block 910) and as described with reference to FIG. figure 5 .
  • the encoder as represented in figure 9 has the same modules as the G.729.1 core coding represented in figure 1 and an additional band extension module 915 which provides an extension signal to the multiplexing module 912.
  • This frequency band extension is calculated on the original full-band signal S SWB while the input signal of the core encoder is obtained by decimation (block 913) and low-pass filtering (block 914). At the output of these blocks, the broadband input signal S WB is obtained.
  • the TDAC coding module 910 is different from that illustrated in FIG. figure 1 .
  • This module is for example that described with reference to the figure 5 and provides the multiplexing module with both the coded core signal and the coded enhancement signal according to the invention.
  • a G.729.1 extended-band decoder is described with reference to the figure 10 . It has the same modules as the G.729.1 decoder described with reference to the figure 2 .
  • the band extension module 1014 which receives from the demultiplexing module 1000, the band extension signal.
  • the TDAC decoding module 1003 is also different from the TDAC decoding module illustrated with reference to FIG. figure 2 .
  • This module is for example that described and illustrated with reference to the figure 6 . It thus receives from the demultiplexing module, both the heart signal and the improvement signal.
  • the invention is used to improve the quality of TDAC coding in the G.729.1 codec.
  • the invention applies to other types of transform coding with a binary allocation and scalable extension of other core codecs than G.729.1.
  • the figure 11a illustrates an encoder or terminal comprising an encoder as described in figure 5 . It comprises a PROC processor cooperating with a memory block BM having a memory storage and / or working MEM.
  • This terminal comprises an input module able to receive a low band signal d LB and a high band signal S HB or any type of digital signal to be coded. These signals may come from another coding stage or a communication network, a digital content storage memory.
  • the description of the figure 5 takes the steps of an algorithm of such a computer program.
  • the computer program can also be stored on a memory medium readable by a reader of the terminal or encoder or downloadable in the memory space thereof.
  • the terminal comprises an output module capable of transmitting a multiplexed stream derived from the coding of the input signals.
  • figure 11b illustrates an example of a decoder or terminal including a decoder as described with reference to the figure 6 .
  • This terminal comprises a PROC processor cooperating with a memory block BM having a memory storage and / or working MEM.
  • the terminal comprises an input module adapted to receive a multiplexed stream coming for example from a communication network, a storage module.
  • the description of the figure 6 takes the steps of an algorithm of such a computer program.
  • the computer program can also be stored on a memory medium readable by a reader of the terminal or downloadable in the memory space thereof.
  • the terminal comprises an output module capable of transmitting decoded signals ( d LB , S HB ) for another coding stage or for content reproduction.
  • such a terminal may comprise both the encoder and the decoder according to the invention.

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EP10745327.6A 2009-07-07 2010-06-25 Codage/décodage perfectionne de signaux audionumériques Active EP2452336B1 (fr)

Applications Claiming Priority (2)

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FR0954682A FR2947944A1 (fr) 2009-07-07 2009-07-07 Codage/decodage perfectionne de signaux audionumeriques
PCT/FR2010/051307 WO2011004097A1 (fr) 2009-07-07 2010-06-25 Codage/décodage perfectionne de signaux audionumériques

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EP2452336A1 EP2452336A1 (fr) 2012-05-16
EP2452336B1 true EP2452336B1 (fr) 2013-11-27

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US (1) US8812327B2 (ko)
EP (1) EP2452336B1 (ko)
KR (1) KR101698371B1 (ko)
CN (1) CN102576536B (ko)
CA (1) CA2766864C (ko)
FR (1) FR2947944A1 (ko)
WO (1) WO2011004097A1 (ko)

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CN104282312B (zh) 2013-07-01 2018-02-23 华为技术有限公司 信号编码和解码方法以及设备
US10424305B2 (en) * 2014-12-09 2019-09-24 Dolby International Ab MDCT-domain error concealment
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EP3751567B1 (en) * 2019-06-10 2022-01-26 Axis AB A method, a computer program, an encoder and a monitoring device
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Publication number Publication date
CN102576536B (zh) 2013-09-04
US20120185255A1 (en) 2012-07-19
CA2766864A1 (fr) 2011-01-13
US8812327B2 (en) 2014-08-19
CA2766864C (fr) 2015-10-27
KR101698371B1 (ko) 2017-01-26
EP2452336A1 (fr) 2012-05-16
CN102576536A (zh) 2012-07-11
WO2011004097A1 (fr) 2011-01-13
KR20120032025A (ko) 2012-04-04
FR2947944A1 (fr) 2011-01-14

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