EP2109183A1 - Improvement of antenna isolation - Google Patents

Improvement of antenna isolation Download PDF

Info

Publication number
EP2109183A1
EP2109183A1 EP09445009A EP09445009A EP2109183A1 EP 2109183 A1 EP2109183 A1 EP 2109183A1 EP 09445009 A EP09445009 A EP 09445009A EP 09445009 A EP09445009 A EP 09445009A EP 2109183 A1 EP2109183 A1 EP 2109183A1
Authority
EP
European Patent Office
Prior art keywords
antenna element
feeders
dual polarized
polarized antenna
compensation line
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
EP09445009A
Other languages
German (de)
French (fr)
Inventor
Björn LINDMARK
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Intel Corp
Original Assignee
Powerwave Technologies Sweden AB
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Powerwave Technologies Sweden AB filed Critical Powerwave Technologies Sweden AB
Publication of EP2109183A1 publication Critical patent/EP2109183A1/en
Ceased legal-status Critical Current

Links

Images

Classifications

    • HELECTRICITY
    • H01ELECTRIC ELEMENTS
    • H01QANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04Resonant antennas
    • H01Q9/0407Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/0428Substantially flat resonant element parallel to ground plane, e.g. patch antenna radiating a circular polarised wave
    • HELECTRICITY
    • H01ELECTRIC ELEMENTS
    • H01QANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00Details of, or arrangements associated with, antennas
    • H01Q1/36Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • HELECTRICITY
    • H01ELECTRIC ELEMENTS
    • H01QANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00Details of, or arrangements associated with, antennas
    • H01Q1/52Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • HELECTRICITY
    • H01ELECTRIC ELEMENTS
    • H01QANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00Antenna arrays or systems
    • H01Q21/24Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
    • HELECTRICITY
    • H01ELECTRIC ELEMENTS
    • H01QANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04Resonant antennas
    • H01Q9/0407Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/045Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means
    • H01Q9/0457Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means electromagnetically coupled to the feed line

Definitions

  • the present invention relates to a dual polarized antenna element and an antenna array, in which the antenna element includes:
  • Dual polarised or X-polarised antennas are today commonly used in cellular systems for mobile communication.
  • the use of such antennas allows the use of polarisation diversity techniques to combat signal fading in the system.
  • Compared to the use of vertical polarised antennas and space diversity techniques the number of antennas needed is reduced to half, which saves costs and reduces the size and the visual appearance of the antenna installations.
  • One important performance measure for dual polarised antennas is the isolation between the two antenna ports feeding the two polarisations. Typically, an isolation of more than 30 dB between the ports is wanted, which corresponds to a power coupling of less than 1/1000 between the ports.
  • An aperture coupled patch antenna element is a commonly used antenna type for dual polarised systems.
  • one or more metallic patches are fed by a micro strip feeding arrangement through a cross shaped aperture in a ground plane, as is shown in figure 1 .
  • the antenna element 101 includes a radiating patch 103, fed through an aperture 109 by a microstrip feed line 105 positioned between a shielding cage 102 and a printed circuit board.
  • Isolation between a transmitting and a receiving signal path in a dual polarized antenna has been described in, for instance, prior art document US6509883 .
  • a signal being transmitted from a first antenna element having one polarisation is received by a second antenna element having another polarisation, thereby causing an unwanted signal to be received by the second antenna element.
  • a compensation path is arranged between the transmitting and receiving signal paths, where the compensation path has a length such that the compensation signal travelling through the compensation path and the unwanted signal have equal magnitude and opposite phase when they meet in the receiving signal path.
  • the compensation path as well as the transmitting and receiving signal paths have to be adapted to have certain lengths in order to be able to cancel out the unwanted signal, having been transmitted from the first antenna and received by the second antenna, since a difference in length of an odd number of half wavelengths has to be present between the paths travelled by the unwanted signal and the compensation signal.
  • the antenna element shown in this document has to have a certain size to achieve efficient cancellation, which is disadvantageous.
  • the present invention aims to provide a dual polarised antenna element, which offers improved antenna isolation for all kinds of essentially capacitive couplings between the feeders.
  • the present invention thus aims to provide compensation for capacitive coupling between the feeders, also including a capacitive coupling occurring via the radiating part, for example a radiating patch, of the antenna element.
  • the object is for a dual polarized antenna element achieved by the use of:
  • the object is also achieved by an antenna array including at least two such dual polarized antenna elements.
  • the present invention achieves compensation of mutual coupling in dual polarized antenna elements using a compensation line being connected between the input ports.
  • this compensation line is short in relation to the wavelength, this connection will act as an inductive element well suited to compensate for the capacitive mutual coupling in the antenna element.
  • the dual polarised antenna element according to the present invention has the advantage that it can provide good antenna isolation through an efficient compensation for essentially all types of capacitive coupling between the feeders in the antenna element, including capacitive coupling between the feeders and the radiating part of the antenna element.
  • the compensation is achieved by the use of a compensation line, which is small in size, not costly to produce, easy to implement and which efficiently cancels out the capacitive coupling being present by its inductive character.
  • the dual polarized antenna element is of the aperture coupled patch antenna type.
  • Each feeder here includes a pair of feed lines extending along slots of a cross shaped aperture such that the feed lines cross each other at a mutual distance, resulting in a capacitive coupling between the feeders.
  • Such a crossing can be arranged as an air-bridge.
  • this capacitive coupling is cancelled by the high impedance connection between the feeders.
  • Dual polarized antenna elements commonly suffer from imbalance due to mutual coupling for various reasons. Even though an antenna element may show a geometrical symmetry to a large extent, including the radiating part and the majority of the feed network, we typically have one or more points of asymmetry causing mutual coupling.
  • Fig. 2 shows one example of this for a patch antenna element including a ground plane 202, a top patch 203 and a lower patch 204.
  • an electromagnetically coupled patch element is fed by two orthogonal feeders 205, 206, both with a capacitive coupling to the two stacked patches.
  • the antenna element is here not symmetrical, since the feeder connections are not symmetrical. For example, if we look into the element along for example the feeder 205 at the bottom of the figure, we see that only one side (the left side) of the other sides of each patch is loaded by another feeder 206, while the other sides (for instance the right side) have an open circuit. Thus, the antenna element is not symmetrical around the plane of the dashed line 207, since there is no feeder connection at the right side of the antenna element.
  • each of the feeders 305, 306, feeding a polarization includes a pair of feed lines 307, 308 extending in parallel along the cross shaped aperture 309, respectively, such that a two of those feed lines cross each other in one point 310.
  • This at least one crossing 310 is typically achieved by using an air bridge for one of the polarizations. This air bridge crossing destroys the symmetry of the antenna element and imposes a capacitive coupling between the two feeders 305, 306.
  • These antenna elements 401 are dual polarized antenna elements and include a first feeder 405 for feeding said antenna element 401 in a first polarization direction.
  • the first feeder 405 has a connection port P1.
  • the antenna elements 401 further have a second feeder 406 for feeding said antenna element 401 in a second polarization direction, also being provided with a connection port P2.
  • Fig. 4a schematically illustrates a general dual polarized antenna element 401, being fed by two feeders 405, 406, having mutual coupling between them.
  • each one of the feeders 405, 406 includes a pair of feed lines 407, 408 extending in parallel along the cross shaped aperture 409, on each side thereof, respectively, such that two of those feed lines 407, 408 cross each other in one point 410, typically being arranged as an air bridge.
  • Such an antenna structure could also result in more than one crossing of feed lines, depending on the shape of the feed lines.
  • a compensation line 420 is arranged between said first and said second feeders 405, 406.
  • the compensation line 420 should be connected to the first and second feeders 405, 406 in a point on each of the feeders that is in close proximity to a radiating part of the antenna element.
  • the mutual coupling between the feeders is of an essentially capacitive character and can be cancelled by the compensation line 420, if the compensation line 420 has an essentially inductive character.
  • This is, according to the present invention, achieved by arranging the compensation line 420 such that its electrical length ⁇ is short and that it is thin such that it has high impedance relative to an impedance of the first and second feeders 405, 406.
  • the electrical length ⁇ of the compensation line 420 should be small, preferably being less than 2n/3 rad, thus ⁇ ⁇ 2n/3 rad.
  • the electrical length ⁇ of the compensation line 420 should be small, preferably being less than 2n/3 rad, thus ⁇ ⁇ 2n/3 rad.
  • other lengths than this could be advantageous for different implementations.
  • the compensation line 420 should have an impedance that is at least twice as high as the impedance for the feeders 405, 406.
  • the electrical length ⁇ is, as is well known for a person skilled in the art, a length that is related to the wavelength of the signal being transmitted.
  • the compensation line 420 being connected between the first and second feeders 405, 406 a novel method of coupling the polarisations together via an essentially inductive connection is used, in such way that the magnitude and phase of this coupling cancels the mutual coupling in other parts of the antenna element.
  • a required isolation level is achieved at low cost, which is small in size and easy to implement.
  • the compensation line 420 is implemented by a high impedance microstrip line in close proximity of the radiating patch 403.
  • the compensation line 420 should have a short electrical length ⁇ and have an impedance, which is much higher than the impedance for the feeders.
  • the feeders 405, 406 can have an impedance of around 50 ⁇ , whereas the compensation line has an impedance of around 220 ⁇ .
  • the compensation line is connected to the first feeder 405 at a first distance D 1 from the radiating part of the antenna element, for instance a radiating patch.
  • the compensation line is also connected to the second feeder 406 at a second distance D 2 from the radiating part.
  • the first and second distances should be very short relative to the wavelength of the transmitted signal.
  • the first and second distances should preferably be much less than half of the wavelength of the transmitted signal, and more preferably much less than a quarter of the wavelength of the transmitted signal, in order to efficiently cancel the capacitive coupling between the feeders.
  • D 1 ⁇ ⁇ /2 and D 2 ⁇ ⁇ /2 preferably D 1 ⁇ ⁇ /4 and D 2 ⁇ ⁇ /4.
  • Such a capacitive coupling can occur in any situation where a feeder or a feed line of one polarization is close to a feeder or a feed line of another polarization. Such a situation can thus occur in an air-bridge, but also somewhere else in the antenna element, where feeders run in close distance to each other. Also, as is exemplified below, there can be a capacitive coupling between one or both of the feeders and the radiating part of the antenna.
  • An antenna element with two input ports is represented by a scattering matrix S or by an impedance matrix Z , both being of the dimension 2 X 2.
  • Each port here corresponds to one of the two orthogonal polarizations of the radiated wave.
  • S 21 2 ⁇ Z 21 ⁇ Z 0 Z 11 + Z 0 ⁇ Z 22 + Z 0 - Z 12 ⁇ Z 21
  • Fig. 5 we have a second 2 X 2 matrix defined by S M or Z M .
  • S M loss-less matrix
  • Z M the coupling from port 1' to 2' is zero. This could be done by using, e.g., a directive coupler.
  • the mutual coupling often includes capacitive coupling between at least one of the first and second feeders and the radiating part, here being a patch, of said antenna element.
  • Fig. 6a shows an antenna element defined by a matrix Z with mutual coupling represented by a capacitance C. Note that the ground reference line in Fig. 5 here has been removed for clarity. Fig 6a also shows a compensation connection in the form of an inductance L, in accordance with the present invention.
  • Equation (7) shows that, in order to have zero coupling when X is real, we need to have X ⁇ ⁇ .
  • this inductive compensation line can be implemented as a connection between the feeders having a short electrical length and being thin, such that it has a high impedance in relation to the feeder impedance.
  • a high impedance transmission line should correspond to a large inductance.
  • High impedance means high impedance relative to the impedance of the feeders used for feeding the polarizations.
  • the electrical length ⁇ of the compensation line should be much less than 1 rad, in order to a result in an approximated expression.
  • the electrical length ⁇ should preferably be less than 2n/3 rad, thus ⁇ ⁇ 2n/3 rad. This electrical length also results in a compensation line having an essentially inductive character.
  • the electrical length ⁇ of the essentially inductive compensation line is longer than 2n/3 rad.
  • the feeders can have an impedance of 50 ⁇
  • the compensation line can have an impedance of more than twice the feeder impedance, for instance 220 ⁇ .
  • the compensation line can, for instance, be implemented as a 0.5 mm wide microstrip line.
  • the patches can have a size of, for instance, 66 mm or 56 mm.
  • the antenna element of the present invention has been designed and simulated for signals in the frequency interval 1800 MHz to 2200 MHz.
  • the inventive idea of the present invention may, however, also be implemented in other frequency intervals, as is clear to a skilled person.
  • dual polarised antenna elements of the present invention are arranged in an antenna array.
  • the two polarisations of two patches of two antenna array elements are each fed by a first feeder and a second feeder.
  • a compensation line between the first and second feeders in close proximity of each of the patches, respectively, thereby enhancing the antenna isolation of the antenna elements of the array.
  • such an antenna array can include essentially any number of dual polarized antenna elements according to the present invention.
  • the antenna isolation of the present invention is combined with other techniques for improving antenna isolation, being any one of the techniques of parasitic impedances and/or shield wall and/or asymmetrical/ rectangular patches and/or diagonal apertures and/or shifted feed positions.
  • Such a combination has the advantage of even further enhancing the level of isolation.
  • the present invention can be used on essentially any dual polarised antenna element, although, for illustrational reasons, it is mainly described in terms of patch antennas, such as aperture coupled patch antennas, in this specification.
  • Figs. 8-10 show simulations of coupling, reflection and radiation patterns for a dual polarised patch antenna element according to prior art and according to the present invention.
  • Figs. 8a , 9a and 10a show simulations for a prior art antenna, basically an antenna element as the one shown in fig. 2 .
  • Figs. 8b , 9b , and 10b show simulations for an antenna element according to the present invention, more specifically for an antenna element as the one shown in fig. 4c , having a compensation line arranged between the feeders.
  • a microstrip line has been used as the compensation line 420, the microstrip line being implemented as a 0.5 mm wide line resulting in an impedance of 220 ⁇ for the compensation line 420.
  • the first and second feeders 205, 206, 405, 406 feeders here have an impedance of 50 ⁇ .
  • a current division between the 50 ⁇ impedance of the first and second feeders 405, 406 and the 220 ⁇ impedance of the compensation line 420 will take place in the antenna element according to the present invention.
  • the mutual coupling 830 is much lower for the antenna element of the present invention (shown in fig. 8b ), as for the prior art antenna element (shown in fig. 8a ). Note here that the two diagrams have differing scales.
  • the antenna element of the present invention thus has a coupling being around 30 dB between the feeder ports.
  • the reflection 840 is more or less similar for the prior art antenna element and the antenna element of the present invention.
  • the cross polarisation, E_cross is greatly improved for the antenna element according to the present invention ( fig. 9b ), as compared to the prior art antenna element ( fig. 9a ).
  • THETA is here defined as the angle from a z-axis being perpendicular to both the x-axis and y axis in the system of coordinates defined in fig. 4c .
  • the radiation pattern in the direction of the polarisation, E_co, is very similar for both the prior art antenna element ( fig. 9a ) and for the antenna element of the present invention ( fig. 9b ). This tells us that that we have not deteriorated that characteristic of the radiation at the same time as we have gained a lot for the cross polarisation.
  • the radiation pattern in the direction of the polarisation, E_co, is also here not deteriorated by the compensation line of the present invention.
  • the coupling isolation (E_cross) for the radiation pattern for the antenna array has shown to be more than 23 dB.

Landscapes

  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Waveguide Aerials (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)

Abstract

A dual polarized antenna element having improved antenna isolation is disclosed by the present invention. The antenna element includes a first feeder for feeding the antenna element in a first polarization direction, and a second feeder for feeding the antenna element in a second polarization direction. According to the present invention, a compensation line is arranged between the first and the second feeders for compensating for an imbalance caused by an essentially capacitive coupling between the first and second feeders. The compensation line is connected to the first and second feeders in close proximity to a radiating part of said antenna element, and has a short electrical length θ and a high impedance relative to an impedance of the first and second feeders, respectively, thereby giving the compensation line an essentially inductive character.

Description

    Technical field
  • The present invention relates to a dual polarized antenna element and an antenna array, in which the antenna element includes:
    • a first feeder for feeding the antenna element in a first polarization direction, and
    • a second feeder for feeding the antenna element in a second polarization direction.
    Background of the invention
  • Dual polarised or X-polarised antennas are today commonly used in cellular systems for mobile communication. The use of such antennas allows the use of polarisation diversity techniques to combat signal fading in the system. Compared to the use of vertical polarised antennas and space diversity techniques the number of antennas needed is reduced to half, which saves costs and reduces the size and the visual appearance of the antenna installations.
  • One important performance measure for dual polarised antennas is the isolation between the two antenna ports feeding the two polarisations. Typically, an isolation of more than 30 dB between the ports is wanted, which corresponds to a power coupling of less than 1/1000 between the ports.
  • An aperture coupled patch antenna element is a commonly used antenna type for dual polarised systems. In aperture coupled patch antenna elements, one or more metallic patches are fed by a micro strip feeding arrangement through a cross shaped aperture in a ground plane, as is shown in figure 1. Here, the antenna element 101 includes a radiating patch 103, fed through an aperture 109 by a microstrip feed line 105 positioned between a shielding cage 102 and a printed circuit board.
  • Isolation between a transmitting and a receiving signal path in a dual polarized antenna has been described in, for instance, prior art document US6509883 . According to this document, a signal being transmitted from a first antenna element having one polarisation is received by a second antenna element having another polarisation, thereby causing an unwanted signal to be received by the second antenna element. In order to compensate for this, a compensation path is arranged between the transmitting and receiving signal paths, where the compensation path has a length such that the compensation signal travelling through the compensation path and the unwanted signal have equal magnitude and opposite phase when they meet in the receiving signal path.
  • Prior art solutions, like the one described in US6509883 , have a disadvantage in that they only compensate for signals having been transmitted from one antenna element and received by another antenna element. Thus, no solution is shown for solving the problem of capacitive coupling related to the feeders themselves.
  • In US6509883 , the compensation path as well as the transmitting and receiving signal paths have to be adapted to have certain lengths in order to be able to cancel out the unwanted signal, having been transmitted from the first antenna and received by the second antenna, since a difference in length of an odd number of half wavelengths has to be present between the paths travelled by the unwanted signal and the compensation signal.
  • The prior art solution will therefore only cancel out this specific unwanted signal. Other unwanted signals, resulting from couplings other than this one, such as unwanted signals originating from capacitive coupling between the feeders in a point where the feeders are close to each other, will not be cancelled by the solution shown in this document, since the distinctive length requirements of the signal paths result in cancellation of the unwanted signal only if the unwanted signal and the compensation signal have travelled exactly those required lengths.
  • Also, a capacitive coupling between the feeders may take place at a very unfortunate point, for which a difference in length of an even number of half wavelength results between the paths travelled by the unwanted signal and by the compensation signal in US6509883 . The compensation signal would in this case add to the unwanted signal instead of cancelling it.
  • Further, due to the signal path length requirements, the antenna element shown in this document has to have a certain size to achieve efficient cancellation, which is disadvantageous.
  • Thus, there is a problem in prior art relating to cancellation of different kinds of couplings being present in a dual polarized antenna element.
  • Summary of the invention
  • It is an object of the present invention to provide a dual polarised antenna element that solves the above stated problems.
  • The present invention aims to provide a dual polarised antenna element, which offers improved antenna isolation for all kinds of essentially capacitive couplings between the feeders. The present invention thus aims to provide compensation for capacitive coupling between the feeders, also including a capacitive coupling occurring via the radiating part, for example a radiating patch, of the antenna element.
  • According to an embodiment of the present invention, the object is for a dual polarized antenna element achieved by the use of:
    • a compensation line being arranged between the first and the second feeders for compensating for an imbalance caused by an essentially capacitive coupling between the first and second feeders, where
    • the compensation line is connected to the first and second feeders in close proximity to a radiating part of the antenna element, and has a short electrical length θ and a high impedance relative to an impedance of the first and second feeders, respectively, thereby giving the compensation line an essentially inductive character.
  • The object is also achieved by an antenna array including at least two such dual polarized antenna elements.
  • Thus, the present invention achieves compensation of mutual coupling in dual polarized antenna elements using a compensation line being connected between the input ports. When this compensation line is short in relation to the wavelength, this connection will act as an inductive element well suited to compensate for the capacitive mutual coupling in the antenna element.
  • The dual polarised antenna element according to the present invention has the advantage that it can provide good antenna isolation through an efficient compensation for essentially all types of capacitive coupling between the feeders in the antenna element, including capacitive coupling between the feeders and the radiating part of the antenna element. The compensation is achieved by the use of a compensation line, which is small in size, not costly to produce, easy to implement and which efficiently cancels out the capacitive coupling being present by its inductive character.
  • According to an embodiment of the present invention, the dual polarized antenna element is of the aperture coupled patch antenna type. Each feeder here includes a pair of feed lines extending along slots of a cross shaped aperture such that the feed lines cross each other at a mutual distance, resulting in a capacitive coupling between the feeders. Such a crossing can be arranged as an air-bridge. In the antenna element according to this embodiment, this capacitive coupling is cancelled by the high impedance connection between the feeders.
  • Detailed exemplary embodiments and advantages of the antenna elements and antenna arrays of the present invention will now be described with reference to the appended drawings illustrating some preferred embodiments.
  • Brief description of the drawings
    • Fig. 1 shows a prior art aperture coupled patch antenna element.
    • Fig. 2 shows an unbalanced prior art antenna element.
    • Figs. 3a-b show unbalanced prior art antenna elements.
    • Figs. 4a-c schematically show dual polarized antenna elements according to the present invention.
    • Fig. 5 schematically illustrates mutual coupling.
    • Figs. 6a-b schematically illustrates capacitive mutual coupling.
    • Figs. 7a-b illustrates transmission line impedances.
    • Figs. 8a-b show simulations for a prior art antenna element (a), and for an antenna element according to the present invention (b).
    • Figs. 9a-b show simulations for a prior art antenna element (a), and for an antenna element according to the present invention (b).
    • Figs. 10a-b show simulations for a prior art antenna element (a), and for an antenna element according to the present invention (b).
    Detailed description of the invention
  • Dual polarized antenna elements commonly suffer from imbalance due to mutual coupling for various reasons. Even though an antenna element may show a geometrical symmetry to a large extent, including the radiating part and the majority of the feed network, we typically have one or more points of asymmetry causing mutual coupling.
  • Fig. 2 shows one example of this for a patch antenna element including a ground plane 202, a top patch 203 and a lower patch 204. Here, an electromagnetically coupled patch element is fed by two orthogonal feeders 205, 206, both with a capacitive coupling to the two stacked patches. The antenna element is here not symmetrical, since the feeder connections are not symmetrical. For example, if we look into the element along for example the feeder 205 at the bottom of the figure, we see that only one side (the left side) of the other sides of each patch is loaded by another feeder 206, while the other sides (for instance the right side) have an open circuit. Thus, the antenna element is not symmetrical around the plane of the dashed line 207, since there is no feeder connection at the right side of the antenna element.
  • In fig 3a, and more in detail in fig. 3b, an aperture coupled patch antenna element 301 having a shielding cage 302 for back radiation and a cross-shaped aperture 309 is disclosed. Here, each of the feeders 305, 306, feeding a polarization, respectively, includes a pair of feed lines 307, 308 extending in parallel along the cross shaped aperture 309, respectively, such that a two of those feed lines cross each other in one point 310. Because of the symmetrical shape of the micro strip feeders, including the feed lines, each feeding one polarisation, they need to cross each other in at least one point 310, as can be seen in fig. 3a and 3b. This at least one crossing 310 is typically achieved by using an air bridge for one of the polarizations. This air bridge crossing destroys the symmetry of the antenna element and imposes a capacitive coupling between the two feeders 305, 306.
  • Thus, in both of the cases shown in figs. 2 and 3, there is an asymmetry present, which will cause mutual port-to-port coupling between the port P1 and the port P2 of the feeders. This mutual coupling and its corresponding imbalance have to be mitigated in order to achieve efficient antenna isolation.
  • According to the present invention, as will be described more in detail below, it has been discovered that such mutual coupling between the feeders often is of essentially capacitive character. From this finding, it has further been realized that an element having an essentially inductive character connected between the feeders could be used for reducing the mutual coupling between the feeders.
  • In figs 4a-4c, three different types of dual polarized antenna elements according to different embodiments of the present invention are shown schematically. (Reference numbers are here only given to parts that are needed for explanation of the present invention.) These antenna elements 401 are dual polarized antenna elements and include a first feeder 405 for feeding said antenna element 401 in a first polarization direction. The first feeder 405 has a connection port P1. The antenna elements 401 further have a second feeder 406 for feeding said antenna element 401 in a second polarization direction, also being provided with a connection port P2.
  • Fig. 4a schematically illustrates a general dual polarized antenna element 401, being fed by two feeders 405, 406, having mutual coupling between them.
  • As shown in fig 4b, for the case that the antenna element 401 is an aperture coupled patch antenna element having a cross-shaped aperture, each one of the feeders 405, 406 includes a pair of feed lines 407, 408 extending in parallel along the cross shaped aperture 409, on each side thereof, respectively, such that two of those feed lines 407, 408 cross each other in one point 410, typically being arranged as an air bridge. Such an antenna structure could also result in more than one crossing of feed lines, depending on the shape of the feed lines.
  • According to the present invention, in order to compensate for the imbalance resulting from the mutual coupling between the feeders, a compensation line 420 is arranged between said first and said second feeders 405, 406. The compensation line 420 should be connected to the first and second feeders 405, 406 in a point on each of the feeders that is in close proximity to a radiating part of the antenna element.
  • As was stated above (and will be proven below), the mutual coupling between the feeders is of an essentially capacitive character and can be cancelled by the compensation line 420, if the compensation line 420 has an essentially inductive character. This is, according to the present invention, achieved by arranging the compensation line 420 such that its electrical length θ is short and that it is thin such that it has high impedance relative to an impedance of the first and second feeders 405, 406. These characteristics of the compensation line 420 make the compensation line essentially inductive.
  • More in detail, as will be shown below, in order to achieve an inductive character for the compensation line 420, the electrical length θ of the compensation line 420 should be small, preferably being less than 2n/3 rad, thus θ < 2n/3 rad. However, as is clear to a skilled person, also other lengths than this could be advantageous for different implementations.
  • Also, the compensation line 420 should have an impedance that is at least twice as high as the impedance for the feeders 405, 406. The electrical length θ is, as is well known for a person skilled in the art, a length that is related to the wavelength of the signal being transmitted.
  • Thus, by the compensation line 420 according to the present invention, being connected between the first and second feeders 405, 406, a novel method of coupling the polarisations together via an essentially inductive connection is used, in such way that the magnitude and phase of this coupling cancels the mutual coupling in other parts of the antenna element. Thereby, a required isolation level is achieved at low cost, which is small in size and easy to implement.
  • In fig. 4c, for a dual polarized patch antenna, the compensation line 420 is implemented by a high impedance microstrip line in close proximity of the radiating patch 403. In order to have an inductive character, the compensation line 420 should have a short electrical length θ and have an impedance, which is much higher than the impedance for the feeders. For example, the feeders 405, 406 can have an impedance of around 50 Ω, whereas the compensation line has an impedance of around 220 Ω.
  • The compensation line is connected to the first feeder 405 at a first distance D1 from the radiating part of the antenna element, for instance a radiating patch. The compensation line is also connected to the second feeder 406 at a second distance D2 from the radiating part. According to an embodiment of the present invention, the first and second distances should be very short relative to the wavelength of the transmitted signal. The first and second distances should preferably be much less than half of the wavelength of the transmitted signal, and more preferably much less than a quarter of the wavelength of the transmitted signal, in order to efficiently cancel the capacitive coupling between the feeders. Thus, preferably D1 << λ/2 and D2 << λ/2, and more preferably D1 << λ/4 and D2 << λ/4.
  • By the use of such a compensation line, having an inductive character, the capacitive coupling between the feeders is cancelled, as will be shown in the following.
  • Such a capacitive coupling can occur in any situation where a feeder or a feed line of one polarization is close to a feeder or a feed line of another polarization. Such a situation can thus occur in an air-bridge, but also somewhere else in the antenna element, where feeders run in close distance to each other. Also, as is exemplified below, there can be a capacitive coupling between one or both of the feeders and the radiating part of the antenna.
  • It will now be shown that a mutual coupling between the feeders, including coupling between the feeders and the radiating parts of the two polarizations, often is of capacitive character and that this mutual coupling can be cancelled by the use of a compensation line between the feeders having an essentially inductive character.
  • A general description of mutual coupling in a radiating part is shown in fig. 5. An antenna element with two input ports is represented by a scattering matrix S or by an impedance matrix Z, both being of the dimension 2 X 2. Each port here corresponds to one of the two orthogonal polarizations of the radiated wave.
  • The scattering matrix S provides the relationship between ingoing voltage waves (plus sign) and outgoing voltage waves (minus sign) on the ports: V - = SV +
    Figure imgb0001
  • The impedance matrix Z determines the ratio between voltage vector V and current vector I on the lines: V = ZI
    Figure imgb0002
  • If all ports have the same characteristic impedance Z 0, these are related by the following well-known matrix equation: Z = Z 0 E + S E - S - 1 S = Z + Z 0 E - 1 Z - Z 0 E ʹ
    Figure imgb0003

    where E is the identity matrix.
  • In particular, from the matrix equation (3) it follows that the mutual coupling between the two ports 1 and 2, S 21, is related to the mutual impedance as: S 21 = 2 Z 21 Z 0 Z 11 + Z 0 Z 22 + Z 0 - Z 12 Z 21
    Figure imgb0004
  • Further, in Fig. 5 we have a second 2 X 2 matrix defined by SM or ZM . When analyzing Fig. 5, it is clear that we, in general, can design a loss-less matrix SM such that the coupling from port 1' to 2' is zero. This could be done by using, e.g., a directive coupler.
  • In accordance with the present invention, we will here study a special case of cross-polar coupling in the antenna element, which is the case when this coupling is a result of a capacitance between the feeders and the radiating parts of the two polarizations. This is illustrated in Figs. 6a and 6b.
  • In general, the mutual coupling often includes capacitive coupling between at least one of the first and second feeders and the radiating part, here being a patch, of said antenna element.
  • Fig. 6a shows an antenna element defined by a matrix Z with mutual coupling represented by a capacitance C. Note that the ground reference line in Fig. 5 here has been removed for clarity. Fig 6a also shows a compensation connection in the form of an inductance L, in accordance with the present invention.
  • Fig. 6b shows the antenna element from Fig. 6a, but with the two shunt loads, corresponding to the mutual coupling and the compensation connection, being represented by a single load jX = jωL + 1 / jωC ,
    Figure imgb0005

    and Z' being replaced by Z.
  • Here, the elements of the impedance matrix Z can be determined from circuit theory as: Z 11 = Z 22 = V 1 I 1 | I 2 = 0 = Z 0 / / Z 0 + jX = Z 0 2 + jXZ 0 2 Z 0 + jX
    Figure imgb0006

    and by performing voltage division and (5): Z 12 = Z 21 = V 2 I 2 | I 2 = 0 = Z 0 Z 0 + jX V 1 I 1 | I 2 = 0 = Z 0 Z 0 2 + jXZ 0 Z 0 + jX 2 Z 0 + jX = Z 0 2 2 Z 0 + jX .
    Figure imgb0007
  • Substitution of (5-6) in (4) gives: S 21 = 2 Z 0 2 2 Z 0 + jX 2 Z 0 + jX Z 0 2 + jX Z 0 + Z 0 2 Z 0 + jX 2 - Z 0 4 = Z 0 3 2 Z 0 + jX 3 Z 0 2 + j 2 X Z 0 - Z 0 4 = Z 0 2 Z 0 + jX 4 Z 0 2 + j 6 X Z 0 - 2 X 2 .
    Figure imgb0008
  • Equation (7) shows that, in order to have zero coupling when X is real, we need to have X → ∞.
  • Since jX is a parallel circuit we have: jX = 1 jωC + 1 jωL = jωL 1 - ω 2 LC
    Figure imgb0009
  • Note here that, from a feeder input port point of view, the capacitive mutual coupling and the compensation line together form a parallel resonance circuit.
  • Thus, the solution is the well-known resonance condition: L = 1 ω 2 C X ∞ and S 21 = 0.
    Figure imgb0010
  • Therefore, the mutual coupling can be cancelled by the use of a compensation line between the feeders having an inductive character.
  • In the following, it will be shown that this inductive compensation line can be implemented as a connection between the feeders having a short electrical length and being thin, such that it has a high impedance in relation to the feeder impedance.
  • We have seen above that mutual coupling from a capacitance can be compensated by adding an inductive element between the feeders. At microwave frequencies (e.g. above 1 GHz), this is preferably done by using for example a transmission line rather than discrete components. An illustration of the use of such a transmission line is shown in Figs. 4a-c.
  • Since the characteristic impedance of a transmission line is Z c = L C ,
    Figure imgb0011

    a high impedance transmission line should correspond to a large inductance.
  • The question is then in which sense such a thin transmission line may be seen as the discrete element required by equation (7) above. Consider the transmission line shown in Fig. 7. In Fig. 7a, a high impedance transmission line of electrical length θ is connected to a line with the system impedance Z0 . In Fig. 7b, a general case is shown.
  • The input impedance Z' at the beginning of the high impedance line is related to the impedance of the load ZL by the well-known transmission line formula: = Z m Z L + j Z m tan θ Z m + j Z L tan θ
    Figure imgb0012
  • If the high impedance transmission line is short, i.e. θ << 1 rad, we may approximate equation (9) as: Z m Z L + j Z m θ Z m + j Z L θ = Z m Z L Z m + j Z m 2 + Z L 2 θ + Z L + Z m θ 2 Z m 2 + Z L 2 θ 2 Z L + Z m 2 + Z L 2 Z m ,
    Figure imgb0013

    where we have used tan θ ≈ sin θ ≈ θ and then dropped the θ2-terms. From equation (10), it is clear that the effect of a short high impedance line is to add a positive series reactance. If the line is very thin so that the impedance is very high, the total impedance is simply: Z L + jZ m θ
    Figure imgb0014
  • Thus, by connecting a compensation line between the feeders, an inductive element between the feeders is added, if the compensation line has a short electrical length θ and a high impedance in relation to the impedance of the feeders.
  • Thus, as was deducted above, such a high impedance inductive compensation line cancels the mutual coupling between the feeders. High impedance here means high impedance relative to the impedance of the feeders used for feeding the polarizations.
  • In connection with equation 10 above, it is, for pedagogic reasons, stated that the electrical length θ of the compensation line should be much less than 1 rad, in order to a result in an approximated expression. However, for practical implementations, according to one embodiment of the invention, the electrical length θ should preferably be less than 2n/3 rad, thus θ < 2n/3 rad. This electrical length also results in a compensation line having an essentially inductive character.
  • Also, as is clear for a skilled person studying equations 10-11 and fig. 5, different electrical lengths θ of the compensation line, having an essentially inductive character, can be suitable for different implementations of the invention. Therefore, according to an embodiment of the present invention, the electrical length θ of the essentially inductive compensation line is longer than 2n/3 rad.
  • As non-limiting numerical examples, the feeders can have an impedance of 50 Ω, and the compensation line can have an impedance of more than twice the feeder impedance, for instance 220 Ω. The compensation line can, for instance, be implemented as a 0.5 mm wide microstrip line. Further, the patches can have a size of, for instance, 66 mm or 56 mm.
  • The antenna element of the present invention has been designed and simulated for signals in the frequency interval 1800 MHz to 2200 MHz. The inventive idea of the present invention may, however, also be implemented in other frequency intervals, as is clear to a skilled person.
  • Further, according to an embodiment of the present invention, dual polarised antenna elements of the present invention are arranged in an antenna array. Here, the two polarisations of two patches of two antenna array elements are each fed by a first feeder and a second feeder. According to the embodiment of the invention, there is arranged a compensation line between the first and second feeders in close proximity of each of the patches, respectively, thereby enhancing the antenna isolation of the antenna elements of the array. As is clear to a skilled person, such an antenna array can include essentially any number of dual polarized antenna elements according to the present invention.
  • Also, according to an embodiment of the present invention, the antenna isolation of the present invention is combined with other techniques for improving antenna isolation, being any one of the techniques of parasitic impedances and/or shield wall and/or asymmetrical/ rectangular patches and/or diagonal apertures and/or shifted feed positions. Such a combination has the advantage of even further enhancing the level of isolation.
  • As is obvious for someone skilled in the art, the present invention can be used on essentially any dual polarised antenna element, although, for illustrational reasons, it is mainly described in terms of patch antennas, such as aperture coupled patch antennas, in this specification.
  • Figs. 8-10 show simulations of coupling, reflection and radiation patterns for a dual polarised patch antenna element according to prior art and according to the present invention. Figs. 8a, 9a and 10a show simulations for a prior art antenna, basically an antenna element as the one shown in fig. 2. Figs. 8b, 9b, and 10b show simulations for an antenna element according to the present invention, more specifically for an antenna element as the one shown in fig. 4c, having a compensation line arranged between the feeders.
  • In these simulations, a microstrip line has been used as the compensation line 420, the microstrip line being implemented as a 0.5 mm wide line resulting in an impedance of 220 Ω for the compensation line 420. The first and second feeders 205, 206, 405, 406 feeders here have an impedance of 50 Ω. Thus, a current division between the 50 Ω impedance of the first and second feeders 405, 406 and the 220 Ω impedance of the compensation line 420 will take place in the antenna element according to the present invention.
  • As can be seen in figs. 8a and 8b, the mutual coupling 830 is much lower for the antenna element of the present invention (shown in fig. 8b), as for the prior art antenna element (shown in fig. 8a). Note here that the two diagrams have differing scales. The antenna element of the present invention thus has a coupling being around 30 dB between the feeder ports. Also, the reflection 840 is more or less similar for the prior art antenna element and the antenna element of the present invention.
  • Further, figs. 9a and 9b show a simulated radiation pattern at 2000 MHz for the azimuth plane (ϕ= 0° in the coordinate system shown in fig. 4c) for the prior art antenna element (fig. 9a) and for the antenna element of the present invention (fig. 9b), both being simulated as having infinite ground planes.
  • As can be seen in figs. 9a and 9b, the cross polarisation, E_cross, is greatly improved for the antenna element according to the present invention (fig. 9b), as compared to the prior art antenna element (fig. 9a). For the present invention, the level of the cross polarisation is 30 dB on the z-axis (THETA =0), which is very desirable. THETA is here defined as the angle from a z-axis being perpendicular to both the x-axis and y axis in the system of coordinates defined in fig. 4c.
  • The radiation pattern in the direction of the polarisation, E_co, is very similar for both the prior art antenna element (fig. 9a) and for the antenna element of the present invention (fig. 9b). This tells us that that we have not deteriorated that characteristic of the radiation at the same time as we have gained a lot for the cross polarisation.
  • Figs. 10a and 10b show a simulated radiation pattern at 2000 MHz for the E-plane (ϕ= 45° in the coordinate system shown in fig. 4c) for the prior art antenna element (fig. 10a), and for the antenna element of the present invention (fig. 10b), both being simulated as having infinite ground planes.
  • As for the azimuth plane, it can be seen in figs. 10a and 10b, that the cross polarisation, E_cross, is greatly improved for the antenna element according to the present invention, as compared to the prior art antenna element. A very good isolation level of 30 dB on the z-axis (THETA =0) for the cross polarisation is here also achieved for the present invention.
  • The radiation pattern in the direction of the polarisation, E_co, is also here not deteriorated by the compensation line of the present invention.
  • Further, in corresponding simulations for an antenna array, including two antenna elements according to the present invention, the coupling isolation (E_cross) for the radiation pattern for the antenna array has shown to be more than 23 dB.

Claims (12)

  1. A dual polarized antenna element, including:
    - a first feeder for feeding said antenna element in a first polarization direction, and
    - a second feeder for feeding said antenna element in a second polarization direction,
    characterized in that
    - a compensation line is arranged between said first and said second feeders for compensating for an imbalance caused by an essentially capacitive coupling between said first and second feeders, where
    - said compensation line is connected to said first and second feeders in close proximity to a radiating part of said antenna element, and has a short electrical length θ and a high impedance relative to an impedance of the first and second feeders, respectively, thereby giving said compensation line an essentially inductive character.
  2. The dual polarized antenna element as claimed in claim 1, characterized in that said compensation line has an electrical length θ being less than 2n/3 rad, θ < 2n/3 rad.
  3. The dual polarized antenna element as claimed in anyone of claims 1-2, characterized in that said compensation line has an impedance being at least twice as high as an impedance for the first and second feeders, respectively.
  4. The dual polarized antenna element as claimed in anyone of claims 1-3, characterized in that said essentially capacitive coupling and said compensation line together, from a feeder input port point of view, form a parallel resonance circuit.
  5. The dual polarized antenna element as claimed in anyone of claims 1-4, characterized in that said essentially capacitive coupling includes at least a capacitive coupling between at least one of said first and second feeders and said radiating part of said antenna element.
  6. The dual polarized antenna element as claimed in anyone of claims 1-5, characterized in that said essentially capacitive coupling includes a capacitive coupling between said first and second feeders in at least one point where said first and second feeders are close to each other.
  7. The dual polarized antenna element as claimed in claim 6, characterized in that
    - said dual polarized antenna element is an aperture coupled patch antenna element, in which
    - said first feeder includes a first pair of feed lines extending in parallel along a first aperture slot, on each side thereof, and
    - said second feeder includes a second pair of feed lines extending in parallel along a second aperture slot, on each side thereof, where
    - said first and second pair of feed lines cross each other in said at least one point, at a mutual distance.
  8. The dual polarized antenna element as claimed in claim 7, characterized in that said first and second feeders cross each other in an air-bridge.
  9. The dual polarized antenna element as claimed in anyone of claims 1-8, characterized in that said dual polarized antenna element is provided with any one of the antenna element isolation techniques in the group: parasitic impedance(s), shield wall(s), asymmetrical patch, rectangular patch, diagonal apertures, shifted feed position(s).
  10. The dual polarized antenna element as claimed in anyone of claims 1-9, characterized in that said compensation line is connected to said first feeder at a first distance D1 from said radiating part and to said second feeder at a second distance D2 from said radiating part, where said first and second distances are very short relative to the wavelength of the transmitted signal.
  11. The dual polarized antenna element as claimed in claim 10, characterized in that said first and second distances D1, D2 are much less than half of the wavelength of the transmitted signal, D1 << λ/2 and D2 << λ/2, and preferably much less than a quarter of the wavelength of the transmitted signal, D1 << λ/4 and D2 << λ/4.
  12. An antenna array, characterized in that said antenna array includes at least two dual polarized antenna elements as defined in any one of claims 1-11.
EP09445009A 2008-04-11 2009-03-27 Improvement of antenna isolation Ceased EP2109183A1 (en)

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
SE0800827A SE532279C2 (en) 2008-04-11 2008-04-11 Improved antenna insulation

Publications (1)

Publication Number Publication Date
EP2109183A1 true EP2109183A1 (en) 2009-10-14

Family

ID=40756784

Family Applications (1)

Application Number Title Priority Date Filing Date
EP09445009A Ceased EP2109183A1 (en) 2008-04-11 2009-03-27 Improvement of antenna isolation

Country Status (2)

Country Link
EP (1) EP2109183A1 (en)
SE (1) SE532279C2 (en)

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102842755A (en) * 2012-07-11 2012-12-26 桂林电子科技大学 Dual-polarized antenna applicable to wireless local area network and manufacturing method of dual-polarized antenna
CN102842756A (en) * 2012-09-24 2012-12-26 桂林电子科技大学 Dual-polarization MIMO (Multiple Input Multiple Output) antenna array
EP3560111A4 (en) * 2016-12-21 2020-12-02 Intel Capital Corporation Wireless communication technology, apparatuses, and methods
CN113555674A (en) * 2020-04-24 2021-10-26 深圳市万普拉斯科技有限公司 Antenna device and mobile terminal

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111355029B (en) * 2020-04-09 2021-09-28 西安电子科技大学 High-performance dual-polarized microstrip antenna for fifth-generation communication system

Citations (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4728960A (en) 1986-06-10 1988-03-01 The United States Of America As Represented By The Secretary Of The Air Force Multifunctional microstrip antennas
US5159298A (en) * 1991-01-29 1992-10-27 Motorola, Inc. Microstrip directional coupler with single element compensation
EP0847101A2 (en) 1996-12-06 1998-06-10 Raytheon E-Systems Inc. Antenna mutual coupling neutralizer
WO1998033234A1 (en) 1997-01-24 1998-07-30 Allgon Ab A substantially flat, aperture-coupled antenna element
US5945951A (en) 1997-09-03 1999-08-31 Andrew Corporation High isolation dual polarized antenna system with microstrip-fed aperture coupled patches
WO2000001030A1 (en) * 1998-06-26 2000-01-06 Racal Antennas Limited Signal coupling methods and arrangements
WO2003052868A1 (en) 2001-12-19 2003-06-26 Raysat Cyprus Limited Antenna element
US20040155656A1 (en) * 2001-05-19 2004-08-12 Leussler Christoph Guenther Transmission and receiving coil for mr apparatus
US20070085540A1 (en) * 2005-09-30 2007-04-19 Du Jian J Method for developing a transmit coil of a magnetic resonance system

Patent Citations (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4728960A (en) 1986-06-10 1988-03-01 The United States Of America As Represented By The Secretary Of The Air Force Multifunctional microstrip antennas
US5159298A (en) * 1991-01-29 1992-10-27 Motorola, Inc. Microstrip directional coupler with single element compensation
EP0847101A2 (en) 1996-12-06 1998-06-10 Raytheon E-Systems Inc. Antenna mutual coupling neutralizer
WO1998033234A1 (en) 1997-01-24 1998-07-30 Allgon Ab A substantially flat, aperture-coupled antenna element
US5945951A (en) 1997-09-03 1999-08-31 Andrew Corporation High isolation dual polarized antenna system with microstrip-fed aperture coupled patches
WO2000001030A1 (en) * 1998-06-26 2000-01-06 Racal Antennas Limited Signal coupling methods and arrangements
US6509883B1 (en) 1998-06-26 2003-01-21 Racal Antennas Limited Signal coupling methods and arrangements
US20040155656A1 (en) * 2001-05-19 2004-08-12 Leussler Christoph Guenther Transmission and receiving coil for mr apparatus
WO2003052868A1 (en) 2001-12-19 2003-06-26 Raysat Cyprus Limited Antenna element
US20070085540A1 (en) * 2005-09-30 2007-04-19 Du Jian J Method for developing a transmit coil of a magnetic resonance system

Non-Patent Citations (3)

* Cited by examiner, † Cited by third party
Title
BOYANOV V: "Isolation improvement in dual port cross-slot coupled patch", PHASED ARRAY SYSTEMS AND TECHNOLOGY, 2003., IEEE INTERNATIONAL SYMPOSI UM ON 14-17 OCT. 2003, PISCATAWAY, NJ, USA,IEEE, 14 October 2003 (2003-10-14), pages 318 - 322, XP010676836, ISBN: 978-0-7803-7827-8 *
LINDMARK B ET AL: "Dual polarised multibeam antenna", ELECTRONICS LETTERS, IEE STEVENAGE, GB, vol. 35, no. 25, 9 December 1999 (1999-12-09), pages 2158 - 2160, XP006013070, ISSN: 0013-5194 *
LINDMARK, ELECTRONIC LETTERS, 9 December 1999 (1999-12-09)

Cited By (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102842755A (en) * 2012-07-11 2012-12-26 桂林电子科技大学 Dual-polarized antenna applicable to wireless local area network and manufacturing method of dual-polarized antenna
CN102842755B (en) * 2012-07-11 2015-07-22 桂林电子科技大学 Dual-polarized antenna applicable to wireless local area network and manufacturing method of dual-polarized antenna
CN102842756A (en) * 2012-09-24 2012-12-26 桂林电子科技大学 Dual-polarization MIMO (Multiple Input Multiple Output) antenna array
CN102842756B (en) * 2012-09-24 2015-07-22 桂林电子科技大学 Dual-polarization MIMO (Multiple Input Multiple Output) antenna array
EP3560111A4 (en) * 2016-12-21 2020-12-02 Intel Capital Corporation Wireless communication technology, apparatuses, and methods
US11424539B2 (en) 2016-12-21 2022-08-23 Intel Corporation Wireless communication technology, apparatuses, and methods
TWI782936B (en) * 2016-12-21 2022-11-11 美商英特爾公司 Wireless communication technology, apparatuses, and methods
US11955732B2 (en) 2016-12-21 2024-04-09 Intel Corporation Wireless communication technology, apparatuses, and methods
CN113555674A (en) * 2020-04-24 2021-10-26 深圳市万普拉斯科技有限公司 Antenna device and mobile terminal
CN113555674B (en) * 2020-04-24 2023-03-17 深圳市万普拉斯科技有限公司 Antenna device and mobile terminal

Also Published As

Publication number Publication date
SE532279C2 (en) 2009-12-01
SE0800827L (en) 2009-10-12

Similar Documents

Publication Publication Date Title
US8120536B2 (en) Antenna isolation
EP2812947B1 (en) Multiple antenna system
US9496914B2 (en) Polarization-diverse antennas and systems
CN107437659A (en) For reducing the apparatus and method of mutual coupling in aerial array
CN106469848B (en) A kind of broadband paster antenna based on double resonance mode
US10003117B2 (en) Two-port triplate-line/waveguide converter having two probes with tips extending in different directions
US20140118206A1 (en) Antenna and filter structures
EP2109183A1 (en) Improvement of antenna isolation
US8773318B2 (en) System of multi-beam antennas
EP3780279A1 (en) Array antenna apparatus and communication device
US8094082B2 (en) Polarization diversity multi-antenna system
Wang et al. High‐Isolation UWB MIMO Antenna with Multiple X‐Shaped Stubs Loaded between Ground Planes
EP2831950B1 (en) Enhanced connected tiled array antenna
Huang et al. A wide-band dual-polarized frequency-reconfigurable slot-ring antenna element using a diagonal feeding method for array design
EP3422465B1 (en) Hybrid circuit, power supply circuit, antenna device, and power supply method
Abedian et al. Mm-wave high isolated dual polarized dielectric resonator antenna for in-band full-duplex systems
CN103594802A (en) Butler matrix structure
WO2023001375A1 (en) Dual-polarization antenna element for generation of millimeter-wave frequency radiation
US8929699B2 (en) Symmetrical branching ortho mode transducer (OMT) with enhanced bandwidth
CN111864361A (en) Antenna unit and dual-polarized antenna with same
JPH08116211A (en) Plane antenna system
Knox Passive interference cancellation in a 2× 2 STAR MIMO antenna network
Egashira et al. Planar array antenna using both‐sided MIC's feeder circuits
Alekseitsev et al. The modified dual-frequency dipole antenna
US20230120328A1 (en) Rf device with isolated antennas

Legal Events

Date Code Title Description
PUAI Public reference made under article 153(3) epc to a published international application that has entered the european phase

Free format text: ORIGINAL CODE: 0009012

AK Designated contracting states

Kind code of ref document: A1

Designated state(s): AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HR HU IE IS IT LI LT LU LV MC MK MT NL NO PL PT RO SE SI SK TR

AX Request for extension of the european patent

Extension state: AL BA RS

17P Request for examination filed

Effective date: 20100316

17Q First examination report despatched

Effective date: 20100409

AKX Designation fees paid

Designated state(s): DE FR

RAP1 Party data changed (applicant data changed or rights of an application transferred)

Owner name: POWERWAVE TECHNOLOGIES, INC.

RAP1 Party data changed (applicant data changed or rights of an application transferred)

Owner name: P-WAVE HOLDINGS, LLC

RAP1 Party data changed (applicant data changed or rights of an application transferred)

Owner name: POWERWAVE TECHNOLOGIES S.A.R.L.

RAP1 Party data changed (applicant data changed or rights of an application transferred)

Owner name: INTEL CORPORATION

STAA Information on the status of an ep patent application or granted ep patent

Free format text: STATUS: THE APPLICATION HAS BEEN REFUSED

18R Application refused

Effective date: 20180216