EP1820267A1 - Controllable power operational transconductance amplifier - Google Patents

Controllable power operational transconductance amplifier

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Publication number
EP1820267A1
EP1820267A1 EP05769963A EP05769963A EP1820267A1 EP 1820267 A1 EP1820267 A1 EP 1820267A1 EP 05769963 A EP05769963 A EP 05769963A EP 05769963 A EP05769963 A EP 05769963A EP 1820267 A1 EP1820267 A1 EP 1820267A1
Authority
EP
European Patent Office
Prior art keywords
current
power
controllable
low power
signals
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP05769963A
Other languages
German (de)
French (fr)
Inventor
Wolfdietrich Georg Kasperkovitz
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Semiconductor Ideas to the Market ItoM BV
Original Assignee
Semiconductor Ideas to the Market ItoM BV
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Semiconductor Ideas to the Market ItoM BV filed Critical Semiconductor Ideas to the Market ItoM BV
Priority to EP05769963A priority Critical patent/EP1820267A1/en
Publication of EP1820267A1 publication Critical patent/EP1820267A1/en
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/45—Differential amplifiers
    • H03F3/45071—Differential amplifiers with semiconductor devices only
    • H03F3/45076—Differential amplifiers with semiconductor devices only characterised by the way of implementation of the active amplifying circuit in the differential amplifier
    • H03F3/4508—Differential amplifiers with semiconductor devices only characterised by the way of implementation of the active amplifying circuit in the differential amplifier using bipolar transistors as the active amplifying circuit
    • H03F3/45085—Long tailed pairs
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32—Modifications of amplifiers to reduce non-linear distortion
    • H03F1/3217—Modifications of amplifiers to reduce non-linear distortion in single ended push-pull amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/30—Single-ended push-pull [SEPP] amplifiers; Phase-splitters therefor
    • H03F3/3069—Single-ended push-pull [SEPP] amplifiers; Phase-splitters therefor the emitters of complementary power transistors being connected to the output
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/30—Single-ended push-pull [SEPP] amplifiers; Phase-splitters therefor
    • H03F3/3083—Single-ended push-pull [SEPP] amplifiers; Phase-splitters therefor the power transistors being of the same type
    • H03F3/3086—Single-ended push-pull [SEPP] amplifiers; Phase-splitters therefor the power transistors being of the same type two power transistors being controlled by the input signal
    • H03F3/3093—Single-ended push-pull [SEPP] amplifiers; Phase-splitters therefor the power transistors being of the same type two power transistors being controlled by the input signal comprising a differential amplifier as phase-splitting element
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2201/00—Indexing scheme relating to details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements covered by H03F1/00
    • H03F2201/32—Indexing scheme relating to modifications of amplifiers to reduce non-linear distortion
    • H03F2201/3233—Adaptive predistortion using lookup table, e.g. memory, RAM, ROM, LUT, to generate the predistortion

Definitions

  • the invention relates to a controllable power operational transconductance amplifier (OTA) suitable for use in a wide field of applications, including portable radio and audio sets, mobile telephone handsets, etcetera.
  • OTA operational transconductance amplifier
  • Such controllable power OTA is on itself known e.g. from US Patent 5,598,129.
  • an OTA derives an output current from a differential input voltage, the ratio of the output current to the differential input voltage being the transconductance g m , of the amplifier.
  • the output current varies proportional to said differential input voltage.
  • OTAs have many applications in particular in the field of radio, television and telecommunication, and are configured to provide a variety of functions such as slew rate limiting, filtering or signal level regulation.
  • a specific area of application for OTAs includes portable devices such as PDAs, portable MP3 players, portable radio and television receivers and mobile telephone handsets.
  • portable devices electrical power is provided by a battery, making power efficiency a primary design target in this specific area of application.
  • Other design targets, which in particular hold for mobile telephone handsets, are robustness, weight and size reduction and low cost implementation, requiring to maximize circuit integration and to reduce the number of IC external components.
  • the prior art controllable power OTA as disclosed in the above mentioned US Patent 5,598,129 comprises a class A input stage effectuating fixed maximum gain amplification followed by a class-AB amplifier stage.
  • a class-AB amplifier stage effectuating fixed maximum gain amplification followed by a class-AB amplifier stage.
  • the static or quiescent currents which are needed in said class-AB amplifier stage to establish voltage and other set levels are being reduced in a trade off with cross-over distortion. This trade off limits power saving to the minimum quiescent current level below which said distortion exceeds an unacceptable level.
  • the overall gain of said prior art controllable power OTA is controlled by a variable attenuation of the fixed maximum power output signal of the class-AB amplifier stage. This is obtained with a controllable class A attenuator following said class-AB amplifier stage by effecting a variable power loss.
  • This power loss is essential to the control of the overall gain of the prior art power OTA and is always there, even when there is no input signal.
  • the gain needed for a comfortable sound volume level within a normal volume control range amounts to an average of not more than 20% of the gain at maximum volume setting. This means that averagely about 80% of the power output of the class- AB amplification stage is wasted, exceeding by far the limited power saving obtained by the above trade off within said class-AB amplifier stage.
  • a controllable power OTA is characterized by a symmetrically structured, controllable input stage for controlling the overall power gain of the power OTA, receiving a differential input signal and deriving therefrom first and second, mutually matched low power current signals being coupled to first and second current controlled output current sources being arranged in class B push pull configuration, including means for bi-directionally rectifying said first and second low power current signals and providing in mutual alternation power amplification of said first and second low power current signals into first and second mutually exclusive high power current output signals being supplied through a current summer to a current output of said controllable power amplifier.
  • the invention is based on the insight that unlike voltage signals, current signals can be rectified accurately with respect to zero value by the simple use of diodes, bipolar or MOSFET transistors. Processing current signals instead of voltage signals allows for a proper class B push pull amplification, which does not need any quiescent current to avoid cross-over distortion.
  • the overall power gain control of the OTA is provided by the controllable input stage, i.e. in the low power signal part of the controllable power OTA where at any setting within the gain control range, linearity and power efficiency within this input stage can easily be obtained. Power gain is being provided with the push pull configured pair of first and second output current sources of the class B output stage.
  • the first and second low power current signals provided by the controllable input stage are alternately amplified within the respective first and second output current sources during mutually exclusive signal periods into alternately occurring, mutually exclusive high power first and second output currents.
  • These mutually exclusive high power first and second output currents are combined into said summer into a continuous high power output current.
  • both first and second current controlled current sources are fully blocked and no power is consumed in said class B output stage.
  • the power gain in said push pull stage is obtained by current amplification therewith avoiding the occurrence of non-linearities.
  • the push pull configured pair of first and second output current sources can be alternately activated by said first and second, mutually matched low power current signals during mutually exclusive signal periods in various alternative ways.
  • said first and second low power current signals are mutually matched in that they are identical in amplitude and signal waveform, hereinafter also being shortly referred to as identical, and supplied in mutually opposite directions to a pair of unidirectional current rectifiers being coupled in mutually same direction of conductivity and included in said means for bi- directionally rectifying said first and second low power current signals.
  • said first and second low power current signals are mutually matched in that they are identical and supplied in mutually same direction to a pair of unidirectional current rectifiers being coupled in mutually opposite direction of conductivity and included in said means for bi- directionally rectifying said first and second low power current signals.
  • said first and second current controlled output current sources comprise respectively first and second transistors having their collector- emitter paths serially connected between a bias voltage and mass, the first and second low power current signals being supplied to the base electrodes of said first and second transistors, respectively, the base-emitter p-n junctions of said first and second transistors constituting said means for bi-directionally rectifying said first and second low power current signals.
  • controllable power OTA in an embodiment of the controllable power OTA according to the invention, the controllable input stage being symmetrical in structure and including first and second mutually matched input OTAs each comprising a differential pair of transistors masscoupled through a common controllable current source, said differential pairs of transistors respectively receiving said differential input signal in mutual phase opposition and providing said first and second low power current signals with zero DC level to said means for bi-directionally rectifying said first and second low power current signals.
  • controllable input stage includes an input OTA comprising a differential pair of transistors masscoupled through a common controllable current source and receiving said differential input signal, said differential pair of transistors providing through common current mirror means said first and second low power current signals in mutually opposite polarities with zero DC level to means for bi-directionally rectifying said first and second low power current signals.
  • an embodiment of the controllable power OTA is characterized by said first and second current controlled output current sources being mutually identical and each comprising a bipolar PNP transistor having its base electrode coupled to the controllable input stage to receive said first and second low power current signals, respectively, its emitter to a bias voltage and its collector to the base electrode of a bipolar NPN transistor, the base-emitter p-n junction of the bipolar PNP transistors of said first and second current controlled output current sources constituting said pair of unidirectional rectifiers, the bipolar NPN transistors of said first and second current controlled output current sources being cascode coupled between said bias voltage and mass and providing said first and second mutually exclusive high power current output signals.
  • said first and second current controlled output current sources being provided with respectively a pair of bipolar NPN transistors arranged in Darlington pair configuration.
  • controllable power OTA is characterized by said first and second current controlled output current sources being provided with respectively MOSFET current mirror means with scaled input and output current mirror stages.
  • the invention also relates to a receiver using a controllable power OTA.
  • the receiver according to the invention is characterized by said controllable power OTA being coupled in common to a sound reproduction device and an antenna input of said receiver.
  • This measure allows to use a single wire for conveying audio signals from said controllable power OTA to said sound reproduction device on the one hand and for receiving RF broadcast signals and supplying the same to the receiver antenna input on the other hand, while securing effective separation between these signals without the use of capacitors and/or coils.
  • Figure 1 is a first embodiment of a controllable power OTA according to the invention
  • Figure 2 is a second embodiment of a controllable power OTA according to the invention.
  • Figure 3 is a push pull configuration of high gain first and second current controlled output current sources for use in a controllable power OTA according to the invention
  • Figure 4 is an alternative high gain embodiment of a current controlled output current source for use in a controllable power OTA according to the invention
  • Figure 5 is a MOSFET embodiment of a current controlled output current source for use in a controllable power OTA according to the invention
  • Figure 6 is an embodiment of a controllable input stage for use in said second embodiment of the controllable power OTA according to the invention
  • Figure 7 is a radio receiver using a controllable power OTA according to the invention.
  • Figure 1 shows a controllable power OTA according to the invention comprising a controllable input stage CIS receiving a differential input signal ⁇ Vin and deriving therefrom first and second low power current signals il and i2 respectively, which are coupled to first and second current controlled output current sources CCSl and CCS2 respectively, being arranged in class B push pull configuration.
  • the controllable input stage CIS comprises first and second mutually identical, also referred to as first and second mutually matched, auxiliary operational transconductance amplifiers OTAl and OT A2 each having a differential voltage input and a single current output.
  • the controllable input stage CIS is therewith symmetrical in structure.
  • conventional OTAs may be used such as e.g.
  • the differential input signal ⁇ Vin is supplied with mutual opposite polarities to the differential inputs of OTAl and OT A2.
  • the output current signals il and i2 of OTAl and 0TA2 hereinafter also being referred to as first and second low power current signals, vary proportionally with the differential input signal ⁇ Vin, and are mutually identical in amplitude and signal wave form, hereinafter being shortly referred to as identical, with mutually opposite polarities or directions.
  • OTA2 are respectively supplied to base electrodes of first and second mutually identical NPN transistors Tl and T2, which transistors constitute said first and second current controlled output current sources CCS 1 and CCS2, respectively.
  • the collector emitter paths of said first and second NPN transistors Tl and T2 are serially connected between bias voltage Vcc and mass, whereas the common connection between the emitter of Tl and the collector of T2 is coupled to a single current output of the controllable power OTA according to the invention.
  • the first and second low power current signals il and i2 of OTAl and OT A2 are being amplified in said first and second NPN transistors Tl and T2 during those half cycle periods, in which the direction of these first and second low power current signals il and i2 corresponds to the direction of conductivity of the base-emitter p-n diode junction of Tl and T2.
  • these first and second low power current signals il and i2 are mutually identical and have mutually opposite directions, either Tl is blocking and T2 is conducting, or vice versa.
  • the direction of il corresponds to the direction of conductivity of the base-emitter p-n diode j unction of T 1 as illustrated in Figure 1.
  • the second low power current i2 is absent (indicated with a dotted arrow), as T2 is blocking.
  • first and second mutually exclusive high power current output signals are obtained at the emitter of Tl and the collector of T2, which add up into a single periodic high power current output signal Io .
  • the common connection of the emitter of Tl and the collector of T2 therewith functions as a current summer.
  • the base-emitter diodes of Tl and T2 therewith function as a pair of unidirectional rectifiers being coupled in mutually same direction of conductivity as seen from the output of the controllable input stage CIS.
  • Tl and T2 operate as bi-directional rectifier means, providing accurate rectification of the first and second low power current signals il and i2 at zero current value. Precisely at each zero crossing, Tl changes from blocking or passive state into conducting or active state and T2 from conducting or active state blocking into passive state, or vice versa.
  • Tl and T2 therewith operate in class B push pull configuration, i.e.
  • first and second low power current signals il and i2 vary proportionally with the differential input signal ⁇ Vin at any value of the transconductance g m , whereas both transistors Tl and T2 provide constant current amplification. This secures linear operation throughout the controllable power OTA as a whole at any setting within the gain control range.
  • Figure 2 shows a second embodiment of a controllable power OTA according to the invention in which the differential input signal ⁇ Vin is supplied with mutual same polarity to the differential inputs of said first and second mutually identical auxiliary operational transconductance amplifiers OTAl and OT A2 of the controllable input stage CIS.
  • the first and second low power current signals il and i2 of OTAl and OT A2, which vary proportionally with the differential input signal ⁇ Vin, are mutually identical and are supplied in mutually same polarity or direction to base electrodes of NPN transistor Tl and PNP transistor T2, respectively.
  • the base-emitter p-n junctions of Tl and Tl function as a pair of unidirectional rectifiers being coupled in mutually opposite direction of conductivity as seen from the output of the controllable input stage CIS.
  • Tl and T2 operate as bi-directional rectifier means, providing accurate rectification of the first and second low power current signals il and i2 at zero current value.
  • the collector-emitter path of Tl is serially connected to the emitter-collector path of T2 between said bias voltage and mass.
  • Tl and T2 therewith obtaining class B push pull current amplification of said first and second low power current signals il and i2 in said first and second NPN transistors Tl and T2, accurately occurring in mutually exclusive half cycle signal periods.
  • first and second mutually exclusive high power current output signals Io 1 and Io2 are obtained at the emitters of Tl and T2, respectively, which add up into a single periodic high power current output signal Io at the current output of the controllable power OTA.
  • the common connection of the emitter of Tl and the collector of T2 therewith functions as a current summer.
  • Figure 3 is a push pull configuration of high gain two stage first and second current controlled output current sources CCSl and CCS for use in a controllable power OTA according to the invention as shown in Figure 1.
  • said first and second current controlled output current sources CCSl and CCS2 are mutually identical and respectively comprise first stage bipolar PNP transistors TI l and T21 , respectively, having base electrodes coupled to the controllable input stage CIS to receive said first and second low power current signals il and i2, respectively.
  • the emitters of Tl 1 and T21 are coupled to the bias voltage Vcc and the collectors to base electrodes of second stage bipolar NPN transistors Tl 2 and T22, respectively.
  • the base-emitter p-n junction of the bipolar PNP transistors Tl 1 and T21 of said first and second current controlled output current sources constitute said pair of unidirectional rectifiers
  • the bipolar NPN transistors Tl 2 and T22 of said first and second current controlled output current sources CCSl and CCS2 are cascode coupled between said bias voltage Vcc and mass and provide first and second mutually exclusive high power current output signals Io 1 and Io2, respectively.
  • the gain of said first and second current controlled output current sources CCSl and CCS2 is respectively determined by the current gain factor of NPN transistor TI l multiplied by the gain factor of the PNP transistor T 12, and by the current gain factor of NPN transistor T21 multiplied by the gain factor of the PNP transistor T22.
  • Figure 4 is an alternative high gain embodiment of a current controlled output current source for use in a controllable power OTA according to the invention as shown in Figure 1, in which said first and second current controlled output current sources CCSl and CCS2 are respectively provided with a pair of bipolar NPN transistors Til and Ti2 arranged in Darlington pair configuration. Also here, the gain of said first and second current controlled output current sources CCSl and CCS2 is respectively determined by the current gain factor of Tl 1 multiplied by the gain factor of Til of this Darlington pair.
  • Figure 5 is a MOSFET embodiment of a current controlled output current source which can be applied in each of both first and second current controlled output current sources CCSl and CCS2 in a controllable power OTA according to the invention.
  • the current controlled output current source comprises MOSFET current mirror means with scaled input and output current mirror stages.
  • the input mirror stage of comprises an input N-gate MOSFET FETi receiving a low power input current i being one of said first and second low power current signals il and i2, at its drain electrode.
  • the gate-source voltage of the input N-gate MOSFET FETi is applied across the gate and source electrodes of each of the parallel arrangement of N-gate MOSFETs FEToI to FEToj constituting said output current mirror stage.
  • Figure 6 shows an alternative embodiment of the controllable OTA input stage CIS for use in said second embodiment of the power OTA according to the invention including a differential pair of transistors 1, 2, the base electrodes thereof constituting the differential input of the controllable OTA input stage CIS, the emitters being coupled in common to controllable current source 14 supplying the controllable gain setting current ig setting the controllable OTA input stage CIS at a wanted transconductance g m or gain factor.
  • a differential input voltage signal ⁇ Vin is coupled between the base electrodes of the differential pair of transistors 1, 2 causing collector output currents icl and ic2 to occur at the collectors of said differential pair of transistors 1, 2 in mutually opposite directions.
  • the collector output current icl is mirrored in current mirror 3-5 into a pair of mutually identical currents icl which are supplied to first and second summers Sl and S2, respectively.
  • the collector output current ic2 is mirrored in current mirror 6-8 into a pair of mutually identical currents ic2 which are mirrored again in current mirrors 9,10 and 11,12.
  • the output currents ic2 of said current mirrors 9,10 and 11,12 are supplied to said first and second summers Sl and S2, respectively.
  • currents icl and ic2 are added to form mutually identical low power output currents il and i2, respectively of the controllable inout stage CIS.
  • FIG. 7 shows a radio receiver REC using a controllable power OTA according to the invention 15 for supplying an audio signal through two wire line 17 to a sound reproduction device SRD.
  • the sound reproduction device SRD is mass connected through an OTA 16.
  • the line 17 is used to receive RF broadcast signals, which are supplied to an antenna input AI of the radio receiver REC. Due to the low output impedance of the controllable power OTA 15 and OTA 16 noise interferences, such as click noise, which are present or induced in said line 17, are effectively shortcircuited to mass and are therewith prevented from disturbing said RF broadcast signals without the use of expensive additional selective elements such as capacitors and/or coils.
  • the present invention has hereabove been disclosed with reference to preferred embodiments thereof.

Abstract

Controllable operational transconductance power amplifier (controllable power OTA) including an input stage receiving a differential input signal (OVin) and deriving therefrom first (i1) and second (i2) low power current signals being coupled to first (ccs1) and second (ccs2) current controlled output current sources being arranged in class B push pull configuration. To obtain an effective gain control while securing power efficiency and linearity, the overall gain of the power OTA is controlled by varying the gain or transconductance of the input stage (c15) and by the use of means for bi-directionally rectifying said first (i1) and second (io) low power current signals and providing in mutual alternation power amplification of said first (i1) and second (i2) low power current signals into first (I01) and second (Io2) mutually exclusive high power current output signals, which are supplied through a current summer to a current output (I0) of said linear power amplifier.

Description

Controllable power operational transconductance amplifier
The invention relates to a controllable power operational transconductance amplifier (OTA) suitable for use in a wide field of applications, including portable radio and audio sets, mobile telephone handsets, etcetera. Such controllable power OTA is on itself known e.g. from US Patent 5,598,129.
In principle, an OTA derives an output current from a differential input voltage, the ratio of the output current to the differential input voltage being the transconductance gm, of the amplifier. In linear OTAs the output current varies proportional to said differential input voltage. OTAs have many applications in particular in the field of radio, television and telecommunication, and are configured to provide a variety of functions such as slew rate limiting, filtering or signal level regulation.
A specific area of application for OTAs includes portable devices such as PDAs, portable MP3 players, portable radio and television receivers and mobile telephone handsets. In portable devices electrical power is provided by a battery, making power efficiency a primary design target in this specific area of application. Other design targets, which in particular hold for mobile telephone handsets, are robustness, weight and size reduction and low cost implementation, requiring to maximize circuit integration and to reduce the number of IC external components.
The prior art controllable power OTA as disclosed in the above mentioned US Patent 5,598,129 comprises a class A input stage effectuating fixed maximum gain amplification followed by a class-AB amplifier stage. To reduce power dissipation the static or quiescent currents which are needed in said class-AB amplifier stage to establish voltage and other set levels, are being reduced in a trade off with cross-over distortion. This trade off limits power saving to the minimum quiescent current level below which said distortion exceeds an unacceptable level.
Furthermore, the overall gain of said prior art controllable power OTA is controlled by a variable attenuation of the fixed maximum power output signal of the class-AB amplifier stage. This is obtained with a controllable class A attenuator following said class-AB amplifier stage by effecting a variable power loss. This power loss is essential to the control of the overall gain of the prior art power OTA and is always there, even when there is no input signal. In practice the gain needed for a comfortable sound volume level within a normal volume control range amounts to an average of not more than 20% of the gain at maximum volume setting. This means that averagely about 80% of the power output of the class- AB amplification stage is wasted, exceeding by far the limited power saving obtained by the above trade off within said class-AB amplifier stage.
It is an object of the present invention to substantially improve the performance of controllable power OTAs, in particular on power saving at any volume control setting, physical size and cost of manufacturing while without affecting linearity of operation.
It is another object of the invention to substantially improve the separation of RF and baseband signals occurring in e.g. headphone wirings of portable radio receivers.
Now, therefore, a controllable power OTA according to the invention is characterized by a symmetrically structured, controllable input stage for controlling the overall power gain of the power OTA, receiving a differential input signal and deriving therefrom first and second, mutually matched low power current signals being coupled to first and second current controlled output current sources being arranged in class B push pull configuration, including means for bi-directionally rectifying said first and second low power current signals and providing in mutual alternation power amplification of said first and second low power current signals into first and second mutually exclusive high power current output signals being supplied through a current summer to a current output of said controllable power amplifier..
The invention is based on the insight that unlike voltage signals, current signals can be rectified accurately with respect to zero value by the simple use of diodes, bipolar or MOSFET transistors. Processing current signals instead of voltage signals allows for a proper class B push pull amplification, which does not need any quiescent current to avoid cross-over distortion. By applying the measures according to the invention the overall power gain control of the OTA is provided by the controllable input stage, i.e. in the low power signal part of the controllable power OTA where at any setting within the gain control range, linearity and power efficiency within this input stage can easily be obtained. Power gain is being provided with the push pull configured pair of first and second output current sources of the class B output stage. To secure proper class B power amplification without the need for a quiescent current, the first and second low power current signals provided by the controllable input stage are alternately amplified within the respective first and second output current sources during mutually exclusive signal periods into alternately occurring, mutually exclusive high power first and second output currents. These mutually exclusive high power first and second output currents are combined into said summer into a continuous high power output current. When there is no input signal, both first and second current controlled current sources are fully blocked and no power is consumed in said class B output stage. Furthermore, the power gain in said push pull stage is obtained by current amplification therewith avoiding the occurrence of non-linearities. The push pull configured pair of first and second output current sources can be alternately activated by said first and second, mutually matched low power current signals during mutually exclusive signal periods in various alternative ways.
In a preferred embodiment said first and second low power current signals are mutually matched in that they are identical in amplitude and signal waveform, hereinafter also being shortly referred to as identical, and supplied in mutually opposite directions to a pair of unidirectional current rectifiers being coupled in mutually same direction of conductivity and included in said means for bi- directionally rectifying said first and second low power current signals.
In an alternative preferred embodiment said first and second low power current signals are mutually matched in that they are identical and supplied in mutually same direction to a pair of unidirectional current rectifiers being coupled in mutually opposite direction of conductivity and included in said means for bi- directionally rectifying said first and second low power current signals.
In a cost effective and robust embodiment of the controllable power OTA according to the invention said first and second current controlled output current sources comprise respectively first and second transistors having their collector- emitter paths serially connected between a bias voltage and mass, the first and second low power current signals being supplied to the base electrodes of said first and second transistors, respectively, the base-emitter p-n junctions of said first and second transistors constituting said means for bi-directionally rectifying said first and second low power current signals.
In an embodiment of the controllable power OTA according to the invention, the controllable input stage being symmetrical in structure and including first and second mutually matched input OTAs each comprising a differential pair of transistors masscoupled through a common controllable current source, said differential pairs of transistors respectively receiving said differential input signal in mutual phase opposition and providing said first and second low power current signals with zero DC level to said means for bi-directionally rectifying said first and second low power current signals.
In another embodiment of the controllable power OTA according to the invention the controllable input stage includes an input OTA comprising a differential pair of transistors masscoupled through a common controllable current source and receiving said differential input signal, said differential pair of transistors providing through common current mirror means said first and second low power current signals in mutually opposite polarities with zero DC level to means for bi-directionally rectifying said first and second low power current signals.
To obtain simultaneously effective rectification and efficient power amplification, an embodiment of the controllable power OTA according to the invention is characterized by said first and second current controlled output current sources being mutually identical and each comprising a bipolar PNP transistor having its base electrode coupled to the controllable input stage to receive said first and second low power current signals, respectively, its emitter to a bias voltage and its collector to the base electrode of a bipolar NPN transistor, the base-emitter p-n junction of the bipolar PNP transistors of said first and second current controlled output current sources constituting said pair of unidirectional rectifiers, the bipolar NPN transistors of said first and second current controlled output current sources being cascode coupled between said bias voltage and mass and providing said first and second mutually exclusive high power current output signals. An alternative embodiment said first and second current controlled output current sources being provided with respectively a pair of bipolar NPN transistors arranged in Darlington pair configuration.
In a MOSFET implementation, the controllable power OTA according to the invention is characterized by said first and second current controlled output current sources being provided with respectively MOSFET current mirror means with scaled input and output current mirror stages.
The invention also relates to a receiver using a controllable power OTA.
To reduce the costs of implementation without reducing performance the receiver according to the invention is characterized by said controllable power OTA being coupled in common to a sound reproduction device and an antenna input of said receiver. This measure allows to use a single wire for conveying audio signals from said controllable power OTA to said sound reproduction device on the one hand and for receiving RF broadcast signals and supplying the same to the receiver antenna input on the other hand, while securing effective separation between these signals without the use of capacitors and/or coils.
These and further aspects and advantages of the invention will be discussed more in detail hereinafter with reference to the disclosure of preferred embodiments, and in particular with reference to the appended Figures in which like reference numerals refer to like elements wherein:
Figure 1 is a first embodiment of a controllable power OTA according to the invention;
Figure 2 is a second embodiment of a controllable power OTA according to the invention;
Figure 3 is a push pull configuration of high gain first and second current controlled output current sources for use in a controllable power OTA according to the invention;
Figure 4 is an alternative high gain embodiment of a current controlled output current source for use in a controllable power OTA according to the invention;
Figure 5 is a MOSFET embodiment of a current controlled output current source for use in a controllable power OTA according to the invention; Figure 6 is an embodiment of a controllable input stage for use in said second embodiment of the controllable power OTA according to the invention;
Figure 7 is a radio receiver using a controllable power OTA according to the invention.
Figure 1 shows a controllable power OTA according to the invention comprising a controllable input stage CIS receiving a differential input signal ΔVin and deriving therefrom first and second low power current signals il and i2 respectively, which are coupled to first and second current controlled output current sources CCSl and CCS2 respectively, being arranged in class B push pull configuration. The controllable input stage CIS comprises first and second mutually identical, also referred to as first and second mutually matched, auxiliary operational transconductance amplifiers OTAl and OT A2 each having a differential voltage input and a single current output. The controllable input stage CIS is therewith symmetrical in structure. For OTAl and OT A2 conventional OTAs may be used such as e.g. known from National Semiconductor Datasheet on IC type LM13700 Dual Operational Transconductance. The transconductance gm, of this known OTA is variable by varying a bias current thereof. For further details of this known controllable OTA, reference is made to the abovementioned Datasheet publication. These details have been omitted inasmuch as such details are not necessary to obtain a complete understanding of the present invention and are within the skill of persons of ordinary skill in the relevant art.
In the embodiment shown the differential input signal ΔVin is supplied with mutual opposite polarities to the differential inputs of OTAl and OT A2. As a result thereof the output current signals il and i2 of OTAl and 0TA2, hereinafter also being referred to as first and second low power current signals, vary proportionally with the differential input signal ΔVin, and are mutually identical in amplitude and signal wave form, hereinafter being shortly referred to as identical, with mutually opposite polarities or directions. These first and second low power current signals il and i2 of OTAl and
OTA2, are respectively supplied to base electrodes of first and second mutually identical NPN transistors Tl and T2, which transistors constitute said first and second current controlled output current sources CCS 1 and CCS2, respectively. The collector emitter paths of said first and second NPN transistors Tl and T2 are serially connected between bias voltage Vcc and mass, whereas the common connection between the emitter of Tl and the collector of T2 is coupled to a single current output of the controllable power OTA according to the invention.
The first and second low power current signals il and i2 of OTAl and OT A2 are being amplified in said first and second NPN transistors Tl and T2 during those half cycle periods, in which the direction of these first and second low power current signals il and i2 corresponds to the direction of conductivity of the base-emitter p-n diode junction of Tl and T2. As these first and second low power current signals il and i2 are mutually identical and have mutually opposite directions, either Tl is blocking and T2 is conducting, or vice versa. Suppose, by way of example, that during the even periods ΔtO, Δt2, Δt4, of a consecutive sequence of half cycle periods ΔtO, Δtl, Δt2, Δt3, Δt4, etcetera, the direction of il corresponds to the direction of conductivity of the base-emitter p-n diode j unction of T 1 as illustrated in Figure 1. Then during these even periods ΔtO, Δt2, Δt4 the second low power current i2 is absent (indicated with a dotted arrow), as T2 is blocking. However, during the odd periods Δtl, Δt3, .... of said consecutive sequence of half cycle periods ΔtO, Δtl, Δt2, Δt3, Δt4, .... the direction of i2 corresponds to the direction of conductivity of the base-emitter p-n diode junction of T2, whereas in these odd periods il is absent as then Tl is blocking (not shown). Consequently, current amplification of said first and second low power current signals il and i2 in said first and second NPN transistors Tl and T2 occur accurately in mutually exclusive half cycle signal periods. As a result thereof, first and second mutually exclusive high power current output signals are obtained at the emitter of Tl and the collector of T2, which add up into a single periodic high power current output signal Io . The common connection of the emitter of Tl and the collector of T2 therewith functions as a current summer.
The base-emitter diodes of Tl and T2 therewith function as a pair of unidirectional rectifiers being coupled in mutually same direction of conductivity as seen from the output of the controllable input stage CIS. With the supply of first and second low power current signals il and i2 in mutually opposite directions to the base electrodes of Tl and T2, respectively, Tl and T2 operate as bi-directional rectifier means, providing accurate rectification of the first and second low power current signals il and i2 at zero current value. Precisely at each zero crossing, Tl changes from blocking or passive state into conducting or active state and T2 from conducting or active state blocking into passive state, or vice versa. Tl and T2 therewith operate in class B push pull configuration, i.e. without the need for a quiescent current. At zero value current input signal both transistors Tl and T2 are blocked and no power is used. As a result thereof said class B push pull arrangement of Tl and T2 operates at maximum current gain without power loss, i.e. at maximum power efficiency.
With the overall power gain of the power OTA according to the invention being controlled in the low power stage and current power amplification in the class B push pull arrangement of Tl and T2, maximum power efficiency is secured at any gain or volume setting.
Furthermore first and second low power current signals il and i2 vary proportionally with the differential input signal ΔVin at any value of the transconductance gm, whereas both transistors Tl and T2 provide constant current amplification. This secures linear operation throughout the controllable power OTA as a whole at any setting within the gain control range.
Figure 2 shows a second embodiment of a controllable power OTA according to the invention in which the differential input signal ΔVin is supplied with mutual same polarity to the differential inputs of said first and second mutually identical auxiliary operational transconductance amplifiers OTAl and OT A2 of the controllable input stage CIS. The first and second low power current signals il and i2 of OTAl and OT A2, which vary proportionally with the differential input signal ΔVin, are mutually identical and are supplied in mutually same polarity or direction to base electrodes of NPN transistor Tl and PNP transistor T2, respectively. The base-emitter p-n junctions of Tl and Tl function as a pair of unidirectional rectifiers being coupled in mutually opposite direction of conductivity as seen from the output of the controllable input stage CIS. With the supply of first and second low power current signals il and i2 in mutually same direction to the base electrodes of Tl and T2, respectively, Tl and T2 operate as bi-directional rectifier means, providing accurate rectification of the first and second low power current signals il and i2 at zero current value. The collector-emitter path of Tl is serially connected to the emitter-collector path of T2 between said bias voltage and mass. Tl and T2 therewith obtaining class B push pull current amplification of said first and second low power current signals il and i2 in said first and second NPN transistors Tl and T2, accurately occurring in mutually exclusive half cycle signal periods. As a result thereof, first and second mutually exclusive high power current output signals Io 1 and Io2 are obtained at the emitters of Tl and T2, respectively, which add up into a single periodic high power current output signal Io at the current output of the controllable power OTA. The common connection of the emitter of Tl and the collector of T2 therewith functions as a current summer. Figure 3 is a push pull configuration of high gain two stage first and second current controlled output current sources CCSl and CCS for use in a controllable power OTA according to the invention as shown in Figure 1. In this embodiment said first and second current controlled output current sources CCSl and CCS2 are mutually identical and respectively comprise first stage bipolar PNP transistors TI l and T21 , respectively, having base electrodes coupled to the controllable input stage CIS to receive said first and second low power current signals il and i2, respectively. The emitters of Tl 1 and T21 are coupled to the bias voltage Vcc and the collectors to base electrodes of second stage bipolar NPN transistors Tl 2 and T22, respectively. The base-emitter p-n junction of the bipolar PNP transistors Tl 1 and T21 of said first and second current controlled output current sources constitute said pair of unidirectional rectifiers, the bipolar NPN transistors Tl 2 and T22 of said first and second current controlled output current sources CCSl and CCS2 are cascode coupled between said bias voltage Vcc and mass and provide first and second mutually exclusive high power current output signals Io 1 and Io2, respectively. The gain of said first and second current controlled output current sources CCSl and CCS2 is respectively determined by the current gain factor of NPN transistor TI l multiplied by the gain factor of the PNP transistor T 12, and by the current gain factor of NPN transistor T21 multiplied by the gain factor of the PNP transistor T22.
Figure 4 is an alternative high gain embodiment of a current controlled output current source for use in a controllable power OTA according to the invention as shown in Figure 1, in which said first and second current controlled output current sources CCSl and CCS2 are respectively provided with a pair of bipolar NPN transistors Til and Ti2 arranged in Darlington pair configuration. Also here, the gain of said first and second current controlled output current sources CCSl and CCS2 is respectively determined by the current gain factor of Tl 1 multiplied by the gain factor of Til of this Darlington pair. Figure 5 is a MOSFET embodiment of a current controlled output current source which can be applied in each of both first and second current controlled output current sources CCSl and CCS2 in a controllable power OTA according to the invention. In the embodiment shown, the current controlled output current source comprises MOSFET current mirror means with scaled input and output current mirror stages. The input mirror stage of comprises an input N-gate MOSFET FETi receiving a low power input current i being one of said first and second low power current signals il and i2, at its drain electrode. The gate-source voltage of the input N-gate MOSFET FETi is applied across the gate and source electrodes of each of the parallel arrangement of N-gate MOSFETs FEToI to FEToj constituting said output current mirror stage. With identical MOSFETs in both input and output current mirror stages a scaling factor j is being obtained, meaning that the high power output current signal Io provided by the output current mirror stage amounts to j times the low power input current I, i.e. Io=j*i.
Figure 6 shows an alternative embodiment of the controllable OTA input stage CIS for use in said second embodiment of the power OTA according to the invention including a differential pair of transistors 1, 2, the base electrodes thereof constituting the differential input of the controllable OTA input stage CIS, the emitters being coupled in common to controllable current source 14 supplying the controllable gain setting current ig setting the controllable OTA input stage CIS at a wanted transconductance gm or gain factor. A differential input voltage signal ΔVin is coupled between the base electrodes of the differential pair of transistors 1, 2 causing collector output currents icl and ic2 to occur at the collectors of said differential pair of transistors 1, 2 in mutually opposite directions. The collector output current icl is mirrored in current mirror 3-5 into a pair of mutually identical currents icl which are supplied to first and second summers Sl and S2, respectively. The collector output current ic2 is mirrored in current mirror 6-8 into a pair of mutually identical currents ic2 which are mirrored again in current mirrors 9,10 and 11,12. The output currents ic2 of said current mirrors 9,10 and 11,12 are supplied to said first and second summers Sl and S2, respectively. In each of said first and second summers Sl and S2 currents icl and ic2 are added to form mutually identical low power output currents il and i2, respectively of the controllable inout stage CIS. Figure 7 shows a radio receiver REC using a controllable power OTA according to the invention 15 for supplying an audio signal through two wire line 17 to a sound reproduction device SRD. The sound reproduction device SRD is mass connected through an OTA 16. The line 17 is used to receive RF broadcast signals, which are supplied to an antenna input AI of the radio receiver REC. Due to the low output impedance of the controllable power OTA 15 and OTA 16 noise interferences, such as click noise, which are present or induced in said line 17, are effectively shortcircuited to mass and are therewith prevented from disturbing said RF broadcast signals without the use of expensive additional selective elements such as capacitors and/or coils. Now, the present invention has hereabove been disclosed with reference to preferred embodiments thereof. Persons skilled in the art will recognize that numerous modifications and changes may be made thereto without exceeding the scope of the appended Claims. For instance, in the embodiments of the controllable power OTA according to the invention as shown in Figure 2 measures could be taken within the normal ability of persons skilled in the art to secure Tl and T2 to provide equal gain factors, or to use low power current signals il and i2 which are not mutually identical compensating gain differences in Tl and T2.
In consequence, the embodiments should be considered as being illustrative, and no restriction should be construed from those embodiments, other than as have been recited in the Claims.

Claims

Claims:
1. Controllable operational transconductance power amplifier (power OTA) characterized by a controllable input stage for controlling the overall power gain of the power OTA, receiving a differential input signal and deriving therefrom first and second, mutually matched low power current signals being coupled to first and second current controlled output current sources being arranged in class B push pull configuration, including means for bi-directionally rectifying said first and second low power current signals and providing in mutual alternation power amplification of said first and second low power current signals into first and second mutually exclusive high power current output signals being supplied through a current summer to a current output of said controllable power amplifier.
2. Controllable power OTA according to claim 1 , characterized by said first and second low power current signals being mutually identical and supplied in mutually opposite directions to a pair of unidirectional current rectifiers being coupled in mutually same direction of conductivity and included in said means for bi-directionally rectifying said first and second low power current signals.
3. Controllable power OTA according to claim 1 , characterized by said first and second low power current signals being mutually identical and supplied in mutually same direction to a pair of unidirectional current rectifiers being coupled in mutually opposite direction of conductivity and included in said means for bi-directionally rectifying said first and second low power current signals.
4. Controllable power OTA according to one of claims 1 to 3, characterized by said first and second current controlled output current sources comprising first and second transistors having their collector-emitter paths serially connected between a bias voltage and mass, the first and second low power current signals being supplied to the base electrodes of said first and second transistors, respectively, the base-emitter p-n junctions of said first and second transistors constituting said means for bi-directionally rectifying said first and second low power current signals.
5. Controllable power OTA according to one of claims 1 to 4, characterized by said controllable input a common controllable current source, said differential pairs of transistors respectively receiving said differential input signal in mutual phase opposition and providing said first and second low power current signals with zero DC level to said means for bi-directionally rectifying said first and second low power current signals.
6. Controllable power OTA according to claim 1 or 2, characterized by said controllable input stage including an input OTA comprising a differential pair of transistors masscoupled through a common controllable current source and receiving said differential input signal, said differential pair of transistors providing through common current mirror means said first and second low power current signals in mutually opposite polarities with zero DC level to means for bi-directionally rectifying said first and second low power current signals.
7. Controllable power OTA according to claim 2, characterized by said first and second current controlled output current sources being mutually identical and each comprising a bipolar PNP transistor having its base electrode coupled to the controllable input stage to receive said first and second low power current signals, respectively, its emitter to a bias voltage and its collector to the base electrode of a bipolar NPN transistor, the base- emitter p-n junction of the bipolar PNP transistors of said first and second current controlled output current sources constituting said pair of unidirectional rectifiers, the collector-emitter paths of said bipolar NPN transistors of said first and second current controlled output current sources being serially connected between said bias voltage and mass and providing said first and second mutually exclusive high power current output signals at the current output of said controllable power amplifier.
8. Controllable power OTA according to one of claims 1 to 6, characterized by said first and second current controlled output current sources being provided with respectively a pair of bipolar NPN transistors arranged in Darlington pair configuration.
9. Controllable power OTA according to one of claims 1 to 6, characterized by said first and second current controlled output current sources being provided with respectively MOSFET current mirror means with scaled input and output current mirror stages.
10. Receiver comprising a controllable power OTA according to one of claims 1 to 8, characterized by said controllable power OTA being coupled in common to a sound reproduction device and an antenna input of said receiver.
EP05769963A 2004-08-02 2005-07-19 Controllable power operational transconductance amplifier Withdrawn EP1820267A1 (en)

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EP04077209A EP1624564A1 (en) 2004-08-02 2004-08-02 Controllable power operational transconductance amplifier
PCT/EP2005/007981 WO2006013019A1 (en) 2004-08-02 2005-07-19 Controllable power operational transconductance amplifier
EP05769963A EP1820267A1 (en) 2004-08-02 2005-07-19 Controllable power operational transconductance amplifier

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