EP1564835B1 - Inline-Mikrowellenfiler mit bis zu zwei Übertragungsnullstellen ausserhalb des Bandes. - Google Patents

Inline-Mikrowellenfiler mit bis zu zwei Übertragungsnullstellen ausserhalb des Bandes. Download PDF

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Publication number
EP1564835B1
EP1564835B1 EP04425096A EP04425096A EP1564835B1 EP 1564835 B1 EP1564835 B1 EP 1564835B1 EP 04425096 A EP04425096 A EP 04425096A EP 04425096 A EP04425096 A EP 04425096A EP 1564835 B1 EP1564835 B1 EP 1564835B1
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EP
European Patent Office
Prior art keywords
filter
coupled
ris
waveguide
resonant cavities
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EP04425096A
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English (en)
French (fr)
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EP1564835A1 (de
Inventor
Danilo Attilio Gaiani
Pietro Marchisio
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Nokia Solutions and Networks SpA
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Nokia Solutions and Networks SpA
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Priority to EP04425096A priority Critical patent/EP1564835B1/de
Priority to AT04425096T priority patent/ATE464670T1/de
Priority to DE602004026535T priority patent/DE602004026535D1/de
Publication of EP1564835A1 publication Critical patent/EP1564835A1/de
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/207—Hollow waveguide filters
    • H01P1/208—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure

Definitions

  • the present invention refers to the field of the microwave filters and more precisely to an inline waveguide filter with up to two out-of-band transmission zeros.
  • the continuous requests for frequency spectrum occupancy is the main cause of more and more stringent requirements on the design of radio links and specifically for microwave filters, in particular as the shape of the out-of-band frequency response is concerned.
  • adjacent channels are very close to each other and very low interference level can be tolerated, so that high out-of-band rejection is needed especially in correspondence of some intolerable disturbs, such as the local oscillator and its harmonics.
  • filters with sharp attenuations might be excessively expensive and ineffective in case the disturbs are close to one or more out-of-band spectral lines (nearly monochromatic interference). In this case the desired sharp attenuations are better obtained by transmission zeros exactly tuned to the interfering frequencies.
  • the values of the coupling elements can be made frequency selective, so as to match in the passband the wanted poles, whereas, at certain frequencies away from the passband the inverter values vanish, thus creating transmission zeros.
  • a multitude of transmission zeros can be generated with this technique but their locations are difficult to control.
  • the Reference [4] discloses a systematic procedure to obtain folded waveguide filters with cross couplings specifically designed to introduce extra transmission zeros.
  • the procedure of the previous paper is a combination of traditional circuit model analysis and full-wave method, where the circuit model acts as a reference.
  • the whole procedure is divided into a number of steps, each involving the tuning of one dimension (coupling size or cavity length) until the simulated S 11 and S 21 parameters fit the corresponding target value of the circuit model.
  • the defect of this approach is the need of a mechanically complicated folded structure with the input and the output ports on the same side of the filter.
  • the paper of reference [5] deals with inline waveguide bandpass filters with arbitrarily located transmission zeros.
  • the design is based on iris-coupled TM 110 -mode cavities utilizing propagating but non-resonating TE 10 or TE 01 modes to create cross coupling between cavities, input, and/or output waveguides.
  • This type of filters allows simpler mechanical structures than the folded ones, with cross-couplings by resonating mode, besides the maximum number of attenuation poles can be equal that of electrical resonances.
  • the defect of this approach arises from the difficulty of simultaneously and independently controlling the different electromagnetic modes, either resonating or propagating, inside the whole structure including the input and output waveguides.
  • the geometry of the iris/port centre offsets shall be accurately designed otherwise the TM 110 mode is not excited.
  • a drawback of this filter is that two different structures are needed at the input and the output ports of the filter.
  • An input structure including the input port provides for the first zero in the lower out-of-band range.
  • a second structure including the output port provides for the second zero in the higher out-of-band range. While the first and the second openings are at the same distance from the input port, the third and the fourth openings are spaced to each other one-half the wavelength the resonators are operated.
  • the input structure is obtained arranging the first and second openings so that they are coupled to the cross-sectional end of a first rectangular waveguide connected to the input port of the filter.
  • the output structure is obtained arranging the third and fourth openings so that they are adjacent to two corresponding windows opened across a side wall of a second rectangular waveguide coupled to the output port of the filter.
  • the goal of the present invention is to overcome the defects of the prior art and indicate a simpler mechanical structure of a direct coupled waveguide filter able to introduce a transmission zero in the lower and/or in the higher out-of-band regions of the frequency response, so as to prevent the use of propagating but non-resonating modes inside the cavities of the filter, and the use of pronounced different structures for coupling an external waveguide at the input and the output ports of the filter.
  • a resonant-cavity waveguide filter also called waveguide filter
  • a metallic hollow body including a given number N of resonant cavities with rectangular cross section separated to each other by coupling structures, such as capacitive (or inductive) irises and/or inductive posts, arranged to obtain a given N th order frequency response, with N attenuation poles, as disclosed in the claims.
  • the coupled-cavity waveguide filter includes:
  • the inline structure of a waveguide filter of the known type is depicted in fig.1 as a basis for the explanation of the successive filtering structure according to the invention.
  • the filter of fig.1 is given as an example, with only three resonant cavities; the reduced number of cavities with respect to the actual number typically used in this type of filters is held ongoing also for the description of the filter embodied by the invention.
  • the three resonant cavities are indicated by RIS-1, RIS-2, and RIS-3.
  • Two capacitive irises IR1-2, IR2-3 delimit adjacent resonant cavities (RIS-1, RIS-2 and RIS-2, RIS-3), respectively.
  • Two input/output waveguide ports are electrically coupled and mechanically connected to the two ends of the filter in correspondence of the resonant cavities RIS-1 and RIS-3, respectively.
  • the two input/output waveguide might have reduced cross section in correspondence of their connection to the remaining part of the filter.
  • the mechanical body of the filter includes two superimposed halves joined together by screws (not visible); the lower of these two halves is visible in the figure.
  • Fig.1a shows an equivalent electrical model of the filter of fig.1 .
  • all the ideal transmission lines, TL1 to TL4 have 90° electrical length and well defined characteristic impedance, so they can act as impedance inverters at the centre frequency of the filter.
  • the physical sizes of the resonant cavities, the capacitive irises, and the two waveguides couplings, are designed to synthesize a 3 rd order Chebyshev response in accordance with the known methods based on an electrical model of the filter, as described in the References [1], [2], and [3] .
  • the fine tuning of the central frequency with respect of the assigned mask is performed by means of tuning screws, not visible in fig.1 .
  • the longitudinal section of the complete filter along the symmetry axis A-A ( fig.1 ) is visible in fig.2 .
  • Fig.4 shows an arrangement of the filter of fig.1 to introduce an extra-transmission zero in the lower out-of-band frequency range of the 3 rd order Chebyshev response.
  • Fig.4a shows the main mechanical dimensions of the filter of fig.4
  • fig.4b shows its equivalent electrical model.
  • the only difference from the filter of fig.1 concerns the position of the input/output waveguide WTA, which now is directly coupled to both the resonant cavities RIS-1 and RIS-2.
  • the two waveguides WTA and WTB are a standard WR42 rectangular waveguide, which dimensions are: 10.7 mm width ("a") and 4.32 mm high ("b").
  • the three resonant cavities (RIS-1, RIS-2, and RIS-3) and the two waveguide (WTA and WTB) have nearly the same rectangular cross-section area.
  • the lengths of the three resonant cavities are obtained at first by the application of well known analytical design criteria about direct coupled waveguide filters described at Ref.[1], [2] and [3]; they're further optimised by numerical analysis and simulation carried out by specific software tools mentioned at Ref.[6].
  • the distance "x”, or "a - x", of an internal lateral wall of the waveguide WTA from the midline between the two resonant cavities RIS-1 and RIS-2, multiplied by "b”, indicates the area of the coupling window with the resonant cavity RIS-1 or RIS-2, respectively. As the area of a coupling windows increases, the area of the other coupling windows decreases of the same amount.
  • the mechanical part of the filter is shown in fig.5 , where the waveguide WTA carries an input signal; the response of the filter wouldn't change with reference to an outgoing signal.
  • the plot of the insertion loss S 21 and return loss S 11 of the filter are shown in fig.6 . From the comparison between the traces of fig.6 and the corresponding of fig.3 , it can be easily appreciated that the slope of the transition zone at the left of the passband is greater for the filter of fig.4 than the filter of fig.1 , thanks to the extra transmission zero inserted just in this frequency range. Notice that:
  • Fig.7 shows an arrangement of the filter of fig. 1 to introduce an extra-transmission zero in the higher out-of-band frequency range.
  • Fig.7a shows the main dimensions of the filter of fig.7
  • fig.7b shows its equivalent electrical model.
  • the only difference from the filter of fig.4 is replacing the capacitive iris IR1-2 with an inductive one, better visible in the perspective representation of figures 7a and 8 .
  • the area of the coupling windows of the input/output waveguide WTA to the resonant cavities RIS-1 and RIS-2 still depends by the distances "x" and "a-x"; therefore, the distance of the extra out-of-band transmission zero from the upper edge of the passband depends by the difference between the areas of the two coupling windows, as previously said for the filter of fig.4 .
  • the plots of the insertion loss S 21 and return loss S 11 of the filter of fig.7 are shown in fig.9 .
  • Fig.10 shows an embodiment of the invention.
  • the filter of fig.10 includes the two arrangements of figures 4 and 7 ;
  • fig.10a shows its equivalent electrical model.
  • the plots of the insertion loss S 21 and return loss S 11 of the filter of fig.10 are shown in fig.11 .
  • the first case is obtained by a filter which differs from that of fig.4 for the replication to the waveguide WTB of the offset coupling made at the waveguide WTA.
  • the second case is obtained by a filter which differs from that of fig.7 for the replication to the waveguide WTB of the offset coupling made at the waveguide WTA; in this case a second inductive iris replaces the capacitive iris IR3-2.
  • Different values of the coupling offsets between the two waveguide WTA and WTB allow a separation of the additional transmission zeros.

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  • Control Of Motors That Do Not Use Commutators (AREA)
  • Control And Other Processes For Unpacking Of Materials (AREA)
  • Electrostatic Charge, Transfer And Separation In Electrography (AREA)
  • Feeding And Guiding Record Carriers (AREA)

Claims (5)

  1. Wellenleiterfilter mit gekoppelten Hohlräumen, umfassend:
    - einen ersten Port zur Kopplung mit einem Ende eines ersten rechteckigen Wellenleiters (WTA, WTB);
    - einen ersten Resonanzhohlraum (RIS-1, RIS-3) mit einer ersten Öffnung, die direkt mit dem ersten Port gekoppelt ist;
    - einen zweiten Resonanzhohlraum (RIS-2), der an den ersten Resonanzhohlraum angrenzt, wobei der zweite Resonanzhohlraum eine zweite Öffnung aufweist, die direkt mit dem ersten Port gekoppelt ist;
    - einen zweiten Port, der dafür ausgelegt ist, mit einem Ende eines zweiten rechteckigen Wellenleiters (WTB, WTA) gekoppelt zu werden;
    - einen dritten Resonanzhohlraum (RIS-3, RIS-1), der an den zweiten Resonanzhohlraum (RIS-2) angrenzt, wobei der dritte Resonanzhohlraum eine dritte Öffnung aufweist, die direkt mit dem zweiten Port gekoppelt ist;
    dadurch gekennzeichnet, dass
    - die gekoppelten Hohlräume des Wellenleiterfilters einen rechteckigen Querschnitt aufweisen;
    - der zweite Resonanzhohlraum (RIS-2) eine vierte Öffnung aufweist, die direkt mit dem zweiten Port gekoppelt ist;
    - der erste (RIS-1, RIS-3) und der zweite (RIS-2) Resonanzhohlraum mittels einer dazwischengestellten induktiven Iris (INDUCTIVE IRIS), die eine erste Extra-Übertragungsnullstelle in den höheren Außerband-Frequenzbereich einführt, miteinander gekoppelt werden;
    - der dritte (RIS-3, RIS-1) und der zweite (RIS-2) Resonanzhohlraum mittels einer dazwischengestellten kapazitiven Iris (CAPACITIVE IRIS), die eine zweite Extra-Übertragungsnullstelle in den niedrigeren Außerband-Frequenzbereich einführt, miteinander gekoppelt werden.
  2. Mikrowellenfilter nach Anspruch 1, dadurch gekennzeichnet, dass die erste und die zweite Öffnung gleiche Querschnittsflächen aufweisen.
  3. Mikrowellenfilter nach Anspruch 1, dadurch gekennzeichnet, dass die erste und die zweite Öffnung verschiedene Querschnittsflächen aufweisen.
  4. Mikrowellenfilter nach Anspruch 1, dadurch gekennzeichnet, dass die dritte und die vierte Öffnung gleiche Querschnittsflächen aufweisen.
  5. Mikrowellenfilter mit gekoppelten Hohlräumen nach Anspruch 1, dadurch gekennzeichnet, dass die dritte und die vierte Öffnung verschiedene Querschnittsflächen aufweisen.
EP04425096A 2004-02-16 2004-02-16 Inline-Mikrowellenfiler mit bis zu zwei Übertragungsnullstellen ausserhalb des Bandes. Expired - Lifetime EP1564835B1 (de)

Priority Applications (3)

Application Number Priority Date Filing Date Title
EP04425096A EP1564835B1 (de) 2004-02-16 2004-02-16 Inline-Mikrowellenfiler mit bis zu zwei Übertragungsnullstellen ausserhalb des Bandes.
AT04425096T ATE464670T1 (de) 2004-02-16 2004-02-16 Inline-mikrowellenfiler mit bis zu zwei übertragungsnullstellen ausserhalb des bandes.
DE602004026535T DE602004026535D1 (de) 2004-02-16 2004-02-16 Inline-Mikrowellenfiler mit bis zu zwei Übertragungsnullstellen ausserhalb des Bandes.

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
EP04425096A EP1564835B1 (de) 2004-02-16 2004-02-16 Inline-Mikrowellenfiler mit bis zu zwei Übertragungsnullstellen ausserhalb des Bandes.

Publications (2)

Publication Number Publication Date
EP1564835A1 EP1564835A1 (de) 2005-08-17
EP1564835B1 true EP1564835B1 (de) 2010-04-14

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EP (1) EP1564835B1 (de)
AT (1) ATE464670T1 (de)
DE (1) DE602004026535D1 (de)

Families Citing this family (16)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101621147B (zh) * 2009-08-11 2014-03-19 南京理工大学 低损耗双零点2.4千兆赫微型带通滤波器
CN103000975B (zh) * 2012-11-23 2015-08-05 广东通宇通讯股份有限公司 腔体滤波器
GB2517987A (en) * 2013-09-09 2015-03-11 Isis Innovation Waveguide
CN103490124B (zh) * 2013-09-26 2016-03-30 西安空间无线电技术研究所 一种波导双工器
WO2015058809A1 (en) * 2013-10-25 2015-04-30 Esa European Space Agency Hybrid folded rectangular waveguide filter
CN105406159B (zh) * 2015-07-30 2018-01-12 电子科技大学 一种ct结构太赫兹交叉耦合波导滤波器
US10964991B2 (en) 2017-03-06 2021-03-30 Telefonaktiebolaget Lm Ericsson (Publ) Tunable waveguide filter input/output coupling arrangement
CN109149034A (zh) * 2017-06-15 2019-01-04 乐山顺辰科技有限公司 一种微波滤波器
CN107565929B (zh) * 2017-09-04 2020-11-03 电子科技大学 滤波器广义综合方法
CN108847516B (zh) * 2018-08-01 2024-01-19 江苏贝孚德通讯科技股份有限公司 一种消失模波导高通滤波器
US11031664B2 (en) 2019-05-23 2021-06-08 Com Dev Ltd. Waveguide band-pass filter
CN110676542B (zh) * 2019-09-05 2021-06-25 京信通信技术(广州)有限公司 端口耦合结构、滤波器及射频组件
CN113054375A (zh) * 2019-12-27 2021-06-29 深圳市大富科技股份有限公司 通信设备及其滤波器
CN112635940B (zh) * 2020-12-22 2022-06-14 华沣通信科技有限公司 一种腔体滤波器直排腔形式对称电容装置
CN115313003B (zh) * 2022-07-18 2024-03-15 电子科技大学长三角研究院(湖州) 一种具有临近通带的新型易加工太赫兹双频带通滤波器
CN116345096B (zh) * 2023-05-19 2023-08-04 电子科技大学 一种低幅度不平坦度的太赫兹90°波导滤波耦合器

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DE2040495A1 (de) * 1970-08-14 1972-02-17 Licentia Gmbh Filteranordnung bestehend aus einem mehrkreisigen Hohlleiterfilter
US6304160B1 (en) 1999-05-03 2001-10-16 The Boeing Company Coupling mechanism for and filter using TE011 and TE01δ mode resonators

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DE602004026535D1 (de) 2010-05-27
EP1564835A1 (de) 2005-08-17
ATE464670T1 (de) 2010-04-15

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