EP0824784A1 - Temperature compensated automatic gain control - Google Patents

Temperature compensated automatic gain control

Info

Publication number
EP0824784A1
EP0824784A1 EP96913015A EP96913015A EP0824784A1 EP 0824784 A1 EP0824784 A1 EP 0824784A1 EP 96913015 A EP96913015 A EP 96913015A EP 96913015 A EP96913015 A EP 96913015A EP 0824784 A1 EP0824784 A1 EP 0824784A1
Authority
EP
European Patent Office
Prior art keywords
power
amplifier
temperature
coupled
control
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP96913015A
Other languages
German (de)
French (fr)
Inventor
Richard K. Kornfeld
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Qualcomm Inc
Original Assignee
Qualcomm Inc
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Qualcomm Inc filed Critical Qualcomm Inc
Publication of EP0824784A1 publication Critical patent/EP0824784A1/en
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03G—CONTROL OF AMPLIFICATION
    • H03G3/00—Gain control in amplifiers or frequency changers without distortion of the input signal
    • H03G3/20—Automatic control
    • H03G3/30—Automatic control in amplifiers having semiconductor devices
    • H03G3/3036—Automatic control in amplifiers having semiconductor devices in high-frequency amplifiers or in frequency-changers
    • H03G3/3042—Automatic control in amplifiers having semiconductor devices in high-frequency amplifiers or in frequency-changers in modulators, frequency-changers, transmitters or power amplifiers
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/02—Transmitters
    • H04B1/03—Constructional details, e.g. casings, housings
    • H04B1/036—Cooling arrangements
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03G—CONTROL OF AMPLIFICATION
    • H03G2201/00—Indexing scheme relating to subclass H03G
    • H03G2201/70—Gain control characterized by the gain control parameter
    • H03G2201/708—Gain control characterized by the gain control parameter being temperature
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/02—Transmitters
    • H04B1/04—Circuits

Definitions

  • the present invention relates to automatic gain control. More particu ⁇ larly, the present invention relates to adjusting the transmit power in a portable radio in response to temperature.
  • the Federal Communications Commission governs the use of the radio frequency (RF) spectrum.
  • the FCC allocates certain bandwidths within the RF spectrum for specific uses.
  • a user of an allocated bandwidth of the RF spectrum must take measures to ensure that the radiated emissions inside and outside of that bandwidth are maintained within acceptable levels to avoid in ⁇ terfering with other users operating in the same and or other bandwidths. These levels are governed by both the FCC and the particular user groups of said bandwidth.
  • the 800 MHz cellular telephone system operates its forward link, the cell to radiotelephone transmission, in the bandwidth of 869.01 MHz to 893.97 MHz and the reverse link, the radiotelephone to cell transmission, in the bandwidth of 824.01 MHz to 848.97 MHz.
  • the forward and reverse link bandwidths are split up into channels each of which occupies a 30 kHz bandwidth.
  • a particular user of the cellular system may operate on one or several of these channels at a time. All users of the system must ensure that they are compliant with the level of radiated emissions allowable inside and outside of the channel or channels that they have been assigned.
  • FDMA frequency division multiple access
  • CDMA code division multiple access
  • the FDMA modulation technique generates signals that occupy one channel at a time while the CDMA modulation technique generates signals that occupy several channels. Both of these techniques must control their return link radiated emissions to within acceptable limits inside and outside of the assigned channel or channels. For maximum system performance, users of the CDMA technique must carefully control the level of radiated power inside the channels in which they are operating. Two methods of controlling the radiated power are open and closed loop power control. Together, these two methods of power control determine the return link transmit energy, as disclosed in U.S. Patent No. 5,056,109 to Gilhousen et al. and assigned to QUALCOMM, Incorporated.
  • FIG. 1 shows a typical cellular radiotelephone.
  • the power amplifier (101) in the transmitter beyond a point where acceptable out of chan ⁇ nel radiated emissions are maintained. This is primarily due to the increased distortion output levels of the power amplifier (101) at high output powers. Also, driving the power amplifier (101) beyond a certain point can cause inter- ference internal to the radio. For example, PA puncturing in CDMA affects syn ⁇ thesizer phase noise due to large current transitions. Both of these issues cause unacceptable radio performance.
  • the CDMA based radio must implement a power control system that operates over a very wide dynamic range, 80 dB to 90 dB, such that the transmitted out ⁇ put power is linearly related to the received input power.
  • both the receiver (103) and transmitter (102) RF sections can cause unacceptable power control perfor- mance.
  • both the FDMA and CDMA based radios must operate on differ ⁇ ent channels while maintaining acceptable output power levels. Variation in output power level and input power detection versus frequency can cause an unacceptable amount of error in the amount of return link transmitted energy.
  • the temperature compensated automatic gain control of the present in- vention encompasses a temperature compensated power amplifier apparatus.
  • This apparatus is comprised of a variable gain amplifier that has a control input for adjusting the gain of the amplifier.
  • a power detector is coupled to the vari ⁇ able gain amplifier and generates a power value of the transmitted signal.
  • a temperature sensor is used to generate a temperature signal for predetermined heat generating components.
  • a power control circuit has a first input coupled to the power detector, a second input coupled to the temperature sensor, and an output coupled to the control input of the variable gain amplifier. The power control circuitry adjusts the variable gain amplifier in response to the power value and the temperature signals.
  • FIG. 1 shows a block diagram of a typical prior art radiotelephone frequency section for use in a radiotelephone system.
  • FIG. 2 shows a block diagram of the power control correction imple ⁇ mentation of the present invention.
  • FIG. 3 shows a block diagram of the power limiting control section as related to FIG. 2.
  • FIG. 4 shows a block diagram of the closed loop power control section as related to FIG. 2.
  • FIG. 5 shows a block diagram of the PA limit threshold control section as related to FIG. 2.
  • FIG. 6 shows an alternate embodiment of the present invention that employs a power limiting control system based on accumulator feedback con- trol.
  • FIG. 7 shows an alternate embodiment of the present invention that employs a power limiting control system based on the closed loop power con ⁇ trol accumulator.
  • FIG. 8 shows an alternate embodiment of the present invention that employs a power limiting control system based on integral feedback control.
  • FIG. 9 shows an alternate embodiment of the present invention that employs a power limiting control system based on a measure of receive power and the closed loop power control setting to estimate output power.
  • FIG. 10 shows a block diagram of the temperature compensated auto ⁇ matic gain control of the present invention.
  • FIG. 11 shows a graph indicating the benefits of the embodiment of FIG. 10.
  • the process of the present invention provides power control correction for a mobile radio as well as maintaining acceptable in and out of band maxi- mum emission levels. This is accomplished by real-time compensation utilizing a set of correction tables that are generated during the production testing of each radio.
  • FIG. 2 shows a block diagram of a CDMA radio with the power control correction implementation of the present invention.
  • FIGs. 3, 4, and 5 detail specific blocks of FIG. 2.
  • the radio is comprised of a receive linearization sec ⁇ tion, transmit linearization section, power amplifier bias control section, and power limiting control section.
  • the receive linearization section includes an automatic gain control (AGC) section.
  • AGC automatic gain control
  • the signal input to the AGC section is received on the forward link and amplified by a low noise amplifier (LNA) (211).
  • LNA low noise amplifier
  • the output of the LNA (211) is input to a variable gain amplifier (212).
  • the variable gain amplifier (212) produces a signal that is converted to a digital signal using an analog to digital converter (ADC) (213).
  • ADC analog to digital converter
  • the power of the digitized received signal is next computed by a digital power detector (214).
  • the power detector (214) includes an integrator that in ⁇ tegrates the detected power with respect to a reference voltage. In the pre ⁇ ferred embodiment, this reference voltage is provided by the radio's demodu ⁇ lator to indicate the nominal value at which the demodulator requires the loop to lock in order to hold the power level constant. The demodulator requires this value for optimum performance since a power level too far out of the op ⁇ timum range will degrade the performance of the demodulator.
  • the power de ⁇ tector (214) performs the integration, thus generating an AGC setpoint. The setpoint and a receive frequency index are input to a receiver linearizing table (216).
  • the AGC setpoint and the frequency index are used to address the lin- earizer (216), thus accessing the proper calibration value.
  • This calibration value is then output to a digital to analog converter (215) that generates the analog representation of the receive AGC setting.
  • the analog value adjusts the biasing of the variable gain amplifier (212).
  • the control of the variable gain amplifier (212) forces the receive AGC loop to close such that the input to the receiver linearizing table (216) follows a prede ⁇ termined straight line with respect to RF input power.
  • This linearization re- moves the undesired linear and non-linear errors in addition to variations ver ⁇ sus frequency that would otherwise be apparent at the input to the receiver linearizing table (216) in the receiver. These errors and variations would con ⁇ tribute to errors in the transmitter.
  • the receive and transmit linearizers utilize the frequency index that specifies the current center frequency on which the receive and transmit chains are operating.
  • the linearizers are loaded with values, in addition to the previously mentioned calibration values, that are indexed by frequency to correct the errors related to operating center fre- quency.
  • the AGC setpoint is the open loop power control signal for the radio. In the preferred embodiment, this is the power control performed by the radio by itself without control input from the cells. As the power of the signal received from the cell increases, the radio decreases its transmit power. This output power control is accomplished by the AGC setpoint that is filtered by a low pass filter (217).
  • the transmit section includes a digital summer (210) that combines the AGC setpoint and a closed loop power control setting (206).
  • the output of the summer (210) is fed into a power control limiting section (205).
  • the operation of the power control limiting section (205) and the closed loop power control section (206), illustrated in FIGs. 3 and 4 respectively, will be discussed sub ⁇ sequently in greater detail.
  • the output of the power control limiting section (205), along with the transmit frequency index, are used to address values stored in a transmitter linearizing table (204).
  • the transmitter linearizing table (204) contains values determined from production testing of the radio.
  • the selected value is input to a digital to analog converter (203) whose output, an analog representation of the digital value input, controls a variable gain amplifier (202).
  • variable gain amplifier (202) The biasing of the variable gain amplifier (202) is adjusted by the analog calibration value to a point such that the input to the transmitter linearizing table (204) follows a predetermined straight line with respect to transmitted RF output power.
  • This linearization removes the undesired linear and non-linear errors along with variations versus frequency in the transmitter. This, com ⁇ bined with the previously mentioned receive linearization, greatly reduces the open and closed loop power control errors due to RF performance imperfec ⁇ tions.
  • the power amplifier (PA) bias control section (218) controls the bias point of the transmit PA (201) based on the transmit gain setting such that the transmit sidebands for the given gain setting are optimized versus PA (201 ) current consumption. This allows a battery powered telephone to maximize talk time by reducing PA (201) current consumption at lower output powers while still maintaining acceptable sideband levels at higher output power levels.
  • the power control limiting section (205) is illustrated in FIG. 3. The power control limiting section (205) controls the closed loop power control and transmit gain settings when the output of the transmit gain summer (210) cor ⁇ responds to a transmit output power level which is equal to or greater than the intended maximum output power.
  • the maximum gain setting is determined by the PA limit threshold control section (209).
  • the threshold control section (209) determines the maximum gain set ⁇ ting based on a nominal value that is modified by a real-time measurement of the transmitted output power. The measurement is accomplished by an analog power detector (207) whose output is transformed into a digital signal by an analog to digital converter (208). The digitized power value is then input to the threshold control section (209).
  • the threshold control section operates by the high power detector (HDET) linearizer (501) scaling the input digitized power value in order to match the numerology of the digital transmit gain control section.
  • the scaled output from the linearizer (501) is subtracted (502) from the nominal maximum gain setting. This maximum gain setting can be hard coded into the radio during assembly or input during manufacturing and testing of the radio.
  • the difference of the maximum gain setting and the scaled output power is then added, by the adder (503), to the maximum gain setting.
  • the sum of these signals is then used as the corrected maximum gain setting.
  • This real-time modification of the detected power helps mitigate the errors intro ⁇ cuted by temperature variations and aging of the transmitter PAs. In other words, if the difference between the maximum gain setting and the real-time measured power value is 0, then no correction is necessary. If there is a differ ⁇ ence between the two, the difference is used to correct the maximum gain set- ting.
  • a digital comparator (301) detects when the output of the transmit gain summer (210) equals or exceeds the maximum gain set ⁇ ting.
  • the comparator (301 ) controls a 2:1 multiplexer (302) that outputs the maximum allowable setting when the output of the summer (210) exceeds the maximum allowable setting.
  • the multiplexer (302) outputs the direct output of the summer (210). This prohibits the transmitter from exceeding its maxi ⁇ mum operating point.
  • the power control com ⁇ mands are collected in an accumulator (401). The operation of the accumulator (401) is controlled by the power control limiting section (205) when the trans- mit PA (201) is outputting the maximum allowable power.
  • the output of the closed loop power control accumulator (401) is latched into a flip-flop (402). While the output of the summer (210) is equal to or greater than the maximum allowable setting, as determined by the comparator (403) and NAND gate (404) circuit, an AND gate (405) masks off any closed loop power control up commands that would force the accumulator (401) above the flip-flop's (402) latched value. This prevents the accumulator from saturating during power limiting yet allows the closed loop power control setting to change anywhere below the latched value.
  • An alternate embodiment of the process of the present invention is illus ⁇ trated in FIG. 6.
  • a power limiting control system is em ⁇ ployed based on accumulator feedback control.
  • the system operates by first measuring the output power of the PA (609) using a power detector (610). The detected power is then digitized by an ADC (611) and compared to a maximum allowable setting by the comparator (601). If the output power is greater than the maximum setting, the power limiting accumulator (602) begins turning power down by reducing the gain of the variable gain amplifier (608). If the output power is less than the maximum setting the power limiting accumulator
  • a closed loop power control limiting function (604 and 605), similar to the preferred embodiment, is employed.
  • the trigger for the closed loop power control limiting function is a comparator
  • the linearizing compensation tables are added into the transmit gain control using a summer (606).
  • a power limiting control system is employed that is based on the closed loop power control ac- cumulator (702).
  • the system operates by first measuring the output power of the PA (705) using a power detector (706). The detected power is digitized (707) and compared to a maximum allowable setting by the comparator (701). If the output power is greater than the maximum setting, the closed loop power control accumulator (702) is modified to turn the amplifier (704) power down by one step each 1.25 ms until the output power is less than the maximum setting. If the output power is less than the maximum setting, the closed loop power control accumulator is not modified.
  • the linearizing compensation tables similar to the preferred embodiment, are added into the transmit gain control using a summer (703).
  • a power limiting con ⁇ trol system is employed that is based on integral feedback control.
  • the system operates by first measuring the output power of the PA (808) using a power detector (809).
  • the detected power is digitized (810) and input to an integrator (801) that follows the equation:
  • the gain control signal is thus limited within a range. If the output power is greater than the setpoint, the integrator turns down the output power of the amplifier (807) at a rate based on the integration constant K until the setpoint is reached. The integrator is allowed to turn power down by as much as 63 dB. If the output power is less than the setpoint, the output of the integrator (801) will be forced to zero, thus not adjusting output power.
  • a closed loop power control limiting function (803 and 804), similar to the preferred embodiment, is employed.
  • the trigger for the closed loop power control limiting function is a comparator (802) that detects when the power limiting integrator (801) is limiting the output power.
  • the linearizing compensation tables similar to the preferred embodi ⁇ ment, are added into the transmit gain control using a summer (805).
  • a power limiting con ⁇ trol svstem is emploved that is based only on a measure of receive power, as determined by the R ⁇ power lookup table (902), and the closed loop power control setting as opposed to actual output power.
  • the transmit power limiting and closed loop power control limiting function (901) can be implemented with either the preferred embodiment using the saturating accumulator (903) or one of the alternate embodiments. However, only the receive power and closed loop power control setting are used to estimate transmit output power.
  • FIG. 10 controls the transmit power based on temperature.
  • This embodiment uses temperature sensors, such as thermistors, placed near heat sensitive components or near the components that generate the majority of the radio's heat, the PA and the DC regulator.
  • the PA output power is then adjusted based on the temperature of these components. This can be accomplished by adjusting the maximum gain setting signal created by the PA limit threshold control (209) in FIG. 2, included in the power detector block (1020) of FIG. 10. This allows the radio's maximum transmit output power to be adjusted either up or down based on the measured temperature.
  • the transmit power level is monitored so that it is not reduced below those levels required by the IS-95 or IS- 54 standards.
  • the transmit AGC (1035) is coupled to the transmit PA (1015).
  • the DC regulator (1010) regulates the DC power to the PA (1015).
  • a power detector (1020) determines the power of the signal transmitted by the PA (1015) and feeds that information to the power control circuit (1030). The power detection can be performed as described in the embodiment of FIG. 2.
  • the power control circuit (1030) uses the temperature detected by the temperature sensors (1025) along with the detected transmit power to adjust the transmit AGC gain through a control input.
  • the power control circuitry (1030) can be implemented in several ways.
  • One method generates a control signal that is proportional to the amount of required transmit power adjustment for a measured temperature.
  • the control signal is summed into the transmit gain control section of the radio detailed in FIG. 2 to reduce the transmit output power, thus lowering the temperature.
  • This signal generation and summation could be performed by either or both digital and analog circuitry using sampled or continuous ver ⁇ sions of the required signals.
  • FIG. 10 shows the AGC (1035) and PA (1015) as being separate, other embodiments use a variable gain PA.
  • the variable gain PA has a gain control input coupled to the power control circuitry (1030) and is control in the same manner as the above embodiment.
  • the power adjustment performed by the embodiment of FIG. 10 does not cause a problem with either the CDMA specification, IS-95, or the AMPS specification, IS-54.
  • IS-95 relaxes the transmit power output requirements at high ambient temperatures.
  • IS- 54 while not specifically relaxing the power output requirements, allows a +2 dB and -4 dB variation in transmit power at any given power level. Part of this range can be used to reduce the transmit power level at high ambient temperatures.
  • FIG. 11 shows that without the temperature adjustment, the internal tempera ⁇ ture of the radio continues to rise as the ambient temperature rises. With the temperature adjustment of the present invention, the radio's internal tempera ⁇ ture begins to level off after reaching a predetermined ambient temperature.
  • the process of the present invention ensures that the transmitted sidebands and synthesizer phase noise of a radio transmitter remains within a predetermined specification by limiting the maximum output power.
  • This power limitation is accomplished by a control loop including a calibration look-up table. Therefore, a radio using the process of the present invention would not exceed it's nominal maximum power level due to the cell issuing too many power tum-up commands. The radio limits the power output even when the cell erroneously decides the radio power should be increased.

Abstract

The process and apparatus of the present invention limits the output power of a radio in response to the temperature of key components of the radio. Temperature sensors (1025) measure the temperature of the components and send the temperature signals to power control circuitry (1030). The transmit power is measured (1020) at the output of the power amplifier (1015). As the temperature increases, the power control circuitry (1030) reduces the transmit power to reduce the temperature of the key components. The power is monitored so that it is not reduced below the power level required by standards.

Description

TEMPERATURE COMPENSATED AUTOMATIC GAIN CONTROL
BACKGROUND OF THE INVENTION
I. FIELD OF THE INVENTION
The present invention relates to automatic gain control. More particu¬ larly, the present invention relates to adjusting the transmit power in a portable radio in response to temperature.
II. DESCRIPTION OF THE RELATED ART
The Federal Communications Commission (FCC) governs the use of the radio frequency (RF) spectrum. The FCC allocates certain bandwidths within the RF spectrum for specific uses. A user of an allocated bandwidth of the RF spectrum must take measures to ensure that the radiated emissions inside and outside of that bandwidth are maintained within acceptable levels to avoid in¬ terfering with other users operating in the same and or other bandwidths. These levels are governed by both the FCC and the particular user groups of said bandwidth.
The 800 MHz cellular telephone system operates its forward link, the cell to radiotelephone transmission, in the bandwidth of 869.01 MHz to 893.97 MHz and the reverse link, the radiotelephone to cell transmission, in the bandwidth of 824.01 MHz to 848.97 MHz. The forward and reverse link bandwidths are split up into channels each of which occupies a 30 kHz bandwidth. A particular user of the cellular system may operate on one or several of these channels at a time. All users of the system must ensure that they are compliant with the level of radiated emissions allowable inside and outside of the channel or channels that they have been assigned. There are several different techniques of modulation that can be used in the cellular radiotelephone system. Two examples of modulation techniques are frequency division multiple access (FDMA) and code division multiple access (CDMA). The FDMA technique is used in the advanced mobile phone system (AMPS) that is described in greater detail in the standards document IS- 54. The requirements of the CDMA radiotelephone system are described in greater detail in the standards document IS-95.
The FDMA modulation technique generates signals that occupy one channel at a time while the CDMA modulation technique generates signals that occupy several channels. Both of these techniques must control their return link radiated emissions to within acceptable limits inside and outside of the assigned channel or channels. For maximum system performance, users of the CDMA technique must carefully control the level of radiated power inside the channels in which they are operating. Two methods of controlling the radiated power are open and closed loop power control. Together, these two methods of power control determine the return link transmit energy, as disclosed in U.S. Patent No. 5,056,109 to Gilhousen et al. and assigned to QUALCOMM, Incorporated.
FIG. 1 shows a typical cellular radiotelephone. In both an FDMA and a CDMA based radiotelephone, there exists the possibility of driving the power amplifier (101) in the transmitter beyond a point where acceptable out of chan¬ nel radiated emissions are maintained. This is primarily due to the increased distortion output levels of the power amplifier (101) at high output powers. Also, driving the power amplifier (101) beyond a certain point can cause inter- ference internal to the radio. For example, PA puncturing in CDMA affects syn¬ thesizer phase noise due to large current transitions. Both of these issues cause unacceptable radio performance.
Maintaining the proper on-channel output power can be difficult due to several undesirable effects in the radiotelephone hardware. For example, the CDMA based radio must implement a power control system that operates over a very wide dynamic range, 80 dB to 90 dB, such that the transmitted out¬ put power is linearly related to the received input power.
The linear and nonlinear errors produced in both the receiver (103) and transmitter (102) RF sections can cause unacceptable power control perfor- mance. Also, both the FDMA and CDMA based radios must operate on differ¬ ent channels while maintaining acceptable output power levels. Variation in output power level and input power detection versus frequency can cause an unacceptable amount of error in the amount of return link transmitted energy.
Another power control problem in radios is the heat generated by power amplifiers and supporting circuitry. The heat dissipation of these parts is directly related to the RF output power of the power amplifier.
This heat dissipation can be handled by large heat sinks, fans, and other mechanical fixtures that remove heat. In each case, however, extra weight and cost is added to the radio. In the case of a portable radio, adding a fan or large heat sink is not feasible due to the need to reduce the size, weight, and cost of the radios.
These issues present significant problems to the designer of both FDMA and CDMA based radios. There is a resulting need to reduce the operating temperature of a radio without adding substantial weight and cost. SUMMARY OF THE INVENTION
The temperature compensated automatic gain control of the present in- vention encompasses a temperature compensated power amplifier apparatus. This apparatus is comprised of a variable gain amplifier that has a control input for adjusting the gain of the amplifier. A power detector is coupled to the vari¬ able gain amplifier and generates a power value of the transmitted signal. A temperature sensor is used to generate a temperature signal for predetermined heat generating components. A power control circuit has a first input coupled to the power detector, a second input coupled to the temperature sensor, and an output coupled to the control input of the variable gain amplifier. The power control circuitry adjusts the variable gain amplifier in response to the power value and the temperature signals.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 shows a block diagram of a typical prior art radiotelephone frequency section for use in a radiotelephone system. FIG. 2 shows a block diagram of the power control correction imple¬ mentation of the present invention.
FIG. 3 shows a block diagram of the power limiting control section as related to FIG. 2.
FIG. 4 shows a block diagram of the closed loop power control section as related to FIG. 2.
FIG. 5 shows a block diagram of the PA limit threshold control section as related to FIG. 2.
FIG. 6 shows an alternate embodiment of the present invention that employs a power limiting control system based on accumulator feedback con- trol.
FIG. 7 shows an alternate embodiment of the present invention that employs a power limiting control system based on the closed loop power con¬ trol accumulator.
FIG. 8 shows an alternate embodiment of the present invention that employs a power limiting control system based on integral feedback control.
FIG. 9 shows an alternate embodiment of the present invention that employs a power limiting control system based on a measure of receive power and the closed loop power control setting to estimate output power. FIG. 10 shows a block diagram of the temperature compensated auto¬ matic gain control of the present invention.
FIG. 11 shows a graph indicating the benefits of the embodiment of FIG. 10.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT
The process of the present invention provides power control correction for a mobile radio as well as maintaining acceptable in and out of band maxi- mum emission levels. This is accomplished by real-time compensation utilizing a set of correction tables that are generated during the production testing of each radio.
FIG. 2 shows a block diagram of a CDMA radio with the power control correction implementation of the present invention. FIGs. 3, 4, and 5 detail specific blocks of FIG. 2. The radio is comprised of a receive linearization sec¬ tion, transmit linearization section, power amplifier bias control section, and power limiting control section.
The receive linearization section includes an automatic gain control (AGC) section. The signal input to the AGC section is received on the forward link and amplified by a low noise amplifier (LNA) (211). The output of the LNA (211) is input to a variable gain amplifier (212). The variable gain amplifier (212) produces a signal that is converted to a digital signal using an analog to digital converter (ADC) (213).
The power of the digitized received signal is next computed by a digital power detector (214). The power detector (214) includes an integrator that in¬ tegrates the detected power with respect to a reference voltage. In the pre¬ ferred embodiment, this reference voltage is provided by the radio's demodu¬ lator to indicate the nominal value at which the demodulator requires the loop to lock in order to hold the power level constant. The demodulator requires this value for optimum performance since a power level too far out of the op¬ timum range will degrade the performance of the demodulator. The power de¬ tector (214) performs the integration, thus generating an AGC setpoint. The setpoint and a receive frequency index are input to a receiver linearizing table (216). The AGC setpoint and the frequency index are used to address the lin- earizer (216), thus accessing the proper calibration value. This calibration value is then output to a digital to analog converter (215) that generates the analog representation of the receive AGC setting. The analog value adjusts the biasing of the variable gain amplifier (212). The control of the variable gain amplifier (212) forces the receive AGC loop to close such that the input to the receiver linearizing table (216) follows a prede¬ termined straight line with respect to RF input power. This linearization re- moves the undesired linear and non-linear errors in addition to variations ver¬ sus frequency that would otherwise be apparent at the input to the receiver linearizing table (216) in the receiver. These errors and variations would con¬ tribute to errors in the transmitter.
In order to reduce the error in the receive and transmit chains versus frequency, the receive and transmit linearizers utilize the frequency index that specifies the current center frequency on which the receive and transmit chains are operating. During factory calibration of the radio, the linearizers are loaded with values, in addition to the previously mentioned calibration values, that are indexed by frequency to correct the errors related to operating center fre- quency.
The AGC setpoint is the open loop power control signal for the radio. In the preferred embodiment, this is the power control performed by the radio by itself without control input from the cells. As the power of the signal received from the cell increases, the radio decreases its transmit power. This output power control is accomplished by the AGC setpoint that is filtered by a low pass filter (217).
The transmit section includes a digital summer (210) that combines the AGC setpoint and a closed loop power control setting (206). The output of the summer (210) is fed into a power control limiting section (205). The operation of the power control limiting section (205) and the closed loop power control section (206), illustrated in FIGs. 3 and 4 respectively, will be discussed sub¬ sequently in greater detail.
The output of the power control limiting section (205), along with the transmit frequency index, are used to address values stored in a transmitter linearizing table (204). The transmitter linearizing table (204) contains values determined from production testing of the radio. The selected value is input to a digital to analog converter (203) whose output, an analog representation of the digital value input, controls a variable gain amplifier (202).
The biasing of the variable gain amplifier (202) is adjusted by the analog calibration value to a point such that the input to the transmitter linearizing table (204) follows a predetermined straight line with respect to transmitted RF output power. This linearization removes the undesired linear and non-linear errors along with variations versus frequency in the transmitter. This, com¬ bined with the previously mentioned receive linearization, greatly reduces the open and closed loop power control errors due to RF performance imperfec¬ tions.
The power amplifier (PA) bias control section (218) controls the bias point of the transmit PA (201) based on the transmit gain setting such that the transmit sidebands for the given gain setting are optimized versus PA (201 ) current consumption. This allows a battery powered telephone to maximize talk time by reducing PA (201) current consumption at lower output powers while still maintaining acceptable sideband levels at higher output power levels. The power control limiting section (205) is illustrated in FIG. 3. The power control limiting section (205) controls the closed loop power control and transmit gain settings when the output of the transmit gain summer (210) cor¬ responds to a transmit output power level which is equal to or greater than the intended maximum output power. The maximum gain setting is determined by the PA limit threshold control section (209). The threshold control section (209) determines the maximum gain set¬ ting based on a nominal value that is modified by a real-time measurement of the transmitted output power. The measurement is accomplished by an analog power detector (207) whose output is transformed into a digital signal by an analog to digital converter (208). The digitized power value is then input to the threshold control section (209).
The threshold control section, detailed in FIG. 5, operates by the high power detector (HDET) linearizer (501) scaling the input digitized power value in order to match the numerology of the digital transmit gain control section. The scaled output from the linearizer (501) is subtracted (502) from the nominal maximum gain setting. This maximum gain setting can be hard coded into the radio during assembly or input during manufacturing and testing of the radio.
The difference of the maximum gain setting and the scaled output power is then added, by the adder (503), to the maximum gain setting. The sum of these signals is then used as the corrected maximum gain setting. This real-time modification of the detected power helps mitigate the errors intro¬ duced by temperature variations and aging of the transmitter PAs. In other words, if the difference between the maximum gain setting and the real-time measured power value is 0, then no correction is necessary. If there is a differ¬ ence between the two, the difference is used to correct the maximum gain set- ting.
Referring to FIG. 3, a digital comparator (301) detects when the output of the transmit gain summer (210) equals or exceeds the maximum gain set¬ ting. The comparator (301 ) controls a 2:1 multiplexer (302) that outputs the maximum allowable setting when the output of the summer (210) exceeds the maximum allowable setting. When the output of the summer (210) is less than the maximum allowable setting, the multiplexer (302) outputs the direct output of the summer (210). This prohibits the transmitter from exceeding its maxi¬ mum operating point. The closed loop power control section (206), illustrated in FIG. 4, accu¬ mulates the power control commands sent on the forward link by the control¬ ling radio cell site and outputs a gain adjust signal. The power control com¬ mands are collected in an accumulator (401). The operation of the accumulator (401) is controlled by the power control limiting section (205) when the trans- mit PA (201) is outputting the maximum allowable power.
When the output of the summer (210) changes from being less than to equal or greater than the maximum allowable setting, the output of the closed loop power control accumulator (401) is latched into a flip-flop (402). While the output of the summer (210) is equal to or greater than the maximum allowable setting, as determined by the comparator (403) and NAND gate (404) circuit, an AND gate (405) masks off any closed loop power control up commands that would force the accumulator (401) above the flip-flop's (402) latched value. This prevents the accumulator from saturating during power limiting yet allows the closed loop power control setting to change anywhere below the latched value. An alternate embodiment of the process of the present invention is illus¬ trated in FIG. 6. In this embodiment, a power limiting control system is em¬ ployed based on accumulator feedback control. The system operates by first measuring the output power of the PA (609) using a power detector (610). The detected power is then digitized by an ADC (611) and compared to a maximum allowable setting by the comparator (601). If the output power is greater than the maximum setting, the power limiting accumulator (602) begins turning power down by reducing the gain of the variable gain amplifier (608). If the output power is less than the maximum setting the power limiting accumulator
(602) returns to a 0 dB correction value. In this embodiment, a closed loop power control limiting function (604 and 605), similar to the preferred embodiment, is employed. However, the trigger for the closed loop power control limiting function is a comparator
(603) that detects when the power limiting accumulator (602) is limiting the output power by comparing the accumulator (602) output to 0 dB with the comparator (603). The linearizing compensation tables, similar to the tables in the preferred embodiment, are added into the transmit gain control using a summer (606).
In another alternate embodiment, illustrated in FIG. 7, a power limiting control system is employed that is based on the closed loop power control ac- cumulator (702). The system operates by first measuring the output power of the PA (705) using a power detector (706). The detected power is digitized (707) and compared to a maximum allowable setting by the comparator (701). If the output power is greater than the maximum setting, the closed loop power control accumulator (702) is modified to turn the amplifier (704) power down by one step each 1.25 ms until the output power is less than the maximum setting. If the output power is less than the maximum setting, the closed loop power control accumulator is not modified. The linearizing compensation tables, similar to the preferred embodiment, are added into the transmit gain control using a summer (703).
In yet another embodiment, illustrated in FIG. 8, a power limiting con¬ trol system is employed that is based on integral feedback control. The system operates by first measuring the output power of the PA (808) using a power detector (809). The detected power is digitized (810) and input to an integrator (801) that follows the equation:
— • (Setpoint - Detected )dt.
The integrator (801), generating a gain control signal, saturates at 0 dB and -63 dB of correction. The gain control signal is thus limited within a range. If the output power is greater than the setpoint, the integrator turns down the output power of the amplifier (807) at a rate based on the integration constant K until the setpoint is reached. The integrator is allowed to turn power down by as much as 63 dB. If the output power is less than the setpoint, the output of the integrator (801) will be forced to zero, thus not adjusting output power.
In this embodiment, a closed loop power control limiting function (803 and 804), similar to the preferred embodiment, is employed. The trigger for the closed loop power control limiting function, however, is a comparator (802) that detects when the power limiting integrator (801) is limiting the output power. The linearizing compensation tables, similar to the preferred embodi¬ ment, are added into the transmit gain control using a summer (805).
In still another embodiment, illustrated in FIG. 9, a power limiting con¬ trol svstem is emploved that is based only on a measure of receive power, as determined by the Rλ power lookup table (902), and the closed loop power control setting as opposed to actual output power. The transmit power limiting and closed loop power control limiting function (901) can be implemented with either the preferred embodiment using the saturating accumulator (903) or one of the alternate embodiments. However, only the receive power and closed loop power control setting are used to estimate transmit output power.
Most of the heat generated by a radio is from the PA and the DC regulator that supports the PA. This generated heat, plus the ambient temperature, may exceed the temperature capability of many components in the radio. The preferred embodiment of the present invention, illustrated in
FIG. 10, controls the transmit power based on temperature.
This embodiment uses temperature sensors, such as thermistors, placed near heat sensitive components or near the components that generate the majority of the radio's heat, the PA and the DC regulator. The PA output power is then adjusted based on the temperature of these components. This can be accomplished by adjusting the maximum gain setting signal created by the PA limit threshold control (209) in FIG. 2, included in the power detector block (1020) of FIG. 10. This allows the radio's maximum transmit output power to be adjusted either up or down based on the measured temperature. The transmit power level is monitored so that it is not reduced below those levels required by the IS-95 or IS- 54 standards.
Referring to FIG. 10, the transmit AGC (1035) is coupled to the transmit PA (1015). The DC regulator (1010) regulates the DC power to the PA (1015). A power detector (1020) determines the power of the signal transmitted by the PA (1015) and feeds that information to the power control circuit (1030). The power detection can be performed as described in the embodiment of FIG. 2.
The power control circuit (1030) uses the temperature detected by the temperature sensors (1025) along with the detected transmit power to adjust the transmit AGC gain through a control input. The power control circuitry (1030) can be implemented in several ways.
One method generates a control signal that is proportional to the amount of required transmit power adjustment for a measured temperature. The control signal is summed into the transmit gain control section of the radio detailed in FIG. 2 to reduce the transmit output power, thus lowering the temperature. This signal generation and summation could be performed by either or both digital and analog circuitry using sampled or continuous ver¬ sions of the required signals.
Other embodiments adjust output power based on measured tempera- ture and transmit output power by adjusting a stepped gain block such as a switchable attenuator in the transmit chain. This gain block can be placed at several different locations in the chain. Additionally, the output power could be adjusted by varying the DC bias point or main DC supply voltage of the PA. While FIG. 10 shows the AGC (1035) and PA (1015) as being separate, other embodiments use a variable gain PA. The variable gain PA has a gain control input coupled to the power control circuitry (1030) and is control in the same manner as the above embodiment. The power adjustment performed by the embodiment of FIG. 10 does not cause a problem with either the CDMA specification, IS-95, or the AMPS specification, IS-54. IS-95 relaxes the transmit power output requirements at high ambient temperatures. IS- 54, while not specifically relaxing the power output requirements, allows a +2 dB and -4 dB variation in transmit power at any given power level. Part of this range can be used to reduce the transmit power level at high ambient temperatures.
The benefits of the embodiment of FIG. 10 are illustrated in FIG. 11. This graph shows that without the temperature adjustment, the internal tempera¬ ture of the radio continues to rise as the ambient temperature rises. With the temperature adjustment of the present invention, the radio's internal tempera¬ ture begins to level off after reaching a predetermined ambient temperature.
In summary, the process of the present invention ensures that the transmitted sidebands and synthesizer phase noise of a radio transmitter remains within a predetermined specification by limiting the maximum output power. This power limitation is accomplished by a control loop including a calibration look-up table. Therefore, a radio using the process of the present invention would not exceed it's nominal maximum power level due to the cell issuing too many power tum-up commands. The radio limits the power output even when the cell erroneously decides the radio power should be increased.

Claims

1. A temperature compensated power amplifier apparatus comprising: a variable gain amplifier having a control input, the variable gain amplifier transmitting a signal; a power detector, coupled to the variable gain amplifier, for generating a power value of the signal; a temperature sensor for generating a temperature signal; and a power control circuit, having a first input coupled to the power detector, a second input coupled to the temperature sensor, and an output coupled to the control input of the variable gain amplifier, the power control circuitry adjusting the variable gain amplifier in response to the power value and the temperature signal.
2. The apparatus of claim 1 and further including a direct current regulator coupled to the variable gain power amplifier for providing power to the amplifier.
3. The apparatus of claim 1 wherein the temperature signal is indicative of a temperature of the variable gain power amplifier.
4. A temperature compensated power amplifier circuit comprising: an automatic gain control amplifier having a control input; a power amplifier coupled to an output of the automatic gain control amplifier, the power amplifier transmitting a power amplified signal; a power detector, coupled to an output of the power amplifier, for generating a power value of the power amplified signal; a temperature sensor for generating a temperature signal; and a power control circuit, having a first input coupled to the power detector, a second input coupled to the temperature sensor, and an output coupled to the control input of the automatic gain control amplifier, the power control circuitry adjusting the automatic gain control amplifier in response to the power value and the temperature signal.
5. A temperature compensated power amplifier apparatus comprising: an automatic gain control amplifier having a control input; a power amplifier coupled to an output of the automatic gain control amplifier, the power amplifier transmitting a power amplified signal; a power detector, coupled to an output of the power amplifier, for generating a power value of the power amplified signal; a plurality of temperature sensors, each temperature sensor generating a temperature signal; and a power control circuit having inputs coupled to the power detector and the plurality of temperature sensors, the power control circuit having an output coupled to the control input of the automatic gain control amplifier, the power control circuit adjusting the automatic gain control amplifier in response to the power value and the plurality of temperature signals.
6. The apparatus of claim 5 and further including a direct current regulator coupled to the power amplifier.
7. The apparatus of claim 6 wherein the plurality of temperature signals each indicate a temperature of a component of the apparatus.
8. A radio having the capability of transmitting a signal in a wireless environment, the radio comprising: a modulator for generating the signal to be transmitted; an automatic gain control amplifier having a control input, the automatic gain control amplifier being coupled to the modulator for providing gain to the signal to be transmitted; a power amplifier coupled to an output of the automatic gain control amplifier, the power amplifier transmitting a power amplified signal; a power detector, coupled to an output of the power amplifier, for generating a power value of the power amplified signal; a plurality of temperature sensors, each temperature sensor generating a temperature signal indicative of a temperature of a predetermined component in the radio; and a power control circuit having inputs coupled to the power detector and the plurality of temperature sensors, the power control circuit having an output coupled to the control input of the automatic gain control amplifier, the power control circuit adjusting the gain of the signal to be transmitted in response to the power value and the plurality of temperature signals.
9. A temperature compensated power amplifier apparatus, the power amplifier having a maximum gain setting, the apparatus comprising: a variable gain amplifier having a control input, the variable gain amplifier transmitting a signal; a power detector, coupled to the variable gain amplifier, for generating a power value of the signal; a temperature sensor for generating a temperature signal; a gain threshold controller, coupled to the power detector and the temperature sensor, for generating an adjusted maximum gain setting from the maximum gain setting in response to the temperature signal; and a power control circuit, having a first input coupled to the power detector, a second input coupled to the temperature sensor, and an output coupled to the control input of the variable gain amplifier, the power control circuitry adjusting the variable gain amplifier in response to the power value, the adjusted maximum gain setting, and the temperature signal.
EP96913015A 1995-04-21 1996-04-22 Temperature compensated automatic gain control Withdrawn EP0824784A1 (en)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
US42655195A 1995-04-21 1995-04-21
US426551 1995-04-21
PCT/US1996/005573 WO1996033555A1 (en) 1995-04-21 1996-04-22 Temperature compensated automatic gain control

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KR (1) KR19990007956A (en)
CN (1) CN1186575A (en)
AR (1) AR001578A1 (en)
AU (1) AU5567696A (en)
BR (1) BR9608406A (en)
CA (1) CA2218686A1 (en)
FI (1) FI973994A (en)
IL (1) IL117831A0 (en)
MX (1) MX9708050A (en)
WO (1) WO1996033555A1 (en)
ZA (1) ZA962952B (en)

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ZA962952B (en) 1996-10-15
MX9708050A (en) 1998-02-28
AR001578A1 (en) 1997-11-26
AU5567696A (en) 1996-11-07
JPH11505380A (en) 1999-05-18
FI973994A (en) 1997-12-15
CN1186575A (en) 1998-07-01
KR19990007956A (en) 1999-01-25
BR9608406A (en) 1998-12-29
WO1996033555A1 (en) 1996-10-24
CA2218686A1 (en) 1996-10-24
IL117831A0 (en) 1996-08-04
FI973994A0 (en) 1997-10-17

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