EP0353112A1 - "Cük"-Gleichspannungswandler und Netzanschluss mit Direktumwandlung, ausgeführt durch einen derartigen Umwandler - Google Patents

"Cük"-Gleichspannungswandler und Netzanschluss mit Direktumwandlung, ausgeführt durch einen derartigen Umwandler Download PDF

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Publication number
EP0353112A1
EP0353112A1 EP89401789A EP89401789A EP0353112A1 EP 0353112 A1 EP0353112 A1 EP 0353112A1 EP 89401789 A EP89401789 A EP 89401789A EP 89401789 A EP89401789 A EP 89401789A EP 0353112 A1 EP0353112 A1 EP 0353112A1
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EP
European Patent Office
Prior art keywords
voltage
ramp
converter
control
circuit
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP89401789A
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English (en)
French (fr)
Inventor
Roger Lannuzel
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Thales SA
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Thomson CSF SA
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Publication date
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Publication of EP0353112A1 publication Critical patent/EP0353112A1/de
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/005—Conversion of dc power input into dc power output using Cuk converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/01—Resonant DC/DC converters

Definitions

  • the present invention relates to DC / DC voltage converters of the so-called "Cük” type.
  • a first circuit comprising in series an inductor 11, a capacitor 12 and a primary winding of transformer 13 receives at its terminals the input voltage V e .
  • the capacitor 12 and the winding 13 can be short-circuited periodically under the control of a control circuit 30 driving an active switching member 14 such as a transistor (generally a power MOS).
  • a similar circuit comprising a second series circuit with an inductor 21, a capacitor 22 and the secondary winding 23 of the transformer, circuit in which the capacitor 22 and the winding 23 can be brought into short -circuit by a passive switching member, generally a diode 24 mounted as a freewheeling diode.
  • the windings 13 and 23 of the transformer can be virtual windings, if a transformation ratio 1: 1 is desired and that there is no need for galvanic isolation; it then suffices to replace the windings with two crossed wires joining the primary and the secondary, or two non-crossed wires, which gives a voltage -V s at the output but makes it possible to combine the two capacitors 12 and 22 in a single capacitor.
  • the present invention is not limited to Cük converters actually comprising a transformer, but also applies to Cük converters in which the windings are virtual, all things identical otherwise.
  • FIG. 2 shows the shape of the various signals obtained at the rate of the control pulses V g delivered by the control circuit 30 (one pulse, of duration D, corresponding to the conduction condition of the transistor 14).
  • This type of converter has two typical advantages.
  • the input and output currents respectively referenced I e and I s , have a low residual ripple: this property, which is inherent in the operation of the converter, is obtained even in the absence of any filtering, so that it will suffice to provide capacitors 15 and 25 of low value at input and output to eliminate this simple residual component.
  • the transformer always works in alternation, without any DC component since there is always a capacitor in series with the winding 13 (that is to say that the average voltage is zero); thus, as the point of rest will correspond to a zero tension, one will be able to have a very large excursion of tension before saturating the transformer, so that, even with a transformer of very small size, one will be able always to be placed very in below this saturation limit.
  • D being the duration or "width" of the pulse V g (expressed in terms of duty cycle) corresponding to the duration of the conduction of the transistor 14.
  • a regulation loop 40 (FIG. 1) receiving as input the output voltage V s and modifying a control voltage V c of the control circuit 30 as a function of the difference measured between this voltage output signal V s and a given reference setpoint voltage.
  • a regulation loop 40 receives on the one hand the measured output voltage V s and on the other hand a reference voltage V ref , and delivers at output a control signal V c making it possible to control the operation of a ramp generator consisting of a current generator 31 charging a capacitor 32.
  • the ramp voltage V ramp obtained is represented in FIG. 3, where it can be seen that the start of the ramp is synchronized on each clock pulse H, pulse which also determines the end of the ramp.
  • the slope of the ramp will vary as a function of the error signal V c , and the instantaneous voltage V ramp of the ramp will be compared by means of a comparator 33 to a fixed threshold V threshold voltage.
  • the output signal from this comparator 33 will constitute the control pulse V g making it possible to put the transistor 14 in the conducting state.
  • the start of the control pulse V g is determined by the variable instant, when the voltage V ramps up to the threshold level V, while the end of the control pulse V g always corresponds to the end of the clock pulse H, that is to say the instant when a switch 34, driven by the clock signal, resets the voltage across the capacitor 32.
  • stabilization networks placed in the loop are generally used which reduce the bandwidth of the system in order to avoid instabilities - but, correlatively, these networks reduce the response time of the converter correspondingly to a variation in voltage. input V e .
  • the load variations are most often relatively small (when the converters supply a set of electronic cards or similar circuits), while the most significant variations are those of the input voltage V e , which may be due to an unstable sector (converter powered by the sector), to sudden peaks or collapses in voltage caused by the start-up of a large consumer device, etc.
  • One of the aims of the present invention is to remedy these various drawbacks, by proposing a regulation and control system which, without compromising on stability, makes it possible to have a time of very weak response, which is even much less than the clock period.
  • the present invention provides a control and regulation system for a Cük converter operating in open loop - therefore always stable, whatever its operating conditions - that is to say in which the control voltage V c is made independent of the input voltage V e .
  • - the slope of each ramp varies according to the input voltage and is independent of the output voltage
  • - the threshold level is a function of the error signal
  • - the control pulses are produced between a fixed instant corresponding to the start of each ramp and a variable instant corresponding to the switching of the comparator circuit.
  • the slope variation of the ramp generator is controlled by a control voltage taken at the midpoint of a divider bridge, the divider bridge being mounted in series with a voltage reference and the divider bridge / voltage reference assembly. being brought to a voltage equal to or proportional to the input voltage, and the values of the elements of the divider bridge and of the voltage reference are chosen so that the output voltage produced by the converter under the control of the control circuit is made essentially independent of the input voltage.
  • the present invention also applies, very advantageously, the production of a direct conversion mains supply, comprising a voltage converter of the aforementioned type directly receiving the mains voltage, the repetition frequency of the control pulses of the control circuit being significantly greater than the mains frequency.
  • FIG. 5 shows, schematically, the control signals making it possible to drive, in a characteristic of the present invention, the Cük converter by a control voltage independent of the input voltage.
  • the pulse V g is started here at a fixed instant, corresponding to the start of the clock signal H, and it is terminated at a variable instant depending on the instant, variable, at which the instantaneous level of the ramp voltage V ramp reaches the level of a threshold voltage V threshold .
  • D is the duration between the start of the ramp and the crossing of the threshold, it can be seen that D is inversely proportional to the control voltage of the ramp (this also unlike the prior art): indeed, if by example the voltage decreases it will be necessary to lengthen the duration of the pulse, therefore provide a ramp voltage V ′ ramp of lower slope.
  • control voltage depends only on the input voltage V e , and is independent of the output voltage V s .
  • Variations in the input voltage will produce a variation in the slope of the ramp, which will result in an immediate shortening or lengthening of the current pulse without waiting, as was the case with the art circuit previous, the next clock pulse, which will eliminate all very brief variations in the input voltage, even if their duration is only a few microseconds, i.e. less than the clock period .
  • a simple feed-forward type command such as that used for other types of converters where the output voltage is proportional to the duration of the pulse cannot therefore be transposed to the case of the Cük converter, for which we are in the presence of a nonlinear function, where neither the rate of increase of V s as a function of D, nor the inverse of this rate are constant, which excludes any regulation by direct application of a control voltage directly related to the input voltage.
  • the invention proposes to generate the control voltage V c by means of the circuit illustrated diagrammatically in FIG. 6, that is to say comprising a divider bridge R2, R1 in series with a voltage reference Z (by example a Zener diode); the assembly R2, R1 and Z receives at its terminals the input voltage V e , and the control voltage between R1 and R2 is taken.
  • a voltage reference Z by example a Zener diode
  • V c (V e .R1 + V z .R2) / (R1 + R2) (2)
  • V s [V e D o V co (R1 + R2)] / [V e R1 + V z R2 - D o V co (R1 + R2)] (3)
  • V z which gives a relation between R1 and R2, easy to adjust, for example by means of an adjustable resistance.
  • FIG. 8 gives an example of a Cük converter controlled by a circuit implementing the lessons just described.
  • the control circuit of the present invention consists of the various circuit elements referenced 110 to 170.
  • the circuit 110 is the circuit, shown in isolation in FIG. 6, which makes it possible to derive the control voltage according to the desired nonlinear law of variation, the values of the resistance R1 111, of the resistance R2 112 and of the reference of the voltage (Zener diode) 113 having been chosen and possibly adjusted to verify at least approximately the relation (4) above.
  • the control voltage V c taken at the midpoint of resistors 111 and 112, and the variation of which as a function of the input voltage V e is given by relation (2) above, is applied to a current generating circuit 120 comprising a first NPN transistor 121 mounted in common collector with a collector resistor 122 enabling it to operate as a current generator, the collector current being proportional to the voltage V c applied to the base of this transistor.
  • the capacitor 124 is attacked by a PNP type transistor 123 mounted as an inverter, so that the charge current of the capacitor 124 mounted in its collector circuit will be proportional to the base voltage of transistor 123, itself proportional to the collector current of transistor 121 upstream.
  • the charging voltage of the capacitor 124 which constitutes the ramp voltage V ramp shown in FIG. 5, is applied to the inverting input of an operational amplifier 130 operating as a comparator, the direct input of which receives the threshold voltage V threshold .
  • the output signal of this comparator drives a buffer stage making it possible to drive the transistor 14, advantageously a power MOS, by the signal V g illustrated in FIG. 5, that is to say by the control pulses of variable width D.
  • a multivibrator 150 comprising an inverter 151 with a resistance 152 / capacity 153 network making it possible to oscillate it at a frequency of the order of 100 kHz with a duty ratio 1: 1 (signal H of FIG. 5), makes it possible to one hand to periodically discharge the capacitor 124 and secondly to lock the control of the transistor 14 by applying the clock signal to the input of the buffer stage 140 (signal V shown in FIG 5).
  • the threshold voltage V threshold is produced by a differential amplifier 161 comparing the output voltage V s a reference voltage V ref produced by a voltage reference 162.
  • This differential amplifier 161 comprises a stabilization network 163, for which one can provide a relatively large gain or phase margin because there will not be a need for a high gain for the amplifier 161, the feedback taking place exclusively on the error voltage and therefore on the load variations which are usually weak and slow, as noted above.
  • the output signal of the differential amplifier 161 is transmitted to the comparator 130 via a photocoupler 164 ensuring the galvanic isolation between the primary and secondary of the converter, the threshold voltage V threshold being taken across a load resistor 165 in series with the photocoupler output.
  • the converter thus produced proved to be particularly efficient.
  • the measured response time less than 5 ⁇ s, was significantly less than the chopping period, thus making it possible to take into account extremely brief variations in the input voltage.
  • a circuit 170 for protection against overcurrents using a current transformer 171 (a shunt is not necessary, since the average output voltage is zero and therefore there is no DC component), the secondary of this transformer discharging on a resistor 172 whose voltage across the terminals is compared to a fixed reference voltage by means of a comparator 173; the fixed reference voltage is determined as a function of the maximum current which the circuit must withstand, for example by means of a divider bridge 174,175.
  • the comparator 173 switches and then applies a pulse to the input of the buffer stage 140 which neutralizes the effect of the control circuit . It will be noted that the action of this protection circuit is instantaneous, and that it can act even when a control pulse is being delivered.
  • the system of the present invention is very advantageously applicable to the production of so-called "transformerless" power supplies (that is to say without transformer operating at the mains frequency): the converter is then directly supplied at input by the mains voltage V e , which will vary with the frequency of the mains frequency.
  • V e mains voltage
  • the variations of the input voltage have practically no effect on the output voltage, we will obtain (provided of course that you choose a clock frequency of the control circuit much higher than the frequency sector) a voltage at the secondary V s having only a slight ripple, even in the absence of any filtering capacitor. This is due to the almost instantaneous response of the control circuit to variations in the input voltage since, typically, the input voltage has been removed from the feedback loop as a setpoint.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)
EP89401789A 1988-07-29 1989-06-23 "Cük"-Gleichspannungswandler und Netzanschluss mit Direktumwandlung, ausgeführt durch einen derartigen Umwandler Withdrawn EP0353112A1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR8810260A FR2634957B1 (fr) 1988-07-29 1988-07-29 Convertisseur de tension continu/continu de type cuk, et alimentation secteur a conversion directe realisee a partir d'un tel convertisseur
FR8810260 1988-07-29

Publications (1)

Publication Number Publication Date
EP0353112A1 true EP0353112A1 (de) 1990-01-31

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ID=9368926

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EP89401789A Withdrawn EP0353112A1 (de) 1988-07-29 1989-06-23 "Cük"-Gleichspannungswandler und Netzanschluss mit Direktumwandlung, ausgeführt durch einen derartigen Umwandler

Country Status (5)

Country Link
US (1) US4975819A (de)
EP (1) EP0353112A1 (de)
JP (1) JPH0287965A (de)
AU (1) AU614165B2 (de)
FR (1) FR2634957B1 (de)

Families Citing this family (19)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5146396A (en) * 1991-06-17 1992-09-08 At&T Bell Laboratories Single stage power factor corrected converter having isolated output
US5294838A (en) * 1992-01-13 1994-03-15 Juravich Gerard D Thermostatically controlled electrical outlet apparatus
DK0584623T3 (da) * 1992-08-28 1997-09-22 Siemens Ag Omformer til produktionen af en konstant udgangsspænding.
US5418709A (en) * 1993-03-24 1995-05-23 The United States Of America As Represented By The Administrator Of The National Aeronautics And Space Administration Forback DC-to-DC converter
US5510698A (en) * 1993-08-05 1996-04-23 Massachusetts Institute Of Technology Markov chain controlled random modulation of switching signals in power converters
US5570276A (en) * 1993-11-15 1996-10-29 Optimun Power Conversion, Inc. Switching converter with open-loop input voltage regulation on primary side and closed-loop load regulation on secondary side
US5815380A (en) * 1993-11-16 1998-09-29 Optimum Power Conversion, Inc. Switching converter with open-loop primary side regulation
US5929614A (en) * 1997-06-13 1999-07-27 Northrop Grumman Corporation High efficiency DC step-up voltage converter
FR2772525B1 (fr) * 1997-12-16 2000-03-17 Sextant Avionique Dispositif d'alimentation pour boite a lumiere
US6094035A (en) * 1999-08-20 2000-07-25 Gain Technology Corporation Amplifying power converter circuits
US6788151B2 (en) 2002-02-06 2004-09-07 Lucent Technologies Inc. Variable output power supply
US6690144B1 (en) * 2002-08-09 2004-02-10 Motorola, Inc. Open loop inductor current control system and method
JP4364651B2 (ja) * 2004-01-07 2009-11-18 三菱電機株式会社 昇圧装置及びモータ制御装置
JP4619822B2 (ja) * 2005-03-03 2011-01-26 株式会社リコー スイッチングレギュレータ及びその電圧制御方法
US7602228B2 (en) * 2007-05-22 2009-10-13 Semisouth Laboratories, Inc. Half-bridge circuits employing normally on switches and methods of preventing unintended current flow therein
KR101818773B1 (ko) * 2011-10-24 2018-02-22 삼성전자주식회사 공진 방식 무선 충전 시스템용 수신 전력 변환 장치
JP6033092B2 (ja) * 2013-01-11 2016-11-30 三菱電機株式会社 電源装置、ｌｅｄ点灯装置およびバッテリ充電装置
JP6274580B2 (ja) * 2015-03-11 2018-02-07 オムロンオートモーティブエレクトロニクス株式会社 絶縁型Ｃｕｋコンバータ、電力伝送制御装置
US10536068B2 (en) * 2016-06-26 2020-01-14 The Regents Of The University Of Colorado, A Body Corporate Hybrid feedforward control architecture and related techniques

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR1454422A (fr) * 1965-05-29 1966-02-11 Crouzet Sa Procédé et dispositif régulateur de tension
FR2570898A1 (fr) * 1984-09-21 1986-03-28 Veeco Instr Inc Circuit de commande d'alimentation commutee regulee
US4734839A (en) * 1987-03-23 1988-03-29 Barthold Fred O Source volt-ampere/load volt-ampere differential converter

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4184197A (en) * 1977-09-28 1980-01-15 California Institute Of Technology DC-to-DC switching converter
US4186437A (en) * 1978-05-03 1980-01-29 California Institute Of Technology Push-pull switching power amplifier
US4257087A (en) * 1979-04-02 1981-03-17 California Institute Of Technology DC-to-DC switching converter with zero input and output current ripple and integrated magnetics circuits
US4262328A (en) * 1979-08-03 1981-04-14 Litton Systems, Inc. DC-to-DC converter
US4355352A (en) * 1979-08-03 1982-10-19 Bloom Gordon E DC to DC Converter
US4868730A (en) * 1986-07-15 1989-09-19 Combustion Electromagnetics, Inc. DC to DC converter current pump

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR1454422A (fr) * 1965-05-29 1966-02-11 Crouzet Sa Procédé et dispositif régulateur de tension
FR2570898A1 (fr) * 1984-09-21 1986-03-28 Veeco Instr Inc Circuit de commande d'alimentation commutee regulee
US4734839A (en) * 1987-03-23 1988-03-29 Barthold Fred O Source volt-ampere/load volt-ampere differential converter

Also Published As

Publication number Publication date
FR2634957B1 (fr) 1993-03-26
AU3907989A (en) 1990-02-01
US4975819A (en) 1990-12-04
AU614165B2 (en) 1991-08-22
JPH0287965A (ja) 1990-03-28
FR2634957A1 (fr) 1990-02-02

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