EP0235889A1

EP0235889A1 - Data reading circuit for semiconductor memory device

Info

Publication number: EP0235889A1
Application number: EP87300411A
Authority: EP
Inventors: Atsushi Suzuki
Original assignee: Fujitsu Ltd
Current assignee: Fujitsu Ltd
Priority date: 1986-01-20
Filing date: 1987-01-19
Publication date: 1987-09-09
Anticipated expiration: 2007-01-19
Also published as: US4843595A; KR870007510A; DE3763267D1; KR900008917B1; JPS62167698A; JPH043035B2; EP0235889B1

Abstract

A data reading circuit for a semiconductor memory device includes: a first input terminal and a second input terminal for receiving complementary signals (DB, DB); a first (12) and a second (11) current mirror type sense amplifiers, each of the current mirror type sense amplifiers including: a reference node (N1, N2); an output terminal; a first transistor (Q3, Q8) connected with the reference node (N1, N2); and a second transistor (Q4, Q9) connected with the output terminal. The gates of the first transistor (Q3) of a first sense amplifier (12) and of the second transistor (Q4) of a second sense amplifier (11) are connected to the first input terminal and the gates of the second transistor (Q4) of the first sense amplifier (12) and of the first transistor (Q8) of the second sense amplifier (11) are connected to the second input terminal. A first short-circuiting transistor (71) is connected between the reference nodes (N1, N2) and able to conduct temporarily upon receipt of a clock signal (Φ2) at its gate to speed up the read out operation of a static random access memory.

Description

The present invention relates to a data reading circuit for a semiconductor memory device, and more particularly, to such a circuit arranged to provide an improved static random access memory which can operate at a speed of, for example, 25 ns to 35 ns.
In a conventional data reading circuit of a static random access memory (static RAM) comprises

a first input terminal and a second input terminal for receiving complementary signals; and,
a first and a second current mirror type sense amplifier, each of the current mirror type sense amplifiers including:
- a reference node;
- an output terminal;
- a first transistor connected with the reference node; and
- a second transistor connected with the output terminal,
- the gate of the first transistor of the first sense amplifier and the gate of the second transistor of the second sense amplifier being connected to the first input terminal, and the gate of the second transistor of the first sense amplifier and the gate of the first transistor of the second sense amplifier being connected to the second input terminal. When a signal from a data bus line is input, the sense amplifier senses the signal and delivers a sense output signal. The sense output signal is input to a first output transistor as a first sense data signal through a first set of inverters, and is input to a second output transistor as a second sense data signal through a second set of:inverters. An output stage is composed of the above-noted first output transistor and second output transistor, which deliver the data output signals upon receipt of the first and second sense data signals.

In the above-mentioned data reading circuit, there is a first delay time from when an input signal is supplied to a sense amplifier to when a waveform of the sense output signal starts to lead or to trail, and a second delay time from when the above-mentioned sense output S_OT is received to when the leading edge of the data signal starts to pass through a set of inverters. The sum of the first delay time and second delay time is regarded as the delay time for the operation.
In this case, if a gate input is given a time difference, to avoid making two of the series-connected output stage transistors simultaneously ON, the second delay time is inevitably long, and thus the problem of a reduced operational speed of the circuit arises.
In the prior art, two sense amplifiers are used and a complementary sense output is fetched from among the sense outputs and input directly to the two series-connected output stage transistors through a set of inverters, thus obtaining the data output DOT from the output stage transistor. In the prior art data reading circuit having the above-described operation the waveform of the complementary sense output signal is the same as in the case of one of the above-described sense amplifiers, and therefore, even in this case a problem arises in that the operation speed remains low.
According to this invention such a data reading circuit also includes a first short-circuiting transistor connected between the reference nodes of both the first and second sense amplifiers, the first short-ciruiting transistor temporarily conducting upon receipt of a clock signal at its gate.
A circuit in accordance with this invention provides a data reading circuit having an increased speed of operation.
A particular example of a data reading circuit in accordance with this invention will now be described and contrasted with the prior art with reference to the accompanying drawings; in which:-

Figures 1 and 2 are a circuit diagram and a timing chart of a prior art data reading circuit, respectively;
Figures 3 and 4 are a circuit diagram and a timing chart of another prior art data reading circuit, respectively;
Figures 5 and 6 are circuit diagrams of a data reading device considered by the inventor to be an intermediate device in the attempt to solve the problems of the prior art;
Figures 7 and 8 are timing charts for the device shown in Figure 5;
Figure 9 is a circuit diagram showing an embodiment of the present invention;
Figure 10 is a detailed circuit diagram of the device shown in Figure 9;
Figure 11 is a timing chart showing the operation of the device shown in Figure 9; and,
Figures 12 and 13 are a circuit diagram and a timing chart of another emobdiment of the present invention, respectively.

Prior to the description of the preferred embodiments, a data reading circuit of a prior art static RAM will'be described with reference to Figures 1 to 4.
Figure 1 shows an example of a prior art data reading circuit. in Figure 1, reference numeral 1 denotes a sense amplifier, 2 and inverter, 31, 32, 33 and 41, 42, 43, 44 inverters, 51(Ql) and 52(Q2) an output pull-up transistor (N channel MOS transistor) and an output pull-down transistor (N channel MOS transistor), respectively, DB and DB data bus lines, S_OTA a sense output, S_OTB and S_OTB sense data input to the transistors 51(Ql) and 52(Q2) for the output pull-up, DOT data output, and N a node.
As shown in Figure 1, a pair of Data bus lines DB and DB are connected to a pair of bit lines through a column selection gate circuit and correspond to each stored memory data "1" and "0" read from a memory cell array 6; "1" representing a HIGH level, and "0" a "LOW" level.
When the signals from the data bus lines DB and DB are input, the sense amplifier 1 senses the signals and delivers the sense output S_OTA. The sense output S_OTA is input, via a node N, to a transistor 51(Q1) through the inverters 31, 32 and 33 as sense data S_OTB, and at the same time, the sense output S_OTA is inverted through the inverters 41, 42, 43, and 44 and input to a transistor 52(Q2) as sense data ^S _OTB.
The transistors 51(Q1) and 52(Q2) form an output stage and deliver the data output D_OT upon receipt of the sense data S_OTB and S_OTB, as described above.
It is particularly important in the circuit of Fig. 1 that the transistors Ql and Q2 of the output stage should not be made "ON" simultaneously.
If such a state appears, a high rush current will flow because the mutual conductance g_m of transistors Ql and Q2 is high.
In this read data output circuit, a LOW level side of the sense data S_OTB, which is input to a gate of transistor Ql, must be reached quickly and a HIGH level side slowly, and a LOW level side of the sense data S_OTB, which is input to a gate of transistor Q2, must be reached quickly and a HIGH level side slowly.
Namely, the time interval from when a sense amplifier 1 receives inputs from the data bus lines DB and DB to when the sense data S_OTB and S_OTB is input to transistors Ql and Q2 of the output stage must be given a time difference corresponding to the time needed for a transition from a LOW level to a HIGH level or a transition from a HIGH level to a LOW level.
The relationship between distinct signals in the circuit of Fig. 1 is shown in Fig. 2.
In the circuit of Fig. 1, a short-circuit transistor (not shown in the figure) is connected between data bus lines DB and DB. In a normal operation, when an input address signal changes, an address transition detector (ATD) clock signal φ1 is generated by an address transition detector ATD to make the above-noted short-circuit transistor "ON". Thus, before data read from a memory cell array 6 appears on the data bus lines DB and DB, the data bus lines DB and DB are once short-circuited to an intermediate level. Thereafter, data from the memory cell array 6 appearing at when an ATD clock signal φ1 trails, that is, when the aforementioned short-circuit transistor is "OFF", is input to the sense amplifier 1 as a signal from the data bus lines.
The time interval from when the read data is input to when the sense output S_OTA starts to lead or to trail is referred to as a time interval Tl, a time interval from when the sense output S_OTA is received to when the sense data S_OTB or S_OTB starts to lead through inverters 2, 31, 32, 33, 41, 42, 43 and 44 is referred to as a time interval Tl'. The sum of the time interval Tl and the time interval Tl' is regarded as the delay time of the operation.
In the circuit of Fig. 1, if a gate input is given a time difference, to avoid making the transistors Ql and Q2 at the output stage "ON" simultaneously, the time interval Tl' becomes long, as a matter of course, and the operational speed of the circuit is reduced.
Figure 3 is a circuit block diagram showing an alternative form of a prior art data reading circuit and Fig. 4 illustrates a timing chart of the signals in the circuit of Fig. 3. In Fig. 4 T2 denotes a delay time of the operation.
In the circuit of Fig. 3, two sense amplifiers 11 and 12 are used to output sense outputs. Among the sense outputs, a pair of complementary sense outputs S_OTA and S_OTA are fetched and input directly to transistors 51(Q1) and 52(Q2) at an output stage through inverters 31, 32, and 33 or inverters 41, 42, and 43, and as a result, data outputs DOT are obtained from the transistors at an output stage.
In the circuit of Fig. 3, it is necessary to avoid competition between the transistors Ql and Q2 at the output stage, i.e., Ql and Q2 must not be made ON simultaneously.
Accordingly, the inverter to which the data delivered from the sense amplifiers 11 and 12 is input is utilized to regulate a threshold level, which is shifted from a "HIGH" level to a LOW level or from a LOW level to a HIGH level.
In case that the threshold level is set to a level lower than the level at which the sense outputs S_OTA and S_OTA intersect, in a state such that the sense outputs S_OTA and S_OTA of the sense amplifiers 11 and 12 are at a level higher than the aforementioned threshold level, both the gates of transistors Ql and Q2 at the output stage are at a LOW level. Therefore, if a read operation is carried out therefrom, since both gates are at a LOW level, a shift can be carried out in such a manner that the side from which it is made necessary to read data is at a HIGH level.
In the circuit of Fig. 3, the waveforms of the sense outputs S_OTA and S_OTA are same as in the case of Fig. 1, where only a sense amplifier is operated, but the operational speed is still low.
A data reading circuit considered by the inventor to be an intermediate circuit in the attempt to solve the problems in the prior art shown in Figs. 1 and 3, is shown in Figs. 5 to 8.
In Fig. 5, reference numeral 7 denotes a reset circuit and φ2 an ATD clock signal. The ATD clock signal φ2 has the same waveform as the ATD clock signal φ1, but the application thereof is delayed relative to the ATD clock signal 01, however, it is possible for the ATD clock signal d2 to have the same waveform as the clock signal φ1, without a delay.
In the circuit of Fig. 5, when data is changed over, a reset circuit carries out a short-circuit between the output lines of the sense amplifiers 11 and 12.
Figure 6 is a block diagram of a circuit showing key points of the sense amplifiers 11 and 12. In Fig. 6, Q3 to Q13 denote transistors and Nl, N2 nodes, respectively. A sense amplifier 11 is composed of transistors Q3 to Q7 and a sense amplifier 12 of transistors Q8 to Q12. A transistor Q13 is utilized to carry out a short-circuit between the output lines of the sense amplifiers 11 and 12 and is equivalent to the reset circuit 7 shown in Fig. 5.
In more detail, Ql, Q2, Q3, Q4, Q7, Q8, Q9, Q12, and Q13 denote each N-channel MOS transistor and Q5, Q6, Q10 and Qll each P-channel MOS transistor, while sense amplifiers 11 and 12 are each current mirror type sense amplifier which is formed by a respective CMOS circuit.
The operation of sense amplifiers 11, 12 will be described hereunder.
The potential of a reference node N1 in a sense amplifier 12 is fed-back to the gates of transistors Q3, Q5 and Q6. Therefore, the potential of node N1 is stable at a potential when the current flowing through Q3 and that flowing through Q5 is the same.
Suppose that the potential of a data bus DB is higher than that of a data bus DB. As the gate voltages of transistors Q5 and Q6 are the same, the conductance of transistor Q5 is the same as that of transistor Q6. Therefore, transistors Q6 and Q5 can supply the same value of current. The voltage of transistor Q4 between the gate and source is smaller than that of transistor Q3 between the gate and source and the conductance of transistor Q4 is smaller than that of transistor Q3, so the sense output S_OT is a high level output.
The conductance of transistor Q8 in the sense amplifier 11 is smaller than that of transistor Q3 in the sense amplifier 12. As a result, the potential of the reference node N2 is lower than that of the reference node Nl, while the current flowing through transistors Q10 and Q8 of the sense amplifier 11 is smaller than that flowing through transistors Q5 and Q3 of the sense amplifier 12. The conductance of transistors Qll and Q10 is smaller than that of transistors Q5 and Q6. Moreover, as the conductance of transistor Q9 is larger than that of transistor Q8, the potential of the sense output S_OT is smaller than that of the sense output S_OT in the sense amplifier 12. When the potentials of the data buses DB and DB are inverted, the potentials of each points in the sense amplifiers 11 and 12 are also inverted.
Figure 7 is a timing chart of signals at key points of the circuit, for explaining the operation of the circuit shown in Fig. 6.
In Fig. 7, Cl, C2, C3, C4, C3', and C4' denote symbols for each curve. The operation of the sense amplifiers 11 and 12 as shown in Fig. 6 will be described with reference to Fig. 7.
First, suppose that a data bus line DB is at a HIGH level and a data bus line DB is at a LOW level.
Due to a read operation from the memory cell, if the data bus line DB is at a HIGH level and the data bus line DB is at a LOW level, a timing change of the potential on the data bus lines DB and DB is as seen in curves Cl and C2, and in this case, the sense outputs S_OT and S of the sense amplifiers 1A are as seen in curves C3 and C4, and both curves show a considerable delay in time.
Nevertheless, if the transistor Q13 is made conductive by an ATD clock signal 02, as shown in Fig. 6, and the sense outputs S _OT and S_OT of the two sense amplifiers 1A and 1B are reset, a high speed operation can be carried out. In this case, the curves C3 and C4 corresponding to the sense outputs SOT and S_OT are as seen in curves C3' and C4' and the sense outputs S_OT and S_OT of the sense amplifiers lA and lB appear almost instantaneously. Further, these pair of sense amplifiers can be formed in a multi-stage structure to carry out a faster operation.
Problems remain, however, with regard to the data reading circuit, which is considered to be an intermediate circuit as shown in Fig.5 to Fig. 8.
This is because the change of the potentials at reference nodes Nl and N2, such that a HIGH level potential and a LOW level potential are produced at the outputs, is slow and inactive. That is, the transition from an old potential level to a new potential level is delayed at the reference nodes N1 and N2 and the old potential level remains.
As the nodes N1 and N2 have a respective parasitic capacity, the charges corresponding to the data which were read in the preceding read-cycle are stored therein. Namely, when the output potential of a sense amplifier changes from a present HIGH or LOW level to a subsequent potential level, a definite time is needed for the completion of the change. For example, when the output potential changes from a HIGH level to a LOW level, the former HIGH level remains, and when changing from a LOW level to a HIGH level, the former LOW level remains.
Accordingly, when an ATD clock signal is trailed, phenomenum occurs whereby, after the potential levels of the sense outputs S_OT and S_OT have been raised or have fallen once in the opposite direction, the desired data will appear. Therefore, the speed will be reduced to an extent such that this phenomenum occurs.
It can be understood from the waveform of the sense outputs S_OT and S_OT of the sense amplifiers 1A and lB in a timing chart shown in Fig. 8 that such a phenomenum must appear.
In the device of Fig. 9 it is intended that the potential level will change rapidly at the reference nodes N1 and N2, and thus enhance the operation speed of the semiconductor memory.
A data reading circuit for a semiconductor memory system, as an embodiment of the present invention, is illustrated in Fig. 9 and Fig. 10. Figure 11 is a timing chart of signals of the device shown in Fig. 9.
In the circuit of Fig. 9, a reset circuit 6 is connected between reference nodes in the sense amplifiers 11 and 12.
Figure 10 is a circuit diagram showing the sense amplifiers 11 and 12 and reset circuits 5 and 6 shown in the device of Fig. 9.
In Fig. 10, Q14 is a N channel MOS transistor for causing a short-circuit between the nodes Nl and N2, and is equivalent to the reset circuit 6 shown in Fig. 9.
In the circuits of Fig. 9 and Fig. 10, an ATD clock signal Ø₂ is applied to a transistor Q14 and conducted therethrough, to cause a short-circuit between the reference nodes Nl and N2, and thus an equipotential state at the reference nodes N1 and N2 is forcibly realized.
In this case, as described with reference to Figs. 5 to 8 in the prior art, a converse data state does not occur and a change can be made from an equipotential state to a new data state.
Also in this case, the waveforms of the sense outputs S_OT and S_OT in the sense amplifiers 1A and lB are as seen from the timing chart as shown in Fig. 11. In the timing chart, it is apparent that a converse data state such as shown in Fig. 7 does not exist.
Figure 12 is a circuit diagram showing an alternative embodiment of the present invention and Figure 13 is a timing chart of the signals in the device shown in Fig. 12.
In Fig. 12, lC, 1D, lE, and 1F denote the same sense amplifiers as the sense amplifiers 1A and 1B, 5A, 5B, and 5C the same reset circuit as the reset circuit 5, and 6A, 6B and 6C, the same reset circuits as the reset circuit 6 shown in the former Figures. In the device of Fig. 12, the sense amplifiers have a multi-stage structure.
In general, with respect to a sense amplifier, the timing the output potentials S_OTA and S_OTA necessary for a transfer to a target potential, i.e., a rise time or a fall time, is shorter in a two-stage structure than in a one stage structure, and shorter in a three-stage structure than in a two-stage structure. Thus, the larger the number of stages in the multi-stage structure, the more advantageously a faster operation can be carried out. Figure 13 shows such a condition in more detail.
In the devices of Figs. 9 and 10, the nodes which produce a HIGH level potential or a LOW level potential of the output in a sense amplifier are short-circuited and a reset operation is carried out. The phenomenum whereby the operation state of the circuit goes from a predetermined state through an intermediate reverse state to a desired state, as shown in Fig. 8, does not occur. Thus, when the potential of the ATD clock signal ø2 falls, a shift to a desired data state is commenced instantly, so that the operational speed of a semiconductor memory device is remarkably enhanced.

Claims

1. A data reading circuit for a semiconductor memory device comprising:

a first input terminal and a second input terminal for receiving complementary signals (DB, DB); and,

a first (12) and a second (11) current mirror type sense amplifier, each of the current mirror type sense amplifiers (12, 11) including:

a reference node (Nl, N2);

an output terminal;

a first transistor (Q3, Q8) connected with the reference node (Nl, N2); and

a second transistor (Q4, Q9) connected with the output terminal,

the gate of the first transistor (Q3) of the first sense amplifier (12) and the gate of the second transistor (Q9) of the second sense amplifier (11) being connected to the first input terminal, and the gate of the second transistor (Q4) of the first sense amplifier (12) and the gate of the first transistor (Q8) of the second sense amplifier (11) being connected to the second input terminal;

characterised in that the circuit also includes a first short-circuiting transistor (72) connected between the reference nodes (NI, N2) of both the first (12) and second (11) sense amplifiers, the first short-ciruiting transistor (72) temporarily conducting upon receipt of a clock signal (φ₂) at its gate.

2. A data reading circuit according to claim 1, which further comprises a second short-circuiting transistor (71), connected between the output terminals of the first (12) and second (11) sense amplifiers, the second short-circuiting transistor (71) temporarily conducting upon receipt of the clock signal ($₂) at its gate.

3. A data reading circuit according to claim 1 or 2, wherein the first sense amplifier (12) is composed of five transistors (Q3 to Q7), the second sense amplifier (11) is composed of five transistors (Q8 to Q12), and transistors Q3, Q4, Q7, Q8, Q9, Q12 and the first short circuiting transistor (71) are N-channel MOS transistors, while transistors Q5, Q6, Q10 and Q11 are P-channel MOS transistors and the first (12) and second (11) sense amplifiers are both current mirror type sense amplifiers which are formed by a respective CMOS circuit.

4. A data reading circuit according to any one of the preceding claims, which further comprises a third short-circuiting transistor connected between the first and second input terminals.