Classifications

• • H—ELECTRICITY
  • H04—ELECTRIC COMMUNICATION TECHNIQUE
  • H04H—BROADCAST COMMUNICATION
  • H04H20/00—Arrangements for broadcast or for distribution combined with broadcast
  • H04H20/65—Arrangements characterised by transmission systems for broadcast
  • H04H20/76—Wired systems
  • H04H20/77—Wired systems using carrier waves
  • H04H20/80—Wired systems using carrier waves having frequencies in two or more frequency bands, e.g. medium wave and VHF
• • H—ELECTRICITY
  • H04—ELECTRIC COMMUNICATION TECHNIQUE
  • H04H—BROADCAST COMMUNICATION
  • H04H20/00—Arrangements for broadcast or for distribution combined with broadcast
  • H04H20/65—Arrangements characterised by transmission systems for broadcast
  • H04H20/67—Common-wave systems, i.e. using separate transmitters operating on substantially the same frequency
• • H—ELECTRICITY
  • H04—ELECTRIC COMMUNICATION TECHNIQUE
  • H04B—TRANSMISSION
  • H04B7/00—Radio transmission systems, i.e. using radiation field
  • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
  • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
  • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
• • H—ELECTRICITY
  • H04—ELECTRIC COMMUNICATION TECHNIQUE
  • H04B—TRANSMISSION
  • H04B7/00—Radio transmission systems, i.e. using radiation field
  • H04B7/24—Radio transmission systems, i.e. using radiation field for communication between two or more posts
  • H04B7/26—Radio transmission systems, i.e. using radiation field for communication between two or more posts at least one of which is mobile
  • H04B7/2625—Radio transmission systems, i.e. using radiation field for communication between two or more posts at least one of which is mobile using common wave

Definitions

• the present invention is related generally to simulcast radio communications systems, and more particulary to a method and apparatus for randomly offsetting the frequencies of each transmitter in a multi—transmitter simulcast radio communications system.
• Simulcast radio communications systems typically include a plurality of radio transmitters having the same carrier frequency and each located at different geographical locations for simultaneously transmitting the same information signal to fixed, portable or mobile radios located throughout a large geographical area.
• the information signal transmitted to the radios can be digital, tone or voice signals. This information signal is modulated onto the carrier signal transmitted by each of the transmitters.
• overlap areas where information signals from both transmitters can be received, the received information signal can be degraded by differences in the transmitter modulation levels, delays or phases, or differences in transmitter frequencies.
• radios in the overlap areas can receive two or more transmitter signals having approximately the same amplitude, deep cancellation nulls
• ⁇ lJRE can occur when the transmitter signals are 180° out of phase with one another. Since both the modulation and frequency of the transmitter signals are highly correlated to minimize audio distortion, the deep cancellation nulls resulting from multi-transmitter interference that occurs in the overlap areas can last for a few seconds or as long as several minutes. Thus, radios located in a null can not receive information signals from the simulcasting transmitters for a long period of time.
• the interruption of communications due to deep can ⁇ cellation nulls of long duration can be alleviated somewhat by intentionally offsetting the frequency of the simulcasting transmitters.
• the transmitter frequencies may be offset by 10 to 50 Hz relative to one another.
• this transmitter frequency offsetting technique insures that any deep cancellation nulls that do occur are of very short duration, it also creates an audible beat frequency having a repetition rate equal to the frequency difference between the transmitter signals.
• This beat frequency may be acceptable in some data communications systems, but it is very annoying to the receiving party in voice communications systems.
• each transmitter in a multi-transmitter simulcast radio 15 communications system includes a signal source for generating a noise signal having a random amplitude and random frequency.
• the noise signal from the signal source is combined with information signals, which may be digital, tone, voice, 20 or analog signals, and the combined signals are frequency modulated onto the corresponding transmitter.
• information signals which may be digital, tone, voice, 20 or analog signals
• the noise signal is frequency modulated onto the corresponding transmitter.
• the noise 25 signal causes the frequency of each transmitter to randomly vary by a pre-selected amount, such as, for example, ⁇ 50 Hz.
• Fig. 1 is a block diagram of a typical simulcast radio communications system that may advantageously utilize the present invention.
• Fig. 2 is a block diagram of random frequency offsetting apparatus embodying the present invention.
• Fig. 3 is a detailed circuit diagram of an embodiment of the random noise source, amplifier and low-pass filter in Fig. 2.
• Fig. 4 is a detailed circuit diagram of another embodiment of the random noise source in Fig. 2.
• a simulcast trans ⁇ mission system for communicating information signals between central station 102 and a plurality of remote stations 110 and 112.
• Central station 102 is coupled to a plurality of radio transmitters 104, 106 and 108 which are enabled to transmit the same information signals at the same carrier frequency.
• the carrier signal of transmitters 104, 106 and 108 can be frequency modulated or envelope modulated by the information signal depend- ing the type of modulation adopted for all radios in each particular simulcast transmission system.
• Remote stations 110 and 112 may include radio transceivers for receiving information signals from transmitters 104, 106 and 108 and transmitting information signals to receivers (not shown) which are also coupled to central station 102.
• transmitters 104, 106 and 108 must be substantially identical and are typically based on a rubidium frequency standard or are phase and frequency sychronized to the same reference signal as described in U.S. patent no. 4,188,582.
• Transmitters 104, 106 and 108 may be geographically separated so that an operator at central station 102 can communicate to remote stations 110 and 112 throughout a rather large geographical area. The characteristics of such simulcast systems are further described in my paper entitled "Wide Area Trunking-A System Configuration For Large Scale Radio Dispatch", presented at the ENTELEC Conference held at Houston, Texas in March 1981.
• deep cancellation nulls can be created when the transmitter signals have approximately the same amplitude and are 180° out of phase with one another. These nulls interrupt the communications path between the central station 102 and the remote station 110 or 112 located in the overlap areas for periods of time that may last from a few seconds to a few minutes. Since both the frequency and the modulation of the transmitter signals are very highly correlated with one another, the resultant nulls remain substantially fixed in geographical location for long time periods. Thus, if a remote station 110 or 112 stops in a null or is fixedly located in a null, communications with that remote station can likewise be interrupted for long periods of time. Such interruptions can cause the remote stations to miss vital communications.
• the deep can ⁇ cellation nulls created by multi-transmitter interference will be randomly distributed in randomly varying locations throughout the overlap areas so that communications between the central station 102 and remote stations 110 and 112 will not be interrupted for long periods of time.
• the location of the nulls in the overlap areas is randomly varied by utilizing the random frequency offsetting apparatus of the present invention, which frequency modulates each transmitter with a random noise, signal.
• Fig. 2 there is illustrated random frequency offsetting apparatus * embodying the present invention that may be advantageously utilized in the multi-transmitter simulcast communications system in Fig. 1.
• the apparatus in Fig. 2 combines a random noise signal from random noise source 202 with the information signal from the central station 102 in Fig. 1 and applies the combined signals to the frequency modulation input of transmitter 208.
• the random noise signal is coupled to the frequency modulation input of transmitter 208
• the information signal is coupled to the envelope modulation input of transmitter 208.
• the information signal can be digital or analog signals or a combination of both.
• Random noise source 202 generates the noise signal, which is amplified by amplifier 204 and " thereafter filtered by low-pass filter 206.
• components of the noise signal having frequencies greater than 100 Hz are attenuated to minimize interference with voice signals which typically have a frequency range from 300 Hz to 3,000 Hz in radio systems. Since low-pass filter 206 only passes signal components in the noise signal having frequencies from 0 to 100 Hz, the filtered noise signal is entirely in the subaudible frequency range. In other applications, low- pass filter 206 may be either a band-pass filter or a high-pass filter depending on the frequency band of the information signal.
• low-pass filter 206 may be replaced by high-pass filter that attenuates components of the noise signal having a frequencies below 2,000 Hz and passes components of the noise signal having frequencies above 2000 Hz.
• the filtered noise signal from low-pass filter 206 is coupled to switch 222 and thereafter to potentiometer 220 and resistor 216 for application to operational amplifier 212.
• operational amplifier 212 is arranged as a summing amplifier for summing the signals from resistors 216 and 218.
• Operational amplifier 212 amplifies the signal from resistor 216 by a factor which is the ratio of resistor 214 to resistor 216 and potentiometer 220, and amplifies the signal from resistor 218 by a factor which is the ratio of resistor 214 to resistor 218.
• the combined signal from operational amplifier 212 is then applied to the frequency modulation input of transmitter 208.
• resistor 216 can be deleted and the filtered noise signal from potentiometer 220 may be coupled by path 226 to the frequency modulation input of transmitter 208.
• the information signal from operational amplifier 212 is then coupled to the envelope modulation input of transmitter 208.
• This arrangement of the random frequency offsetting apparatus of the present invention can be used in simulcast transmission systems utilizing amplitude modulation, single-sideband modulation, or other envelope modulation techniques.
• the amount of amplification of the filtered noise signal by operational amplifier 212 may be adjusted by means of potentiometer 220 for setting of the frequency deviation of transmitter 208 by the filtered noise signal to some pre-selected low deviation, such as 4 ⁇ 50 Hz. Since deviation of transmitter 208 by the filtered noise signal is so small, the received information signal at remote stations 110 and 112 in Fig. 1 will be substantially unaffected by the noise signal when the transceiver of the remote station is captured by the RF signal from one of the transmitters 104, 106 and 108 in Fig. 1.
• the information signal is coupled to delay compensation circuitry 210 which takes into account the different delays introduced by the signal paths from the central station to each transmitter.
• Delay compensation circuitry 210 is necessary to insure that the modulation of each transmitter is in phase with the modulation of the other transmitters.
• the characteristics of the delay compensation circuitry 210 are described in my paper referred to hereinabove and in U.S. patent no. 4,255,814.
• the delayed information signal from delay compensation circuitry 210 is coupled via resistor 218 to operational amplifier 212 where it is combined with the filtered noise signal from low-pass filter 206.
• the filtered noise signal from low-pass filter 206 may be coupled to operational amplifier 212 directly via path 224 or via switch 222.
• the filtered noise signal can be selectively coupled to operational amplifier 212 in response to a noise select signal.
• One state of the noise select signal can enable switch 222 for coupling the filtered noise signal to operational amplifier 212 during normal operation, and a second state of the select signal can disable switch 222 for decoupling the filtered noise signal from operational amplifier 212 when it is desired to adjust the frequency of transmitter 208 and/or the delay of delay compensation circuitry 210.
• the random noise source in Fig. 3 is a zener diode 302 which is reverse biased by resistor 304 to operate in the voltage/current "knee" region just preceding the point of rapidly increasing zener current. When a zener diode is biased at this point, it generates a low amplitude noise signal.
• the noise signal from zener diode 302 is coupled via capacitor 306 and resistor 308 to operational amplifier 312.
• Operational amplifier 312 amplifies the noise signal by a factor that is the ratio of resistor 310 to resistor 308.
• Operational amplifier may also include a potentiometer in place of, or in series with, resistor 308 or resistor 310 so that its gain can be adjusted.
• the output from operational amplifier 312 is coupled to a low-pass filter comprised of operational amplifier 320, resistors 314, 316, 324 and 324 and 326 and capacitors 318 and 322.
• the low-pass filter has approximately a 100 Hz bandwidth for passing only the low frequency components of the noise signal generated by zener diode 302.
• the filtered noise signal from amplifier 320 may then be coupled to switch 222 (or directly to potentiometer 220) in Fig. 2 for application to transmitter 208.
• the digital noise generator in Fig. 4 includes a clock source 402 for providing a clock signal and a sixteen-bit shift register 404. Outputs from the 14th and 15th stages Q-J4 and Q-15 of shift register 404 are coupled to exclusive-OR gate 406, which is in turn coupled by way of inverting gate 408 to the serial input of first stage Q- ] .
• the digital noise generator in Fig. 4 generates a pseudorandom digital noise signal at the 8th stage output QQ (or any other output) of shift register 404, which is characterized by the following equation:
• AND gate 410 and flip-flop 412 generate a pulse that resets all stages of shift register 404 to a binary zero state whenever lock up occurs.
• the noise signal generated at output Qg is a serial bit stream having a random bit pattern that is repeated approximately once every 109 seconds. The noise signal from output Qg may then be coupled to amplifier 204 in Fig. 2 for application to transmitter 208.
• random frequency offsetting circuitry for simulcast transmitters has been described that randomly varies the location of deep cancellation nulls occurring during multi-transmitter interference.
• communications from simulcasting transmitters to remote stations located in the overlap areas will only be momentarily interrupted by the randomly located deep cancellation nulls.
• the inventive random frequency offsetting appartus can be utilized in simulcast systems communicating digital signals, voice signals or digital and voice signals by appropriately tailoring the frequency band of the noise signal that randomly offsets the simulcasting transmitters.

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• Engineering & Computer Science (AREA)
• Signal Processing (AREA)
• Computer Networks & Wireless Communication (AREA)
• Noise Elimination (AREA)
• Transmitters (AREA)

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• 1982
  • 1982-10-28 CA CA000414363A patent/CA1202085A/en not_active Expired
  • 1982-10-29 IL IL67120A patent/IL67120A/xx unknown
  • 1982-11-10 MX MX195130A patent/MX152176A/es unknown
  • 1982-11-12 EP EP83900128A patent/EP0094417A1/en not_active Withdrawn
  • 1982-11-12 WO PCT/US1982/001599 patent/WO1983001878A1/en unknown
  • 1982-11-22 KR KR1019820005265A patent/KR840002782A/ko unknown
  • 1982-11-23 AR AR291391A patent/AR229626A1/es active

Non-Patent Citations (1)

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